JP2003125530A - Leakage detection device for high-voltage vehicle - Google Patents
Leakage detection device for high-voltage vehicleInfo
- Publication number
- JP2003125530A JP2003125530A JP2001317148A JP2001317148A JP2003125530A JP 2003125530 A JP2003125530 A JP 2003125530A JP 2001317148 A JP2001317148 A JP 2001317148A JP 2001317148 A JP2001317148 A JP 2001317148A JP 2003125530 A JP2003125530 A JP 2003125530A
- Authority
- JP
- Japan
- Prior art keywords
- voltage
- leakage
- circuit
- power supply
- level
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Withdrawn
Links
Classifications
-
- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L3/00—Electric devices on electrically-propelled vehicles for safety purposes; Monitoring operating variables, e.g. speed, deceleration or energy consumption
- B60L3/0023—Detecting, eliminating, remedying or compensating for drive train abnormalities, e.g. failures within the drive train
- B60L3/0069—Detecting, eliminating, remedying or compensating for drive train abnormalities, e.g. failures within the drive train relating to the isolation, e.g. ground fault or leak current
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R31/00—Arrangements for testing electric properties; Arrangements for locating electric faults; Arrangements for electrical testing characterised by what is being tested not provided for elsewhere
- G01R31/50—Testing of electric apparatus, lines, cables or components for short-circuits, continuity, leakage current or incorrect line connections
- G01R31/52—Testing for short-circuits, leakage current or ground faults
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R31/00—Arrangements for testing electric properties; Arrangements for locating electric faults; Arrangements for electrical testing characterised by what is being tested not provided for elsewhere
- G01R31/36—Arrangements for testing, measuring or monitoring the electrical condition of accumulators or electric batteries, e.g. capacity or state of charge [SoC]
Landscapes
- Engineering & Computer Science (AREA)
- Life Sciences & Earth Sciences (AREA)
- Sustainable Development (AREA)
- Sustainable Energy (AREA)
- Power Engineering (AREA)
- Transportation (AREA)
- Mechanical Engineering (AREA)
- Physics & Mathematics (AREA)
- General Physics & Mathematics (AREA)
- Electric Propulsion And Braking For Vehicles (AREA)
- Testing Of Short-Circuits, Discontinuities, Leakage, Or Incorrect Line Connections (AREA)
- Emergency Protection Circuit Devices (AREA)
Abstract
Description
【０００１】[0001]
【発明の属する技術分野】この発明は、例えば、電気自
動車に搭載した駆動用バッテリからの漏電を検出する高
電圧車両用漏電検出器に関するものである。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a leak detector for a high-voltage vehicle, which detects a leak from a driving battery mounted on an electric vehicle, for example.
【０００２】[0002]
【従来の技術】従来、このような漏電検出器として、例
えば、図７に示す漏電検知方法（特開昭５７−１１９２
６３号公報）がある。この方法は交流電源７１から交流
電圧が、常時、直流電源Ｂｇと接地との間に印加され、
またコンデンサ７４は直流電源Ｂｇに対して等価的に示
す対地キャパシタンスとして作用する。2. Description of the Related Art Conventionally, as such an earth leakage detector, for example, an earth leakage detecting method shown in FIG. 7 (Japanese Patent Laid-Open No. 57-1192).
63). In this method, an AC voltage is constantly applied from the AC power supply 71 between the DC power supply Bg and the ground,
Further, the capacitor 74 acts as an equivalent capacitance to ground for the DC power source Bg.
【０００３】一方、可変コンデンサ７５の容量値をコン
デンサ７４の容量と同じ値に設定しておけば、差動変流
器７２の一次巻線でコンデンサ７５から流れる電流はコ
ンデンサ７４に流れる電流を相殺し、起磁力が零となる
ので、差動変流器７２の二次巻線にはほとんど電流が流
れない。On the other hand, if the capacitance value of the variable capacitor 75 is set to the same value as the capacitance of the capacitor 74, the current flowing from the capacitor 75 in the primary winding of the differential current transformer 72 cancels the current flowing in the capacitor 74. However, since the magnetomotive force becomes zero, almost no current flows in the secondary winding of the differential current transformer 72.
【０００４】しかし、直流電源Ｂｇの内部又は母線に短
絡事故が生じると、コンデンサ７４のキャパシタンスが
変化し、その結果コンデンサ７５との相殺関係が崩れ、
差動変流器７２の二次巻線に出力を生じ、この出力信号
を検出すれば直流電源Ｂｇ側の漏電を検知できる。However, when a short-circuit accident occurs in the DC power source Bg or in the bus bar, the capacitance of the capacitor 74 changes, and as a result, the canceling relationship with the capacitor 75 is broken.
An output is generated in the secondary winding of the differential current transformer 72, and by detecting this output signal, the leakage current on the DC power supply Bg side can be detected.
【０００５】また、車両に搭載したバッテリーと車体と
の間の漏電を検出する従来の回路として、特開平８−７
０５０３号公報に示す検出回路がある。この検出回路は
図５および図６に示す様に、走行駆動回路系Ａにおける
車体Ｅへの地絡を検出するためのもので、交流信号出力
回路として発振回路１０と、電圧レベル変化検出回路と
して検出部２０とからなり、発振回路１０と検出部２０
との接続点Ｐと走行駆動回路系Ａのバッテリ群Ｂのプラ
ス母線４との間がカップリングコンデンサ１０Ａで接続
されており、直流成分が遮断される。Further, as a conventional circuit for detecting electric leakage between a battery mounted on a vehicle and a vehicle body, Japanese Patent Laid-Open No. 8-7
There is a detection circuit shown in Japanese Patent No. 0503. As shown in FIGS. 5 and 6, this detection circuit is for detecting a ground fault to the vehicle body E in the traveling drive circuit system A. The detection circuit is an oscillation circuit 10 as an AC signal output circuit and a voltage level change detection circuit. The detecting unit 20 and the oscillation circuit 10 and the detecting unit 20.
A coupling capacitor 10A connects between a connection point P of the connection point P and the positive bus 4 of the battery group B of the traveling drive circuit system A, and the DC component is cut off.
【０００６】発振回路１０において発振器１１は、デュ
ーティ比５０％の一定周波数の矩形波パルスを発生し、
次段のインピーダンス変換器１２は、発振器１１の矩形
波パルスをそのままのデューティ比で出力し、発振回路
１０の交流信号出力は、検出抵抗１３を介して接続点Ｐ
に現れる。検出抵抗１３は、地絡発生時に、地絡抵抗３
１によって分圧器として作用する。In the oscillator circuit 10, the oscillator 11 generates a rectangular wave pulse having a constant frequency with a duty ratio of 50%,
The impedance converter 12 at the next stage outputs the rectangular wave pulse of the oscillator 11 with the same duty ratio, and the AC signal output of the oscillation circuit 10 is connected to the connection point P via the detection resistor 13.
Appear in. The detection resistor 13 is provided with a ground fault resistor 3 when a ground fault occurs.
1 acts as a voltage divider.
【０００７】検出部２０には、発振回路１０の交流信号
出力が現れる検出抵抗１３とカップリングコンデンサ１
０Ａとの接続点Ｐの電圧レベルを基準電圧Ｖ１と比較す
るための比較器２１が設けられており、接続点Ｐは比較
器２１の反転入力端子に接続されている。比較器２１の
非反転入力端子には、分圧抵抗２２、２３によって基準
電圧Ｖ１を設定した基準電圧回路が接続されている。In the detection section 20, the detection resistor 13 and the coupling capacitor 1 in which the AC signal output of the oscillation circuit 10 appears.
A comparator 21 is provided for comparing the voltage level of the connection point P with 0A with the reference voltage V1, and the connection point P is connected to the inverting input terminal of the comparator 21. A reference voltage circuit in which the reference voltage V1 is set by the voltage dividing resistors 22 and 23 is connected to the non-inverting input terminal of the comparator 21.
【０００８】なお、インピーダンス変換器１２および比
較器２１を構成する演算増幅器は、地絡発生時に逆電
圧、過電圧から保護するため、インピーダンス変換器１
２の出力側、比較器２１の入力側に保護用のダイオード
１５〜１８が接続されている。Incidentally, the operational amplifiers constituting the impedance converter 12 and the comparator 21 are protected from reverse voltage and overvoltage when a ground fault occurs, so that the impedance converter 1
The protective diodes 15 to 18 are connected to the output side of 2 and the input side of the comparator 21.
【０００９】このような回路構成により、地絡が発生し
ていない平常時には、接続点Ｐのインピーダンスに変化
がないため、比較器２１の反転入力端子には、予め設定
した基準電圧Ｖ１より高い波高値を有する矩形波パルス
が入力されるため、比較器２１の出力はデューティ比５
０％の矩形波パルスとなる。このため、抵抗２４および
コンデンサ２５の平滑回路２６によって現れる平滑電圧
は、基準電圧より低くなり、それが比較器２７の非反転
入力端子に入力されて、比較器２７の出力は正常を示す
ローレベルとなる。With such a circuit configuration, the impedance of the connection point P does not change during normal times when a ground fault does not occur. Since a rectangular wave pulse having a high value is input, the output of the comparator 21 has a duty ratio of 5
It becomes a rectangular wave pulse of 0%. Therefore, the smoothed voltage appearing by the smoothing circuit 26 of the resistor 24 and the capacitor 25 becomes lower than the reference voltage, which is input to the non-inverting input terminal of the comparator 27, and the output of the comparator 27 is low level indicating normal. Becomes
【００１０】しかし、マイナス母線と車体Ｅとの間に地
絡が発生し、図５に示す地絡抵抗３１が現れた場合に
は、カップリングコンデンサ１０Ａは、バッテリ群１、
カップリングコンデンサ１０Ａ、検出抵抗１３、インピ
ーダンス変換器１２、アースラインＧＮＤ、車体Ｅ、地
絡抵抗３１、バッテリ群Ｂの経路で、バッテリ群Ｂの電
圧値まで充電される。However, if a ground fault occurs between the minus busbar and the vehicle body E and the ground fault resistance 31 shown in FIG. 5 appears, the coupling capacitor 10A is connected to the battery group 1,
The coupling capacitor 10A, the detection resistor 13, the impedance converter 12, the earth line GND, the vehicle body E, the ground fault resistor 31, and the battery group B are charged to the voltage value of the battery group B through the path.
【００１１】同時に、インピーダンス変換器１２の出力
は、交流信号出力の矩形波パルスであるため、検出抵抗
１３、カップリングコンデンサ１０Ａ、バッテリ群Ｂ、
地絡抵抗３１、車体Ｅ、インピーダンス変換器１２の経
路で伝達し、カップリングコンデンサ１０Ａの充電完了
と共に、インピーダンス変換器１２の出力である矩形波
パルスの波高値が検出抵抗１３および地絡抵抗３１で分
圧される発振振幅に小さくなって安定する。At the same time, since the output of the impedance converter 12 is a rectangular wave pulse of the AC signal output, the detection resistor 13, the coupling capacitor 10A, the battery group B,
The peak value of the rectangular wave pulse, which is the output of the impedance converter 12, is transmitted through the path of the ground fault resistance 31, the vehicle body E, and the impedance converter 12 and the charging of the coupling capacitor 10A is completed. The oscillation amplitude divided by is reduced and becomes stable.
【００１２】このため、比較器２１の反転入力端子に
は、基準電圧Ｖ１より低い波高値の矩形波パルスが入力
され、比較器２１のデューティ比は１００％に変化す
る。この結果、抵抗２４およびコンデンサ２５の平滑回
路２６によって現れる平滑電圧Ｖｒは、基準電圧Ｖ２よ
り高くなり、それが比較器２７の非反転入力端子に入力
されて、比較器２７の出力は地絡を示すハイレベルとな
る。以上の通り、バッテリ群Ｂにおいて地絡が発生した
場合には、比較器２７の論理レベルより地絡を検出する
ことができる。Therefore, a rectangular wave pulse having a peak value lower than the reference voltage V1 is input to the inverting input terminal of the comparator 21, and the duty ratio of the comparator 21 changes to 100%. As a result, the smoothed voltage Vr generated by the smoothing circuit 26 of the resistor 24 and the capacitor 25 becomes higher than the reference voltage V2, which is input to the non-inverting input terminal of the comparator 27, and the output of the comparator 27 is grounded. It becomes the high level shown. As described above, when the ground fault occurs in the battery group B, the ground fault can be detected from the logic level of the comparator 27.
【００１３】[0013]
【発明が解決しようとする課題】上記特開昭５７−１１
９２６３号公報に記載された従来技術は、地絡事故を判
定する直流電源と車体間の絶縁抵抗値の変化に拘わりな
く、直流電源がアース側に短絡し対地キャパシタンス１
４が変化してコンデンサ１５との相殺関係が崩れ、差動
変流器１２の二次巻線に出力が生じた時に地絡を判定す
るものである。そのため地絡事故を判定するための絶縁
抵抗値を設定できず、直流電源と車体間の絶縁劣化が進
行して絶縁抵抗値がどの程度低下した時に地絡事故を判
定するか予め設定することはできなかった。従って、直
流電源と車体間の絶縁劣化が進行し始めると頻繁に地絡
事故を判定することになり、事故判定に対する信頼性が
低い。また、対地キャパシタンス１４が多少変化しても
コンデンサ１５との相殺関係が崩れて差動変流器１２の
二次巻線に出力が生じるため、地絡事故判定を正確に行
えなかった。DISCLOSURE OF THE INVENTION Problems to be Solved by the Invention
According to the conventional technology disclosed in Japanese Patent No. 9263, the DC power supply is short-circuited to the ground side regardless of the change in the insulation resistance value between the DC power supply for judging a ground fault and the vehicle body, and the ground capacitance 1
4 is changed, the canceling relationship with the capacitor 15 is broken, and an output is generated in the secondary winding of the differential current transformer 12, a ground fault is determined. Therefore, the insulation resistance value for determining the ground fault cannot be set, and it is not possible to set in advance how much the insulation resistance between the DC power supply and the vehicle body will deteriorate and the insulation resistance value will decrease. could not. Therefore, when the insulation deterioration between the DC power supply and the vehicle body starts to progress, a ground fault is frequently determined, and the reliability of the fault determination is low. Further, even if the ground capacitance 14 is slightly changed, the canceling relationship with the capacitor 15 is broken and an output is generated in the secondary winding of the differential current transformer 12, so that the ground fault accident determination cannot be accurately performed.
【００１４】特開平８−７０５０３号公報に記載された
従来技術は、インピーダンス変換器１２を通して発振器
１１より比較器２１に入力される矩形波パルスのレベル
はダイオードの順方向電圧のみで制限される。そのた
め、周囲温度の上昇によりダイオードの順方向電圧に変
化が生じて矩形波パルスのレベルが、地絡判定用の基準
電圧Ｖ１より低下して比較器２１に入力されると地絡事
故を誤判定することになる。In the conventional technique disclosed in Japanese Patent Laid-Open No. 8-70503, the level of the rectangular wave pulse input from the oscillator 11 to the comparator 21 through the impedance converter 12 is limited only by the forward voltage of the diode. Therefore, when the ambient voltage rises, the forward voltage of the diode changes, and the level of the rectangular wave pulse falls below the reference voltage V1 for ground fault determination and is input to the comparator 21, so that a ground fault accident is erroneously determined. Will be done.
【００１５】この発明は、上記のような問題点を解消す
るためになされたもので、ダイオードの温度特性に影響
を受けず、また絶縁破壊時の絶縁抵抗値を予め設定する
ことで地絡発生の誤判定を阻止して信頼性よく漏電を検
出することができる高電圧車両用漏電検出器を得ること
を目的とする。The present invention has been made to solve the above problems, and is not affected by the temperature characteristics of the diode, and a ground fault occurs by presetting the insulation resistance value at the time of dielectric breakdown. It is an object of the present invention to provide a leakage detector for a high-voltage vehicle that can prevent the erroneous determination of and reliably detect the leakage.
【００１６】[0016]
【課題を解決するための手段】この発明は図１の基本構
成図に示すように、電気自動車内で車体と電気的に絶縁
された直流電源系統の漏電を検出する高電圧車両用漏電
検出器において、一定レベルの交流信号を発振し、この
交流信号をコンデンサＣを通して前記直流電源系統Ｂに
出力する発振部ＯＳと、この出力された交流信号のレベ
ルが、漏電時に前記直流電源系統Ｂと車体間に発生する
絶縁抵抗による電圧降下分、低下したかを判定する判定
部とを含む漏電検出器ＬＥＤを備えたものである。As shown in the basic configuration diagram of FIG. 1, the present invention is a high voltage vehicle leakage detector for detecting a leakage of a DC power supply system electrically insulated from a vehicle body in an electric vehicle. , An oscillating unit OS that oscillates an AC signal of a constant level and outputs this AC signal to the DC power supply system B through a capacitor C, and the level of the output AC signal is the DC power supply system B and the vehicle body at the time of leakage. A leakage detector LED including a determination unit that determines whether or not a voltage drop due to an insulation resistance that occurs between the two is provided.
【００１７】この発明によれば、直流電源系統と車体間
の絶縁が劣化して、直流電源系統と車体に絶縁抵抗が生
じたならば発振部より出力された一定レベルの交流信号
はコンデンサ、絶縁抵抗を通してアースとなる車体に流
れるため、この流れる交流信号を電圧にて検出し、この
電圧レベルが予めその抵抗値を設定した絶縁抵抗の両端
電圧分低下したかを判定することで漏電検出を行う。According to the present invention, if the insulation between the DC power supply system and the vehicle body deteriorates and an insulation resistance occurs between the DC power supply system and the vehicle body, a constant level AC signal output from the oscillating unit is isolated by the capacitor and the insulation. Since the current flows through the resistor to the vehicle body that serves as the ground, this AC signal that flows is detected as a voltage, and it is determined whether or not this voltage level has dropped by the voltage across the insulation resistance for which the resistance value has been set in advance. .
【００１８】この発明に係る高電圧車両用漏電検出器に
おける絶縁抵抗の値は直流電源系統より車体に漏電電流
が流れると予想されるしきい値で予め設定する。この発
明によれば、絶縁抵抗の値を、直流電源系統と車体間の
絶縁が劣化して漏電が開始されるしきい値にて設定する
ことで、検出した交流信号のレベルが、しきい値を超え
た絶縁抵抗における電圧降下分、低下したかを判定する
ことで漏電検出を行う。The value of the insulation resistance in the leakage detector for a high-voltage vehicle according to the present invention is preset with a threshold value at which leakage current is expected to flow from the DC power supply system to the vehicle body. According to the present invention, the value of the insulation resistance is set at the threshold value at which the insulation between the DC power supply system and the vehicle body is deteriorated and the electric leakage is started. Leakage detection is performed by determining whether the voltage has dropped by the amount of voltage drop in the insulation resistance that exceeded.
【００１９】この発明に係る高電圧車両用漏電検出器に
おける発振部ＯＳは温度補償手段を設けたものである。
この発明によれば、発振部ＯＳは温度補償手段を設ける
ことにより、発振される交流信号は周囲温度の上昇によ
りそのレベルが変動することがないため、交流信号のレ
ベルに基づいて漏電検出を行う際にも、周囲温度の上昇
により漏電の誤検出を阻止できる。The oscillator section OS in the leakage detector for a high-voltage vehicle according to the present invention is provided with temperature compensating means.
According to the present invention, by providing the temperature compensating means in the oscillating unit OS, the level of the oscillated AC signal does not fluctuate due to the rise in the ambient temperature, so that the leakage detection is performed based on the level of the AC signal. Also in this case, it is possible to prevent erroneous detection of electric leakage due to an increase in ambient temperature.
【００２０】[0020]
【発明の実施の形態】実施の形態
次に本発明における高電圧車両用漏電検出器の実施の形
態を図について説明する。図２は本実施の形態に係る高
電圧車両用漏電検出器の回路構成を示す図である。図に
おいて、ＰＧは無安定マルチバイブレータから構成され
る矩形波パルス（以下、矩形波と記載する。）発振回路
である。この矩形波発振回路ＰＧは、演算増幅器Ｑ３の
反転入力端子（＋入力端子と記載する。）に印加するバ
イアス電圧（＋６Ｖ）を、抵抗Ｒ３１，３２との分圧比
で決まる電圧に設定することでデューティ比５０％の矩
形波を出力するようにしている。また、パルス幅はコン
デンサＣ３と帰還抵抗Ｒ３４との時定数と＋入力端子に
かかる電圧にて決まる。BEST MODE FOR CARRYING OUT THE INVENTION Next, an embodiment of a leakage detector for a high-voltage vehicle according to the present invention will be described with reference to the drawings. FIG. 2 is a diagram showing a circuit configuration of the leakage detector for a high voltage vehicle according to the present embodiment. In the figure, PG is a rectangular wave pulse (hereinafter, referred to as rectangular wave) oscillation circuit composed of an astable multivibrator. In this rectangular wave oscillating circuit PG, the bias voltage (+6 V) applied to the inverting input terminal (described as + input terminal) of the operational amplifier Q3 is set to a voltage determined by the voltage division ratio between the resistors R31 and R32. A rectangular wave with a duty ratio of 50% is output. The pulse width is determined by the time constant of the capacitor C3 and the feedback resistor R34 and the voltage applied to the + input terminal.
【００２１】矩形波発振回路ＰＧは抵抗Ｒ４を通して矩
形波を演算増幅器Ｑ４で構成されるインピーダンス変換
回路に入力するが、演算増幅器Ｑ４の＋入力端子には入
力される矩形波の振幅ｐ−ｐを、一定値に制限する理想
ダイオードから構成される制限回路（温度補償手段）Ｌ
Ｍ１，ＬＭ２が接続されている。The rectangular wave oscillating circuit PG inputs the rectangular wave to the impedance conversion circuit composed of the operational amplifier Q4 through the resistor R4, and the amplitude pp of the rectangular wave input to the + input terminal of the operational amplifier Q4. , A limiting circuit (temperature compensating means) L composed of an ideal diode for limiting to a constant value
M1 and LM2 are connected.
【００２２】制限回路ＬＭ１は、入力された矩形波のハ
イ側レベルを演算増幅器Ｑ１の＋入力端子に抵抗Ｒ１１
とＲ１２との分圧比できまる基準電圧（Ｖｈ＝＋４Ｖ）
に制限するように動作する。また、制限回路ＬＭ２は、
入力された矩形波のロー側レベルを演算増幅器Ｑ２の＋
入力端子に抵抗Ｒ２１とＲ２２との分圧比できまる基準
電圧（Ｖｌ＝＋１Ｖ）に制限するように動作する。従っ
て、インピーダンス変換回路を構成する演算増幅器Ｑ４
を通して出力される矩形波はピーク−ピークの振幅は３
Ｖとなる。The limiting circuit LM1 connects the high side level of the input rectangular wave to the + input terminal of the operational amplifier Q1 by the resistor R11.
Reference voltage (Vh = + 4V) that can be calculated by the voltage division ratio of R12 and R12
Works to limit to. Further, the limiting circuit LM2 is
The low side level of the input rectangular wave is set to + of the operational amplifier Q2.
The input terminal operates so as to be limited to the reference voltage (Vl = + 1V) that can be obtained by the voltage division ratio of the resistors R21 and R22. Therefore, the operational amplifier Q4 forming the impedance conversion circuit
The square wave output through is peak-peak with an amplitude of 3
It becomes V.
【００２３】インピーダンス変換回路Ｑ４の出力は直列
接続された検出抵抗Ｒ１、抵抗Ｒ２を通して整流回路Ｒ
ＥＣに入力される。この整流回路ＲＥＣは演算増幅器Ｑ
５１からなるインピーダンス変換回路Ｑ５１、インピー
ダンス変換回路Ｑ５１より出力された矩形波を半波整流
する整流ダイオードＤ５１，５２、演算増幅器Ｑ５２等
を用いて構成した理想ダイオード、インピーダンス変換
回路Ｑ５１の出力と理想ダイオードの整流出力を加算し
て出力電圧の正・負極性に関係なく、その大きさに比例
した単一極性の電圧を出力する反転増幅加算回路（以
下、加算回路と記載する。）より構成されている。The output of the impedance conversion circuit Q4 passes through a detection resistor R1 and a resistor R2 connected in series, and a rectifier circuit R
Input to EC. This rectifier circuit REC is an operational amplifier Q
An impedance conversion circuit Q51 composed of 51, rectifying diodes D51 and 52 for half-wave rectifying the rectangular wave output from the impedance conversion circuit Q51, an ideal diode configured by using an operational amplifier Q52, the output of the impedance conversion circuit Q51 and the ideal diode. It is configured by an inverting amplification adder circuit (hereinafter, referred to as an adder circuit) that adds the rectified outputs of the above and outputs a voltage of a single polarity proportional to the magnitude of the output voltage regardless of the positive or negative polarity of the output voltage. There is.
【００２４】理想用ダイオードにおける演算増幅器Ｑ５
２は、＋入力端子に、矩形波の振幅の中心を０Ｖから見
て２．５Ｖに設定するように、電源電圧６Ｖを抵抗Ｒ５
１，Ｒ５２の抵抗比で分圧した２．５Ｖが基準電圧とし
て印加され、また−入力端子（非反転入力端子）と出力
端子との間には、−入力端子にカソードを、出力端子に
アノードを接続したダイオードＤ５１を接続し、出力端
子にカソードを接続したダイオードＤ５２のアノードと
−入力端子との間に帰還抵抗Ｒ５４を接続し、−入力端
子とインピーダンス変換回路Ｑ５１の出力端子に入力抵
抗Ｒ５２を接続して構成している。Operational amplifier Q5 in ideal diode
2 has a power supply voltage of 6 V and a resistor R5 at the + input terminal so that the center of the amplitude of the rectangular wave is set to 2.5 V when viewed from 0 V.
2.5 V divided by the resistance ratio of R1 and R52 is applied as a reference voltage, and between the −input terminal (non-inverting input terminal) and the output terminal, the cathode is at the −input terminal and the anode is at the output terminal. The feedback resistor R54 is connected between the anode of the diode D52 having the cathode connected to the output terminal and the −input terminal, and the input resistor R52 is connected to the −input terminal and the output terminal of the impedance conversion circuit Q51. Are connected and configured.
【００２５】また、加算回路を構成する演算増幅器Ｑ５
３は、＋入力端子に、矩形波の振幅の中心を２．５Ｖに
設定するように電源電圧６Ｖを抵抗Ｒ５１，Ｒ５２の抵
抗比で分圧した２．５Ｖが基準電圧として印加され、−
入力端子と出力端子との間にはコンデンサＣ５と帰還抵
抗Ｒ５７の並列回路を接続し、−入力端子と理想ダイオ
ード側のダイオードＤ５２のアノードとの間には入力抵
抗Ｒ５６を接続している。Further, an operational amplifier Q5 forming an adder circuit.
In No. 3, 2.5 V obtained by dividing the power supply voltage 6 V by the resistance ratio of the resistors R51 and R52 is applied as a reference voltage to the + input terminal so that the center of the amplitude of the rectangular wave is set to 2.5 V.
A parallel circuit of a capacitor C5 and a feedback resistor R57 is connected between the input terminal and the output terminal, and an input resistor R56 is connected between the negative input terminal and the anode of the diode D52 on the ideal diode side.
【００２６】理想ダイオードを構成する入力抵抗Ｒ５２
と帰還抵抗Ｒ５４とは同抵抗値とし、演算増幅器Ｑ５２
のゲインを１とする。また、加算回路を構成する入力抵
抗Ｒ５６の値は帰還抵抗Ｒ５７の値に対して１／２とし
演算増幅器Ｑ５３のゲインを２とする。Input resistor R52 forming an ideal diode
And the feedback resistor R54 have the same resistance value, and the operational amplifier Q52
The gain of is set to 1. Further, the value of the input resistor R56 forming the adder circuit is 1/2 of the value of the feedback resistor R57, and the gain of the operational amplifier Q53 is 2.
【００２７】また、加算回路は直流出力を得るために、
矩形波から成る加算結果を帰還抵抗Ｒ５７とコンデンサ
Ｃ５との積分時定数で平滑化して直流電圧を比較回路に
出力し、漏電判定するしきい値と比較されて漏電判定を
行う。比較回路を構成する演算増幅器Ｑ６は、＋入力端
子と演算増幅器Ｑ５３との間に入力抵抗Ｒ６３を接続
し、また＋入力端子と出力端子との間に帰還抵抗Ｒ６４
を接続している。In order to obtain a DC output, the adder circuit
The addition result composed of a rectangular wave is smoothed by the integration time constant of the feedback resistor R57 and the capacitor C5, and a DC voltage is output to the comparison circuit. The operational amplifier Q6 that constitutes the comparison circuit has an input resistor R63 connected between the + input terminal and the operational amplifier Q53, and a feedback resistor R64 between the + input terminal and the output terminal.
Are connected.
【００２８】−入力端子には抵抗Ｒ６１，Ｒ６２との抵
抗比で決まる電圧のしきい値が印加される。出力端子は
抵抗Ｒ６５を通してオープンコレクタＴＲのベースに接
続される。A voltage threshold value determined by the resistance ratio of the resistors R61 and R62 is applied to the input terminal. The output terminal is connected to the base of the open collector TR through the resistor R65.
【００２９】比較回路Ｑ６は加算回路Ｑ５３に混入した
ノイズにより誤動作を生じないように、出力がローから
ハイに変わる直流入力電圧と、ハイからローに変わる直
流入力電圧に有る程度の幅を持たせシュミット回路を採
用している。The comparator circuit Q6 should have a width within the range of the DC input voltage whose output changes from low to high and the DC input voltage whose output changes from high to low so as to prevent malfunction due to noise mixed in the adder circuit Q53. Uses a Schmidt circuit.
【００３０】上記インピーダンス変換回路Ｑ４の出力端
子と整流回路ＲＥＣ側におけるインピーダンス変換回路
Ｑ５１の入力端子との間に挿入された、直列回路からな
る検出抵抗Ｒ１及び抵抗Ｒ２の接続点と車載用バッテリ
ー群Ｂｇの−電極端子との間には、車載用バッテリー群
Ｂｇと本回路とを直流的に絶縁すると共に、矩形波発振
回路ＰＧよりインピーダンス変換回路Ｑ４を通して出力
された矩形波を、検出抵抗Ｒ１を通して車載用バッテリ
ー群Ｂｇの−電極端子Ｎおよび車載用バッテリー群Ｂｇ
の＋電極端子Ｐに流すカップリングコンデンサＣＰが接
続されている。インピーダンス変換回路Ｑ４の出力端子
とインピーダンス変換回路Ｑ５１の入力端子には、アー
スに対してツェナーダイオードＺＤ１，ＺＤ２が過電圧
保護、逆電圧保護の目的で接続されている。A connection point between the detection resistor R1 and the resistor R2 formed of a series circuit inserted between the output terminal of the impedance conversion circuit Q4 and the input terminal of the impedance conversion circuit Q51 on the rectifier circuit REC side, and a vehicle battery group. Between the negative electrode terminal of Bg, the in-vehicle battery group Bg and this circuit are galvanically isolated, and the rectangular wave output from the rectangular wave oscillation circuit PG through the impedance conversion circuit Q4 is passed through the detection resistor R1. -Electrode terminal N of vehicle battery group Bg and vehicle battery group Bg
A coupling capacitor CP that flows to the + electrode terminal P of is connected. Zener diodes ZD1 and ZD2 are connected to the ground at the output terminal of the impedance conversion circuit Q4 and the input terminal of the impedance conversion circuit Q51 for the purpose of overvoltage protection and reverse voltage protection.
【００３１】以下、本実施の形態に係る高電圧車両用漏
電検出器の動作について説明する。矩形波発振回路ＰＧ
は、コンデンサＣ３，抵抗Ｒ３３，Ｒ３４の値でパルス
幅が決まり、抵抗Ｒ３１，Ｒ３２の抵抗比で決まるバイ
アス電圧に基づいて設定されたデューティ比５０％の矩
形波を、抵抗Ｒ４を通して出力する。The operation of the leakage detector for a high voltage vehicle according to this embodiment will be described below. Square wave oscillator PG
The pulse width is determined by the values of the capacitor C3 and the resistors R33 and R34, and a rectangular wave having a duty ratio of 50% set based on the bias voltage determined by the resistance ratio of the resistors R31 and R32 is output through the resistor R4.
【００３２】矩形波は図３のＣＨ１に示すようにハイレ
ベルが約５Ｖ、ローレベルが０．５Ｖのパルス信号であ
る。この矩形波は同じく図３のＣＨ２に示されるよう
に、ハイレベルは制限回路ＬＭ１により＋４に制限され
ると共にローレベルは制限回路ＬＭ２により＋１に制限
され、最終的にピーク−ピークが３Ｖに制限された矩形
波がインピーダンス変換回路Ｑ４を通して出力される。
インピーダンス変換回路Ｑ４は、地絡発生時に負荷イン
ピーダンスが変動しても矩形波発振回路ＰＧの発振周波
数が変動しないよう設けてある。The rectangular wave is a pulse signal having a high level of about 5V and a low level of 0.5V, as indicated by CH1 in FIG. This rectangular wave also has a high level limited to +4 by the limiting circuit LM1 and a low level limited to +1 by the limiting circuit LM2 as shown by CH2 in FIG. The rectangular wave thus generated is output through the impedance conversion circuit Q4.
The impedance conversion circuit Q4 is provided so that the oscillation frequency of the rectangular wave oscillation circuit PG does not change even if the load impedance changes when a ground fault occurs.
【００３３】制限回路ＬＭ１の動作としては、演算増幅
器Ｑ１の−入力端子に入力される矩形波のハイレベルが
＋入力端子に印加されたバイアス電圧＋４Ｖを超えると
演算増幅器Ｑ１の出力端子はローレベルとなり、ダイオ
ードＤ１が導通し矩形波のハイレベルが＋４Ｖに制限さ
れる。The operation of the limiting circuit LM1 is as follows. When the high level of the rectangular wave input to the-input terminal of the operational amplifier Q1 exceeds the bias voltage + 4V applied to the + input terminal, the output terminal of the operational amplifier Q1 becomes low level. Then, the diode D1 becomes conductive and the high level of the rectangular wave is limited to + 4V.
【００３４】また、制限回路ＬＭ２の動作としては、演
算増幅器Ｑ２の−入力端子に入力される矩形波のローレ
ベルが＋入力端子に印加されたバイアス電圧＋１Ｖを低
下すると演算増幅器Ｑ２の出力端子はハイレベルとな
り、ダイオードＤ２が導通し矩形波のローレベルが＋１
Ｖに制限される。Further, as the operation of the limiting circuit LM2, when the low level of the rectangular wave input to the-input terminal of the operational amplifier Q2 lowers the bias voltage + 1V applied to the + input terminal, the output terminal of the operational amplifier Q2 becomes It becomes high level, the diode D2 becomes conductive and the low level of the rectangular wave becomes +1.
Limited to V.
【００３５】ここで、車載用バッテリー群Ｂｇと車体間
の絶縁状態が正常な場合は、車載用バッテリー群Ｂｇの
＋および−電極端子と車体間の絶縁抵抗ＲLは無限大に
近いため、矩形波はカップリングコンデンサＣＰを通し
て車載用バッテリー群Ｂｇの＋電極端子および−電極端
子と車体間に流れることは無く、検出抵抗Ｒ１、抵抗Ｒ
２を通して整流回路ＲＥＣに入力される。Here, when the insulation state between the vehicle-mounted battery group Bg and the vehicle body is normal, the insulation resistance RL between the + and-electrode terminals of the vehicle-mounted battery group Bg and the vehicle body is close to infinity, so that the rectangle The wave does not flow between the + electrode terminal and the − electrode terminal of the vehicle battery group Bg and the vehicle body through the coupling capacitor CP, and the detection resistor R1 and the resistor R
It is input to the rectifier circuit REC through 2.
【００３６】整流回路ＲＥＣにおいては、矩形波はイン
ピーダンス変換回路Ｑ５１を通して入力点ａに現れて理
想ダイオードに入力されるが、矩形波は経路１Ｌ１，経
路２Ｌ２の二つの経路を通って加算回路Ｑ５３に入力さ
れる。経路１Ｌ１を通った矩形波は抵抗Ｒ５５を通して
インピーダンス変換回路Ｑ５１に入力された状態で点ｃ
に現れ加算回路Ｑ５３に入力される。一方、経路２Ｌ２
を通った点ｂの現れた矩形波は、矩形波のＶｍ＝２．５
Ｖ以上を反転した半波整流波形となる。In the rectifying circuit REC, the rectangular wave appears at the input point a through the impedance conversion circuit Q51 and is input to the ideal diode, but the rectangular wave passes through the two paths 1L1 and 2L2 to the adding circuit Q53. Is entered. The rectangular wave that has passed through the path 1L1 is input to the impedance conversion circuit Q51 through the resistor R55, and the point c
Appears on the input side and is input to the adding circuit Q53. On the other hand, route 2L2
The rectangular wave in which the point b that has passed through appears is Vm = 2.5 of the rectangular wave.
The half-wave rectified waveform is obtained by inverting V or more.
【００３７】ｃ点に現れた矩形波はＲ５６＝Ｒ５７でゲ
イン１となる加算器（反転増幅加算器）Ｑ５３に入力さ
れ、また点ｂに現れた矩形波はＲ５６（Ｒ５７／２）、
Ｒ５７でゲイン２となる加算器（反転増幅加算器）Ｑ５
３に入力され、各経路１，２Ｌ１，Ｌ２を通った矩形波
を加算する。The rectangular wave appearing at point c is input to an adder (inverting amplification adder) Q53 having a gain of 1 when R56 = R57, and the rectangular wave appearing at point b is R56 (R57 / 2),
Adder with gain of 2 at R57 (inverted amplification adder) Q5
The rectangular waves that are input to 3 and have passed through the paths 1, 2L1 and L2 are added.
【００３８】加算結果として、経路１Ｌ１を通して入力
された矩形を反転すると共に、経路２Ｌ２を通して入力
された半波整流波形をレベルを２倍にして反転して双方
の矩形波を加算する。加算器Ｑ５３より実際に出力され
る加算後の矩形波は、Ｖｍ＝２．５Ｖ以上の波形はＶｍ
＝２．５Ｖ以下の波形で減算されてＶｍ＝２．５Ｖ以上
の整流波形となって出力される。As a result of the addition, the rectangle input through the path 1L1 is inverted, and the half-wave rectified waveform input through the path 2L2 is doubled in level and inverted to add both rectangular waves. The square wave after addition which is actually output from the adder Q53 has a waveform of Vm = 2.5V or more.
= 2.5V or less is subtracted and a rectified waveform of Vm = 2.5V or more is output.
【００３９】この整流波形は抵抗Ｒ５７とコンデンサＣ
５の積分回路で平滑され、直流電圧として比較回路Ｑ６
の＋入力端子に入力される。比較回路Ｑ６の−入力端子
には、以下の式で導き出した漏電検出判定のしきい値が
設定されている。This rectified waveform has a resistor R57 and a capacitor C.
It is smoothed by the integrating circuit of No. 5 and is compared with the comparison circuit Q6 as a DC voltage.
Is input to the + input terminal of. The negative input terminal of the comparison circuit Q6 is set with the threshold value of the leakage detection determination derived by the following formula.
【００４０】[0040]
【数１】 [Equation 1]
【００４１】この式において、ＲLは絶縁抵抗、１／ｊ
ωＣはカップリングコンデンサのインピーダンス、Ｒは
検出抵抗、ＶPPは＋，−電源電圧、ＶOSは矩形波電圧レ
ベルである。In this equation, R L is the insulation resistance, 1 / j
ωC is the impedance of the coupling capacitor, R is the detection resistance, V PP is the + and-power supply voltages, and V OS is the rectangular wave voltage level.
【００４２】この式から明らかなように絶縁破壊により
生じる絶縁抵抗ＲLを、例えば自動車メーカが決めた１
００ＫΩを低下すると、直流化された矩形波のレベルＶ
は、絶縁抵抗ＲLを１００ＫΩにして設定したしきい値
電圧より下がるため比較回路Ｑ６の出力はハイレベルと
なる。As is clear from this equation, the insulation resistance R L caused by the dielectric breakdown is determined by, for example, 1
When 00KΩ is decreased, the level V of the rectangular wave converted to DC is
Is lower than the threshold voltage set by setting the insulation resistance R L to 100 KΩ, the output of the comparison circuit Q6 becomes high level.
【００４３】しかし、絶縁破壊が生じていない間は、矩
形波はカップリングコンデンサＣＰ、擬似的な絶縁抵抗
ＲLを通してアースに流れることは無いため、カップリ
ングコンデンサＣＰ、絶縁抵抗ＲLにより電圧降下を起
こし、レベルがしきい値以下に下がることはなく漏電判
定はなされない。However, as long as the insulation breakdown does not occur, the rectangular wave does not flow to the ground through the coupling capacitor CP and the pseudo insulation resistance R L. Therefore, the voltage drop occurs due to the coupling capacitor CP and the insulation resistance R L. And the level does not drop below the threshold value, and the leakage is not judged.
【００４４】しかし、車載用バッテリー群Ｂｇの＋電極
端子あるいは−電極端子と車体間の絶縁が劣化し、電極
端子と車体間の絶縁抵抗ＲLが１００ＫΩ以下に低下す
ると、インピーダンス変換回路Ｑ４より矩形波が、検出
抵抗Ｒ１、カップリングコンデンサＣＰ、絶縁抵抗ＲL
を通して接地側に流れる。点Ｘにおいて抵抗Ｒ２の両端
に現れる矩形波のレベルは上記式で示されるように検出
抵抗Ｒ１、絶縁抵抗Ｒ L、カップリングコンデンサＣＰ
のインピーダンス１／ｊωＣによる電圧降下分だけレベ
ルは低下する。However, the positive electrode of the on-vehicle battery group Bg
Insulation between the terminal or-electrode terminal and the car body deteriorates
Insulation resistance R between terminal and car bodyLDrops below 100 KΩ
Then, the rectangular wave is detected by the impedance conversion circuit Q4.
Resistance R1, coupling capacitor CP, insulation resistance RL
Through to the ground side. Both ends of the resistor R2 at the point X
The square wave level appearing at is detected as shown in the above equation.
Resistance R1, insulation resistance R L, Coupling capacitor CP
Of the voltage drop due to the impedance 1 / jωC of
Le drops.
【００４５】この絶縁抵抗ＲLの発生によりレベルが低
下した矩形波を整流回路ＲＥＣにおいて全波整流し平滑
化した後に、抵抗Ｒ６３を通して比較回路Ｑ６の＋入力
端子に入力すると、平滑化信号のレベルは抵抗６１，６
２の抵抗比で決まる基準電圧と比較される。平滑化信号
のレベルが基準電圧より低下すると、比較回路Ｑ６の出
力端子はローレベルからハイレベルに反転し抵抗Ｒ６５
を通してオープンコレクタを動作させ、図示しない漏電
警報手段を稼働させる。When the rectangular wave whose level is lowered due to the generation of the insulation resistance R L is full-wave rectified and smoothed by the rectifier circuit REC and then input to the + input terminal of the comparison circuit Q6 through the resistor R63, the level of the smoothed signal is Are resistors 61 and 6
It is compared with a reference voltage determined by a resistance ratio of 2. When the level of the smoothed signal becomes lower than the reference voltage, the output terminal of the comparison circuit Q6 is inverted from low level to high level and the resistor R65 is turned on.
The open collector is operated through to activate the leak warning means (not shown).
【００４６】なお、整流回路ＲＥＣから出力された信号
にノイズが混入すると、信号レベルは＋６Ｖを中心に
＋、−方向に変動することがある。その結果、比較回路
Ｑ６の出力はハイ、ローを繰り返し、誤った漏電警報、
誤った漏電解除を出すことになる。When noise is mixed in the signal output from the rectifier circuit REC, the signal level may fluctuate in + and-directions around + 6V. As a result, the output of the comparator circuit Q6 repeats high and low, resulting in a false leakage alarm,
You will issue an incorrect leak release.
【００４７】従って、本実施の形態では比較回路Ｑ６に
シュミット回路を採用し、平滑化信号のレベルが基準電
圧レベルより低下し、一旦比較回路Ｑ６の出力レベルが
ハイとなったならば、この出力信号を帰還抵抗Ｒ６４よ
り＋入力端子側に流す。Therefore, in the present embodiment, the Schmitt circuit is adopted as the comparison circuit Q6, and if the level of the smoothed signal becomes lower than the reference voltage level and the output level of the comparison circuit Q6 once becomes high, this output is output. A signal is made to flow from the feedback resistor R64 to the + input terminal side.
【００４８】この結果、帰還抵抗Ｒ６４による電圧降下
分、＋入力端子側の電圧レベルが低下する。このため、
比較回路Ｑ６は、平滑化信号のレベルがノイズにより多
少プラス方向に変動しても基準電圧を超えることはない
ため、漏電警報を維持できる。As a result, the voltage level at the + input terminal side decreases by the amount of the voltage drop due to the feedback resistor R64. For this reason,
The comparator circuit Q6 can maintain the leakage alarm because the level of the smoothed signal does not exceed the reference voltage even if the level of the smoothed signal fluctuates in the positive direction due to noise.
【００４９】[0049]
【発明の効果】この発明によれば、電気自動車内で車体
と電気的に絶縁された直流電源系統の漏電を検出する高
電圧車両用漏電検出器において、一定レベルの交流信号
を発振し、この交流信号をコンデンサＣを通して前記直
流電源系統Ｂに出力する発振部ＯＳと、この出力された
交流信号のレベルが、漏電時に前記直流電源系統Ｂと車
体間に発生する絶縁抵抗による電圧降下分、低下したか
を判定する判定部ＤＴとを含む漏電検出器ＬＥＤを備え
ることで、直流電源系統と車体間の絶縁が劣化して、直
流電源系統と車体に絶縁抵抗が生じたならば発振部より
出力された一定レベルの交流信号はコンデンサ、絶縁抵
抗を通してアースとなる車体に流れるため、この流れる
交流電流を電圧にて検出しこの電圧レベルが、予めその
抵抗値を設定した絶縁抵抗の両端電圧分低下したかを判
定して漏電検出を行うことで、漏電検出を確実に行える
という効果がある。According to the present invention, in a high-voltage vehicle leakage detector for detecting a leakage of a DC power supply system electrically insulated from a vehicle body in an electric vehicle, an AC signal of a constant level is oscillated, and An oscillation unit OS that outputs an AC signal to the DC power supply system B through a capacitor C, and the level of the output AC signal is reduced by a voltage drop due to an insulation resistance generated between the DC power supply system B and the vehicle body at the time of leakage. By providing the leakage detector LED including the determination unit DT that determines whether or not the DC power supply system and the vehicle body are deteriorated in insulation, and an insulation resistance occurs between the DC power supply system and the vehicle body, an output from the oscillation unit is generated. Since the generated AC signal of a certain level flows through the capacitor and the insulation resistance to the vehicle body that serves as the ground, the flowing AC current is detected by the voltage, and this voltage level sets the resistance value in advance. By performing the determination to leakage detection or dropped across voltage of the edge resistance, there is an effect that surely perform a leakage detection.
【００５０】この発明によれば、絶縁抵抗の値を、直流
電源系統と車体間の絶縁が劣化して漏電が開始されるし
きい値にて設定することで、検出した交流信号のレベル
が、しきい値を超えた抵抗値となった絶縁抵抗における
電圧降下分、低下したかを判定して漏電検出を行うこと
で、絶縁劣化の進行と共に早期に漏電検出を行うことが
できるという効果がある。According to the present invention, by setting the value of the insulation resistance at the threshold value at which the insulation between the DC power supply system and the vehicle body deteriorates and electric leakage starts, the detected AC signal level is By detecting whether or not the voltage drop has occurred in the insulation resistance that has become a resistance value that exceeds the threshold value and detecting the leakage, it is possible to detect the leakage early as the insulation deterioration progresses. .
【００５１】この発明によれば、発振部ＯＳは温度補償
手段を設けることにより、発振される交流信号は周囲温
度の上昇によりそのレベルが変動することがないため、
交流信号のレベルに基づいて漏電検出を行う際にも、周
囲温度の上昇により漏電の誤検出を阻止できるため、漏
電検出の信頼性を向上できるという効果がある。According to the present invention, since the oscillator section OS is provided with the temperature compensating means, the level of the oscillated AC signal does not fluctuate due to the rise of the ambient temperature.
Even when the leakage detection is performed based on the level of the AC signal, it is possible to prevent erroneous detection of the leakage due to the rise in the ambient temperature, and thus it is possible to improve the reliability of the leakage detection.
【図１】図１はこの発明に係る高電圧車両用漏電検出器
の基本構成を示す図である。FIG. 1 is a diagram showing a basic configuration of a leakage detector for a high-voltage vehicle according to the present invention.
【図２】図２は本実施の形態に係る高電圧車両用漏電検
出器の構成を示す回路図である。FIG. 2 is a circuit diagram showing a configuration of a high voltage vehicle leakage detector according to the present embodiment.
【図３】図３は本実施の形態に係る矩形波発振回路より
出力される矩形波の波形図である。FIG. 3 is a waveform diagram of a rectangular wave output from the rectangular wave oscillator circuit according to the present embodiment.
【図４】図４は図に示す高電圧車両用漏電検出器の各点
に矩形波の波形を示す図である。FIG. 4 is a diagram showing a waveform of a rectangular wave at each point of the leakage detector for a high-voltage vehicle shown in FIG.
【図５】図５は従来の地絡検出器の構成を示す図であ
る。FIG. 5 is a diagram showing a configuration of a conventional ground fault detector.
【図６】図６は従来の地絡検出器の動作を説明する波形
図である。FIG. 6 is a waveform diagram for explaining the operation of the conventional ground fault detector.
【図７】図７は従来技術による漏電検知方法を説明する
図である。FIG. 7 is a diagram illustrating a leakage detection method according to a conventional technique.
Ｃ コンデンサ ＯＳ 発振部 Ｂ 直流電源系統 ＬＥＤ 漏電検出器 C capacitor OS oscillator B DC power supply system LED leakage detector
Claims (3)
た直流電源系統の漏電を検出する高電圧車両用漏電検出
器において、一定レベルの交流信号を発振し、この交流
信号をコンデンサを通して前記直流電源系統に出力する
発振部と、この出力された交流信号のレベルが、漏電時
に前記直流電源系統と車体間に発生する絶縁抵抗による
電圧降下分、低下したかを判定する判定部とを含む漏電
検出器を備えたことを特徴とする高電圧車両用漏電検出
器。1. A leakage detector for a high-voltage vehicle, which detects a leakage of a DC power supply system electrically insulated from a vehicle body in an electric vehicle, oscillates an AC signal of a constant level, and passes this AC signal through a capacitor. An oscillating unit for outputting to the DC power supply system, and a judging unit for judging whether or not the level of the outputted AC signal is reduced by a voltage drop due to an insulation resistance generated between the DC power supply system and the vehicle body at the time of electric leakage. A leakage detector for a high-voltage vehicle, which is provided with a leakage detector.
車体に漏電電流が流れると予想されるしきい値で予め設
定することを特徴とする請求項１に記載の高電圧車両用
漏電検出器。2. The leakage detection for a high-voltage vehicle according to claim 1, wherein the value of the insulation resistance is preset with a threshold value at which a leakage current is expected to flow from the DC power supply system to the vehicle body. vessel.
を特徴とする請求項１に記載の高電圧車両用漏電検出
器。3. The leakage detector for a high voltage vehicle according to claim 1, wherein the oscillating unit is provided with a temperature compensating means.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001317148A JP2003125530A (en) | 2001-10-15 | 2001-10-15 | Leakage detection device for high-voltage vehicle |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001317148A JP2003125530A (en) | 2001-10-15 | 2001-10-15 | Leakage detection device for high-voltage vehicle |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JP2003125530A true JP2003125530A (en) | 2003-04-25 |
Family
ID=19135066
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2001317148A Withdrawn JP2003125530A (en) | 2001-10-15 | 2001-10-15 | Leakage detection device for high-voltage vehicle |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2003125530A (en) |
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2011172373A (en) * | 2010-02-18 | 2011-09-01 | Toyota Motor Corp | Drive system |
| KR101065583B1 (en) | 2008-09-04 | 2011-09-19 | 주식회사 엘지화학 | Apparatus and Method for detecting leakage current of battery |
| CN103176095A (en) * | 2011-12-23 | 2013-06-26 | 比亚迪股份有限公司 | Device and method for electric leakage detection |
| JP5823007B1 (en) * | 2014-09-25 | 2015-11-25 | 三菱電機株式会社 | Electric leakage detection device for vehicles |
| JP2016050921A (en) * | 2014-09-02 | 2016-04-11 | 富士電機機器制御株式会社 | Current detector |
| CN113433484A (en) * | 2021-07-29 | 2021-09-24 | 上海玖行能源科技有限公司 | Alternating current pile grounding detection system and control method |
-
2001
- 2001-10-15 JP JP2001317148A patent/JP2003125530A/en not_active Withdrawn
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR101065583B1 (en) | 2008-09-04 | 2011-09-19 | 주식회사 엘지화학 | Apparatus and Method for detecting leakage current of battery |
| JP2011172373A (en) * | 2010-02-18 | 2011-09-01 | Toyota Motor Corp | Drive system |
| CN103176095A (en) * | 2011-12-23 | 2013-06-26 | 比亚迪股份有限公司 | Device and method for electric leakage detection |
| JP2016050921A (en) * | 2014-09-02 | 2016-04-11 | 富士電機機器制御株式会社 | Current detector |
| JP5823007B1 (en) * | 2014-09-25 | 2015-11-25 | 三菱電機株式会社 | Electric leakage detection device for vehicles |
| CN113433484A (en) * | 2021-07-29 | 2021-09-24 | 上海玖行能源科技有限公司 | Alternating current pile grounding detection system and control method |
| CN113433484B (en) * | 2021-07-29 | 2024-05-03 | 上海玖行能源科技有限公司 | AC pile grounding detection system and control method |
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