JP2003018046A - Cdma baseband reception circuit - Google Patents
Cdma baseband reception circuitInfo
- Publication number
- JP2003018046A JP2003018046A JP2001195685A JP2001195685A JP2003018046A JP 2003018046 A JP2003018046 A JP 2003018046A JP 2001195685 A JP2001195685 A JP 2001195685A JP 2001195685 A JP2001195685 A JP 2001195685A JP 2003018046 A JP2003018046 A JP 2003018046A
- Authority
- JP
- Japan
- Prior art keywords
- search
- matched filter
- tap
- correlation value
- path
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Classifications
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
- Y02D30/00—Reducing energy consumption in communication networks
- Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks
Landscapes
- Mobile Radio Communication Systems (AREA)
Abstract
Description
【０００１】[0001]
【発明の属する技術分野】本発明はスペクトル拡散通信
システムにおけるベースバンド受信回路に関し、とくに
ＣＤＭＡ基地局間非同期セルラシステムにおける移動局
用ベースバンド受信回路に適する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a baseband receiver circuit in a spread spectrum communication system, and more particularly to a baseband receiver circuit for mobile stations in an asynchronous cellular system between CDMA base stations.
【０００２】[0002]
【従来の技術】ディジタル移動体通信におけるスペクト
ル拡散通信システムでは、送信局と受信局で用いる拡散
符号の同期捕捉が必要となる。スペクトル拡散通信シス
テムを代表するＣＤＭＡ基地局間非同期セルラシステム
では、移動局が電源投入時に在圏するセルを判定するた
め、初期セルサーチと呼ばれる同期捕捉を実施する。2. Description of the Related Art In a spread spectrum communication system in digital mobile communication, it is necessary to acquire synchronization of spread codes used by a transmitting station and a receiving station. In a CDMA inter-base station asynchronous cellular system, which represents a spread spectrum communication system, a mobile station determines a cell in which the mobile station is located when the power is turned on. Therefore, a synchronization acquisition called an initial cell search is performed.
【０００３】ＣＤＭＡ基地局間非同期セルラシステムに
おける初期セルサーチの代表的なものとして、３ＧＰＰ
（Ｗ−ＣＤＭＡ）の技術資料ＴＳ２５．２１１に記載さ
れている技術がある。その記載内容はセルサーチを３段
階の処理に分けて高速化を図ったものとなっている。3GPP is a typical initial cell search in an asynchronous cellular system between CDMA base stations.
There is a technology described in technical document TS25.211 of (W-CDMA). The contents of the description are intended to increase the speed by dividing the cell search into three steps.
【０００４】上記３段階のセルサーチにおける第１段階
は、１スロット周期で２５６〔ｃｈｉｐ〕長の共通の符
号が挿入されたＰＳＣＨ（Ｐｒｉｍａｒｙ Ｓｙｎｃｈ
ｒｏｎｉｓａｔｉｏｎ Ｃｈａｎｎｅｌ）をサーチする
ことにより、スロットタイミングを検出する。その際に
ＢＰＳＫ変調されたＰＳＣＨとの相関処理はマッチドフ
ィルタを用いる場合が多い。The first step in the above three-step cell search is a PSCH (Primary Synch) in which a common code of 256 [chip] length is inserted in one slot period.
The slot timing is detected by searching for the channel. In that case, a matched filter is often used for the correlation processing with the BPSK-modulated PSCH.
【０００５】また、スペクトル拡散通信システム特有の
通信中におけるマルチパスを積極的に利用したＲＡＫＥ
合成受信では、ＣＰＩＣＨ（Ｃｏｍｍｏｎ Ｐｉｌｏｔ
Ｃｈａｎｎｅｌ）との相関を求めることによりパスサ
ーチを行う。その際に、ＱＰＳＫ変調されたＣＰＩＣＨ
との相関はマッチドフィルタを用いて行う場合が多い。In addition, RAKE that actively utilizes multipath during communication, which is peculiar to spread spectrum communication systems.
In combined reception, CPICH (Common Pilot)
Path search is performed by obtaining the correlation with the channel). At that time, CPICH modulated by QPSK
Correlation with is often done using a matched filter.
【０００６】基本的にセルサーチとパスサーチの処理は
同時に行う必要性がないため、１つのマッチドフィルタ
を時分割で使用して共有することが可能である。マッチ
ドフィルタをセルサーチとパスサーチで時分割で共用す
る従来例が「Ｍａｔｓｕｓｉｔａ Ｔｅｃｈｎｉｃａｌ
Ｊｏｕｒｎａｌ Ｖｏｌ．４５ Ｎｏ．２ Ａｐｒ．
１９９９」に記載されている。Basically, since it is not necessary to perform the cell search and the path search at the same time, one matched filter can be used by time division and shared. The conventional example in which the matched filter is shared by the cell search and the path search in a time-sharing manner is "Matsusita Technical".
Journal Vol. 45 No. 2 Apr.
1999 ".
【０００７】図７を用いて上記従来例を説明する。マッ
チドフィルタ２００はフリップフロップ２００１、乗算
器２００２、加算器２００３により構成される。まず、
パスサーチ時の動作について説明する。Ｉｃｈ受信信号
ＲＸＩとＩｃｈ拡散符号ＰＮＩはマッチドフィルタ２０
０に入力され、シンボル時間分用意されたフリップフロ
ップ２００１と乗算器２００２、および加算器２００３
によりＩ成分ベースバンド受信データＲＸＩと拡散符号
ＰＮＩの相関結果が得られる。得られた相関結果は加算
器２００３に入力される。マッチドフィルタ２０１、２
０２、２０３に関しても同様な処理が行われる。The above conventional example will be described with reference to FIG. The matched filter 200 includes a flip-flop 2001, a multiplier 2002, and an adder 2003. First,
The operation at the time of path search will be described. The Ich received signal RXI and the Ich spread code PNI are matched filters 20.
Flip-flop 2001, multiplier 2002, and adder 2003 which are input to 0 and are prepared for the symbol time.
As a result, the correlation result of the I component baseband received data RXI and the spread code PNI is obtained. The obtained correlation result is input to the adder 2003. Matched filters 201, 2
Similar processing is performed for 02 and 203.
【０００８】マッチドフィルタ２０１にはＩ成分ベース
バンド受信データＲＸＩと拡散符号ＰＮＱが入力され、
ＲＸＩとＰＮＱの相関結果が得られる。マッチドフィル
タ２０２にはＱ成分ベースバンド受信データＲＸＱと拡
散符号ＰＮＩが入力され、ＲＸＱとＰＮＩの相関結果が
得られる。マッチドフィルタ２０３にはＱ成分ベースバ
ンド受信データＲＸＱと拡散符号ＰＮＱが入力され、Ｒ
ＸＱとＰＮＱの相関結果が得られる。The I component baseband received data RXI and the spread code PNQ are input to the matched filter 201,
The correlation result of RXI and PNQ is obtained. The Q component baseband received data RXQ and the spread code PNI are input to the matched filter 202, and the correlation result of RXQ and PNI is obtained. The Q component baseband received data RXQ and the spread code PNQ are input to the matched filter 203, and R
The correlation result of XQ and PNQ is obtained.
【０００９】マッチドフィルタ２００とマッチドフィル
タ２０３の出力は加算器２０４に、マッチドフィルタ２
０１とマッチドフィルタ２０２の出力は加算器２０５
に、それぞれ入力され加算される。なお、マッチドフィ
ルタ２０１の出力は極性を反転して加算器に入力するこ
とにより、減算される。以上によりＱＰＳＫ復調に必要
となるＲＸＩ＊ＰＮＩ＋ＲＸＱ＊ＰＮＱの出力ＸとＲＸ
Ｑ＊ＰＮＩ−ＲＸＩ＊ＰＮＱの出力Ｙが得られる。The outputs of the matched filters 200 and 203 are sent to the adder 204 and the matched filter 2
01 and the output of the matched filter 202 are the adder 205
Are input and added. The output of the matched filter 201 is subtracted by inverting the polarity and inputting it to the adder. From the above, RXI * PNI + RXQ * PNQ outputs X and RX required for QPSK demodulation
The output Y of Q * PNI-RXI * PNQ is obtained.
【００１０】次にセルサーチ時はＢＰＳＫ復調でよいた
め、拡散符号をＰＮＩのみ使用するものとして、マッチ
ドフィルタ２００の出力ＲＸＩ＊ＰＮＩとマッチドフィ
ルタ２０２の出力ＲＸＱ＊ＰＮＩのみが得られればよい
ことになる。従って加算器２０４にはマッチドフィルタ
２００の出力のみ入力され、加算器２０５にはマッチド
フィルタ２０２のみが入力されることになり、マッチド
フィルタ２０１と２０３は未使用となる。Next, since BPSK demodulation may be used at the time of cell search, only the output RXI * PNI of the matched filter 200 and the output RXQ * PNI of the matched filter 202 should be obtained assuming that only the PNI is used as the spread code. Become. Therefore, only the output of the matched filter 200 is input to the adder 204, only the matched filter 202 is input to the adder 205, and the matched filters 201 and 203 are unused.
【００１１】[0011]
【発明が解決しようとする課題】上記従来例ではパスサ
ーチに必要な４つのマッチドフィルタを用意すると、セ
ルサーチ時には２つのマッチドフィルタが未使用とな
り、不要な回路が存在し、回路を有効活用できないとい
う問題が発生する。この問題はセルサーチに使用するＰ
ＳＣＨとパスサーチに使用するＣＰＩＣＨとで変調方式
が異なることによるＷ−ＣＤＭＡ特有の問題でもある。
ｃｄｍａＯｎｅのように、セルサーチとパスサーチで使
用するチャネルが同一の場合には、このような問題は発
生しない。In the above-mentioned conventional example, if four matched filters required for path search are prepared, two matched filters are not used during cell search, and unnecessary circuits exist and circuits cannot be effectively used. The problem occurs. This problem is used for cell search P
This is also a problem peculiar to W-CDMA due to the different modulation schemes between the SCH and the CPICH used for path search.
Such a problem does not occur when the channels used in the cell search and the path search are the same as in cdmaOne.
【００１２】[0012]
【課題を解決するための手段】上記課題は、下り回線に
含まれるセルサーチ用チャネルとパスサーチ用チャネル
とで変調方式が異なるＣＤＭＡセルラシステムにおい
て、セルサーチに用いるマッチドフィルタとパスサーチ
に用いるマッチドフィルタを時分割で共用する手段と、
マッチドフィルタにおけるタップ長をセルサーチ時とパ
スサーチ時で異ならせてサーチする手段と、パスサーチ
時には用途に応じてサーチ範囲を可変する手段を備えた
ＣＤＭＡベースバンド受信回路とすることで解決され
る。SUMMARY OF THE INVENTION In a CDMA cellular system in which the cell search channel and the path search channel included in the downlink have different modulation methods, the above-mentioned problem is solved by using a matched filter used for the cell search and a matched filter used for the path search. A means to share a filter by time sharing,
This is solved by using a CDMA baseband receiving circuit provided with a means for searching by making the tap length in the matched filter different between the cell search and the path search, and a means for varying the search range according to the application at the time of the path search. .
【００１３】[0013]
【発明の実施の形態】図１に本発明の一実施例になるＣ
ＤＭＡ基地局間非同期セルラシステムにおける移動局受
信回路の構成を示す。ＣＤＭＡ基地局間非同期セルラシ
ステムの移動局における受信回路は、サーチ部１０、ア
ンテナ２０、ＲＦ部３０、Ａ／Ｄ変換器４０、復調部５
０、ＲＡＫＥ合成部６０、シーケンサ７０により構成さ
れる。DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS FIG. 1 shows an embodiment C of the present invention.
1 shows a configuration of a mobile station receiving circuit in an asynchronous cellular system between DMA base stations. The receiving circuit in the mobile station of the asynchronous cellular system between CDMA base stations includes a search unit 10, an antenna 20, an RF unit 30, an A / D converter 40, and a demodulation unit 5.
0, a RAKE combining unit 60, and a sequencer 70.
【００１４】アンテナ２０から受信したＲＦ帯域の受信
信号はＲＦ部３０によりダウンコンバートおよび帯域制
限され、Ｉ成分、Ｑ成分に分離されたベースバンド帯域
の受信信号となる。ＲＦ部３０の出力となるＩ成分ベー
スバンド受信信号、Ｑ成分ベースバンド受信信号はそれ
ぞれＡ／Ｄ変換器４０に入力され、拡散符号周波数の数
倍（４倍程度）の周波数でオーバサンプリングおよび量
子化（４ｂｉｔ程度）されたディジタル信号のベースバ
ンド受信データに変換される。The received signal in the RF band received from the antenna 20 is down-converted and band-limited by the RF unit 30 and becomes a received signal in the base band band separated into I component and Q component. The I-component baseband received signal and the Q-component baseband received signal that are output from the RF unit 30 are input to the A / D converter 40, and oversampling and quantum are performed at a frequency that is several times (about four times) the spreading code frequency. The converted digital signal (about 4 bits) is converted into baseband received data.
【００１５】Ａ／Ｄ変換器４０の出力となるＩ成分ベー
スバンド受信データ４１、Ｑ成分ベースバンド受信デー
タ４２は復調部５０およびサーチ部１０にそれぞれ入力
される。電源投入時は移動局の在圏する基地局のフレー
ムタイミング抽出やスクランブリングコード同定といっ
たセルサーチを行う必要がある。The I component baseband received data 41 and the Q component baseband received data 42, which are the outputs of the A / D converter 40, are input to the demodulation section 50 and the search section 10, respectively. When the power is turned on, it is necessary to perform a cell search such as frame timing extraction and scrambling code identification of the base station in which the mobile station is located.
【００１６】セルサーチは主にスロットタイミング抽出
を行う１ｓｔサーチ、フレームタイミング抽出およびコ
ードグループ同定を行う２ｎｄサーチ、スクランブリン
グコード同定を行う３ｒｄサーチに分けられる。Cell search is mainly divided into 1st search for slot timing extraction, 2nd search for frame timing extraction and code group identification, and 3rd search for scrambling code identification.
【００１７】３ＧＰＰ（Ｗ−ＣＤＭＡ）における１ｓｔ
サーチはスロット周期（１フレームあたり１５スロッ
ト）に２５６ｃｈｉｐ長の共通の符号が挿入されたＰＳ
ＣＨをサーチすることによりスロットタイミングを検出
する。２ｎｄサーチはＰＳＣＨと同じタイミングで多重
されており、毎スロットごと異なった２５６ｃｈｉｐ長
の符号が１フレームで一巡するＳＳＣＨ（Ｓｅｃｏｎｄ
ａｒｙ Ｓｙｎｃｈｒｏｎｉｓａｔｉｏｎ Ｃｈａｎｎ
ｅｌ）をサーチすることにより、フレームタイミングを
検出すると同時にコードグループが識別される。３ｒｄ
サーチは２ｎｄサーチで識別されたコードグループに属
するスクランブリングコード（８コード程度）について
それぞれ相関値を求め、その中で最も相関が高いスクラ
ンブリングコードを定める。1st in 3GPP (W-CDMA)
The search is a PS in which a common code of 256 chips is inserted in the slot cycle (15 slots per frame).
The slot timing is detected by searching the CH. The 2nd search is multiplexed at the same timing as the PSCH, and the SSCH (Second) in which a 256-chip length code that is different for each slot makes one cycle in one frame
ary Synchronization Chann
The code group is identified at the same time that the frame timing is detected by searching (e). 3rd
In the search, a correlation value is obtained for each of scrambling codes (about 8 codes) belonging to the code group identified by the 2nd search, and the scrambling code having the highest correlation among them is determined.
【００１８】サーチ部１０では１ｓｔサーチ、２ｎｄサ
ーチ、３ｒｄサーチに必要な相関処理がなされ、サーチ
部の出力となる１ｓｔサーチ結果７１、２ｎｄサーチ結
果７２、３ｒｄサーチ結果７３はシーケンサ７０に送ら
れ、シーケンサ７０において所定の手順に従い、セルサ
ーチ処理が行われる。セルサーチ終了後はスクランブリ
ングコードとフレームタイミングを報告信号７４として
復調部５０に報告し、復調部５０はシーケンサ７０から
報告されたスクランブリングコードとフレームタイミン
グをもとに基地局からの下り回線チャネルを復調する。
復調する際には、サーチ部においてＲＡＫＥ合成に必要
となる伝播路におけるマルチパスを推定するためにパス
サーチを行う。The search unit 10 performs the correlation processing required for the 1st search, the 2nd search, and the 3rd search, and the 1st search result 71, the 2nd search result 72, and the 3rd search result 73, which are the outputs of the search unit, are sent to the sequencer 70. Cell search processing is performed in sequencer 70 according to a predetermined procedure. After the cell search is completed, the scrambling code and the frame timing are reported to the demodulation unit 50 as a report signal 74, and the demodulation unit 50 determines the downlink channel from the base station based on the scrambling code and the frame timing reported from the sequencer 70. Demodulate.
At the time of demodulation, the search unit performs a path search in order to estimate multipaths in the propagation path required for RAKE combining.
【００１９】サーチ部１０ではパスサーチに必要な相関
処理がなされ、サーチ部１０の出力となるパスサーチ結
果７１（セルサーチにおける１ｓｔサーチ結果と共用）
はシーケンサ７０に送られ、シーケンサ７０において所
定の手順に従いパスサーチ処理が行われる。パスサーチ
により検出されたパス情報７５は復調部５０に送られ、
復調部５０ではパス情報７５をもとに各フィンガ毎に復
調を行う。各フィンガの復調結果５１（図１では４フィ
ンガ）はＲＡＫＥ合成部６０によりＲＡＫＥ合成が行わ
れ、受信データ６１を得る。受信データ６１はデインタ
リーブ、誤り訂正等を行う処理部に送出され、ユーザ情
報の音声あるいはデータとなる。The search unit 10 performs the correlation processing required for the path search and outputs the result of the path search result 71 (shared with the 1st search result in the cell search).
Is sent to the sequencer 70, and the path search process is performed in the sequencer 70 according to a predetermined procedure. The path information 75 detected by the path search is sent to the demodulation unit 50,
The demodulation unit 50 demodulates each finger based on the path information 75. The demodulation result 51 (4 fingers in FIG. 1) of each finger is RAKE-combined by the RAKE combining unit 60 to obtain the reception data 61. The received data 61 is sent to a processing unit that performs deinterleaving, error correction, etc., and becomes voice or data of user information.
【００２０】図２に本発明のサーチ部１０の構成図を示
す。サーチ部はマッチドフィルタ１０１、１０２、拡散
符号発生器ＰＮＧ１０３、累算器Σ１０４、２ｎｄサー
チ部１１４、３ｒｄサーチ部１１５により構成される。FIG. 2 shows a block diagram of the search unit 10 of the present invention. The search unit includes matched filters 101 and 102, a spread code generator PNG 103, an accumulator Σ104, a 2nd search unit 114, and a 3rd search unit 115.
【００２１】セルサーチ時はＩ成分ベースバンド受信デ
ータ４１とＱ成分ベースバンド受信データ４２はサーチ
部１０に入力され、それぞれマッチドフィルタ１０１、
１０２に入力される。マッチドフィルタ１０１ではＩ成
分ベースバンド受信データ４１と拡散符号発生器１０３
から出力されるセルサーチ用拡散符号ＰＮＳ１１１との
相関がとられ、（ＲＸＩ＊ＰＮＳ）の相関値１０５が得
られる。At the time of cell search, the I component baseband received data 41 and the Q component baseband received data 42 are input to the search unit 10, and are matched filter 101, respectively.
It is input to 102. In the matched filter 101, the I component baseband received data 41 and the spread code generator 103
The correlation value 105 of (RXI * PNS) is obtained by correlating with the cell search spreading code PNS111 output from.
【００２２】また、マッチドフィルタ１０２では、Ｑ成
分ベースバンド受信データ４２と拡散符号発生器１０３
から出力されるセルサーチ用拡散符号ＰＮＳ１１１との
相関がとられ、（ＲＸＱ＊ＰＮＳ）の相関値１０８が得
られる。セルサーチ時は相関値１０５と相関値１０８が
累算器１０４に入力され、累算器１０４により、数１の
演算がなされ、セルサーチに必要な結果が得られる。累
算器１０４の出力７１はシーケンサにおいて所定の手順
に従いセルサーチ処理が行われる。In the matched filter 102, the Q component baseband received data 42 and the spread code generator 103 are also included.
The cell search spreading code PNS111 output from the above is correlated, and the correlation value 108 of (RXQ * PNS) is obtained. At the time of cell search, the correlation value 105 and the correlation value 108 are input to the accumulator 104, and the accumulator 104 performs the operation of the equation 1 to obtain the result required for the cell search. The output 71 of the accumulator 104 is subjected to cell search processing in a sequencer according to a predetermined procedure.
【００２３】Σ｛（ＲＸＩ＊ＰＮＳ）＾２＋（ＲＸＱ＊
ＰＮＳ）＾２｝
パスサーチ時はＩ成分ベースバンド受信データ４１とＱ
成分ベースバンド受信データ４２はサーチ部１０に入力
され、それぞれマッチドフィルタ１０１、１０２に入力
される。マッチドフィルタ１０１ではＩ成分ベースバン
ド受信データ４１と拡散符号発生器１０３から出力され
るパスサーチ用拡散符号ＰＮＩ１１２とＰＮＱ１１３と
の相関がとられ、（ＲＸＩ＊ＰＮＩ）の相関値１０６と
（ＲＸＩ＊ＰＮＱ）の相関値１０７が得られる。Σ {(RXI * PNS) ^ 2 + (RXQ *
PNS) ^ 2} I component baseband received data 41 and Q at the time of path search
The component baseband received data 42 is input to the search unit 10 and input to the matched filters 101 and 102, respectively. In the matched filter 101, the I component baseband received data 41 and the path search spreading code PNI112 and PNQ113 output from the spreading code generator 103 are correlated, and the correlation value 106 of (RXI * PNI) and (RXI * PNQ). ) Correlation value 107 is obtained.
【００２４】また、マッチドフィルタ１０２ではＱ成分
ベースバンド受信データ４２と拡散符号発生器１０３か
ら出力されるパスサーチ用拡散符号ＰＮＩ１１２とＰＮ
Ｑ１１３との相関がとられ、（ＲＸＱ＊ＰＮＩ）の相関
値１０９と（ＲＸＱ＊ＰＮＱ）の相関値１１０が得られ
る。パスサーチ時は相関値１０６、１０７、１０９、１
１０が累算器１０４に入力され、累算器１０４に入力さ
れにより数２の演算がなされ、パスサーチに必要な結果
が得られる。累算器１０４の出力７１はシーケンサにお
いて所定の手順に従いパスサーチ処理が行われる。In the matched filter 102, the Q component baseband received data 42 and the path search spreading codes PNI 112 and PN output from the spreading code generator 103.
The correlation with Q113 is obtained, and the correlation value 109 of (RXQ * PNI) and the correlation value 110 of (RXQ * PNQ) are obtained. Correlation values 106, 107, 109, 1 during path search
10 is input to the accumulator 104, and is input to the accumulator 104 to perform the operation of the equation 2 to obtain the result required for the path search. The output 71 of the accumulator 104 is subjected to path search processing in a sequencer according to a predetermined procedure.
【００２５】
Σ｛（ＲＸＩ＊ＰＮＩ）＋（ＲＸＱ＊ＰＮＱ）｝＾２
＋Σ｛（ＲＸＱ＊ＰＮＩ）−（ＲＸＩ＊ＰＮＱ）｝＾２
次に図３を用いてマッチドフィルタ１０１の詳細な説明
を行う。マッチドフィルタ１０１は、シフトレジスタ１
００１、セレクタ回路１００２、１００３、１００４、
１００５、１６ｔａｐ積算器１００６、１００７、１０
０８、１００９、加算器１０１０、１０１１、１０１
２、セレクタ回路１０１３、１０１４により構成され
る。なお、図３のマッチドフィルタはセルサーチ時で最
大６４ｔａｐ分の相関値、パスサーチ時で最大３２ｔａ
ｐ分の相関値を出力する構成となっている。Σ {(RXI * PNI) + (RXQ * PNQ)} ^ 2 + Σ {(RXQ * PNI) − (RXI * PNQ)} ^ 2 Next, a detailed description of the matched filter 101 will be given with reference to FIG. To do. The matched filter 101 is the shift register 1
001, selector circuits 1002, 1003, 1004,
1005, 16 tap integrators 1006, 1007, 10
08, 1009, adders 1010, 1011, 101
2 and selector circuits 1013 and 1014. The matched filter of FIG. 3 has a maximum correlation value of 64 taps during cell search and a maximum of 32 taps during path search.
It is configured to output a correlation value for p.
【００２６】まず、セルサーチ時におけるマッチドフィ
ルタの動作を説明する。Ｉ成分ベースバンド受信データ
４１はシフトレジスタ１００１に入力され、逐次保持さ
れていく。シフトレジスタ１００１に保持された受信デ
ータはセレクタ１００２、１００３、１００４、１００
５に入力され、１６ｔａｐ積算器１００６、１００７、
１００８、１００９に必要な受信データが選択される。First, the operation of the matched filter at the time of cell search will be described. The I component baseband received data 41 is input to the shift register 1001 and is sequentially held. The received data held in the shift register 1001 is the selectors 1002, 1003, 1004, 100.
5 taps, 16 tap integrators 1006, 1007,
Received data required for 1008 and 1009 are selected.
【００２７】セレクタ１００２ではシフトレジスタ１０
０１に保持された受信データＤ〔０，１，２，…，１２
４，１２６〕の中からＤ〔０，２，４，…，２８，３
０〕の１６種類を選択し受信データ１０１５となる。同
じようにセレクタ１００３ではシフトレジスタ１００１
に保持された受信データＤ〔０，１，２，…，１２４，
１２６〕の中からＤ〔３２，３４，３６，…，６０，６
２〕の１６種類を選択し受信データ１０１６となる。セ
レクタ１００４ではシフトレジスタ１００１に保持され
た受信データＤ〔０，１，２，…，１２４，１２６〕の
中からＤ〔６４，６６，６８，…，９２，９４〕の１６
種類を選択し受信データ１０１７となる。セレクタ１０
０４ではシフトレジスタ１００１に保持された受信デー
タＤ〔０，１，２，…，１２４，１２６〕の中からＤ
〔９６，９８，１００，…，１２４，１２６〕の１６種
類を選択し受信データ１０１８となる。In the selector 1002, the shift register 10
Received data D [0, 1, 2, ..., 12 held in 01
4,126] out of D [0,2,4, ..., 28,3
0] is selected and the received data 1015 is obtained. Similarly, in the selector 1003, the shift register 1001
Received data D [0, 1, 2, ..., 124,
126] from D [32, 34, 36, ..., 60, 6
2] is selected and the received data 1016 is obtained. In the selector 1004, 16 of D [64, 66, 68, ..., 92, 94] out of the received data D [0, 1, 2, ...
The type is selected and becomes the reception data 1017. Selector 10
In 04, D out of the received data D [0, 1, 2, ..., 124, 126] held in the shift register 1001.
16 types of [96, 98, 100, ..., 124, 126] are selected to form the reception data 1018.
【００２８】一方、拡散符号発生器１０３から出力され
た６４ｂｉｔのセルサーチ用拡散符号ＰＮＳ１１１はＰ
ＮＳ〔０，１，２，…，３０，３１〕がセレクタ１０１
３へ入力され、ＰＮＳ〔３２，３３，…，６２，６３〕
がセレクタ１０１４へ入力される。セルサーチ時はセレ
クタ１０１３においてＰＮＳ〔０，１，２，…，３０，
３１〕が選択され、１６ｔａｐ積算器１００６へはＰＮ
Ｓ〔０，１，…，１４，１５〕が入力され、１６ｔａｐ
積算器１００７へはＰＮＳ〔１６，１７，…，３０，３
１〕が入力される。また、セレクタ１０１４においては
ＰＮＳ〔３２，３３，３４，…，６２，６３〕が選択さ
れ、１６ｔａｐ積算器１００８へはＰＮＳ〔３２，３
３，…，４６，４７〕が入力され、１６ｔａｐ積算器１
００９へはＰＮＳ〔４８，４９，…，６２，６３〕が入
力される。On the other hand, the 64-bit cell search spreading code PNS111 output from the spreading code generator 103 is P
NS [0, 1, 2, ..., 30, 31] is the selector 101
3 is input to PNS [32, 33, ..., 62, 63]
Is input to the selector 1014. At the time of cell search, PNS [0, 1, 2, ..., 30,
31] is selected, and PN is input to the 16 tap integrator 1006.
S [0,1, ..., 14,15] is input and 16 taps
PNS [16, 17, ...
1] is input. Further, PNS [32, 33, 34, ..., 62, 63] is selected in the selector 1014, and PNS [32, 3] is supplied to the 16 tap integrator 1008.
3, ..., 46, 47] is input, and 16 tap integrator 1 is input.
PNS [48, 49, ..., 62, 63] is input to 009.
【００２９】１６ｔａｐ積算器１００６、１００７、１
００８、１００９では４ｂｉｔ×１６の受信データと１
６ｃｈｉｐの拡散符号との積算処理がそれぞれ行われ
る。16 tap integrators 1006, 1007, 1
In 008 and 1009, received data of 4 bits × 16 and 1
Integration processing with a 6-chip spreading code is performed.
【００３０】図４に１６ｔａｐ積算器の構成を示す。１
６ｔａｐ積算器は４ｂｉｔ乗算器１００６ａ、５ｂｉｔ
１６入力加算器１００６ｂにより構成される。FIG. 4 shows the configuration of the 16 tap integrator. 1
6 tap integrator is a 4 bit multiplier 1006a, 5 bit
It is composed of a 16-input adder 1006b.
【００３１】１６ｔａｐ積算器では受信データ１０１５
と拡散符号１０１９との積算処理を行う。４ｂｉｔ×１
６の受信データ１０１５と１ｂｉｔ×１６の拡散符号を
それぞれ乗算器１００６ａを用いて乗算し、５ｂｉｔ×
１６の乗算結果が得られる。５ｂｉｔ×１６の乗算結果
は加算器１００６ｂにそれぞれ入力され全ての総和がと
られることにより積算結果が得られる。In the 16 tap integrator, received data 1015
And spread code 1019 are integrated. 4 bits x 1
The received data 1015 of 6 and the spreading code of 1 bit × 16 are respectively multiplied by the multiplier 1006a to obtain 5 bits ×
16 multiplication results are obtained. The multiplication result of 5 bits × 16 is input to the adder 1006b and the sum of all is taken to obtain the integration result.
【００３２】図３の説明に戻り、１６ｔａｐ積算器１０
０６の積算出力と１６ｔａｐ積算器１００７の積算出力
は加算器１０１１により加算され１０ｂｉｔの相関値１
０６が得られる。同じく、１６ｔａｐ積算器１００８の
積算出力と１６ｔａｐ積算器１００９の積算出力は加算
器１０１１により加算され１０ｂｉｔの相関値１０７が
得られる。セルサーチ時は相関値１０６と相関値１０７
とが加算器１０１０により加算され、（ＲＸＩ＊ＰＮ
Ｓ）の相関値１０５が６４タップ分得られる。マッチド
フィルタ１０２についてもマッチドフィルタ１０１と同
様の処理がＱ成分ベースバンド受信データ４２について
なされ、（ＲＸＱ＊ＰＮＳ）の相関値１０８が６４タッ
プ分得られる。Returning to the description of FIG. 3, the 16-tap integrator 10
The integrated output of 06 and the integrated output of 16 tap integrator 1007 are added by adder 1011 and correlation value 1 of 10 bits is added.
06 is obtained. Similarly, the integrated output of the 16 tap integrator 1008 and the integrated output of the 16 tap integrator 1009 are added by the adder 1011 to obtain a 10-bit correlation value 107. Correlation value 106 and correlation value 107 during cell search
And are added by the adder 1010, and (RXI * PN
The correlation value 105 of S) is obtained for 64 taps. The matched filter 102 also performs the same processing as the matched filter 101 on the Q component baseband received data 42, and obtains a correlation value 108 of (RXQ * PNS) for 64 taps.
【００３３】３ＧＰＰ（Ｗ−ＣＤＭＡ）において１ｓｔ
サーチで使用するＰＳＣＨの符号は２５６ｃｈｉｐ長の
符号長を持つ。従って、マッチドフィルタは２５６ｔａ
ｐ分の相関値が必要となるが、本発明ではタップ係数を
切替えて相関値の累積を求めることにより回路規模の増
大を招くことなく２５６ｔａｐ分の相関値を得ることが
できる。1st in 3GPP (W-CDMA)
The PSCH code used in the search has a code length of 256 chips. Therefore, the matched filter is 256ta
Although a correlation value for p is required, in the present invention, the correlation value for 256 taps can be obtained without switching the circuit scale by switching the tap coefficient to obtain the cumulative correlation value.
【００３４】図５のタイミングチャートを用いて、タッ
プ係数を切替えて相関値の累積を求める方法を説明す
る。図５に示す１シンボル＝２５６ｃｈｉｐ期間におい
て、先頭１／４シンボル期間（６４ｃｈｉｐ期間）はタ
ップ係数をＴａｐA method of finding the cumulative correlation value by switching the tap coefficient will be described with reference to the timing chart of FIG. In the 1 symbol = 256 chip period shown in FIG. 5, tap coefficients are tapped in the first ¼ symbol period (64 chip periods).
〔０〕からＴａｐ〔６３〕の６４ｔａ
ｐを設定し、６４ｔａｐ分の相関値を得る。次の１／４
シンボル期間においてはタップ係数をＴａｐ〔６４〕か
らＴａｐ〔１２７〕の６４ｔａｐを設定し６４ｔａｐ分
の相関値を得る。同じように次の１／４シンボル期間に
おいてはタップ係数をＴａｐ〔１２８〕からＴａｐ〔１
９１〕の６４ｔａｐを設定し６４ｔａｐ分の相関値を得
る。続いてＴａｐ〔１９２〕からＴａｐ〔２５５〕の６
４ｔａｐを設定し６４ｔａｐ分の相関値をそれぞれ得
る。それぞれの相関値は６４ｔａｐ分の相関値を保持す
る機能を所有した累算器１０４により累積相関値が得ら
れ、２５６ｔａｐ分の相関値を得ることができる。以上
により１シンボル期間中に２５６ｔａｐ相関値を６４ｃ
ｈｉｐ時間にわたり求めることができる。64ta from [0] to Tap [63]
p is set and a correlation value for 64 taps is obtained. Next 1/4
In the symbol period, the tap coefficient is set to 64 taps from Tap [64] to Tap [127] to obtain a correlation value for 64 taps. Similarly, in the next quarter symbol period, tap coefficients are changed from Tap [128] to Tap [1
91] is set to obtain 64 taps and a correlation value for 64 taps is obtained. Then, from Tap [192] to Tap [255], 6
4 taps are set to obtain correlation values for 64 taps. The cumulative correlation value of each correlation value is obtained by the accumulator 104 having the function of holding the correlation value of 64 taps, and the correlation value of 256 taps can be obtained. As a result, the 256 tap correlation value is 64c during one symbol period.
It can be determined over the hip time.
【００３５】タップ係数を切替えながら２５６ｔａｐ相
関値を１ｓｌｏｔ＝２５６０ｃｈｉｐ時間にわたり求
め、相関値が最大となるタイミングを検出することによ
りスロットタイミングが得られる。１ｓｔサーチで得ら
れたスロットタイミングを用いて２ｎｄサーチ部１１４
によりフレームタイミング抽出およびコードグループ識
別を行い、３ｒｄサーチ部１１５においてスクランブリ
ングコード同定を行うことによりセルサーチ処理を終え
る。The slot timing can be obtained by obtaining the 256 tap correlation value over 1 slot = 2560 chip time while switching the tap coefficient and detecting the timing at which the correlation value becomes maximum. The 2nd search unit 114 is used by using the slot timing obtained in the 1st search.
Then, frame timing extraction and code group identification are performed by the 3rd search section 115, and scrambling code identification is performed by the 3rd search section 115, thereby ending the cell search processing.
【００３６】次にパスサーチ時におけるマッチドフィル
タの動作を図３を用いて説明する。Ｉ成分ベースバンド
受信データ４１はシフトレジスタ１００１に入力され逐
次保持されていく。シフトレジスタ１００１に保持され
た受信データはセレクタ１００２、１００３、１００
４、１００５に入力され、１６ｔａｐ積算器１００６、
１００７、１００８、１００９に必要な受信データが選
択される。セレクタ１００２ではシフトレジスタ１００
１に保持された受信データＤ〔０，１，２，…，１２
４，１２６〕の中からＤ〔０，２，４，…，２８，３
０〕の１６種類を選択し受信データ１０１５となる。同
じようにセレクタ１００３ではシフトレジスタ１００１
に保持された受信データＤ〔０，１，２，…，１２４，
１２６〕の中からＤ〔３２，３４，３６，…，６０，６
２〕の１６種類を選択し受信データ１０１６となる。セ
レクタ１００４ではシフトレジスタ１００１に保持され
た受信データＤ〔０，１，２，…，１２４，１２６〕の
中からＤ〔０，２，４，…，２８，３０〕の１６種類を
選択し受信データ１０１７となる。セレクタ１００４で
はシフトレジスタ１００１に保持された受信データＤ
〔０，１，２，…，１２４，１２６〕の中からＤ〔３
２，３４，３６，…，６０，６２〕の１６種類を選択し
受信データ１０１８となる。Next, the operation of the matched filter at the time of path search will be described with reference to FIG. The I component baseband received data 41 is input to the shift register 1001 and is sequentially held. The received data held in the shift register 1001 is the selectors 1002, 1003, 100.
4, 1005, 16 tap integrator 1006,
Received data required for 1007, 1008, and 1009 are selected. In the selector 1002, the shift register 100
Received data D [0, 1, 2, ..., 12 held in 1
4,126] out of D [0,2,4, ..., 28,3
0] is selected and the received data 1015 is obtained. Similarly, in the selector 1003, the shift register 1001
Received data D [0, 1, 2, ..., 124,
126] from D [32, 34, 36, ..., 60, 6
2] is selected and the received data 1016 is obtained. The selector 1004 selects and receives 16 types of D [0, 2, 4, ..., 28, 30] from the received data D [0, 1, 2, ..., 124, 126] held in the shift register 1001. It becomes the data 1017. In the selector 1004, the received data D held in the shift register 1001
From [0, 1, 2, ..., 124, 126], D [3
2, 34, 36, ..., 60, 62] are selected as the reception data 1018.
【００３７】一方、拡散符号発生器１０３から出力され
た３２ｂｉｔのパスサーチ用拡散符号ＰＮＩ１１２はセ
レクタ１０１３へ入力され、３２ｂｉｔのパスサーチ用
拡散符号ＰＮＱ１１３はセレクタ１０１４へ入力され
る。パスサーチ時はセレクタ１０１３においてＰＮＩ
〔０，１，２，…，３０，３１〕が選択され、１６ｔａ
ｐ積算器１００６へＰＮＩ〔０，１，…，１４，１５〕
が入力され、１６ｔａｐ積算器１００７へはＰＮＩ〔１
６，１７，…，３０，３１〕が入力される。また、セレ
クタ１０１４においてはＰＮＱ〔０，１，２，…，３
０，３１〕が選択され、１６ｔａｐ積算器１００８へは
ＰＮＱ〔０，１，…，１４，１５〕が入力され、１６ｔ
ａｐ積算器１００９へはＰＮＱ〔１６，１７，…，３
０，３１〕が入力される。On the other hand, the 32-bit path search spreading code PNI112 output from the spreading code generator 103 is input to the selector 1013, and the 32-bit path search spreading code PNQ113 is input to the selector 1014. During path search, the PNI is selected by the selector 1013.
[0, 1, 2, ..., 30, 31] is selected and 16 ta
p integrator 1006 to PNI [0, 1, ..., 14, 15]
Is input to the 16 tap integrator 1007, and PNI [1
6, 17, ..., 30, 31] are input. Further, in the selector 1014, PNQ [0, 1, 2, ..., 3
0,31] is selected, PNQ [0,1, ..., 14,15] is input to the 16 tap integrator 1008, and 16 t
to the ap accumulator 1009, PNQ [16, 17, ..., 3
0, 31] is input.
【００３８】１６ｔａｐ積算器１００６、１００７、１
００８、１００９では４ｂｉｔ×１６の受信データと１
６ｃｈｉｐの拡散符号との積算処理がそれぞれ行われ
る。16 tap integrators 1006, 1007, 1
In 008 and 1009, received data of 4 bits × 16 and 1
Integration processing with a 6-chip spreading code is performed.
【００３９】１６ｔａｐ積算器１００６の積算出力と１
６ｔａｐ積算器１００７の積算出力は加算器１０１１に
より加算され１０ｂｉｔの相関値１０６が得られる。１
６ｔａｐ積算器１００８の積算出力と１６ｔａｐ積算器
１００９の積算出力は加算器１０１１により加算され１
０ｂｉｔの相関値１０７が得られる。The integrated output of the 16 tap integrator 1006 and 1
The integrated output of the 6 tap integrator 1007 is added by the adder 1011 to obtain the correlation value 106 of 10 bits. 1
The integrated output of the 6 tap integrator 1008 and the integrated output of the 16 tap integrator 1009 are added by the adder 1011 to obtain 1
A correlation value 107 of 0 bit is obtained.
【００４０】以上によりパスサーチ時はマッチドフィル
タ１０１の出力として（ＲＸＩ＊ＰＮＩ）の相関値１０
６と（ＲＸＩ＊ＰＮＱ）の相関値１０７がそれぞれ３２
ｔａｐ分出力される。マッチドフィルタ１０２について
もマッチドフィルタ１０１と同様な処理がＱ成分ベース
バンド受信データ４２についてなされ、マッチドフィル
タ１０２の出力として（ＲＸＱ＊ＰＮＩ）の相関値１０
９と（ＲＸＱ＊ＰＮＱ）の相関値１１０がそれぞれ３２
ｔａｐ分出力される。As described above, the correlation value 10 of (RXI * PNI) is output as the output of the matched filter 101 during the path search.
6 and the correlation value 107 of (RXI * PNQ) is 32, respectively.
Output for tap. The matched filter 102 also performs the same processing as the matched filter 101 on the Q component baseband received data 42, and outputs (RXQ * PNI) correlation value 10 as the output of the matched filter 102.
9 and the correlation value 110 of (RXQ * PNQ) is 32, respectively.
Output for tap.
【００４１】３ＧＰＰ（Ｗ−ＣＤＭＡ）のパスサーチに
使用するＣＰＩＣＨは拡散比が２５６倍である。従っ
て、マッチドフィルタは２５６ｔａｐ分の相関値が必要
となるが、本発明ではセルサーチと同様にタップ係数を
切替えて相関値の累積を求めることにより回路規模の増
大を招くことなく２５６ｔａｐ分の相関値を得ることが
できる。The CPICH used for the path search of 3GPP (W-CDMA) has a spreading ratio of 256 times. Therefore, the matched filter needs a correlation value of 256 taps, but in the present invention, the correlation value of 256 taps is not increased by increasing the circuit scale by switching the tap coefficient and calculating the accumulation of correlation values as in the cell search. Can be obtained.
【００４２】図６のタイミングチャートを用いて、タッ
プ係数を切替えて相関値の累積を求める方法を説明す
る。図６に示す１シンボル＝２５６ｃｈｉｐ期間におい
て、先頭１／８シンボル期間（３２ｃｈｉｐ期間）はタ
ップ係数をＴａｐA method of switching the tap coefficient to obtain the cumulative correlation value will be described with reference to the timing chart of FIG. In the 1 symbol = 256 chip period shown in FIG. 6, the tap coefficient is Tap during the first 1/8 symbol period (32 chip period).
〔０〕からＴａｐ〔３１〕の３２ｔａ
ｐを設定し、３２ｔａｐ分の相関値を得る。次の１／８
シンボル期間においてはタップ係数をＴａｐ〔３２〕か
らＴａｐ〔６３〕の３２ｔａｐを設定し、３２ｔａｐ分
の相関値を得る。同じようにタップ係数をＴａｐ〔６
４〕からＴａｐ〔９５〕、Ｔａｐ〔９６〕からＴａｐ
〔１２７〕、Ｔａｐ〔１２８〕からＴａｐ〔１５９〕、
Ｔａｐ〔１６０〕からＴａｐ〔１９１〕、Ｔａｐ〔１９
２〕からＴａｐ〔２２３〕、Ｔａｐ〔２２４〕からＴａ
ｐ〔２５５〕と切替えて、それぞれ３２ｔａｐ分の相関
値を得る。32ta from [0] to Tap [31]
By setting p, a correlation value for 32 taps is obtained. Next 1/8
In the symbol period, the tap coefficient is set to 32 taps from Tap [32] to Tap [63] to obtain a correlation value for 32 taps. Similarly, tap coefficient
4] to Tap [95], Tap [96] to Tap
[127], Tap [128] to Tap [159],
Tap [160] to Tap [191], Tap [19]
2] to Tap [223], Tap [224] to Ta
By switching to p [255], a correlation value of 32 taps is obtained.
【００４３】それぞれの相関値は累算器１０４により累
積相関値が得られ、２５６ｔａｐ分の相関値を得ること
ができる。以上により１シンボル期間中に２５６ｔａｐ
相関値を３２ｃｈｉｐ時間にわたり求めることができ
る。The cumulative correlation value of each correlation value is obtained by the accumulator 104, and the correlation value of 256 taps can be obtained. Due to the above, 256 taps in one symbol period
Correlation values can be determined over 32 chip times.
【００４４】通常、パスサーチはサーチ範囲が３２ｃｈ
ｉｐ程度あれば十分であるが、それ以上必要な場合はセ
ルサーチと同様にタップ係数を切替えながら相関をとる
ことによりサーチ範囲は拡大できる。Normally, the path search has a search range of 32 ch.
About ip is sufficient, but if more is needed, the search range can be expanded by taking the correlation while switching the tap coefficient as in the cell search.
【００４５】さらに図３に示すマッチドフィルタ１０１
はタップ数を削減できる工夫もなされている。パスサー
チ時においてサーチ範囲が１６ｃｈｉｐでよい場合は、
１６ｔａｐ積算器１００６、１００７、１００８、１０
０９のうち１００６と１００８の２つのみ使用するとよ
い。Furthermore, the matched filter 101 shown in FIG.
Has been devised to reduce the number of taps. If the search range is 16 chips during the path search,
16 tap integrators 1006, 1007, 1008, 10
Only two of 1006 and 1008 out of 09 should be used.
【００４６】セレクタ１００２ではシフトレジスタ１０
０１に保持された受信データＤ〔０，１，２，…，１２
４，１２６〕の中からＤ〔０，２，４，…，２８，３
０〕の１６種類を選択し、セレクタ１００４ではシフト
レジスタ１００１に保持された受信データＤ〔０，１，
２，…，１２４，１２６〕の中からＤ〔０，２，４，
…，２８，３０〕の１６種類を選択し使用する。セレク
タ１００３、１００５は使用しない。In the selector 1002, the shift register 10
Received data D [0, 1, 2, ..., 12 held in 01
4,126] out of D [0,2,4, ..., 28,3
16] of the received data D [0, 1, held in the shift register 1001 by the selector 1004.
2, ..., 124,126] out of D [0,2,4,
, 28, 30] are selected and used. The selectors 1003 and 1005 are not used.
【００４７】拡散符号発生器１０３から出力されるパス
サーチ用拡散符号１１２、１１３は１６ｂｉｔ出力（３
２ｂｉｔのうち前半１６ｂｉｔ〔１５：０〕を使用）と
し、セレクタ１０１３、１０１４へ入力される。パスサ
ーチ時はセレクタ１０１３においてＰＮＩが選択され、
１６ｔａｐ積算器１００６へはＰＮＩ〔０，１，…，１
４，１５〕が入力される。また、セレクタ１０１４にお
いてはＰＮＱが選択され、１６ｔａｐ積算器１００８へ
はＰＮＱ〔０，１，…，１４，１５〕が入力される。The spreading codes for path search 112, 113 output from the spreading code generator 103 are 16-bit output (3
Of the 2 bits, the first half 16 bits [15: 0] is used) and is input to the selectors 1013 and 1014. At the time of path search, PNI is selected by the selector 1013,
PNI [0, 1, ..., 1 to the 16 tap integrator 1006
4, 15] is input. Further, PNQ is selected in the selector 1014, and PNQ [0, 1, ..., 14, 15] is input to the 16 tap integrator 1008.
【００４８】１６ｔａｐ積算器１００６、１００８では
４ｂｉｔ×１６の受信データと１６ｃｈｉｐの拡散符号
との積算処理がそれぞれ行われ、マッチドフィルタ１０
１の出力として（ＲＸＩ＊ＰＮＩ）の相関値１０６と
（ＲＸＩ＊ＰＮＱ）の相関値１０７がそれぞれ１６ｔａ
ｐ分出力される。マッチドフィルタ１０２についてもマ
ッチドフィルタ１０１と同様な処理がＱ成分ベースバン
ド受信データ４２についてなされ、マッチドフィルタ１
０２の出力として（ＲＸＱ＊ＰＮＩ）の相関値１０９と
（ＲＸＱ＊ＰＮＱ）の相関値１１０がそれぞれ１６ｔａ
ｐ分出力される。In the 16-tap integrators 1006 and 1008, the 4-bit × 16 received data and the 16-chip spreading code are integrated, and the matched filter 10
As an output of 1, the correlation value 106 of (RXI * PNI) and the correlation value 107 of (RXI * PNQ) are 16 ta respectively.
Output for p minutes. The matched filter 102 also performs the same processing as the matched filter 101 on the Q component baseband received data 42.
As the output of 02, the correlation value 109 of (RXQ * PNI) and the correlation value 110 of (RXQ * PNQ) are 16 ta respectively.
Output for p minutes.
【００４９】図６において、タップ係数を１／８シンボ
ル期間（３２ｃｈｉｐ期間）で切替えていたものを１／
１６シンボル期間（１６ｃｈｉｐ期間）で切替えて累積
をとることにより１６ｔａｐ分、すなわちサーチ範囲１
６ｃｈｉｐの相関値を得ることができる。In FIG. 6, the tap coefficient switched in 1/8 symbol period (32 chip period) is 1 /
By switching over 16 symbol periods (16 chip periods) and accumulating, 16 taps, that is, search range 1
A correlation value of 6 chips can be obtained.
【００５０】サーチ範囲が１６ｃｈｉｐの場合は使用し
ない１６ｔａｐ積算器１００７、１００９、セレクタ１
００３、１００５のクロック供給を停止させることによ
り低消費電力化が期待できる。Not used when the search range is 16 chips 16 tap accumulators 1007 and 1009, selector 1
Lower power consumption can be expected by stopping the clock supply of 003 and 1005.
【００５１】なお、以上の説明では受信データをシフト
しながら符号と相関をとるデータシフト型マッチドフィ
ルタについて説明したが、ＰＮ符号をシフトしながら相
関をとるＰＮシフト型マッチドフィルタに適用すること
も容易である。ＰＮシフト型マッチドフィルタについて
は特開平１０−２８５０７９に詳細が記載されている。In the above description, the data shift type matched filter that correlates with the code while shifting the received data has been described, but it can be easily applied to a PN shift type matched filter that correlates while shifting the PN code. Is. Details of the PN shift type matched filter are described in JP-A-10-285079.
【００５２】[0052]
【発明の効果】下り回線に含まれるセルサーチ用チャネ
ルとパスサーチ用チャネルとで変調方式が異なるＣＤＭ
Ａセルラシステムにおいて、セルサーチに用いるマッチ
ドフィルタとパスサーチに用いるマッチドフィルタを時
分割で共用する際に、マッチドフィルタのタップ長をセ
ルサーチ時とパスサーチ時で異ならせてサーチすること
により、マッチドフィルタの回路を有効活用することが
できる。また、パスサーチ時には用途に応じてサーチ範
囲を可変させることにより低消費電力化が期待できる。EFFECT OF THE INVENTION CDM in which the modulation system is different between the cell search channel and the path search channel included in the downlink.
In the A cellular system, when the matched filter used for the cell search and the matched filter used for the path search are shared in a time division manner, the tap length of the matched filter is made different between the cell search and the path search to perform the matched search. The filter circuit can be effectively used. In addition, low power consumption can be expected by varying the search range according to the application during path search.
【図１】本発明の一実施例のＣＤＭＡ移動局ベースバン
ド受信回路のブロック図。FIG. 1 is a block diagram of a CDMA mobile station baseband receiving circuit according to an embodiment of the present invention.
【図２】本発明の一実施例におけるサーチ部を示したブ
ロック図。FIG. 2 is a block diagram showing a search unit according to an embodiment of the present invention.
【図３】本発明の一実施例におけるマッチドフィルタを
示したブロック図。FIG. 3 is a block diagram showing a matched filter according to an embodiment of the present invention.
【図４】１６ｔａｐ積算器を詳しく示したブロック図。FIG. 4 is a block diagram showing in detail a 16 tap integrator.
【図５】セルサーチ時における累積相関値の求め方を説
明するタイミングチャート。FIG. 5 is a timing chart explaining how to obtain a cumulative correlation value during cell search.
【図６】パスサーチ時における累積相関値の求め方を説
明するタイミングチャート。FIG. 6 is a timing chart explaining how to obtain a cumulative correlation value during path search.
【図７】従来例のマッチドフィルタを示したブロック
図。FIG. 7 is a block diagram showing a conventional matched filter.
１０…サーチ部、２０…アンテナ、３０…ＲＦ部、４０
…Ａ／Ｄ変換器、４１…Ｉ成分ベースバンド受信デー
タ、４２…Ｑ成分ベースバンド受信データ、５０…復調
部、５１…復調結果、６０…ＲＡＫＥ合成部、６１…受
信データ、７０…シーケンサ、７１…１ｓｔサーチ結果
（パスサーチ結果と兼用）、７２…２ｎｄサーチ結果、
７３…３ｒｄサーチ結果、７４…報告信号、７５…パス
情報、１０１…マッチドフィルタ、１０２…マッチドフ
ィルタ、１０３…拡散符号発生器、１０４…累積器、１
０５…セルサーチ用相関値、１０６…パスサーチ用相関
値、１０７…パスサーチ用相関値、１０８…セルサーチ
用相関値、１０９…パスサーチ用相関値、１１０…パス
サーチ用相関値、１１１…セルサーチ用拡散符号、１１
２…パスサーチ用拡散符号、１１３…パスサーチ用拡散
符号、１１４…２ｎｄサーチ部、１１５…３ｒｄサーチ
部、２００…マッチドフィルタ、２０１…マッチドフィ
ルタ、２０２…マッチドフィルタ、２０３…マッチドフ
ィルタ、２０４…加算器、２０５…加算器、１００１…
シフトレジスタ、１００２…セレクタ、１００３…セレ
クタ、１００４…セレクタ、１００５…セレクタ、１０
０６…１６ｔａｐ積算器、１００６ａ…乗算器、１００
６ｂ…加算器、１００７…１６ｔａｐ積算器、１００８
…１６ｔａｐ積算器、１００９…１６ｔａｐ積算器、１
０１０…加算器、１０１１…１６ｔａｐ積算器、１０１
２…加算器、１０１３…セレクタ、１０１４…セレク
タ、１０１５…受信データ、１０１６…受信データ、１
０１７…受信データ、１０１８…受信データ、１０１９
…拡散符号、２００１…フリップフロップ、２００２…
乗算器、２００３…加算器。10 ... Search unit, 20 ... Antenna, 30 ... RF unit, 40
... A / D converter, 41 ... I component baseband reception data, 42 ... Q component baseband reception data, 50 ... Demodulation section, 51 ... Demodulation result, 60 ... RAKE combining section, 61 ... Reception data, 70 ... Sequencer, 71 ... 1st search result (also used as path search result), 72 ... 2nd search result,
73 ... 3rd search result, 74 ... Report signal, 75 ... Path information, 101 ... Matched filter, 102 ... Matched filter, 103 ... Spread code generator, 104 ... Accumulator, 1
05 ... Cell search correlation value, 106 ... Path search correlation value, 107 ... Path search correlation value, 108 ... Cell search correlation value, 109 ... Path search correlation value, 110 ... Path search correlation value, 111 ... Spreading code for cell search, 11
2 ... Spread code for path search, 113 ... Spread code for path search, 114 ... 2nd search section, 115 ... 3rd search section, 200 ... Matched filter, 201 ... Matched filter, 202 ... Matched filter, 203 ... Matched filter, 204 ... Adder, 205 ... Adder, 1001 ...
Shift register, 1002 ... selector, 1003 ... selector, 1004 ... selector, 1005 ... selector, 10
06 ... 16 tap integrator, 1006a ... Multiplier, 100
6b ... adder, 1007 ... 16 tap integrator, 1008
16 tap integrator, 1009 16 tap integrator, 1
010 ... adder, 1011, ... 16 tap integrator, 101
2 ... Adder, 1013 ... Selector, 1014 ... Selector, 1015 ... Received data, 1016 ... Received data, 1
017 ... Received data, 1018 ... Received data, 1019
... Spread code, 2001 ... Flip-flop, 2002 ...
Multiplier, 2003 ... Adder.
───────────────────────────────────────────────────── フロントページの続き Ｆターム(参考） 5K022 EE02 EE33 5K067 AA02 BB03 BB04 CC04 CC10 EE02 EE10 ─────────────────────────────────────────────────── ─── Continued front page F-term (reference) 5K022 EE02 EE33 5K067 AA02 BB03 BB04 CC04 CC10 EE02 EE10
Claims (3)
とパスサーチ用チャネルとで変調方式が異なるＣＤＭＡ
セルラシステムにおいて、セルサーチに用いるマッチド
フィルタとパスサーチに用いるマッチドフィルタを時分
割で共用するにあたり、セルサーチ時とパスサーチ時と
でマッチドフィルタのタップ長を異ならせてサーチする
ことを特徴とするＣＤＭＡベースバンド受信回路。1. A CDMA in which a modulation method is different between a cell search channel and a path search channel included in a downlink.
In a cellular system, when the matched filter used for the cell search and the matched filter used for the path search are shared by time division, the tap length of the matched filter is made different between the cell search and the path search. CDMA baseband receiver circuit.
は、基地局間非同期セルラシステムであることを特徴と
するＣＤＭＡベースバンド受信回路。2. The CDMA baseband receiver circuit according to claim 1, wherein the CDMA cellular system is an inter-base station asynchronous cellular system.
は、セルサーチ用チャネルがＢＰＳＫ変調方式、パスサ
ーチ用チャネルがＢＰＳＫ変調方式以外（例えばＱＰＳ
Ｋ変調）で変調されており、セルサーチ時はパスサーチ
時におけるタップ長の２倍の長さをもってサーチするこ
とを特徴とするＣＤＭＡベースバンド受信回路。3. The CDMA cellular system according to claim 1, wherein the cell search channel is other than the BPSK modulation system and the path search channel is other than the BPSK modulation system (for example, QPS).
A CDMA baseband receiving circuit which is modulated by K modulation) and searches with a length twice as long as a tap length at the time of path search at the time of cell search.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001195685A JP3918467B2 (en) | 2001-06-28 | 2001-06-28 | CDMA baseband receiver circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001195685A JP3918467B2 (en) | 2001-06-28 | 2001-06-28 | CDMA baseband receiver circuit |
Publications (3)
| Publication Number | Publication Date |
|---|---|
| JP2003018046A true JP2003018046A (en) | 2003-01-17 |
| JP2003018046A5 JP2003018046A5 (en) | 2005-06-23 |
| JP3918467B2 JP3918467B2 (en) | 2007-05-23 |
Family
ID=19033624
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2001195685A Expired - Fee Related JP3918467B2 (en) | 2001-06-28 | 2001-06-28 | CDMA baseband receiver circuit |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP3918467B2 (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2010017763A1 (en) * | 2008-08-13 | 2010-02-18 | 中兴通讯股份有限公司 | Matched filter circuit apparatus in the base band process system of the terminal device and method thereof |
-
2001
- 2001-06-28 JP JP2001195685A patent/JP3918467B2/en not_active Expired - Fee Related
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2010017763A1 (en) * | 2008-08-13 | 2010-02-18 | 中兴通讯股份有限公司 | Matched filter circuit apparatus in the base band process system of the terminal device and method thereof |
Also Published As
| Publication number | Publication date |
|---|---|
| JP3918467B2 (en) | 2007-05-23 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US6459883B2 (en) | Generic finger architecture for spread spectrum applications | |
| JP4268712B2 (en) | Communication apparatus and method for interference suppression in DS-CDMA system | |
| KR100705064B1 (en) | Combining sub-chip resolution samples in fingers of a spread-spectrum rake receiver | |
| US20010030990A1 (en) | Reverse link correlation filter in wireless communication systems | |
| US6747969B1 (en) | Transmission gap interference measurement | |
| US7826493B2 (en) | Frequency offset correction circuit for WCDMA | |
| KR20030040547A (en) | Method and apparatus for canceling pilot interference in a cdma communication system | |
| KR20040028772A (en) | Method and apparatus for canceling pilot interference in a wireless communication system | |
| KR19980070379A (en) | Initial Synchronization Method and Receiver for DS-CDMA Base Station Asynchronous Cellular System | |
| US8472410B2 (en) | Rake receiver architecture within a WCDMA terminal | |
| WO2000069086A1 (en) | Method and apparatus for high-speed software reconfigurable code division multiple access communication | |
| US6834046B1 (en) | Acquisition of an unevenly spaced synchronization channel in a wireless communication system | |
| KR100474683B1 (en) | Apparatus for synchronization acquisition in mobile communication system and method thereof | |
| US20030039303A1 (en) | Receiver and method for CDMA despreading using rotated QPSK PN sequence | |
| US6934553B2 (en) | Receiving unit, receiving method and semiconductor device | |
| JPH11154931A (en) | Rake receiver, a mobile set of portable telephone set using it and base station | |
| JP2003018046A (en) | Cdma baseband reception circuit | |
| KR100353840B1 (en) | Apparatus and method for serearching cell in wireless communication system | |
| US7684471B2 (en) | Rake-finger combiner with reduced resource requirement | |
| JP3824482B2 (en) | CDMA receiver | |
| JP2002164812A (en) | Path search circuit for spread spectrum communication | |
| Bahl | Cell searching in WCDMA | |
| KR100354164B1 (en) | Signal Demodulation Apparatus in CDMA | |
| EP1410519A1 (en) | High performance w-cdma slot synchronisation for initial cell search with reduced hardware | |
| EP1091507B1 (en) | Wireless communication system with asymmetrically spaced synchronization channel components |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| A521 | Written amendment |
Free format text: JAPANESE INTERMEDIATE CODE: A523 Effective date: 20041006 |
|
| A621 | Written request for application examination |
Free format text: JAPANESE INTERMEDIATE CODE: A621 Effective date: 20041006 |
|
| RD01 | Notification of change of attorney |
Free format text: JAPANESE INTERMEDIATE CODE: A7421 Effective date: 20060418 |
|
| A977 | Report on retrieval |
Free format text: JAPANESE INTERMEDIATE CODE: A971007 Effective date: 20060518 |
|
| A131 | Notification of reasons for refusal |
Free format text: JAPANESE INTERMEDIATE CODE: A131 Effective date: 20061003 |
|
| A521 | Written amendment |
Free format text: JAPANESE INTERMEDIATE CODE: A523 Effective date: 20061201 |
|
| TRDD | Decision of grant or rejection written | ||
| A01 | Written decision to grant a patent or to grant a registration (utility model) |
Free format text: JAPANESE INTERMEDIATE CODE: A01 Effective date: 20070123 |
|
| A61 | First payment of annual fees (during grant procedure) |
Free format text: JAPANESE INTERMEDIATE CODE: A61 Effective date: 20070205 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20100223 Year of fee payment: 3 |
|
| S111 | Request for change of ownership or part of ownership |
Free format text: JAPANESE INTERMEDIATE CODE: R313113 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20100223 Year of fee payment: 3 |
|
| R350 | Written notification of registration of transfer |
Free format text: JAPANESE INTERMEDIATE CODE: R350 |
|
| S111 | Request for change of ownership or part of ownership |
Free format text: JAPANESE INTERMEDIATE CODE: R313111 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20100223 Year of fee payment: 3 |
|
| R371 | Transfer withdrawn |
Free format text: JAPANESE INTERMEDIATE CODE: R371 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20100223 Year of fee payment: 3 |
|
| S111 | Request for change of ownership or part of ownership |
Free format text: JAPANESE INTERMEDIATE CODE: R313111 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20100223 Year of fee payment: 3 |
|
| R350 | Written notification of registration of transfer |
Free format text: JAPANESE INTERMEDIATE CODE: R350 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20100223 Year of fee payment: 3 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20110223 Year of fee payment: 4 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20110223 Year of fee payment: 4 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20120223 Year of fee payment: 5 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20120223 Year of fee payment: 5 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20130223 Year of fee payment: 6 |
|
| FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20130223 Year of fee payment: 6 |
|
| LAPS | Cancellation because of no payment of annual fees |