JP2002044953A - Rectifier of three-phase half-voltage output type - Google Patents
Rectifier of three-phase half-voltage output typeInfo
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- JP2002044953A JP2002044953A JP2000226785A JP2000226785A JP2002044953A JP 2002044953 A JP2002044953 A JP 2002044953A JP 2000226785 A JP2000226785 A JP 2000226785A JP 2000226785 A JP2000226785 A JP 2000226785A JP 2002044953 A JP2002044953 A JP 2002044953A
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Abstract
Description
【0001】[0001]
【発明の属する技術分野】この発明は三相半電圧出力形
整流装置に関し、さらに詳細にいえば、半電圧の出力を
行うことができる三相半電圧出力形整流装置に関する。The present invention relates to a three-phase half-voltage output rectifier, and more particularly to a three-phase half-voltage output rectifier capable of outputting a half voltage.
【0002】[0002]
【従来の技術】インバータ機器の普及に伴い、従来の交
流負荷と比較して高調波発生量の大きな整流器負荷が急
増しており、高調波電流に伴う、電力系統の進相コンデ
ンサ、変圧器の過熱、焼損などの障害が顕在化しつつあ
る。2. Description of the Related Art With the spread of inverter equipment, the load of rectifiers, which generate a large amount of harmonics as compared with the conventional AC load, is increasing rapidly. Obstacles such as overheating and burnout are becoming apparent.
【0003】このため、高圧系統で受電する需要家に対
しては、受電端での総量規制となる特定需要家ガイドラ
インが適用され、業務用空調機においては6HP(20
A/相)以上のインバータ機が計算対象となっている。
また、海外については、欧州が先行して16A/相以下
の機器に対しEN61000−3−2なる規格を200
1年より適用する予定になっている。For this reason, a specific customer guideline which is a total amount regulation at a receiving end is applied to a customer who receives power in a high-voltage system, and 6HP (20
A / phase) The above inverters are to be calculated.
As for overseas, Europe has set the standard of EN61000-3-2 for equipment of 16A / phase or less.
It will be applied from one year.
【0004】このような点を考慮して、三相整流回路の
簡便な高調波低減法として、図6に示すように、交流電
源側に交流リアクトルを挿入する方法が提案されてい
る。また、特定需要家の高調波抑制法として、図9に示
すように、Y−Y、Y−Δ変圧器と2組の整流回路を用
いた12相整流法が提案されている。In consideration of the above points, as a simple method for reducing harmonics of a three-phase rectifier circuit, a method of inserting an AC reactor into an AC power supply as shown in FIG. 6 has been proposed. As a method for suppressing harmonics of a specific customer, as shown in FIG. 9, a 12-phase rectification method using a YY, Y-Δ transformer and two sets of rectification circuits has been proposed.
【0005】[0005]
【発明が解決しようとする課題】図6に示す三相整流回
路を採用する場合には十分な高調波低減を達成すること
ができない。When the three-phase rectifier circuit shown in FIG. 6 is employed, it is not possible to achieve a sufficient reduction in harmonics.
【0006】さらに説明する。A further description will be given.
【0007】図6に示す三相整流回路においては、直流
電圧降下の制約より、挿入される交流リアクトルとして
数%程度のものを採用しているが、図7中(A)に示す
ように、コンバータ入力電圧波形が6ステップであるた
め、図7中(B)の電流波形に示すように、電流歪みが
大きく、この結果、高調波低減効果が不十分になってし
まう。In the three-phase rectifier circuit shown in FIG. 6, an AC reactor of about several percent is used due to the restriction of DC voltage drop. However, as shown in FIG. Since the converter input voltage waveform has six steps, as shown in the current waveform of FIG. 7B, the current distortion is large, and as a result, the effect of reducing harmonics becomes insufficient.
【0008】ここで、入力電圧波形が6ステップになる
原理を図8に示す各部の波形を参照して説明する。Here, the principle that the input voltage waveform becomes six steps will be described with reference to the waveforms of each part shown in FIG.
【0009】直流電圧を2Eとし、直流部の中間電位を
Nで示すと、各相のダイオードは180°通電し、中間
電位Nを基準とした相電圧は図8中(A)(B)(C)
に示すような三相波形となる。また、図6中のA点の電
位VAOはVAO=VAN−VONとなる。よって、直
流中間電位Nと中性点電位Oとの電位差VONはVON
=(VAN+VBN+VCN)/3となり、相電圧波形
からの合成により図8中(D)に示す波形となる。Assuming that the DC voltage is 2E and the intermediate potential of the DC portion is indicated by N, the diodes of each phase conduct at 180 °, and the phase voltages based on the intermediate potential N are shown in FIGS. C)
A three-phase waveform as shown in FIG. The potential VAO at point A in FIG. 6 is VAO = VAN-VON. Therefore, the potential difference VON between the DC intermediate potential N and the neutral point potential O is VON
= (VAN + VBN + VCN) / 3, and the waveform shown in FIG. 8D is obtained by synthesis from the phase voltage waveform.
【0010】このため、整流回路相電圧VAOはVAO
=VAN−VONの関係より、同様に合成すると、図8
中(E)に示すように6ステップ波形となる。For this reason, the rectifier circuit phase voltage VAO becomes VAO
= VAN-VON, a similar synthesis results in FIG.
As shown in the middle (E), a six-step waveform is obtained.
【0011】また、図8中(A)(B)に示す波形よ
り、線間電圧基本波実効値VABと直流電圧2Eとの関
係はVAB=2E・61/2/πである。From the waveforms shown in FIGS. 8A and 8B, the relationship between the line voltage fundamental effective value VAB and the DC voltage 2E is VAB = 2E ・1/2 / π.
【0012】図9に示す三相整流回路12相整流動作を
行う回路)においては、位相差30°の電流Ia2{図
10中(B)参照}、Ic2{図10中(C)参照}が
変圧器のY−Δ結線により合成され、一次巻線に6ステ
ップの電流Ir2{図10中(E)参照}を形成し、変
圧器のY−Y結線による同位相電流Ir1{図10中
(D)参照}との合成により12ステップ電流Ir{図
10中(F)参照}を形成することができる。In the three-phase rectifier circuit shown in FIG. 9 for performing a 12-phase rectification operation), a current Ia2 having a phase difference of 30 ° {see FIG. 10 (B)} and Ic2 {see FIG. 10 (C)}. The Y-Δ connection of the transformer is combined to form a six-step current Ir2 {see FIG. 10E} in the primary winding, and the in-phase current Ir1 due to the Y-Y connection of the transformer {FIG. A 12-step current Ir (see (F) in FIG. 10) can be formed by combination with D).
【0013】そして、この場合には、一次巻線電流Ir
が12ステップ波形となるので5次高調波、7次高調波
を大幅に低減することができる。In this case, the primary winding current Ir
Is a 12-step waveform, so that the fifth and seventh harmonics can be greatly reduced.
【0014】しかし、全負荷容量相当の大型変圧器が必
要になり、全体としての大型化、コストアップを招いて
しまうという不都合がある。However, there is a disadvantage that a large transformer corresponding to the entire load capacity is required, resulting in an increase in size and cost as a whole.
【0015】一方、三相交流電圧は、国内、北米では2
00V系であるのに対し、欧州、オセアニアなどでは4
00V系である。したがって、例えば、国内機器を欧
州、オセアニアなどに供給する場合には、電源装置を供
給地域に合わせて専用設計することが必要になるという
不都合がある。また、上記の12相整流を採用して波形
を改善するとともに、巻線比を変えて降圧することも考
えられるが、全負荷容量相当の大型変圧器が必要になる
ので、機器単体での対処法としては現実的な方法とは言
い難い。On the other hand, the three-phase AC voltage is 2 in Japan and North America.
While it is a 00V system, in Europe and Oceania, etc.
It is a 00V system. Therefore, for example, when domestic equipment is supplied to Europe, Oceania, and the like, there is a disadvantage that the power supply device needs to be designed specifically for the supply area. It is also conceivable that the above-mentioned 12-phase rectification is used to improve the waveform and step down by changing the winding ratio. However, a large transformer equivalent to the full load capacity is required. It is hard to say that it is a realistic method.
【0016】[0016]
【発明の目的】この発明は上記の問題点に鑑みてなされ
たものであり、変圧器容量を小さくすることができ、電
源高調波を低減し、しかも三相交流電源電圧の変化に簡
単に対処することができる三相半電圧出力形整流装置を
提供することを目的としている。SUMMARY OF THE INVENTION The present invention has been made in view of the above-mentioned problems, and can reduce a transformer capacity, reduce power supply harmonics, and easily cope with a change in three-phase AC power supply voltage. It is an object of the present invention to provide a three-phase half-voltage output rectifier capable of performing the following.
【0017】[0017]
【課題を解決するための手段】請求項1の三相半電圧出
力形整流装置は、三相交流電源と第1の三相整流回路と
の間に、交流リアクトルおよび変圧器の一次巻線を直列
接続してあるとともに、この変圧器のΔ結線した二次巻
線に対して第2の三相整流回路を接続してあり、両三相
整流回路が直流側で各々並列接続されてあるものであ
る。According to a first aspect of the present invention, there is provided a three-phase half-voltage output rectifier including an AC reactor and a primary winding of a transformer between a three-phase AC power supply and a first three-phase rectifier circuit. In addition to being connected in series, a second three-phase rectifier circuit is connected to the Δ-connected secondary winding of this transformer, and both three-phase rectifier circuits are connected in parallel on the DC side, respectively. It is.
【0018】請求項2の三相半電圧出力形整流装置は、
両三相整流回路の出力端子間に1対のコンデンサを互い
に直列接続して、両コンデンサの接続点を直流中間電位
点とし、各三相整流回路の入力端子と直流中間電位点と
の間に交流スイッチを接続してあるものである。A three-phase half-voltage output rectifier according to claim 2 is
A pair of capacitors are connected in series between the output terminals of both three-phase rectifier circuits, and the connection point of both capacitors is set as the DC intermediate potential point, and between the input terminal of each three-phase rectifier circuit and the DC intermediate potential point. An AC switch is connected.
【0019】[0019]
【作用】請求項1の三相半電圧出力形整流装置であれ
ば、三相交流電源と第1の三相整流回路との間に、交流
リアクトルおよび変圧器の一次巻線を直列接続してある
とともに、この変圧器のΔ結線した二次巻線に対して第
2の三相整流回路を接続してあり、両三相整流回路が直
流側で各々並列接続されてあるので、両三相整流回路が
互いに所定の位相差で動作し、しかも、電源高調波を低
減することができるとともに、一次巻線電圧を第1の三
相整流回路とによる分圧により低減して変圧器容量を小
さくすることができる。また、基本波電圧に対する直流
電圧を、6ステップ波形を採用した場合の1/2にする
ことができるので、三相交流電源電圧の変化(増加)に
簡単に対処することができる。According to the three-phase half-voltage output rectifier of the first aspect, an AC reactor and a primary winding of a transformer are connected in series between a three-phase AC power supply and a first three-phase rectifier circuit. In addition, a second three-phase rectifier circuit is connected to the Δ-connected secondary winding of this transformer, and both three-phase rectifier circuits are connected in parallel on the DC side. The rectifier circuits operate with a predetermined phase difference from each other, and can reduce power supply harmonics, and reduce the primary winding voltage by voltage division with the first three-phase rectifier circuit to reduce the transformer capacity. can do. Further, since the DC voltage with respect to the fundamental wave voltage can be reduced to half of the case where a six-step waveform is employed, it is possible to easily deal with a change (increase) in the three-phase AC power supply voltage.
【0020】請求項2の三相半電圧出力形整流装置であ
れば、両三相整流回路の出力端子間に1対のコンデンサ
を互いに直列接続して、両コンデンサの接続点を直流中
間電位点とし、各三相整流回路の入力端子と直流中間電
位点との間に交流スイッチを接続しているので、請求項
1の作用に加え、交流スイッチの導通期間を制御するこ
とによって電源高調波を一層低減することができるとと
もに、交流リアクトルの容量を低減することができる。In the three-phase half-voltage output rectifier of the present invention, a pair of capacitors is connected in series between the output terminals of the three-phase rectifier circuits, and the connection point of the two capacitors is set to a DC intermediate potential point. Since an AC switch is connected between the input terminal of each three-phase rectifier circuit and the DC intermediate potential point, in addition to the function of claim 1, power supply harmonics can be reduced by controlling the conduction period of the AC switch. The power consumption can be further reduced, and the capacity of the AC reactor can be reduced.
【0021】[0021]
【発明の実施の形態】以下、添付図面を参照して、この
発明の三相半電圧出力形整流装置の実施の態様を詳細に
説明する。DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS Hereinafter, an embodiment of a three-phase half-voltage output rectifier according to the present invention will be described in detail with reference to the accompanying drawings.
【0022】図1はこの発明の三相半電圧出力形整流装
置の一実施態様を示す電気回路図である。FIG. 1 is an electric circuit diagram showing one embodiment of a three-phase half-voltage output type rectifier of the present invention.
【0023】この三相半電圧出力形整流装置は、三相交
流電源1の各相の出力端子に対して交流リアクトル2お
よび変圧器3の一次巻線31をこの順に直列接続し、変
圧器3の一次巻線31に対して第1の三相整流回路4を
接続している。そして、この変圧器3の二次巻線32を
Δ結線し、変圧器3の二次巻線32に対して第2の三相
整流回路5を接続している。また、両三相整流回路4、
5の正出力端子どうしを互いに接続しているとともに、
負出力端子どうしを互いに接続し、正出力端子と負出力
端子との間に、互いに等しい静電容量を有する1対の平
滑コンデンサ6を直列接続し、両平滑コンデンサ6の接
続点の電位を直流中間電位Nとしている。In this three-phase half-voltage output rectifier, an AC reactor 2 and a primary winding 31 of a transformer 3 are connected in series to an output terminal of each phase of a three-phase AC power supply 1 in this order. The first three-phase rectifier circuit 4 is connected to the primary winding 31. Then, the secondary winding 32 of the transformer 3 is Δ-connected, and the second three-phase rectifier circuit 5 is connected to the secondary winding 32 of the transformer 3. Also, both three-phase rectifier circuits 4,
5 positive output terminals are connected to each other,
The negative output terminals are connected to each other, and a pair of smoothing capacitors 6 having the same capacitance are connected in series between the positive output terminal and the negative output terminal. It is set to the intermediate potential N.
【0024】なお、一次巻線31の巻数N1と二次巻線
32の巻数N2との比をN1/N2=1/31/2として
いる。[0024] Note that the ratio of the number of turns N2 of the number of turns N1 of the primary winding 31 secondary winding 32 with N1 / N2 = 1/3 1/2 .
【0025】また、三相交流電源1の各相の出力電圧を
ea、eb、ecで表し、各相に対応する一次巻線をA
1、B1、C1で、二次巻線をA2、B2、C2でそれ
ぞれ表し、各相に対応する一次巻線電流をiA、iB、
iCで表し、各相に対応する二次巻線出力電流をia2
b2、ib2c2、ic2a2で表し、各相に対応する
第1の三相整流回路4の入力端子をa1、b1、c1で
表し、各相に対応する第2の三相整流回路5の入力端子
をa2、b2、c2で表し、第1の三相整流回路4の出
力電流をid1で、第2の三相整流回路5の出力電流を
id2で、合成出力電流をidで表し、各平滑コンデン
サ6の端子間電圧をEで表している。The output voltage of each phase of the three-phase AC power supply 1 is represented by ea, eb, ec, and the primary winding corresponding to each phase is represented by A.
1, B1 and C1, secondary windings are represented by A2, B2 and C2, respectively, and primary winding currents corresponding to each phase are iA, iB,
The secondary winding output current corresponding to each phase is represented by ia2
b2, ib2c2, ic2a2, the input terminals of the first three-phase rectifier circuit 4 corresponding to each phase are denoted by a1, b1, c1, and the input terminals of the second three-phase rectifier circuit 5 corresponding to each phase. a2, b2, c2, the output current of the first three-phase rectifier circuit 4 is denoted by id1, the output current of the second three-phase rectifier circuit 5 is denoted by id2, the combined output current is denoted by id, and each smoothing capacitor 6 Is represented by E.
【0026】次いで、各部の信号波形を示す図2を参照
して図1の三相半電圧出力形整流装置の作用を説明す
る。Next, the operation of the three-phase half-voltage output rectifier shown in FIG. 1 will be described with reference to FIG. 2 showing signal waveforms at various parts.
【0027】図2中(A)〜(F)に示すように、電源
電圧半周期において両三相整流回路のダイオードの導通
期間は180°であり、第1の三相整流回路4と第2の
三相整流回路5とは互いに30°に位相差で動作する。
ここで、変圧器3の二次側電圧を第2の三相整流回路5
の相電圧Va2N、Vb2N、Vc2N{図2中(D)
〜(F)参照}の波形を用いて合成すると、図2中
(G)〜(I)に示すように、2Eの振幅を有する線間
電圧波形Va2b2、Vb2c2、Vc2a2となる。
また、変圧器3の巻数比が1:31/2であるから、変圧
器3の一次側電圧VAa1、VBb1、VCc1{図2
中(J)〜(L)参照}は2E/31/2に降圧される。As shown in FIGS. 2A to 2F, in the half cycle of the power supply voltage, the conduction period of the diodes of the two three-phase rectifier circuits is 180 °, and the first three-phase rectifier circuit 4 and the second three-phase rectifier circuit are connected to each other. Operate with a phase difference of 30 ° from each other.
Here, the secondary voltage of the transformer 3 is converted to a second three-phase rectifier circuit 5.
Phase voltages Va2N, Vb2N, Vc2N of FIG. 2 (D)
2 (F) to (F), the line voltage waveforms Va2b2, Vb2c2, and Vc2a2 having an amplitude of 2E are obtained as shown in (G) to (I) in FIG.
In addition, since the turns ratio of the transformer 3 is 1: 3 1/2 , the primary voltages VAa1, VBb1, and VCc1 of the transformer 3 {FIG.
In (J) ~ (L) see} is lowered to 2E / 3 1/2.
【0028】直流中間電位Nと三相交流電源1の中性点
Oの電位との差VONは、6ステップの場合と同様の関
係より、 VON=(Va1N+Vb1N+Vc1N)/3 となり、第1の三相整流回路4における相電圧波形から
の合成により、図2中(M)に示す波形となる。The difference VON between the DC intermediate potential N and the potential of the neutral point O of the three-phase AC power supply 1 is VON = (Va1N + Vb1N + Vc1N) / 3 from the same relationship as in the case of six steps, and the first three-phase The waveform shown in FIG. 2 (M) is obtained by combining the rectifier circuit 4 with the phase voltage waveform.
【0029】また、三相交流電源1の中性点Oを基準と
した第1の三相整流回路4の相電圧Va1OはVa1O
=Va1N−VONより合成され{図2中(N)参
照}、これより全整流回路の相電圧VAOはVAO=V
Aa1+Va1Nの関係から求められる{図2中(O)
参照}。同様にしてB点の相電圧についても求めると
(図示せず)、A点、B点間の線間電圧VABはVAB
=VAO−VBOで求めることができ、図2中(P)に
示すように、12ステップの波形になる。したがって、
全負荷容量の約1/2の小容量変圧器を用いて良好なコ
ンバータ波形を得ることができ、電源高調波を大幅に低
減することができる。The phase voltage Va1O of the first three-phase rectifier circuit 4 based on the neutral point O of the three-phase AC power supply 1 is Va1O.
= Va1N-VON (see (N) in FIG. 2), from which the phase voltage VAO of all rectifier circuits is VAO = V
Calculated from the relationship of Aa1 + Va1N {(O) in FIG.
reference}. Similarly, when the phase voltage at point B is obtained (not shown), the line voltage VAB between points A and B is VAB
= VAO-VBO, and the waveform has 12 steps as shown in FIG. Therefore,
A good converter waveform can be obtained using a small-capacity transformer having about 1/2 of the total load capacity, and power supply harmonics can be greatly reduced.
【0030】この線間電圧波形より基本波電圧実効値V
AB1と直流電圧2Eとの関係を求めると、VAB1=
4E・61/2/πとなり、前述の6ステップの場合の関
係VAB1=2E・61/2/πと比較すると、基本波電
圧は同じであるから、直流電圧は1/2の半電圧となる
ことが分かる。From the line voltage waveform, the fundamental wave voltage effective value V
When the relationship between AB1 and the DC voltage 2E is obtained, VAB1 =
4E · 6 1/2 / π, and the fundamental voltage is the same as the relation VAB1 = 2E · 6 1/2 / π in the case of the above-described six steps. It turns out that it becomes.
【0031】次いで、変圧器3の容量について試算を行
う。Next, a trial calculation is performed on the capacity of the transformer 3.
【0032】ここで、変圧器3の一次巻線電流をISと
し、直流電圧2Eを2E=Vdとし、変圧器の一次側に
印加される電圧実効値Veffを図2の波形より求める
と、 Veff={(1/π)(Vd/31/2)2(2π/3)}1/2 =Vd・21/2/3 となる。Here, if the primary winding current of the transformer 3 is IS, the DC voltage 2E is 2E = Vd, and the effective voltage Veff applied to the primary side of the transformer is obtained from the waveform of FIG. = {(1 / π) (Vd / 3 1/2 ) 2 (2π / 3)} 1/2 = Vd · 2 1/2/3
【0033】変圧器3の二次側については、巻数比N
1:N2=1:31/2より、二次電流実効値はIS/3
1/2となり、二次電圧実効値は一次側の場合と同様に、
図2の波形より、Vd・(2/3)1/2となる。For the secondary side of the transformer 3, the turns ratio N
1: N2 = 1: 3 1/2 , the effective secondary current is IS / 3
It becomes 1/2 , and the secondary voltage effective value is the same as the case of the primary side,
From the waveform of FIG. 2, Vd · (2/3) 1/2 is obtained.
【0034】そして、変圧器平均容量(VA)tota
lを三相分の一次、二次VA容量の平均値とすると、上
述の一次、二次電流、電圧の関係より、次式で表され
る。 (VA)total=(1/2)・3{Veff・IS
+(IS/31/2)・Vd(2/3)1/2} また、直流部電流Idと変圧器3の一次巻線電流ISと
の関係は、Id1、Id2の波形から、数1となり、I
d=IS・6・21/2/πとなる。Then, the average transformer capacity (VA) tota
Assuming that 1 is the average value of the primary and secondary VA capacities for the three phases, it is expressed by the following equation from the relationship between the primary, secondary current and voltage described above. (VA) total = (1/2) · 3 {Veff · IS
+ (IS / 3 1/2 ) · Vd (2/3) 1/2 } Also, the relationship between the DC section current Id and the primary winding current IS of the transformer 3 is expressed by the following equation (1) from the waveforms of Id1 and Id2. And I
d = IS ・6.21 / 2 / π.
【0035】[0035]
【数1】 (Equation 1)
【0036】以上の関係より変圧器の平均容量を求める
と、 (VA)total=(π/6)・Vd・Id=0.5
24Vd・Id で表され、変圧器の容量を全負荷容量の50%程度に低
減することができる。換言すれば、一次巻線31は三相
交流電源1と第1の三相整流回路4と直列に接続されて
いることに起因して電圧が一次巻線31と第1の三相整
流回路4とにより分圧され、一次巻線電圧がほぼ半減す
る。一方、一次巻線電流は従来と同等である。この結
果、変圧器3の容量をほぼ半減することができる。From the above relationship, the average capacity of the transformer is obtained as follows: (VA) total = (π / 6) · Vd · Id = 0.5
It is represented by 24 Vd · Id, and the capacity of the transformer can be reduced to about 50% of the total load capacity. In other words, since the primary winding 31 is connected in series with the three-phase AC power supply 1 and the first three-phase rectifier circuit 4, the voltage is changed between the primary winding 31 and the first three-phase rectifier circuit 4. And the primary winding voltage is almost halved. On the other hand, the primary winding current is equivalent to the conventional one. As a result, the capacity of the transformer 3 can be reduced by almost half.
【0037】さらに、図2に示すように、コンバータ入
力電圧と電源相電圧との位相関係は15°である。この
ため、入力力率を1近くにするためには、三相交流電源
と三相整流回路との間に接続される交流リアクトルの容
量は、図3に示す関係(電源電圧ea、コンバータ入力
電圧VAOの関係を示すベクトル図)から、 ea/VLS=tan(π/12)=0.27 となり、30%程度の容量を選択すればよいことにな
る。Further, as shown in FIG. 2, the phase relationship between the converter input voltage and the power supply phase voltage is 15 °. For this reason, in order to make the input power factor close to 1, the capacity of the AC reactor connected between the three-phase AC power supply and the three-phase rectifier circuit has the relationship shown in FIG. 3 (power supply voltage ea, converter input voltage From the vector diagram showing the relationship of VAO), ea / VLS = tan (π / 12) = 0.27, and a capacity of about 30% may be selected.
【0038】図4はこの発明の三相半電圧出力形整流装
置の他の実施態様を示す電気回路図である。FIG. 4 is an electric circuit diagram showing another embodiment of the three-phase half-voltage output rectifier of the present invention.
【0039】この三相半電圧出力形整流装置が図1の三
相半電圧出力形整流装置と異なる点は、両三相整流回路
の各入力端子と直流中性電位Nの点との間に交流スイッ
チ7を接続した点のみである。This three-phase half-voltage output type rectifier differs from the three-phase half-voltage output type rectifier shown in FIG. 1 in that each of the three-phase rectifier circuits has an input terminal and a DC neutral potential N point. This is only the point where the AC switch 7 is connected.
【0040】この三相半電圧出力形整流装置において、
交流スイッチ7を全て開放すると図1の三相半電圧出力
形整流装置と同じ動作となる。電源電圧半周期において
両三相整流回路のダイオードの導通期間は180°であ
り、第1の三相整流回路4と第2の三相整流回路5とは
互いに30°の位相差で動作する。ここで、角整流回路
のダイオードの通電状態が変わり、相電圧がE、−Eの
間で変化するエッジにおいて、交流スイッチ7を各々1
5°期間にわたって、直流中性電位Nに導通させると、
各三相整流回路の各相電圧はE、N、−Eの3レベルの
波形が生成される。以上の相電圧波形を用いて、12ス
テップの場合と同様に波形を合成すると、図5に示すよ
うな各部の波形が得られ、24ステップの全整流回路相
電圧、全整流回路線間電圧波形が得られ、ステップ数の
倍増により、整流回路入力歪をさらに改善することがで
き、ひいては電源高調波をさらに低減することができ
る。In this three-phase half-voltage output type rectifier,
When all the AC switches 7 are opened, the operation is the same as that of the three-phase half-voltage output rectifier of FIG. In the half cycle of the power supply voltage, the conduction period of the diodes of the two three-phase rectifier circuits is 180 °, and the first three-phase rectifier circuit 4 and the second three-phase rectifier circuit 5 operate with a phase difference of 30 ° from each other. Here, at the edge where the energization state of the diode of the angular rectification circuit changes and the phase voltage changes between E and −E, the AC switches 7 are set to 1 each.
When conducting to the DC neutral potential N over a 5 ° period,
For each phase voltage of each three-phase rectifier circuit, three-level waveforms of E, N, and -E are generated. When the waveforms are synthesized using the above-described phase voltage waveforms in the same manner as in the case of 12 steps, the waveforms of the respective parts as shown in FIG. 5 are obtained, and the 24 step full rectifier circuit phase voltage and the full rectifier circuit line voltage waveform Is obtained, and by doubling the number of steps, the input distortion of the rectifier circuit can be further improved, and the power supply harmonics can be further reduced.
【0041】また、この実施態様においては、相電圧波
形に示すように、電源相電圧とコンバータ入力電圧との
位相差が7.5°に半減されるため、交流リアクトルの
容量は ea/VLS=tan(π/24)=0.13 となり、13%程度に低減することができる。In this embodiment, as shown in the phase voltage waveform, the phase difference between the power supply phase voltage and the converter input voltage is halved to 7.5 °, so that the capacity of the AC reactor is ea / VLS = tan (π / 24) = 0.13, which can be reduced to about 13%.
【0042】さらに、上記の何れの実施態様において
も、直流出力電圧の半減が可能であるから、例えば、4
00V系統の三相交流電源に対しても、200V系統仕
様の直流負荷の適用を行うことができる。Furthermore, in any of the above embodiments, the DC output voltage can be halved,
A 200 V system DC load can be applied to a 00 V system three-phase AC power supply.
【0043】[0043]
【発明の効果】請求項1の発明は、両三相整流回路を互
いに所定の位相差で動作させて電源高調波を低減するこ
とができるとともに、一次巻線電圧を第1の三相整流回
路とによる分圧により低減して変圧器容量を小さくする
ことができ、さらに、基本波電圧に対する直流電圧を、
6ステップ波形を採用した場合の1/2にすることがで
きるので、三相交流電源電圧の変化(増加)に簡単に対
処することができるという特有の効果を奏する。According to the first aspect of the present invention, the power supply harmonics can be reduced by operating both three-phase rectifier circuits with a predetermined phase difference, and the primary winding voltage can be reduced by the first three-phase rectifier circuit. And the transformer capacity can be reduced by the voltage division by
Since this can be reduced to half of the case where the six-step waveform is adopted, a unique effect is provided in that it is possible to easily cope with a change (increase) in the three-phase AC power supply voltage.
【0044】請求項2の発明は、請求項1の効果に加
え、交流スイッチの導通期間を制御することによって電
源高調波を一層低減することができるとともに、交流リ
アクトルの容量を低減することができるという特有の効
果を奏する。According to the second aspect of the present invention, in addition to the effect of the first aspect, the power supply harmonics can be further reduced by controlling the conduction period of the AC switch, and the capacity of the AC reactor can be reduced. It has a unique effect.
【図1】この発明の三相半電圧出力形整流装置の一実施
態様を示す電気回路図である。FIG. 1 is an electric circuit diagram showing an embodiment of a three-phase half-voltage output rectifier of the present invention.
【図2】図1の三相半電圧出力形整流装置の各部の信号
波形を示す図である。FIG. 2 is a diagram showing signal waveforms at various parts of the three-phase half-voltage output rectifier of FIG. 1;
【図3】電源電圧、コンバータ入力電圧のベクトル図で
ある。FIG. 3 is a vector diagram of a power supply voltage and a converter input voltage.
【図4】この発明の三相半電圧出力形整流装置の他の実
施態様を示す電気回路図である。FIG. 4 is an electric circuit diagram showing another embodiment of the three-phase half-voltage output rectifier of the present invention.
【図5】図4の三相半電圧出力形整流装置の各部の信号
波形を示す図である。5 is a diagram showing signal waveforms at various parts of the three-phase half-voltage output rectifier of FIG.
【図6】従来の三相整流回路の一例を示す電気回路図で
ある。FIG. 6 is an electric circuit diagram showing an example of a conventional three-phase rectifier circuit.
【図7】図6の三相整流回路の相電圧と相電流とを示す
図である。FIG. 7 is a diagram showing a phase voltage and a phase current of the three-phase rectifier circuit of FIG. 6;
【図8】図6の三相整流回路の各部の波形を示す図であ
る。8 is a diagram showing waveforms of respective parts of the three-phase rectifier circuit of FIG.
【図9】従来の12相整流回路を示す電気回路図であ
る。FIG. 9 is an electric circuit diagram showing a conventional 12-phase rectifier circuit.
【図10】図9の12相整流回路の各部の波形を示す図
である。FIG. 10 is a diagram showing waveforms of respective parts of the 12-phase rectifier circuit of FIG.
1 三相交流電源 2 交流リアクトル 3 変圧器 4 第1の三相整流回路 5 第2の三相整流回路 6 平滑コンデンサ 7 交流スイッチ 31 一次巻線 32 二次巻線 REFERENCE SIGNS LIST 1 three-phase AC power supply 2 AC reactor 3 transformer 4 first three-phase rectifier circuit 5 second three-phase rectifier circuit 6 smoothing capacitor 7 AC switch 31 primary winding 32 secondary winding
───────────────────────────────────────────────────── フロントページの続き Fターム(参考) 5H006 AA07 CA07 CB01 CC01 CC04 HA09 5H740 BA18 BB02 BB05 BB07 NN01 NN05 ──────────────────────────────────────────────────続 き Continued on the front page F term (reference) 5H006 AA07 CA07 CB01 CC01 CC04 HA09 5H740 BA18 BB02 BB05 BB07 NN01 NN05
Claims (2)
路(4)との間に、交流リアクトル(2)および変圧器
(3)の一次巻線(31)を直列接続してあるととも
に、この変圧器(3)のΔ結線した二次巻線(32)に
対して第2の三相整流回路(5)を接続してあり、両三
相整流回路(4)(5)が直流側で各々並列接続されて
あることを特徴とする三相半電圧出力形整流装置。An AC reactor (2) and a primary winding (31) of a transformer (3) are connected in series between a three-phase AC power supply (1) and a first three-phase rectifier circuit (4). A second three-phase rectifier circuit (5) is connected to the Δ-connected secondary winding (32) of the transformer (3). ) Are connected in parallel on the DC side, respectively.
間に1対のコンデンサ(6)を互いに直列接続して、両
コンデンサ(6)の接続点を直流中間電位点とし、各三
相整流回路(4)(5)の入力端子と直流中間電位点と
の間に交流スイッチ(7)を接続してある請求項1に記
載の三相半電圧出力形整流装置。2. A pair of capacitors (6) are connected in series between output terminals of both three-phase rectifier circuits (4) and (5), and a connection point of both capacitors (6) is set as a DC intermediate potential point. The three-phase half-voltage output rectifier according to claim 1, wherein an AC switch (7) is connected between an input terminal of each of the three-phase rectifier circuits (4) and (5) and a DC intermediate potential point.
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Cited By (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2008278713A (en) * | 2007-05-07 | 2008-11-13 | Fuji Electric Systems Co Ltd | Parallel 24-pulse rectifier circuit |
JP2008295155A (en) * | 2007-05-23 | 2008-12-04 | Shinko Electric Co Ltd | Twelve-phase rectifier circuit |
EP2523327A1 (en) * | 2011-05-11 | 2012-11-14 | Siemens Aktiengesellschaft | Frequency inverter with excess voltage protection and method for operating same |
CN112448511A (en) * | 2019-08-15 | 2021-03-05 | 比亚迪股份有限公司 | Motor and energy conversion device thereof |
RU2747554C1 (en) * | 2020-06-24 | 2021-05-06 | Федеральное государственное бюджетное образовательное учреждение высшего образования «Саратовский государственный технический университет имени Гагарина Ю.А.» | Universal dc voltage converter for multi-level voltage inverter power supply |
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CN105610309B (en) * | 2015-11-18 | 2019-01-18 | 哈尔滨工业大学(威海) | A kind of heavy-duty rectifier using DC side electric current direct injection |
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Publication number | Priority date | Publication date | Assignee | Title |
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JP2008278713A (en) * | 2007-05-07 | 2008-11-13 | Fuji Electric Systems Co Ltd | Parallel 24-pulse rectifier circuit |
JP2008295155A (en) * | 2007-05-23 | 2008-12-04 | Shinko Electric Co Ltd | Twelve-phase rectifier circuit |
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CN112448511A (en) * | 2019-08-15 | 2021-03-05 | 比亚迪股份有限公司 | Motor and energy conversion device thereof |
RU2747554C1 (en) * | 2020-06-24 | 2021-05-06 | Федеральное государственное бюджетное образовательное учреждение высшего образования «Саратовский государственный технический университет имени Гагарина Ю.А.» | Universal dc voltage converter for multi-level voltage inverter power supply |
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