EP4244966A1 - Vorrichtung zur gleichtaktarmen umrichtung von wechselspannung - Google Patents
Vorrichtung zur gleichtaktarmen umrichtung von wechselspannungInfo
- Publication number
- EP4244966A1 EP4244966A1 EP21814724.7A EP21814724A EP4244966A1 EP 4244966 A1 EP4244966 A1 EP 4244966A1 EP 21814724 A EP21814724 A EP 21814724A EP 4244966 A1 EP4244966 A1 EP 4244966A1
- Authority
- EP
- European Patent Office
- Prior art keywords
- conductor
- voltage
- phase
- switching branches
- switching
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 238000006243 chemical reaction Methods 0.000 title claims abstract description 9
- 239000004020 conductor Substances 0.000 claims abstract description 58
- 230000002457 bidirectional effect Effects 0.000 claims abstract description 32
- 229910052710 silicon Inorganic materials 0.000 claims description 3
- 238000001914 filtration Methods 0.000 claims description 2
- 229910002601 GaN Inorganic materials 0.000 description 7
- JMASRVWKEDWRBT-UHFFFAOYSA-N Gallium nitride Chemical compound [Ga]#N JMASRVWKEDWRBT-UHFFFAOYSA-N 0.000 description 7
- 239000004065 semiconductor Substances 0.000 description 7
- 230000007935 neutral effect Effects 0.000 description 6
- 230000000694 effects Effects 0.000 description 5
- 238000005516 engineering process Methods 0.000 description 5
- 239000003990 capacitor Substances 0.000 description 4
- 238000007667 floating Methods 0.000 description 4
- 239000000463 material Substances 0.000 description 3
- 238000000034 method Methods 0.000 description 3
- 230000000903 blocking effect Effects 0.000 description 2
- 230000010354 integration Effects 0.000 description 2
- XUIMIQQOPSSXEZ-UHFFFAOYSA-N Silicon Chemical compound [Si] XUIMIQQOPSSXEZ-UHFFFAOYSA-N 0.000 description 1
- 230000005540 biological transmission Effects 0.000 description 1
- 238000010276 construction Methods 0.000 description 1
- 230000001419 dependent effect Effects 0.000 description 1
- 230000007717 exclusion Effects 0.000 description 1
- 238000002955 isolation Methods 0.000 description 1
- 238000004519 manufacturing process Methods 0.000 description 1
- 230000001105 regulatory effect Effects 0.000 description 1
- 230000000717 retained effect Effects 0.000 description 1
- 230000033764 rhythmic process Effects 0.000 description 1
- 239000010703 silicon Substances 0.000 description 1
- 230000001629 suppression Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/10—Arrangements incorporating converting means for enabling loads to be operated at will from different kinds of power supplies, e.g. from ac or dc
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
- H02M1/123—Suppression of common mode voltage or current
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
- H02M1/126—Arrangements for reducing harmonics from ac input or output using passive filters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4216—Arrangements for improving power factor of AC input operating from a three-phase input voltage
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the invention relates to a device for low-common-mode conversion of AC voltage.
- DC voltages are required in many areas of technology.
- transport of electrical energy is mainly realized with AC voltage networks.
- PFC Power Factor Correction
- pulse rectifiers emulate the (almost) ideal behavior of an ohmic resistance load on the supply network side (input side/AC side). As a result, only minor mains reactions, i.e. minor current distortions and minor reactive currents, are caused. This corresponds to a high power factor.
- DC direct current
- DC-DC direct current converter stages
- inverter stages Three-phase pulse rectifiers are typically used in the high power range of around 5...100 kW and beyond.
- CM common mode
- EMC electromagnetic compatibility
- Vienna rectifier is also known from the prior art, e.g. from the article "A novel three-phase three-switch three-level pwm rectifier" by the authors J. W. Kolar and F. C. Zach, published in Proc. 28th Power Conversion Conference, PCIM '94, Jun. 28-30, 1994, pages 125-138, but this is also complex and requires three high-frequency clocked semiconductor switches and three step-up chokes on the AC voltage side, and moreover cannot be described as inherently low in common mode this switching-frequency (or: high-frequency) common-mode interference voltages at its output, which can only be sufficiently suppressed by input-side filter circuits made of large-volume passive components (chokes, capacitors).
- the topology referred to as Swiss Rectifier which, for example, from the article "SWISS rectifier - A Novel Three-Phase Buck-Type PFC Rectifier Topology for Electric Vehicle Battery Charging” by the authors TB Soeiro, T. Friedli, and JW Kolar, published in Proc . 27th Applied Power Electronics Conference and Exposition (APEC), 2012, exhibits significant switching-frequency common-mode interference voltages (CM) and, on the other hand, the Swiss rectifier works in buck mode (buck). CM share and DM share) on the net page. Proceeding from this, it is the object of the invention to specify a device for low-common-mode conversion of AC voltage which avoids one or more problems from the prior art.
- CM common-mode interference voltages
- the object is achieved by a device for low-common-mode conversion of AC voltage.
- the device has a voltage supply, with the voltage being supplied during operation via a 1-phase 2-wire AC voltage network, a 1-phase 3-wire AC voltage network or a 3-phase multi-wire AC voltage network.
- the device has three first switching branches, each first switching branch having a bidirectional switch that can be clocked at a low frequency, the outputs of the first switching branches each being switchable and being able to be routed to a first conductor, each of the inputs of the voltage supply being in a positive semi-oscillation by means of a first rectifier device is routed to a second conductor during operation, each of the inputs of the voltage supply being routed to a third conductor during operation in a negative semi-oscillation by means of a second rectifier device.
- the device also has at least two second switching branches, with each second switching branch having a switch that can be clocked at high frequency, with a first of the second switching branches being arranged between the first conductor and the second conductor, with a second of the second switching branches being arranged between the first conductor and the third Head is arranged.
- Exactly one first effective step-up inductor is arranged in the feed line of the second conductor to the first of the second switching branches.
- Exactly one second effective step-up inductor is also arranged in the supply of the third conductor to the second of the second switching branches.
- FIG. 2 shows a further schematic representation of elements according to embodiments of FIG.
- FIG. 6 shows a further schematic representation of elements according to embodiments of FIG.
- FIG. 7 shows a further schematic representation of elements according to embodiments of FIG.
- FIG. 9 shows a further schematic representation of elements according to embodiments of FIG.
- FIG. 11 shows an example curve of input voltages and the switching behavior according to FIG.
- references to standards or specifications or norms are to be understood as a reference to standards or specifications or norms which are/were applicable at the time of filing and/or - insofar as priority is claimed - also at the time of priority filing. However, this is not to be understood as a general exclusion of applicability to subsequent or superseding standards or specifications or norms.
- FIG. 1 schematically shows elements of the invention according to different embodiments.
- a device for converting AC voltage with low common mode has a voltage supply.
- a different number of inputs can be provided.
- the provision of 3 inputs El ... E3 may be sufficient for a (European) three-phase network.
- These can, for example, as shown in FIG. 4a or 4b, be routed to corresponding voltage leads El . . . E3.
- a neutral conductor N can also be routed to a further "voltage supply" E4, as shown in Figure 4a.
- one phase can be connected to an input - here El - as a voltage supply and another phase (the opposite phase) to another voltage supply on another input - here E3 - are applied, while the one "voltage supply" - here E2 - is connected to the neutral conductor.
- a special switching position can be provided for certain network types, which of course can also be designed differently in hard-wired applications (for only one network type).
- the voltage can be supplied during operation via a 1-phase 2-wire AC voltage network, a 1-phase 3-wire AC voltage network or a 3-phase multi-wire AC voltage network.
- the device also has three first switching branches, each first switching branch having a bidirectional switch SA, SB, SC that can be clocked at a low frequency.
- the bidirectional switches SA, SB, SC which can be clocked at low frequencies, is irrelevant for understanding.
- the transistor switches or technologies shown symbolically in FIG. 5a can be used.
- the three bidirectional power switches are only clocked at a low frequency, i.e. typically with 3 times the frequency of the AC voltage present in one phase, and therefore cause practically no switching losses.
- the bidirectional switches SA, SB, SC of the first switching branches can be selected from a group comprising Si-based IGBT or GaN (gallium nitride)-based transistors, in particular monolithic bidirectional GaN transistors.
- a bidirectional switch SA, SB, SC that can be clocked at a low frequency can, as shown in FIG. 5a, be constructed from several individual elements (e.g. IGBT and diodes) or monolithically.
- the outputs of the first switching branches can each be switched to a first conductor m--shown in FIGS. 1, 2, 6-10.
- each of the inputs of the voltage supply El Rectifier device Dlb, D2b, D3b is performed in a negative semi-oscillation on a third conductor n in operation.
- the device also has at least two second switching branches, each of the second switching branches having a high-frequency clockable switch SI, S2, with a first of the second switching branches - e.g. S1 - being arranged between the first conductor m and the second conductor p, and with a second of the second switching branches - e.g. S2 - is arranged between the first conductor m and the third conductor n.
- SI clockable switch
- Exactly one first effective step-up inductor Lp is arranged in the feed line of the second conductor p to the first of the second switching branches S1.
- Exactly one second effective step-up inductor Ln is also arranged in the supply of the third conductor n to the second of the second switching branches S2.
- An effective step-up choke can be constructed from a number of individual step-up chokes which are connected in parallel or in series in order to have specific electrical properties.
- the bidirectional switches SA, SB, SC of the first switching branches can be controlled during operation in such a way that an input phase voltage of the voltage supply that is the smallest in absolute terms can be switched to the first conductor m.
- the downstream DC-DC stages in the application for onboard chargers can be constructed without a transformer (non-floating), which means that losses during operation and material costs as well as weight and size can be saved during construction. That is, improved energy efficiency and cost efficiency can be provided.
- the proposed three-phase PFC topology also has a number of other advantageous properties for other areas of application.
- the devices according to the invention come with only two high-frequency clocked circuit breakers S1, S2 off. These can be clocked with comparatively low clock rates of 100 kHz. That is, in the device according to the invention, no effective step-up choke is arranged in the first conductor m.
- the devices according to the invention also manage with only two step-up chokes Lp, Ln, while most conventional circuits each require three (i.e. one high-frequency switch and one choke per mains phase).
- the devices according to the invention also work in boost operation, which leads to continuous, non-pulsating input currents and thus also minimizes the push-pull requirements (differential mode, abbreviation DM) on the line-side EMC filter.
- boost operation which leads to continuous, non-pulsating input currents and thus also minimizes the push-pull requirements (differential mode, abbreviation DM) on the line-side EMC filter.
- the push-pull component of the EMC filter can advantageously also be shifted to the DC side of the circuit.
- the two filter capacitors CF1, CF2 can fulfill this DM filter function.
- filter chokes LF1/2, drawn in the series branches p and n, on the network side of CF1, CF2 can be used to increase the filter effect.
- three filter elements are usually required on the AC side for DM suppression.
- a first inductance LI is arranged downstream of the first rectifier device Dia, D2a, D3a in the second conductor p and a second inductance L2 is arranged downstream of the second rectifier device Dlb, D2b, D3b in the third conductor n ,
- a first filter capacitance CF1 being arranged downstream of the first inductance LI towards the first conductor m and a second filter capacitance CF2 downstream of the second inductance L2 towards the first conductor m.
- a (further) EMC filter arranged on the input side can also be present. However, this can be dimensioned significantly smaller compared to previous circuit arrangements.
- the EMC filter arranged on the input side can be dimensioned in such a way that it is essentially set up for common mode filtering.
- the proposed circuit can also work in discontinuous (DCM) or discontinuous limit operation (BM or CrCM), but discontinuous operation (CCM) is to be seen as the primarily advantageous mode of operation, which requires high transmission power (>10 kW ) with low conduction losses.
- DCM or BM operation the increased conduction losses in the higher power range can, as usual, be reduced by parallel connection (and phase-shifted control "interleaving") of several strands.
- transformer symbols shown in the figures in the background of the DC-DC stages are to be regarded as optional. When using a conventional onboard charger, for example, transformers can be used.
- the device according to the invention can supply both DC-DC stages with a transformer and without a transformer, since the device has a low level of common mode.
- the DC-DE stages are represented by a dashed outline.
- the representation of the high-voltage batteries and the transformers in the figures are only optional unless explicitly described as components of an embodiment.
- Such a strand arrangement is shown in FIG. This means that the performance can be scaled accordingly by parallelizing such strands.
- the network phase with the minimum absolute value is switched through to the center point m, which also defines the center potential of the two intermediate circuit partial voltages uZK1, uZK2.
- a bidirectional semiconductor switch Sa, Sb, Sc is provided for each network phase for this connection.
- the bidirectional switches SA, SB, SC of the first switching branches can be controlled or switched during operation with up to three times the respective input mains frequency.
- the through-connection of the network phase with the minimum amount at point m in addition to the EMC behavior, also benefits the achievable current flow in this phase, which, due to the principle, always has to go through the zero crossings.
- some conventional three-phase PFC topologies e.g. Vienna Rectifier
- undesired discontinuous operation occurs in the area of the current zero crossings and thus current distortions (deviations from the sinusoidal shape). Since in the proposed device the bidirectional switch practically always connects the network phase with the minimum absolute value directly to the midpoint m, there is also no temporary discontinuous operation with associated current distortions.
- a sinusoidal curve results for all three mains currents ia, ib, ic, ip corresponds to the current in the respective maximum mains phase (positive polarity), in corresponds analogously to the current in the respective minimum mains phase (negative polarity) .
- FIG. 11 shows the typical course in relation to a three-phase European AC voltage network.
- FIG. 6 shows an advantageous implementation of the low-frequency clockable bidirectional switches S1SA, S2SB, S3SC with IGBTs and silicon (Si) diodes.
- each bidirectional switch S1SA, S2SB, S3SC that can be clocked at a low frequency can have an IGBT and four diodes.
- This refinement with only one mit, that is to say only one standard power semiconductor (IGBT) that can be turned off, is particularly cost-effective and requires only a small amount of control effort.
- IGBT silicon
- IGBTs have comparatively low conduction losses, but higher switching losses (than, for example, MOSFETs).
- IGBTs are very robust semiconductor switches and are available in many versions at low cost. They are also ideally suited for production-related integration into a common power module (together with the surrounding diodes, which results in one power module per bridge branch, for example), which is an important argument for automotive (onboard charger) and industrial applications.
- IGBTs are available in the various relevant voltage classes. This is worth mentioning because the voltage load of the bidirectional switches, as well as the two high-frequency controlled switches (SI, S2) in the proposed PFC topology when operating on a typical European three-phase network (400 V AC) has an intermediate value in relation to standard voltage classes. In this application, types with a blocking voltage of 1000 V would be preferable, which is covered by IGBTs.
- a further advantageous implementation of the bidirectional semiconductor switch can be seen in the use of monolithic, bidirectional GaN transistors.
- Such transistors based on GaN material can implement a low-frequency clockable bidirectional switch S1SA, S2SB, S3SC directly as a single element.
- S1SA, S2SB, S3SC low-frequency clockable bidirectional switch
- S1SA, S2SB, S3SC low-frequency clockable bidirectional switch
- Monolithic, bidirectional GaN transistors also have a comparatively weak switching behavior, which would not have an effect in the proposed application due to the low-frequency switching. Instead, types optimized for minimal conduction losses could be fully utilized.
- any network/every network type can be used with suitable wiring.
- any network/every network type can be used with suitable wiring.
- the use with a single-phase network or the fallback solution of a single-phase operation will be briefly discussed.
- the neutral conductor N can be connected by means of a further diode branch D4a, D4b.
- This is particularly advantageous when the invention is used as an onboard charger (abbreviated OBL), because in this way charging, which is important in an emergency, can also be ensured at a single-phase household socket.
- OBL onboard charger
- one of the mains phases a,b,c can work with N as a return conductor.
- the bidirectional switch Sd drawn in this branch is only to be regarded as optional. If Sd were omitted or permanently switched off, both intermediate circuit capacitances CZK1, CZK2 would be charged simultaneously at all times, even in single-phase operation, which advantageously leads to a lower total capacitance requirement and smaller sizes for the intermediate circuit capacitors.
- a (small) capacitance eg 3 pF
- This also enables operation with a lower DC output voltage.
- FIG. 12 This capacity makes it possible to achieve a desired output voltage on the DC side of 2 * 400 V even when connected to a conventional (European) three-phase network with 400 V AC.
- the device of the invention can also be operated in a split-phase network (see FIG. 4c), such as is found in North America, for example.
- this can advantageously be implemented directly by laying the neutral conductor N via the supply line to a mains phase connection terminal on the OBL side (here, for example, b/E2) and permanently directly to the circuit center point m via the existing bidirectional switch (here, Sb). can be connected.
- a mains phase connection terminal on the OBL side here, for example, b/E2
- Sb bidirectional switch
- the center point m is therefore on the extremely quiet neutral conductor potential (0 V), which minimizes any low-frequency leakage currents from a high-voltage (abbreviated HV) battery side.
- both intermediate circuit capacitances CZK1, CZK2 can also be charged simultaneously in this case, so that there is no increased need for capacitance.
- a HV battery traction battery
- a charging voltage range of around 400 - 800 V can also be charged by the proposed device alone, i.e. without downstream DC-DC stages for reducing the intermediate circuit voltage uZKl/2, can be loaded.
- the existing non-floating DC-DC stages could be deactivated during operation on the split-phase grid, i.e. the associated step-down switches could be switched through permanently. This avoids switching losses there and thus further increases the overall efficiency.
- the proposed three-phase PFC topology is also of particular interest for use in North America, since it is universal here for the 120/240V split-phase network described, as well as for the existing 208V AC and 240V AC three-phase networks (with grounded star point) is to be used - with power semiconductors that can all be in the blocking voltage class of 600 V.
- buck-boost buck-boost
- FIG. 7 a buck/boost variant (buck-boost) is shown in FIG. 7 using the example of a European three-phase network, which can also realize low output voltages as a single-stage circuit (ie with only two chokes and then four switches operated at high frequency).
- FIG. 8 shows an isolated single-stage variant based on a boost full bridge, e.g. single-stage OBC.
- Figure 10 shows an isolated single-stage variant based on a phase-controlled full bridge (PSFB), e.g. for single-stage OBC.
- PSFB phase-controlled full bridge
- variants with a bidirectional power flow can also be made possible, both for the non-floating buck/boost version (buck-boost) and for the non-floating versions.
- the rectifier diodes of the proposed PFC basic topology must each be provided with an anti-parallel power transistor (eg IGBT) with low-frequency control, regardless of the variant.
- IGBT anti-parallel power transistor
- connection to a suitable network can be implemented, for example, using suitable mains cables.
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Rectifiers (AREA)
Abstract
Description
Claims
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
DE102020214265.3A DE102020214265A1 (de) | 2020-11-12 | 2020-11-12 | Vorrichtung zur gleichtaktarmen Umrichtung von Wechselspannung |
PCT/EP2021/081496 WO2022101396A1 (de) | 2020-11-12 | 2021-11-12 | Vorrichtung zur gleichtaktarmen umrichtung von wechselspannung |
Publications (1)
Publication Number | Publication Date |
---|---|
EP4244966A1 true EP4244966A1 (de) | 2023-09-20 |
Family
ID=78770605
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
EP21814724.7A Pending EP4244966A1 (de) | 2020-11-12 | 2021-11-12 | Vorrichtung zur gleichtaktarmen umrichtung von wechselspannung |
Country Status (3)
Country | Link |
---|---|
EP (1) | EP4244966A1 (de) |
DE (1) | DE102020214265A1 (de) |
WO (1) | WO2022101396A1 (de) |
Family Cites Families (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US6545887B2 (en) * | 1999-08-06 | 2003-04-08 | The Regents Of The University Of California | Unified constant-frequency integration control of three-phase power factor corrected rectifiers, active power filters and grid-connected inverters |
US9472625B2 (en) | 2014-03-17 | 2016-10-18 | Infineon Technologies Austria Ag | Operational Gallium Nitride devices |
ES2908960T3 (es) | 2015-07-01 | 2022-05-04 | Abb Schweiz Ag | Convertidor eléctrico y método de control |
FR3060230B1 (fr) | 2016-12-14 | 2019-01-25 | Renault S.A.S | Procede de commande d'un dispositif de charge embarque sur un vehicule electrique ou hybride. |
KR102486104B1 (ko) * | 2018-04-03 | 2023-01-09 | 현대자동차주식회사 | 전기 자동차의 충전 장치 |
NL2021926B1 (en) | 2018-11-02 | 2020-05-14 | Prodrive Tech Bv | Electrical power converter |
DE102019106485B4 (de) | 2019-03-14 | 2021-04-08 | Dr. Ing. H.C. F. Porsche Aktiengesellschaft | Weissach-Gleichrichteranordnung |
-
2020
- 2020-11-12 DE DE102020214265.3A patent/DE102020214265A1/de active Pending
-
2021
- 2021-11-12 WO PCT/EP2021/081496 patent/WO2022101396A1/de unknown
- 2021-11-12 EP EP21814724.7A patent/EP4244966A1/de active Pending
Also Published As
Publication number | Publication date |
---|---|
DE102020214265A1 (de) | 2022-05-12 |
WO2022101396A1 (de) | 2022-05-19 |
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