EP2901816B1 - Circuit de service avec convertisseur cadencé pour l'excitation d'une rangée de del - Google Patents
Circuit de service avec convertisseur cadencé pour l'excitation d'une rangée de del Download PDFInfo
- Publication number
- EP2901816B1 EP2901816B1 EP13841314.1A EP13841314A EP2901816B1 EP 2901816 B1 EP2901816 B1 EP 2901816B1 EP 13841314 A EP13841314 A EP 13841314A EP 2901816 B1 EP2901816 B1 EP 2901816B1
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- EP
- European Patent Office
- Prior art keywords
- switch
- led
- current
- operating circuit
- control unit
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
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- 239000003990 capacitor Substances 0.000 claims description 10
- 238000000034 method Methods 0.000 claims description 6
- 238000012935 Averaging Methods 0.000 claims description 5
- 238000005259 measurement Methods 0.000 description 8
- 238000004804 winding Methods 0.000 description 7
- 230000005347 demagnetization Effects 0.000 description 6
- 238000012937 correction Methods 0.000 description 3
- 238000001228 spectrum Methods 0.000 description 3
- 230000004913 activation Effects 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 239000004065 semiconductor Substances 0.000 description 2
- 230000006978 adaptation Effects 0.000 description 1
- 230000001419 dependent effect Effects 0.000 description 1
- 238000001514 detection method Methods 0.000 description 1
- 238000011161 development Methods 0.000 description 1
- 230000018109 developmental process Effects 0.000 description 1
- 238000007599 discharging Methods 0.000 description 1
- 230000005611 electricity Effects 0.000 description 1
- 238000011156 evaluation Methods 0.000 description 1
- 238000001914 filtration Methods 0.000 description 1
- 239000011147 inorganic material Substances 0.000 description 1
- 229910010272 inorganic material Inorganic materials 0.000 description 1
- 230000010354 integration Effects 0.000 description 1
- 238000011835 investigation Methods 0.000 description 1
- 230000005415 magnetization Effects 0.000 description 1
- 238000012423 maintenance Methods 0.000 description 1
- 238000012544 monitoring process Methods 0.000 description 1
- 239000011368 organic material Substances 0.000 description 1
- 230000000630 rising effect Effects 0.000 description 1
Images
Classifications
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
- H05B45/30—Driver circuits
- H05B45/37—Converter circuits
- H05B45/3725—Switched mode power supply [SMPS]
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
- H05B45/30—Driver circuits
- H05B45/37—Converter circuits
- H05B45/3725—Switched mode power supply [SMPS]
- H05B45/375—Switched mode power supply [SMPS] using buck topology
Definitions
- the invention relates to an operating circuit for driving an LED track with at least one LED.
- the LED path is controlled by a clocked converter, preferably by a buck converter.
- the invention relates in particular to the indirect determination of the current (I LED ) through the LED path.
- LEDs have become an attractive alternative to conventional light sources such as incandescent or gas discharge lamps.
- LED Light Emitting Diode
- LEDs are therefore always operated in a mode in which the current flow through the LED is controlled.
- switching regulators for example step-down converters or buck converters.
- a switching regulator is for example from the DE 10 2006 034 371 A1 known.
- a control unit controls a high-frequency clocked switch (for example, a power transistor, FET, MOSFET).
- a high-frequency clocked switch for example, a power transistor, FET, MOSFET.
- the invention provides an operating circuit for an LED track with at least one LED according to claim 1.
- the operating circuit at at least one input-side terminal, a supply voltage can be supplied, and the operating circuit comprises a coil and a clocked by a control unit first switch, wherein in conductively-switched first switch in the coil, an energy is stored, which is non-conductive switched first switch via a diode and via the LED path discharges, wherein a capacitor is provided, which is arranged parallel to the LED track and the LED is connected during the phase of the discharge of the coil the current through the LED maintains, and wherein the control unit is adapted to determine the switch current through the first switch on a first measuring resistor, preferably the supply voltage to a second measuring resistor and preferably a measuring voltage at the Determine LED distance at a third measuring resistor and calculate the LED current through the D-distance.
- the control unit can calculate the LED voltage as the difference between the supply voltage and the measurement voltage.
- the controller may also measure the LED voltage based on a measurement of a voltage on the coil during the turn-off time of the first switch.
- the controller may calculate the LED current from the product of the supply voltage and the switch current as transmitted power divided by the LED voltage.
- the control unit may average the switch current (low pass filtering, time averaging, integration).
- the LED current can be supplied to the control unit as a feedback signal, in particular as an actual value.
- the control unit may control the on time of the first switch.
- the control unit may specify a switch-off threshold value for the first switch.
- the averaging of the switch current can be done by a low-pass filter, which can detect the time average of the current.
- Fig. 1 shows a circuit arrangement - inter alia - a buck converter (Buck converter) for the operation of at least the LED track (with one or more series-connected LEDs), with a first switch LS, which is also used as a converter switch of the buck converter Example of a clocked converter, can be called.
- the circuit arrangement also referred to below as the operating circuit, is supplied with a DC voltage or a rectified AC voltage V bus .
- the DC voltage or a rectified AC voltage V bus can be fed via a mains rectifier directly from an AC voltage network or by the interposition of an active power factor correction circuit or via a DC-DC converter, for example, a potential-separated DC-DC converter.
- a capacitor C bus is arranged.
- a first measurement resistor R VbusShunt is connected via a first resistor R Vbus to the supply voltage V bus.
- the supply voltage V bus can be detected by a control unit SE (eg a microcontroller, an ASIC, an IC, etc.).
- the actual converter wherein first a diode D1, the first switch LS and a second measuring resistor R shunt are connected in series parallel to the capacitor C bus . Between diode D1 and the first switch LS, the potential-lower side of the diode D1 is connected via a coil L buck to a second optional capacitor C LED connected in parallel with the diode D1. At the second measuring resistor R shunt , for example from the control unit SE, the switch current I LS can be detected by the first switch LS.
- a choke winding ZX also referred to as choke ZX
- the charging and discharging processes (magnetization and demagnetization) of the coil L buck can be detected in a measuring circuit.
- zero crossings ie a demagnetization and thus discharge of the coil L buck to the zero level, can be detected.
- the control unit SE for example by the current I Lbuck is detected by the coil, for example on the inductor winding ZX.
- the demagnetization of the coil L buck which connected to the drop of the current I Lbuck to zero, by means of a voltage monitoring to throttle winding ZX be detected by due control unit SE.
- a third measuring resistor R VLEDShunt is connected via a further resistor R VLED , to which a measuring voltage V LED can be detected by the control unit SE.
- the LED voltage can thus be determined. It results from the difference between the supply voltage V bus and the measured voltage V LED determined at the third measuring resistor.
- a second switch FS is connected to its potential-lower side between the first switch LS and the second measuring resistor R Shunt via a further resistor, via which a filter of the first order (low pass) can be switched on or off ,
- the first switch is driven via a driver circuit LS DRV with a driver voltage V gate
- the second switch FS is driven via a driver circuit with the voltage V duty
- the respective control can also be effected by a control unit SE, wherein, for example, the driver circuit LS DRV and / or the driver circuit with the voltage V duty can be part of the control unit SE.
- the low-pass filter TPF is now used to average the detected at the second measuring resistor R shunt switch current I LS .
- the invention provides the following for measuring the LED current I LED as an actual value:
- the switch current I LS through the first switch LS is detected when the first switch LS on the second measuring resistor R shunt . This current increases substantially linearly during the switch-on time phase of the first switch LS and drops to zero when the switch LS is opened.
- the current through the coil L buck thus shows a zigzag-shaped time course: when the first switch is turned on, the current shows a rising edge, with the first switch turned off there is a falling edge.
- the switch current I LS is therefore zero before it rises again when the first switch LS is switched on again.
- the switch LS is turned off when a shutdown threshold (stored, for example, in the control unit SE) is reached.
- This switch current profile I LS is now averaged by being supplied to the low-pass circuit TPF.
- the averaging switch current I LS is detected.
- the high-frequency, approximately zigzag course of the LED current I LED (in the exemplary embodiment, the LED current I LED drops to zero by the coil L buck before being switched on again, which corresponds to operation in the so-called "borderline mode") can be combined be with a relatively low-frequency PWM control (LF PWM, low-frequent PWM).
- LF PWM low-frequency PWM control
- a large fluctuation range of the current can have a disadvantageous effect on LEDs, since the spectrum of the emitted light can change as the current amplitude changes.
- a pulse modulation method for example the PWM (Pulse-Width Modulation) method.
- the LEDs are supplied by the operating circuit with low-frequency (typically with a frequency in the range of 100-1000 Hz) pulse packets with (in the time average) constant current amplitude.
- the electricity within one Pulse packets are superimposed on the above-mentioned high-frequency ripple.
- the brightness of the LEDs can now be controlled by the frequency of the pulse packets; For example, the LEDs can be dimmed by increasing the time interval between the pulse packets.
- the high-frequency clocking of the first switch LS is combined with a PWM signal, wherein the frequency of the PWM signal is low-frequency in relation to the frequency of the high-frequency clocking of the first switch (LS).
- the frequency of the high-frequency clocking and the low-frequency PWM signal are matched to one another in order to avoid flickering effects.
- the frequency of the high-frequency clocking may be an integer multiple of the frequency of the low-frequency PWM signal.
- the switch can be operated in a high-frequency PWM mode.
- the duty cycle for the high-frequency clocking of the first switch is set depending on the average value of the determined LED current or switch current at a fixed predetermined frequency.
- a maintenance of the current through the LED can be done by the parallel connection of a capacitor C LED , as will be explained later.
- the adjustment of the current through the LED can be done by appropriate selection of the turn-on and turn-off times. For example, these times may be selected such that the first switch LS is turned on when the current falls below a certain minimum reference value and the switch is turned off when the current exceeds a maximum reference value (turn-off threshold).
- the minimum reference value can also be zero.
- the current path between the second measuring resistor R shunt in series with the first switch LS, the converter switch, towards the low-pass filter TPF is enabled only during the switch-on period of the low-frequency PWM signal.
- the current path is interrupted, so that the resulting low-pass filtered (averaged) signal is maintained and thus an evaluation of the mean value in the turn-off of the low-frequency PWM signal can be performed by the control unit.
- the LED current I LED can be determined by referring (eg, dividing or otherwise correlating) the power transmitted through the converter to the LED voltage.
- the transmitted power is calculated by the determined at the first measuring resistance supply voltage V bus , which is multiplied by the time-averaged switch current I LS . This can again be done by the control unit SE, for example.
- the LED voltage is determined for example by means of a measurement on the third measuring resistor R VLEDShunt , which is connected in series with the LED track LED.
- the LED voltage results from the difference between the supply voltage V bus and the measured voltage V LED determined at the third measuring resistor.
- the control unit SE could measure the LED voltage but also, for example, by measuring a voltage on the coil L buck during the turn-off of the first switch LS, for example by means of a voltage measurement on the inductor winding ZX during the demagnetization phase of the coil L buck .
- the voltage across the coil L bucx corresponds to the sum of the voltages across the diode D1 and the LED voltage. It can thus be concluded that the LED voltage, since when deducting the passage Spannug the diode D1, the voltage across the coil L buck corresponds to the LED voltage.
- the LED current I LED is indirectly determined by calculating the transmitted power and the indirect determination of the LED voltage.
- the investigations and / or the calculations are preferably carried out by the control unit SE. It can also be included in the calculation of the transmitted power, a correction factor that includes, for example, the switching behavior or the losses of the converter.
- the calculated LED current can thus be used as actual value variable for a regulation of the LED current.
- the turn-on time T on of the first switch LS of the (buck) converter can be used as the control variable for the control.
- the duty cycle of the low-frequency PWM drive if present, can be used.
- the switch-off threshold for the first switch LS in the control unit SE can be shifted depending on the mean value of the switch current I LS .
- the duty cycle of the low-frequency PWM control can be fixed at least in a partial range of the LED operation, for example at high brightness, at 100% duty cycle or near this range. In this area, the height of the LED current and thus the brightness of the LED can be influenced by adjusting the switch-off threshold for the first switch LS and thus via the control variable the switch-on time T on of the converter.
- the control unit SE are thus preferably a signal representing the supply voltage V bus , a signal representing the time average of the switch current I LS (in the on time periods of the low-frequency PWM modulation, if present), and / or a signal which supplies the supply voltage V bus minus the voltage V LED detected at the third measuring resistor R VLEDSchunt .
- control unit SE can also selectively release the low-pass filter TPF via activation of the second switch FS (eg during the switch-on period of the PWM signal) or disconnect (eg during the switch-off period of the PWM signal), ie the path between the second measuring resistor R shunt the first switch LS and the low-pass filter TPF.
- the optional capacitor C LED parallel to the LED track LED is known as such and can serve to avoid that the LED current identically traces the course through the coil L buck .
- non-conductive switched first switch LS in particular during the phase of demagnetization of the coil L Buck , the current through the LED due to the cached in the capacitor C LED energy can be maintained.
- it is disadvantageous in terms of the spectrum of the LED track LED if the LED current performs such large strokes (except for a pure PWM drive between 0 and 1, then only one current flows at 1).
- the low-frequency PWM signal need not be generated by the control unit itself, but it can be supplied from outside, for example by an externally supplied PWM control signal, and then of course the release / disconnecting element, the second switch FS, for the low-pass filter TPF be supplied.
- the release / disconnect window for the connection element, the second switch FS, between low-pass filter TPF and the second measurement resistor R Shun t may deviate from a PWM switch-on pulse in that the "disconnect" occurs only when a zero crossing or the fall of the current through the coil L buck is detected to zero. This can take place via the throttle winding ZX, for example via a pin on the throttle winding ZX, by the control unit SE. This ensures that the averaging window for the low-pass circuit TPF always covers complete triangular waveforms of the coil current.
- the coil L buck can also be arranged between the second capacitor C LED and the LED track LED.
- the low-pass filter TPF and the second switch FS can optionally also be integrated in the control unit SE.
- Fig. 2 shows by way of example the current I LS through the first switch LS, the average current I LS , which is determined by the low-pass filter TPF, the current waveform I Lbuck on the coil L buck and a low-frequency PWM signal LF PWM.
- the inventive detection of the switch current only during the turn-on period of the low-frequency PWM signal can also be used in a simplified embodiment, if only the switch current but not the LED voltage and / or the supply voltage for determining the LED current is considered , This may be the case, in particular, when the LED voltage and / or the supply voltage are fixed. So the LED voltage can be known if the number of LEDs of the LED range is known. The supply voltage can be fixed, for example, when connecting an active power factor correction circuit.
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- Circuit Arrangement For Electric Light Sources In General (AREA)
- Dc-Dc Converters (AREA)
- Led Devices (AREA)
Claims (9)
- Circuit de service pour une rangée de DEL comportant au moins une DEL,- une tension d'alimentation (Vbus) pouvant être conduite au circuit de service sur au moins une connexion côté entrée, et le circuit de service présentant une bobine (LBuck) et un premier commutateur (LS) cadencé à haute fréquence par une unité de commande (SE) du circuit de service, une première résistance de mesure (RVbusShunt), une deuxième résistance de mesure (RShunt) et une troisième résistance de mesure (RVledShunt),- l'unité de commande étant agencée pour détecter sur la deuxième résistance de mesure (RShunt) un courant de commutateur (ILS) traversant le premier commutateur (LS) quand le premier commutateur (LS) est en circuit,- le circuit de service étant constitué de telle sorte que, quand le premier commutateur (LS) est commuté sur conduction, une énergie est stockée de façon intermédiaire dans la bobine (LBuck) et se décharge, quand le premier commutateur (LS) est commuté sur non-conduction, par le biais d'une diode (D1) du circuit de service et par le biais de la rangée de DEL,caractérisé en ce que- le circuit de service présente en outre un filtre passe-bas (TPF), le filtre passe-bas (TPF) étant agencé pour calculer la moyenne dans le temps du courant de commutateur (ILS) détecté sur la deuxième résistance de mesure (RShunt),- l'unité de commande (SE) étant agencée- pour déterminer le courant de commutateur (ILS), dont la valeur moyenne dans le temps a été calculée, traversant le premier commutateur sur la deuxième résistance de mesure (RShunt) et le filtre passe-bas (TPF),- la tension d'alimentation (Vbus) sur la première résistance de mesure (RVbusShunt) et- une tension de mesure (Vled) sur la rangée de DEL sur la troisième résistance de mesure (RVledShunt),et pour calculer à partir de cela le courant de DEL (ILED) traversant la rangée de DEL,- l'unité de commande (SE) étant agencée pour combiner le cadencement haute fréquence du courant de commutateur (ILS) avec un signal PWM basse fréquence par comparaison,un deuxième commutateur (FS) étant prévu dans le circuit de service, qui est agencé pour ne libérer un trajet de courant entre la deuxième résistance de mesure (RShunt) et le filtre passe-bas (TPF) que pendant une durée de mise en circuit du signal PWM et pour interrompre le trajet de courant pendant une durée de mise hors circuit du signal PWM.
- Circuit de service selon la revendication 1, l'unité de commande (SE) étant agencée pour calculer la tension de DEL en tant que différence entre la tension d'alimentation (Vbus) et la tension de mesure (Vled).
- Circuit de service selon la revendication 1 ou 2, l'unité de commande (SE) étant agencée pour calculer le courant de DEL (ILED) à partir du produit de la tension d'alimentation (Vbus) et du courant de commutateur (ILS) en tant que puissance transmise divisée par la tension de DEL.
- Circuit de service selon l'une des revendications précédentes, l'unité de commande (SE) étant agencée pour spécifier une valeur de seuil de coupure pour le premier commutateur (LS).
- Circuit de service selon l'une des revendications précédentes, le courant de commutateur (ILS), dont la valeur moyenne a été calculée, et filtré en passe-bas, étant maintenu pendant la durée de mise hors circuit, et l'unité de commande (SE) étant agencée pour analyser le courant de commutateur (ILS), dont la valeur moyenne a été calculée, pendant la durée de mise hors circuit du signal PWM.
- Circuit de service selon l'une des revendications précédentes, l'unité de commande (SE) étant agencée pour commander un rapport cyclique du signal PWM, et l'unité de commande (SE) étant agencée pour régler la valeur de seuil de coupure pour le premier commutateur (LS) en fonction du courant de commutateur (ILS) dont la valeur moyenne a été calculée.
- Circuit de service selon l'une des revendications précédentes, un signal reproduisant la tension d'alimentation (Vbus), un signal reproduisant le courant de commutateur (ILS) dont la valeur moyenne a été calculée et/ou un signal qui reproduit la différence entre la tension d'alimentation (Vbus) et la tension de mesure (Vled) pouvant être conduit à l'unité de commande (SE).
- Circuit de service selon l'une des revendications précédentes, un condensateur étant prévu dans le circuit de service et étant disposé parallèlement à la rangée de DEL et étant agencé pour maintenir le courant traversant la DEL quand le premier commutateur (LS) est commuté sur non-conduction.
- Procédé de fonctionnement, par un circuit de service, d'une rangée de DEL, avec
au moins une DEL, présentant les étapes suivantes :- amenée d'une tension d'alimentation (Vbus) au circuit de service sur au moins une connexion côté entrée,
le circuit de service présentant une bobine (LBuck) et un premier commutateur (LS) cadencé à haute fréquence par une unité de commande (SE) du circuit de service, une première résistance de mesure (RVbusShunt), une deuxième résistance de mesure (RShunt) et une troisième résistance de mesure (RVledShunt),- détection, par l'unité de commande, sur la deuxième résistance de mesure (RShunt), d'un courant de commutateur (ILS) traversant le premier commutateur (LS) quand le premier commutateur (LS) est en circuit,- stockage intermédiaire d'une énergie dans la bobine quand le premier commutateur est commuté sur conduction, la bobine se déchargeant, quand le premier commutateur (LS) est commuté sur non-conduction, par le biais d'une diode (D1) du circuit de service et par le biais de la rangée de DEL,caractérisé par les étapes suivantes :- calcul de la moyenne temporelle par un filtre passe-bas (TPF) du circuit de service, du courant de commutateur (LS) détecté sur la deuxième résistance de mesure (RShunt),- détermination, par l'unité de commande (SE), du courant de commutateur (ILS), dont la valeur moyenne dans le temps a été calculée, traversant le premier commutateur sur la deuxième résistance de mesure (RShunt) et le filtre passe-bas (TPF),- détermination, par l'unité de commande (SE), de la tension d'alimentation (Vbus) sur la première résistance de mesure (RVbusShunt), et- détermination, par l'unité de commande (SE), d'une tension de mesure (Vled) sur la rangée de DEL sur la troisième résistance de mesure (RVledShunt)et, à partir de là, calcul du courant de DEL (ILED) traversant la rangée de DEL,- combinaison du cadencement haute fréquence du courant de commutateur (ILS) avec un signal PWM basse fréquence par comparaison,- libération, par un deuxième commutateur (FS) du circuit de service, d'un trajet de courant entre la deuxième résistance de mesure (RShunt) et le filtre passe-bas (TPF) uniquement pendant une durée de mise en circuit du signal PWM, et- interruption du trajet de courant pendant une durée de mise hors circuit du signal PWM.
Applications Claiming Priority (3)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
ATGM385/2012U AT13687U1 (de) | 2012-09-28 | 2012-09-28 | Betriebsschaltung mit getaktetem Konverter zur Ansteuerung einer LED-Strecke |
DE201210217748 DE102012217748A1 (de) | 2012-09-28 | 2012-09-28 | Betriebsschaltung mit getaktetem Konverter zur Ansteuerung einer LED-Strecke |
PCT/AT2013/000157 WO2014047668A2 (fr) | 2012-09-28 | 2013-09-30 | Circuit de service avec convertisseur cadencé pour l'excitation d'une rangée de del |
Publications (2)
Publication Number | Publication Date |
---|---|
EP2901816A2 EP2901816A2 (fr) | 2015-08-05 |
EP2901816B1 true EP2901816B1 (fr) | 2017-11-08 |
Family
ID=50389065
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
EP13841314.1A Active EP2901816B1 (fr) | 2012-09-28 | 2013-09-30 | Circuit de service avec convertisseur cadencé pour l'excitation d'une rangée de del |
Country Status (2)
Country | Link |
---|---|
EP (1) | EP2901816B1 (fr) |
WO (1) | WO2014047668A2 (fr) |
Families Citing this family (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE202015101996U1 (de) * | 2015-04-22 | 2015-05-11 | Tridonic Gmbh & Co Kg | Getakteter Wandler für dimmbare Leuchtmittel mit dynamisch einstellbarem Filter |
KR102301218B1 (ko) * | 2018-01-30 | 2021-09-10 | 주식회사 엘지에너지솔루션 | 릴레이 구동 회로 진단 장치 |
EP4345211A1 (fr) | 2022-09-29 | 2024-04-03 | Apison | Dispositif pour le compactage de materiaux |
Family Cites Families (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE102006034371B4 (de) * | 2006-04-21 | 2019-01-31 | Tridonic Ag | Betriebsschaltung und Betriebsverfahren für Leuchtdioden |
US7550934B1 (en) * | 2008-04-02 | 2009-06-23 | Micrel, Inc. | LED driver with fast open circuit protection, short circuit compensation, and rapid brightness control response |
US8344638B2 (en) * | 2008-07-29 | 2013-01-01 | Point Somee Limited Liability Company | Apparatus, system and method for cascaded power conversion |
JP5760169B2 (ja) * | 2010-10-25 | 2015-08-05 | パナソニックIpマネジメント株式会社 | 点灯装置および、これを用いた照明器具 |
-
2013
- 2013-09-30 WO PCT/AT2013/000157 patent/WO2014047668A2/fr active Application Filing
- 2013-09-30 EP EP13841314.1A patent/EP2901816B1/fr active Active
Non-Patent Citations (1)
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Also Published As
Publication number | Publication date |
---|---|
WO2014047668A2 (fr) | 2014-04-03 |
WO2014047668A3 (fr) | 2014-06-26 |
EP2901816A2 (fr) | 2015-08-05 |
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