EP2491647B1 - Mélangeur passif doté d'une intermodulation réduite de second ordre - Google Patents

Mélangeur passif doté d'une intermodulation réduite de second ordre Download PDF

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Publication number
EP2491647B1
EP2491647B1 EP09749000.7A EP09749000A EP2491647B1 EP 2491647 B1 EP2491647 B1 EP 2491647B1 EP 09749000 A EP09749000 A EP 09749000A EP 2491647 B1 EP2491647 B1 EP 2491647B1
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EP
European Patent Office
Prior art keywords
signal
terminal
cancellation
voltage
component
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EP09749000.7A
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German (de)
English (en)
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EP2491647A1 (fr
Inventor
Sven Mattisson
Pietro Andreani
Daniele Mastantuono
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Telefonaktiebolaget LM Ericsson AB
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Telefonaktiebolaget LM Ericsson AB
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Priority to PL15002353T priority Critical patent/PL2983289T3/pl
Priority to EP15002353.9A priority patent/EP2983289B1/fr
Priority to EP18156694.4A priority patent/EP3346606B1/fr
Priority to PL18156694T priority patent/PL3346606T3/pl
Publication of EP2491647A1 publication Critical patent/EP2491647A1/fr
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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D1/00—Demodulation of amplitude-modulated oscillations
    • H03D1/02—Details
    • H03D1/04—Modifications of demodulators to reduce interference by undesired signals
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/12—Transference of modulation from one carrier to another, e.g. frequency-changing by means of semiconductor devices having more than two electrodes
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/14—Balanced arrangements
    • H03D7/1425—Balanced arrangements with transistors
    • H03D7/1458—Double balanced arrangements, i.e. where both input signals are differential
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/14—Balanced arrangements
    • H03D7/1425—Balanced arrangements with transistors
    • H03D7/1466—Passive mixer arrangements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D2200/00—Indexing scheme relating to details of demodulation or transference of modulation from one carrier to another covered by H03D
    • H03D2200/0041—Functional aspects of demodulators
    • H03D2200/0088—Reduction of intermodulation, nonlinearities, adjacent channel interference; intercept points of harmonics or intermodulation products
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/16—Multiple-frequency-changing
    • H03D7/165—Multiple-frequency-changing at least two frequency changers being located in different paths, e.g. in two paths with carriers in quadrature

Definitions

  • the invention generally relates to the field of receiver structures in radio communication systems. More specifically, the invention relates to passive mixers in the receiver structures and to a technique for converting a first signal having a first frequency into a second signal having a second frequency by using a third signal having a third frequency.
  • a mixer In radio communication systems, a mixer is used to up-convert a baseband (BB) signal or an intermediate frequency (IF) signal to a higher frequency, e. g. a radio frequency (RF) signal, for ease of transmission (when the mixer is used in a transmitter) or to down-convert a high frequency signal, e.g. an RF signal, to a lower frequency signal, e.g. a BB signal or an IF signal, for ease of signal processing (when the mixer is used in a receiver).
  • the up-conversion or down-conversion is respectively performed by mixing the input signal of the mixer with a local oscillator (LO) signal generated by a local oscillator.
  • the RF signal is mixed with the LO signal in order to generate an IF signal or a BB signal.
  • the transmitter and receiver architectures are separated, i.e. separate circuitries are used for the receiver and the transmitter.
  • a transceiver is used, which is a device that has both a transmitter and a receiver which are combined and share common circuitry.
  • Transceivers normally include a duplexer which is a device that allows simultaneous bi-directional (full duplex) communication over a single channel. In radio communication systems, the duplexer isolates the receiver from the transmitter while permitting them to share a common antenna.
  • a challenge in modern radio communication systems has been, and continues to be, to design receivers (and transmitters) that can meet increasingly strict performance standards while fitting into ever shrinking packages.
  • many modern radio receivers (and transmitters) are implemented on a single application specific integrated circuit (ASIC).
  • ASIC application specific integrated circuit
  • Intermodulation can only occur in nonlinear systems.
  • Nonlinear systems are generally composed of active components, meaning that the components must be biased with an external power source which is not the input signal (i.e. the active components must be "turned on”).
  • passive components can perform in a non-linear manner and cause intermodulation.
  • Diodes or transistors are widely known for their passive nonlinear effects, but parasitic nonlinearity can arise in other components as well. For example, audio transformers exhibit non-linear behavior near their saturation point, electrolytic capacitors can start to behave as rectifiers under large-signal conditions, and RF connectors and antennas can exhibit nonlinear characteristics.
  • a passive mixer In the receiver case, a passive mixer generates IF or BB signals that result from the sum and difference of the LO and RF signals combined in the mixer. These sum and difference signals at the IF port are of equal amplitude, but generally only the difference signal is desired for processing and demodulation so the sum frequency (also known as the image signal) must be removed, typically by means of IF bandpass or BB lowpass filtering.
  • the Second Order Intercept Point is a measure of linearity that quantifies the second-order distortion generated by nonlinear systems and devices.
  • the fundamental output power rises in a one-to-one ratio (in terms of dB) of the input power, while the second-order output power rises in a two-to-one ratio.
  • the second order intercept point is the point at which the first- and second-order lines intersect, assuming that the power levels do not flatten off due to saturation.
  • the IP2 is the theoretical point on the RF input vs. IF output curve where the desired input signal and second order products become equal in amplitude as the RF input is raised.
  • TDMA Time Division Multiple Access
  • FDMA Frequency Division Multiple Access
  • CDMA Code Division Multiple Access
  • WCDMA Wideband Code Division Multiple Access
  • the wireless transmitter and receiver are not on at the same time but only in different, non-overlapping, time slots.
  • the strongest receiver (Rx) interference is due to an external transmitter, picked up via the antenna of the TDMA or TDD system.
  • the strongest Rx interferer is typically the wireless transmitter (Tx) itself, via leakage through the duplex filter of the system. Since the transmitter leakage at full power typically is ⁇ 10 dB stronger than any external interferer, this will mainly set the IM2 and IP2 requirements.
  • a WCDMA transmitter at +25 dBm power will result in a -25 dBm Rx signal when the duplexer attenuation is 50 dB.
  • the receiver IP2 has to be ⁇ +44 dBm for the rectified Tx spectrum to be below the -108 dBm limit.
  • GSM Global System for Mobile Communications
  • the strongest interferer is 5 dB lower or -30 dBm, resulting in a 10 dB lower IP2 requirement for the same distortion levels.
  • this filter typically is a Surface Acoustic Wave (SAW) filter which cannot be integrated into the transceiver ASIC, but has to be located on the printed circuit board (PCB) or module substrate, adding to the cost and complexity of the receiver structure.
  • SAW Surface Acoustic Wave
  • AC alternating current
  • a passive metal oxide semiconductor (MOS) mixer offers good performance in terms of noise and linearity, especially when its BB or IF port is at a virtual ground.
  • the virtual ground eliminates the modulation of the mixer switches by the BB or IF signal which improves IP2.
  • Due to the inherent nature of the MOS device its switching threshold and channel conductance depends on the LO, RF and IF signals. These interdependencies will generate cross products of these signals, including ones that cause IM2.
  • By grounding the IF port e.g. via a virtual ground, some of these cross products can be reduced resulting in less IM2 and consequently a higher IP2. Still the switching threshold will be modulated by the RF signal, resulting in an IM2 contribution in addition to that of the nonlinear channel conductance.
  • JP 2008 118176 A may be construed to disclose a radio transmitter in which an IF up-conversion section is provided with variable amplifiers provided for each of inputted signals (modulated wave signals) of a plurality of systems, and the signal level of each of the inputted signals of the plurality of systems is adjusted prior to up-converting the inputted signals of the plurality of systems.
  • US 2007/197185 A1 may be construed to disclose a broadband tuner with a reduced odd harmonic mixing and a method for reducing odd harmonic mixing in the broadband tuner.
  • the broadband tuner includes an arrangement of one or more filters, a plurality of mixers and one or more adders.
  • the plurality of mixers mix a plurality of input Radio Frequency (RF) signals with one or more Local Oscillator (LO) signals, to generate a plurality of mixing products.
  • the LO signals may be square wave LO signals with predefined amplitude coefficients and phases.
  • the plurality of mixing products are then added by the adders to reduce mixing of the odd harmonics of the LO signals.
  • CA 2,375,438 A1 may be construed to disclose a modification to a Gilbert mixer circuit.
  • the modifications alleviate disadvantages and problems introduced because of low voltage power supply typically found in low- power devices such as portable cellular phones.
  • the circuit can be applied to both single stage and dual mixers to give low noise performance and Automatic Gain Control (AGC).
  • AGC Automatic Gain Control
  • US 4,949,398 may be construed to disclose a simple balanced-mixer circuit that uses the resistive channel of a GaAs MESFET and that exhibits superior intermodulation performance, with other performance parameters, e.g., conversion loss, port impedances, and LO sensitivity, being equal to or better than other diode mixers.
  • performance parameters e.g., conversion loss, port impedances, and LO sensitivity
  • US 5,263,198 A may be construed to disclose a mixer including a local oscillator (LO) matching network having an LO input port, an RF matching network also having an input port and an IF filter which provides an IF output from the mixer.
  • LO local oscillator
  • a FET having a gate, drain and source operates at the center of the mixer.
  • a resonant loop is connected between the drain and gate of the FET.
  • the gate of the FET is connected to an output of the LO matching network.
  • the drain of the FET is connected to an output of the RF matching network.
  • the source of the FET is connected to an input of the IF filter.
  • the resonant loop may incorporate a DC blocking capacitor which does not function as part of the resonant loop, but which serves to block DC allowing the drain and gate of the FET to be biased independently.
  • EP 2 079 162 A1 may be construed to disclose different techniques for signal processing having reduced flicker noise.
  • a semiconductor circuitry for processing a frequency signal comprises a field effect transistor.
  • the field effect transistor has a gate terminal for receiving a bias signal and a bulk terminal for receiving a back-bias signal.
  • the semiconductor circuitry further comprises a first circuit portion to provide an alternating bias signal and a second circuit portion to provide a forward back-bias signal.
  • a passive mixer for converting a first signal having a first frequency into a second signal having a second frequency by using a third signal having a third frequency.
  • the passive mixer comprises a cancellation component for generating a first cancellation signal for cancelling second order intermodulation components by superimposing the first signal weighted by a cancellation value on the third signal; and a mixing component having a first terminal for receiving the first signal, a second terminal for outputting the second signal, and a third terminal for receiving the first cancellation signal, wherein the mixing component is adapted to provide the second signal as output at the second terminal by mixing the first signal provided as input at the first terminal and the first cancellation signal provided as input at the third terminal.
  • the above need is satisfied by a passive mixer for converting a first signal having a first frequency into a second signal having a second frequency by using a third signal having a third frequency.
  • the passive mixer comprises a cancellation component for generating a second cancellation signal for cancelling second order intermodulation components by superimposing the first signal weighted by a cancellation value on a bias, or reference, voltage; and a mixing component having a first terminal for receiving the first signal, a second terminal for outputting the second signal, a third terminal for receiving the third signal, and a fourth terminal for receiving the second cancellation signal, wherein the mixing component is adapted to provide the second signal as output at the second terminal by mixing the first signal provided as input at the first terminal and the third signal provided as input at the third terminal together with the second cancellation signal provided as input at the fourth terminal.
  • the cancellation component may be adapted to apply only one of the first and second cancellation signals or both the first cancellation signal and the second cancellation signal.
  • the mixing component may comprise four terminals, the first to fourth terminals according to the second aspect, but may only use three of the four terminals, e.g. the first to third terminals. For example, the three terminals are used by providing them with the respective signals, the fourth terminal remains unused and the mixing component then generates the first cancellation signal without considering the fourth signal (bias voltage). If the bias voltage would additionally be provided, the mixing component may generate the second cancellation signal using the four terminals.
  • the mixing component may be adapted to receive both the first and second cancellation signals and to provide the second signal as output at the second terminal by mixing the first signal provided as input at the first terminal and the first cancellation signal provided as input at the third terminal together with the second cancellation signal provided as input at the fourth terminal.
  • the mixing component may comprise a voltage controlled switch.
  • the mixing component comprises a field effect transistor switch, like a Metal Oxide Semiconductor Field Effect Transistor (MOSFET), a Junction Field Effect Transistor (JFET), a Metal Semiconductor Field Effect Transistor (MESFET) and the like or a transistor providing similar characteristics as a field effect transistor, like an Insulated Gate Bipolar Transistor (IGBT).
  • the field effect transistor switch may have its drain operatively connected to the first terminal, its gate operatively connected to the third terminal and its source operatively connected to the second terminal.
  • the field effect transistor switch may have its drain operatively connected to the first terminal, its gate operatively connected to the third terminal, its source operatively connected to the second terminal and its bulk connected to the fourth terminal.
  • source and drain may be interchanged for a symmetric device and what constitutes the drain and the source of a field effect transistor may be bias, or signal, dependent.
  • the drain is connected to the first terminal and the source to the second terminal.
  • the mixing component may alternatively comprise more than one voltage controlled switch, for example two complementary voltage controlled switches.
  • one N-channel transistor and one P-channel transistor may be connected in parallel to each other, and may share the first and second terminals, but may have distinct third terminals and, in case of the second aspect, distinct fourth terminals, e.g. distinct gate and bulk terminals.
  • the passive mixer may be used in a receiver arrangement for example of a transceiver comprising both a transmitter and a receiver.
  • the passive mixer may be used in at least one of the receiver and the transmitter of the transceiver.
  • the passive mixer is realized as an integrated circuit provided on the same application specific integrated circuit (ASIC) as the transceiver.
  • ASIC application specific integrated circuit
  • the passive mixer may be arranged in the receiver.
  • the first signal may then be a radio frequency (RF) signal received by the receiver
  • the third signal may be a local oscillator (LO) signal provided by a local oscillator arranged in the receiver
  • the second signal may be one of an intermediate frequency (IF) signal and a baseband (BB) signal dependent on whether the passive mixer is adapted to perform direct conversion or indirect conversion.
  • the passive mixer is adapted to perform indirect conversion
  • the received RF signal is down-converted by the passive mixer into an IF signal having a center frequency different from zero.
  • the IF signal may then be further down-converted by a similar or a different mixer into a BB signal.
  • direct conversion the RF signal is directly converted into a BB signal having a center frequency equal to zero, i.e. having a spectrum of a certain bandwidth around zero.
  • the passive mixer may be arranged in the transmitter.
  • the first signal may then be one of an IF signal and a BB signal dependent on whether the passive mixer is adapted to perform direct conversion or indirect conversion
  • the third signal may be an LO signal provided by an LO arranged in the transmitter
  • the second signal may be an RF signal to be transmitted by the transmitter.
  • the second order intermodulation (IM2) components to be cancelled may comprise terms dependent on the voltage at the first terminal of the mixing component (the input voltage of the mixing component).
  • the second terminal (output terminal) of the mixing component connected to a virtual ground or may have a voltage close to ground such that the voltage swing at this terminal is very low compared to the voltage swing of the first terminal.
  • the IM2 components may then be proportional to the square of the voltage at the first terminal.
  • the voltage swing at the second terminal may not be much less than that of the first terminal and the IM2 components may be dependent on both the voltage at the first terminal and the voltage at the second terminal.
  • the IM2 components are dependent on the voltage difference between the voltage at the first terminal and the voltage at the second terminal.
  • both the cancellation values for the first cancellation signal and the second cancellation signal may be set as fixed values.
  • both cancellation values may be equal to 0.5 or a value close to 0.5.
  • the cancellation values may initially be set to the fixed value and may then be adapted when the operating conditions of the passive mixer change, e.g. when the temperature of the passive mixer changes during operation.
  • one cancellation value may be fixed and the other may be adapted to a value that depends on one or more of the operating conditions, device mismatches, process spread or temperature.
  • the mixing component may comprise a field effect transistor switch having its drain operatively connected to the first terminal, its gate operatively connected to the third terminal and its source operatively connected to the second terminal.
  • the IM2 components to be cancelled may comprise a term proportional to the second order of the drain source voltage.
  • the passive mixer may be used in current mode, i.e. the second terminal (output terminal) of the mixing component may be grounded or may be at virtual ground.
  • the mixing component in this realization comprises a field effect transistor switch
  • the drain of the field effect transistor may receive the RF signal and the source of the field effect transistor may be connected to ground or to virtual ground.
  • a first sensing component may be used for sensing the voltage at the first terminal, e.g. the voltage at the drain of the field effect transistor.
  • the second terminal (output terminal) of the passive mixer is connected to ground or to virtual ground, so that, as outlined above, the IM2 components may be proportional to the square of the voltage at the first terminal, i.e. the square of the voltage of the RF signal.
  • the voltage sensed at the first terminal by the first sensing component may be considered.
  • the weighted first signal e.g. the weighted RF signal
  • the third signal e.g. the local oscillator signal
  • the weighted first signal e.g. the weighted RF signal
  • the bias voltage e.g. the bulk voltage of the field effect transistor
  • the first sensing component may be connected to the first terminal and to the cancellation component, in order so sense the voltage at the first terminal and in order to provide the weighted first signal to the cancellation component.
  • the cancellation component may be connected to the first terminal via the first sensing component and to the third terminal in order to receive the weighted first signal and to superimpose the weighted first signal and the third signal.
  • the first sensing component may be connected to the first terminal and to the cancellation component, in order to sense the voltage at the first terminal and in order to provide the weighted first signal to the cancellation component.
  • the cancellation component may be connected to the first terminal via the first sensing component and to the fourth terminal in order to receive the weighted first signal and to superimpose the weighted first signal and the bias voltage.
  • the second terminal of the mixing component may not be connected to a virtual ground and the passive mixer may not be used in current mode, but in voltage mode.
  • the second terminal of the mixing component e.g. the source of the field effect transistor
  • the second terminal of the mixing component is not connected to a virtual-ground node, but may be connected to a capacitor which itself may be connected to ground.
  • the second terminal of the mixing component may be loaded by the capacitor that may provide an RF short to ground.
  • the RF signal at the first terminal and the IF signal or BB signal at the second terminal my be widely separated in frequency. Therefore, the voltages at the first terminal and the second terminal may be sensed independently from each other.
  • the passive mixer comprises, in addition to the first sensing component for sensing the voltage at the first terminal, a second sensing component for sensing the voltage at the second terminal.
  • the second sensing component may be connected to the second terminal in order to sense the voltage at the second terminal and to the cancellation component in order provide the cancellation component with the information about the sensed voltage at the second terminal.
  • the cancellation component may not only be connected to the first sensing component and to the third terminal but may further be connected to the second terminal via the second sensing component in order to generate the first cancellation signal by not only considering the sensed voltage at the first terminal but by additionally considering the sensed voltage at the second terminal.
  • the passive mixer may further comprise two or more mixing components and a more-phase generator for generating the third signal with two or more different phases.
  • the more-phase generator may be supplied by two opposing signal sources and may in this way float with respect to ground in order to generate two or more phases of the third signal.
  • the two opposing current sources for supplying signal with opposing phases may by locally decoupled via a capacitor.
  • the different phases of the third signal may be individually fed into one or more of the two or more mixing components.
  • both of the two or more different phases may be fed into all of the two or more mixing components.
  • one of the different phases may be supplied to one of the mixing components, another of the different phases my be supplied to another one of the mixing components and so on.
  • the first signal weighted by the cancellation value is superimposed on one phase of the third signal and the first signal weighted by the same or an adapted cancellation value is superimposed on another phase of the third signal in order to generate the first cancellation signal having multiple phases.
  • each phase of the third signal may be modulated with the appropriate weighted first signal in order to generate the first cancellation signal at the respective mixing component.
  • the cancellation component may be adapted to generate the second cancellation signal by superimposing the first signal weighted by the cancellation value on the bias voltage.
  • the different phases of the third signal may then be provided to the third terminal of one or more of the two or more mixing components.
  • the passive mixer may be adapted to also consider IM2 due to other devices, e.g. base stations.
  • a transceiver apparatus comprising a transmitter for transmitting a radio frequency transmit signal and a receiver for receiving a radio frequency receive signal.
  • the receiver of the transceiver apparatus comprises a low noise amplifier for amplifying the high frequency receive signal; and a passive mixer comprising a local oscillator for generating a local oscillator signal; a cancellation component for generating a first cancellation signal for cancelling second order intermodulation components by superimposing the amplified radio frequency receive signal weighted by a cancellation value on the local oscillator signal; and a mixing component having a first terminal for receiving the amplified radio frequency receive signal, a second terminal for outputting one of an intermediate frequency signal and a baseband signal, and a third terminal for receiving the first cancellation signal, wherein the mixing component is adapted to provide one of the intermediate frequency signal and the baseband signal as output at the second terminal by mixing the amplified radio frequency receive signal provided as input at the first terminal and the first cancellation signal provided as input at the third terminal.
  • a further transceiver apparatus comprising a transmitter for transmitting a radio frequency transmit signal and a receiver for receiving a radio frequency receive signal.
  • the receiver of the transceiver apparatus comprises a low noise amplifier for amplifying the high frequency receive signal; and a passive mixer comprising a local oscillator for generating a local oscillator signal; a cancellation component for generating a second cancellation signal for cancelling second order intermodulation components by superimposing the amplified radio frequency receive signal weighted by a cancellation value on a bias voltage; and a mixing component having a first terminal for receiving the amplified radio frequency receive signal, a second terminal for outputting one of an intermediate frequency signal and a baseband signal, a third terminal for receiving the local oscillator signal, and a fourth terminal for receiving the second cancellation signal, wherein the mixing component is adapted to provide one of the intermediate frequency signal and the baseband signal as output at the second terminal by mixing the amplified radio frequency receive signal provided as input at the first terminal and the local oscillator signal provided as input at the
  • the receiver may further comprise one of a bandpass filter and a lowpass filter connected to the second terminal.
  • a lowpass filter may typically be connected to the second terminal of the mixing component for filtering the baseband signal via a passband of a predetermined frequency range.
  • a bandpass filter having a passband of a predetermined frequency range may typically be connected to the second terminal of the mixing component for filtering the intermediate frequency signal output at the second terminal.
  • the lowpass filter may be augmented by AC coupling (i.e. a highpass filter) when there is little signal energy at DC (e.g. for WCDMA) and the bandpass filter may be implemented as a combination of a highpass (or AC coupling) and a lowpass filter.
  • a mobile communication terminal is described also, the mobile communication terminal comprising the transceiver apparatus according to the third or fourth aspect as outlined above.
  • the method comprises the steps of generating, by a cancellation component, a first cancellation signal for cancelling second order intermodulation components by superimposing the first signal weighted by a cancellation value on the third signal; receiving, at a first terminal of a mixing component, the first signal; receiving, at a third terminal of the mixing component, the first cancellation signal; and outputting, at a second terminal of the mixing component, the second signal by mixing the first signal provided as input at the first terminal and the first cancellation signal provided as input at the third terminal.
  • the method comprises the steps of generating, by a cancellation component, a second cancellation signal for cancelling second order intermodulation components by superimposing the first signal weighted by a cancellation value on a bias voltage; receiving, at a first terminal of a mixing component, the first signal; receiving, at a third terminal of the mixing component, the third signal; receiving, at a fourth terminal of the mixing component, the second cancellation signal; and outputting, at a second terminal of the mixing component, the second signal by mixing the first signal provided as input at the first terminal and the third signal provided as input at the third terminal together with the second cancellation signal provided as input at the fourth terminal.
  • the cancellation value with which the first signal is weighted in order to generate the first and second cancellation signals may be a fixed value, e.g. 0.5 or a value around 0.5.
  • other values of the fixed cancellation values may be used which take into account the operating conditions, e.g. which provide a good compromise over process and temperature. It is also conceivable that a set of different cancellation values my be provided and that one of the set of different cancellation values may be selected based on the operating conditions.
  • the set of fixed cancellation values may comprise different values for different operating conditions.
  • the cancellation value may also be determined based on a voltage sensed by a first sensing component at the first terminal.
  • a voltage at the second terminal may be sensed by a second sensing component and the first cancellation signal, the second cancellation signal or both the first and the second cancellation signals may be generated by additionally considering the sensed voltage at the second terminal.
  • MOS Metal Oxide Semiconductor
  • FET Field Effect Transistor
  • JFET Junction Field Effect Transistor
  • MESFET Metal Semiconductor Field Effect Transistor
  • IGBT Insulated Gate Bipolar Transistor
  • the invention may make use of n-channel MOSFETs, p-channel MOSFETs, n-channel JFETs or p-channel JFETs.
  • ASIC application specific integrated circuit
  • the ASIC may be built from Field-programmable gate arrays (FPGAs), programmable logic devices (PLDs), like complex programmable logic devices (CPLDs), or any other standard parts known to those skilled in the art. It will also be appreciated that when the present invention is described as a method, this method may also be embodied on the ASIC.
  • FPGAs Field-programmable gate arrays
  • PLDs programmable logic devices
  • CPLDs complex programmable logic devices
  • FIG. 1 shows a block diagram of a radio frequency (RF) transceiver apparatus 110 for use in a mobile communication device 100.
  • the mobile communication device 100 comprising the RF transceiver apparatus 110 is adapted to transmit a radio frequency transmit signal 102 from an antenna 112 and is adapted to receive a radio frequency receive signal 104 with the antenna 112.
  • the mobile terminal comprises a duplexer 114 connected to the RF transceiver apparatus 110 via an impedance matching network 116 and a power amplifier 118, so that the transceiver apparatus 110 can be used for both transmitting the radio frequency transmit signal by means of a transmitter 130 and receiving the radio frequency receive signal by means of a receiver 120.
  • the impedance matching network 116 is connected to the receiver 120 of the RF transceiver apparatus 110 and the power amplifier 118 is connected to the transmitter 130 of the RF transceiver apparatus 110.
  • the transmitter 130 of the RF transceiver apparatus 110 comprises a driver amplifier 310, a mixer 330, a local oscillator (LO) 340 and a baseband (BB) filter 350.
  • the receiver 120 of the RF transceiver apparatus 110 comprises a low noise amplifier (LNA) 210, a mixer 230, a local oscillator (LO) 240 and a baseband (BB) filter 250.
  • LNA low noise amplifier
  • LO local oscillator
  • BB baseband
  • a data signal is passed to the BB filter 350, filtered by the BB filter 350 and passed to the mixer 330, where the BB data signal is up-converted into an RF signal using an LO signal generated by the LO 340.
  • the RF signal is then passed to the driver amplifier 310, the power amplifier 118, the duplexer 114 and finally to the antenna 112 for transmitting the RF transmit signal 102.
  • an RF receive signal 104 is received by the antenna 112, is passed by the duplexer 114 to the impedance matching network 116 and then to the receiver 120 of the RF transceiver apparatus 110.
  • the LNA 210 amplifies the RF receive signal
  • the mixer 230 directly down-converts the amplified RF receive signal into a BB signal by mixing the amplified RF receive signal with an LO signal generated by the LO 240 and then passes the BB signal to the BB filter 250 for further BB filtering and amplification.
  • Fig. 2 illustrates the receiver 120 of the RF transceiver apparatus 110 shown in Fig. 1 comprising the LNA 210 for amplifying the RF receive signal, the mixer 230 for downconverting the amplified RF receive signal into the BB signal by using the LO signal generated by the LO 240 and the BB amplifier 250 for filtering and amplifying the down-converted BB signal.
  • Fig. 3 schematically illustrates a passive mixer 230 of the receiver 120 shown in Fig. 2 useful for understanding the present invention.
  • the passive mixer 230 comprises a MOSFET 231 as a mixing component having a drain, a gate and a source (the bulk is grounded for ease of simplicity), the drain being operatively connected to a first terminal 232, the source being operatively connected to a second terminal 234 and the gate being operatively connected to a third terminal 236 of the passive mixer 230.
  • the first terminal 232 is adapted to receive the RF receive signal (amplified by the LNA 210), the second terminal 234 is adapted to output the BB signal and the third terminal is adapted to receive a third signal, a first cancellation signal, the generation of which will be described in more detail below.
  • I ds ⁇ ⁇ V ds ⁇ V gs - V th - V ds 2
  • I ds the drain-source current
  • ⁇ a geometry dependent constant
  • V gs the gate-source voltage
  • V ds the drain-source voltage
  • V th the MOSFET threshold voltage
  • the sign reversal in the drain-source current I ds reflects the change in reference direction due to the terminal swapping.
  • the cancellation of the IM2 term can be achieved by choosing the cancellation value ⁇ appropriately. Since the source is grounded V g will equal V gs . As shown above, the IM2 component is proportional to V rf *V rf /2.
  • the IM2 component can be canceled.
  • Fig. 3 The latter is exemplarily shown in Fig. 3 , where the RF signal is weighted by the amplifier 222 with the cancellation value ⁇ (by scaling the drive strength of the first sense amplifier 222 in relation to the LO) and is then added to the LO signal in order to generate the first cancellation signal at the cancellation component 220.
  • the first cancellation signal is then provided to the third terminal 236 (connected to the gate), the RF signal is provided to the first terminal 232 (connected to the drain) and the BB signal is generated as output at the second terminal 234 (connected to the source) by mixing the RF signal and the first cancellation signal.
  • the above will cancel the IM2 due to the MOSFET 231 switch channel conductance, which covers most of the switch conduction angle.
  • the MOSFET 231 will start in the sub-threshold region and will enter the saturation region as soon as any significant current starts to flow through the MOSFET 231.
  • the drain-source current I ds is much smaller and the characteristic is exponential also contributing with some IM2.
  • the cancellation value ⁇ When the cancellation value ⁇ is selected to deviate slightly from the linear cancellation criterion, i.e. the cancellation value ⁇ would be selected to not equal 0.5, the IM2 generated in the sub-threshold region and the saturation region can be compensated by allowing some residual IM2 in the linear region.
  • the cancellation value ⁇ can be tuned such that it nulls the sum of all IM2 contributions but does not null all individual IM2 components separately, e.g. the one in the linear region.
  • the cancellation component 220 is adapted to generate the first cancellation signal for cancelling IM2 components by superimposing the RF receive signal weighted by the cancellation value ⁇ on the LO signal.
  • the first sense amplifier 222 can be used in order to sense the voltage at the first terminal 232.
  • the appropriate cancellation value for cancelling the IM2 component can be determined by evaluating equation (1).
  • the unweighted RF receive signal is provided to the first terminal 232 of the MOSFET 231 and the first cancellation signal is provided to the third terminal 236 of the MOSFET 231.
  • the MOSFET 231 switch By mixing the amplified RF receive signal with the first cancellation signal, the MOSFET 231 switch outputs a BB signal at its source and thus at the second terminal 234 of the mixing component.
  • the BB signal is then filtered and amplified by the BB amplifier 250 comprising, for example as shown in Fig. 3 , an amplifier 252, a resistor 254 and a capacitor 256, wherein the resistor 254 and the capacitor are operatively connected to the input and the output of the amplifier 252 for feedback control.
  • Fig. 4 shows another mixer of the receiver shown in Fig. 2 useful for understanding the present invention, which is used in voltage mode.
  • the source of the MOSFET 231 and thus the second terminal 234 are not directly connected to virtual ground but are connected via an impedance, e.g. as shown in Fig. 4 a capacitor 258, to ground, i.e. the MOSFET 231 is loaded by the capacitor 258.
  • the voltage at the second terminal 234 is not close to zero since the second terminal 234 is not connected to virtual ground. Therefore, the voltage at the second terminal 234 has to be considered in equations (1) to (4) in order to determine the drain-source voltage V ds and the gate-source voltage V gs .
  • the drain-source voltage V ds is unlike in the first embodiment not merely equal to the RF voltage V rf but is equal to the difference between the RF voltage V rf at the first terminal 232 and the IF voltage V s at the second terminal 234.
  • the gate-source voltage V gs (without any additional cancellation signal) is not merely equal to the voltage of the LO signal V lo but is equal to the difference between the voltage of the LO signal and the source voltage V s (the voltage at the second terminal 234).
  • both the drain voltage V d at the first terminal 232 and the source voltage V s at the second terminal 234 have to be sensed in order to determine the drain-source voltage V ds and the gate-source voltage V gs of the MOSFET 231.
  • the RF voltage at the first terminal 232 and the IF voltage at the second terminal 234 are widely separated in frequency, they can be sensed independently.
  • the first sense amplifier 222 is used and in order to sense the voltage at the second terminal 234, a second sense amplifier 224 is used.
  • the sensed voltage at the first terminal 232 and the sensed voltage at the second terminal 234 are used to adapt the cancellation value ⁇ .
  • the RF signal is weighted by the cancellation value ⁇ 1 and the IF signal is weighted by the cancellation value ⁇ 2 and the weighted signals are provided to the cancellation component 220.
  • the cancellation values ⁇ 1 and ⁇ 2 may be the same for simplicity or individually set to maximize performance.
  • the LO signal is superimposed on both the weighted RF signal and the weighted IF signal, in order to generate a first cancellation signal which is then provided to the third terminal 236 and the gate of the MOSFET 231.
  • the output of the second terminal 234 is then again provided to the BB amplifier 252 for amplification and filtering.
  • Fig. 6 shows a passive mixer embodiment for cancelling second order intermodulation components.
  • the passive mixer is operated in current mode, like in the passive mixer of Fig. 3 , but in contrast to the passive mixer shown in Fig. 3 (and also to the second passive mixer embodiment shown in Figs. 4 ), the bulk terminal of the MOSFET 231, which is operatively connected to a fourth terminal 238 of the passive mixer, is additionally considered.
  • V th is a complex nonlinear function of the bulk, source and drain voltages
  • the above linearized model is thus not exact, but provides a good estimation.
  • the cancellation criterion ⁇ ⁇ ⁇ can be selected to slightly deviate from 0.5 in order to minimize the aggregate IM2 components.
  • the amplified RF receive signal is provided to the drain of the MOSFET 231 and the first sense amplifier 242 is adapted to sense the voltage of the RF signal at the first terminal 232 in order to the select the appropriate cancellation value.
  • the RF receive signal is weighted with the determined cancellation value and is superimposed on a bias voltage at the cancellation component 240 in order to generate the second cancellation signal.
  • the second cancellation signal is provided to the bulk terminal of the MOSFET 231.
  • the MOSFET 231 switch is adapted to mix the amplified RF receive signal provided as input at the drain and the local oscillator signal provided as input at the gate together with the second cancellation signal provided as input at the bulk of the MOSFET 231 in order to generate and output a BB signal at the source.
  • the BB signal is then amplified by the BB amplifier 250.
  • the passive mixer of Fig. 3 and the passive mixer embodiment of Fig. 6 can be combined to a fourth passive mixer embodiment as shown in Fig. 8 .
  • the voltage at the first terminal 232 is sensed by two distinct sense amplifiers 222, 242, a first one 222 connected to the first terminal 232 and the third terminal 236 (via a first cancellation component 220) and a second one 242 connected to the first terminal 232 and the fourth terminal 238 (via a second cancellation component 240).
  • two distinct cancellation values can be determined by the two sense amplifiers 222, 242, i.e. a first cancellation value determined by the first sense amplifier 222 and a second cancellation value determined by the second sense amplifier 242.
  • a first cancellation signal is determined by adding the RF signal weighted by the first cancellation value to the LO signal and a second cancellation signal is determined by adding the RF signal weighted by the second cancellation value on a bias voltage.
  • the first cancellation signal is input to the gate of the MOSFET 231 via the third terminal 236 and the second cancellation signal is input to the bulk of the MOSFET 231 via the fourth terminal 238.
  • a BB signal is provided at the source of the MOSFET 231 and the second terminal 234.
  • the BB signal is finally filtered and amplified by a BB amplifier 250.
  • an additional sense amplifier 244 is added to the passive mixer embodiment of Fig. 6 .
  • the additional (second) sense amplifier 244 is connected between the second terminal 234 and the second cancellation component 244 rather than to the first terminal 232 and the first cancellation component 220. In this way, the passive mixer embodiment shown in Fig. 9 operates in voltage mode.
  • the RF receive signal is weighted with a first cancellation value (determined by the first sense amplifier 242 by sensing the voltage at the first terminal 232) and, in addition thereto, the voltage (BB voltage) at the second terminal 234 is sensed by the second sense amplifier 244 so that the BB signal is weighted by a second cancellation value (determined by the second sense amplifier 244 by sensing the voltage at the second terminal 234).
  • Both the RF signal weighted by the first cancellation value and the IF signal (BB signal) weighted by the second cancellation value are added to a bias voltage at the cancellation component 240 in order to generate the second cancellation signal.
  • the second cancellation signal is provided to the bulk terminal of the MOSFET 231.
  • the MOSFET 231 switch is adapted to mix the amplified RF receive signal provided as input at the drain and the local oscillator signal provided as input at the gate together with the second cancellation signal provided as input at the bulk of the MOSFET 231 in order to generate and output a BB signal at the source.
  • the BB signal is then amplified by the BB amplifier 250.
  • a further sense amplifier 224 is added to the passive mixer embodiment of Fig. 9 .
  • the second cancellation signal which is provided to the bulk of the MOSFET 231, is determined in the way as described with respect to Fig. 9 above.
  • the further sense amplifier 224 is adapted to sense the voltage at the second terminal (like the sense amplifier 244).
  • the sense amplifier 244 and the sense amplifier 224 are both adapted to sense the voltage at the second terminal 234, the BB signal can be weighted with different cancellation values by the two amplifiers 224, 244.
  • the BB signal weighted by one cancellation value is supplied to the second cancellation component 240 (to generate the second cancellation signal) and the BB signal weighted by the same or a different cancellation value is supplied to the first cancellation component 220 to be added to the LO signal in order to generate the first cancellation signal.
  • a BB signal is generated and output at the source and finally filtered and amplified by a BB amplifier 250.
  • the passive mixer embodiment shown in Fig. 11 is a combination of the previously described passive mixers and passive mixer embodiments.
  • a first cancellation signal is generated by superimposing the RF signal weighted by a cancellation value and the BB signal weighted by a cancellation value on the LO signal at the first cancellation component 220 and a second cancellation signal is generated by superimposing the RF signal weighted by a cancellation value and the BB signal weighted by a cancellation value on the bulk voltage at the second cancellation component 240.
  • the first and second cancellation signals are then provided to the respective terminals of the MOSFET 231 (the gate and bulk) in order to generate the BB signal at the source as described above with respect to the passive mixers and passive mixer embodiments.
  • FIG. 12 An additional passive mixer embodiment is shown in Fig. 12 .
  • a more-phase generator exemplarily shown as a 4-phase generator 270 in Fig. 12 .
  • the 4-phase generator comprises two opposing signal sources in order to generate different phases of the LO signal received by the 4-phase generator 270 as input.
  • the RF receive signal (amplified by the LNA 210) is provided at the drain of four MOSFETs 231 shown in Fig. 12 .
  • the voltage of the RF signal (the voltage at the drain of the four MOSFETs 230) is sensed by the first sense amplifier 222 and the RF receive signal is weighted with a cancellation value by the first sense amplifier 222.
  • the weighted RF receive signal is then added to the different phases generated by the 4-phase generator 270 at the respective cancellation components 220.
  • the RF signals applied to the respective cancellation components 220 may be weighted with the same or with different cancellation values. If required by the operating conditions (mismatch, process speed, temperature and the like), the RF signal can be weighted with a first cancellation value and can be added (at a first cancellation component 220) to the first phase of the LO signal generated by the 4-phase generator 270 and the RF signal can be weighted by a second cancellation value (different from the first cancellation value) and can be added (at a second cancellation component 220) to the second phase of the LO signal generated by the 4-phase generator and so on. In this way the appropriate cancellation signals are determined.
  • the RF signal is then mixed by the four MOSFETs 231 with the respective cancellation signals in the same manner as described above to output BB (or IF) signals at the source of the MOSFETs 231 which are finally filtered by the BB amplifiers 250 in order to generate I and Q quadrature components.
  • the passive mixer embodiment illustrated in Fig. 13 differs from the passive mixer embodiment of Fig. 12 in that the weighted RF signal is superimposed on the bias voltage of the MOSFETs 231 rather than on the different phases of the LO signal.
  • the different phases of the LO signal are instead supplied to the gate of the MOSFETs 231.
  • the RF signal provided as input at the drain is mixed with the respective phase of the LO signal provided as input at the gate together with the cancellation signal provided as input at the bulk, in order to generate the BB (or IF) signal.
  • the technique described above results in noticeable IM2 improvements on the order of 20 dB, in particular for the current mode mixer. This significant improvement leads to decreased duplexer requirements and therefore to lower costs, smaller size and smaller losses.
  • the described technique eliminates the need for a SAW interstage filter between the LNA and the mixer, which also improves band flexibility and reduces the costs and size of the receiver structures and the devices.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Transceivers (AREA)
  • Superheterodyne Receivers (AREA)

Claims (14)

  1. Mélangeur passif (230) destiné à convertir un premier signal (RF) ayant une première fréquence en un deuxième signal (IF) ayant une deuxième fréquence par l'utilisation d'un troisième signal (LO) ayant une troisième fréquence, comprenant :
    - un premier composant d'annulation (240) apte à générer un premier signal d'annulation pour annuler des composants d'intermodulation de deuxième ordre par l'ajout du premier signal pondéré par une première valeur d'annulation (α) sur une tension de polarisation ; et
    - un composant de mélange (231) ayant une première borne (232) apte à recevoir le premier signal, une deuxième borne (234) apte à délivrer le deuxième signal, une troisième borne (236) apte à recevoir le troisième signal, et une quatrième borne (238) apte à recevoir le premier signal d'annulation, dans lequel le composant de mélange (231) est apte à fournir le deuxième signal en tant que sortie à la deuxième borne (234) par le mélange du premier signal fourni en tant qu'entrée à la première borne (232) et du troisième signal fourni en tant qu'entrée à la troisième borne (236) avec le premier signal d'annulation fourni en tant qu'entrée à la quatrième borne (238), dans lequel le composant de mélange (231) comprend un commutateur de transistor dont le drain est relié opérationnellement à la première borne (232), la grille est reliée opérationnellement à la troisième borne (236), la source est reliée opérationnellement à la deuxième borne (234) et la masse est reliée à la quatrième borne (238) ou dont la source est reliée opérationnellement à la première borne (232), la grille est reliée opérationnellement à la troisième borne (236), le drain est relié opérationnellement à la deuxième borne (234) et la masse est reliée à la quatrième borne (238).
  2. Mélangeur passif (230) selon la revendication 1, dans lequel le composant de mélange (231) comprend une paire de deux des commutateurs de transistor, dans lequel les deux commutateurs de transistors sont reliés en parallèle, ils partagent la première borne (232) et la deuxième borne (234) et chacun d'entre eux a une troisième borne distincte (236) et une quatrième borne distincte (238).
  3. Mélangeur passif (230) selon la revendication 1 ou 2, dans lequel le commutateur de transistor est un transistor à effet de champ, FET.
  4. Mélangeur passif (230) selon l'une quelconque des revendications 1 à 3, dans lequel le premier composant d'annulation (240) est relié à la première borne (232) et à la quatrième borne (238).
  5. Mélangeur passif (230) selon l'une quelconque des revendications précédentes, dans lequel la première valeur d'annulation pour le premier signal d'annulation est une valeur fixe.
  6. Mélangeur passif (230) selon l'une quelconque des revendications 1 à 4, comprenant en outre un premier composant de détection (242) apte à détecter la tension à la première borne (232) et à adapter la première valeur d'annulation sur la base de la tension détectée à la première borne (232).
  7. Mélangeur passif (230) selon la revendication 6, comprenant en outre :
    un deuxième composant d'annulation (220) apte à générer un deuxième signal d'annulation pour annuler les composants d'intermodulation de deuxième ordre par l'ajout du premier signal pondéré par une deuxième valeur d'annulation (α) sur le troisième signal ; et
    un deuxième composant de détection (222) apte à détecter la tension à la première borne (232) et à adapter la deuxième valeur d'annulation sur la base de la tension détectée à la première borne.
  8. Mélangeur passif (230) selon la revendication 6, comprenant en outre un deuxième composant de détection (244) apte à détecter la tension à la deuxième borne (234), dans lequel le premier composant d'annulation (240) est apte à générer le premier signal d'annulation pour qu'il soit en outre dépendant de la tension détectée à la deuxième borne (234).
  9. Mélangeur passif (230) selon la revendication 8, comprenant en outre :
    un deuxième composant d'annulation (220) apte à générer un deuxième signal d'annulation pour annuler les composants d'intermodulation de deuxième ordre par l'ajout du deuxième signal pondéré par une deuxième valeur d'annulation (α) sur le troisième signal ; et
    un troisième composant de détection (224) apte à détecter la tension à la deuxième borne (234) et à adapter la deuxième valeur d'annulation sur la base de la tension détectée à la deuxième borne (234).
  10. Mélangeur passif (230) selon la revendication 9, comprenant en outre un quatrième composant de détection (222) apte à détecter la tension à la première borne (232), dans lequel le deuxième composant d'annulation (220) est apte à générer le deuxième signal d'annulation pour qu'il soit en outre dépendant de la tension détectée à la première borne (232).
  11. Mélangeur passif (230) selon l'une quelconque des revendications précédentes dépendant de la revendication 4, dans lequel le premier composant d'annulation (240) est en outre relié à la deuxième borne (234).
  12. Mélangeur passif (230) selon l'une quelconque des revendications précédentes, comprenant en outre au moins deux composants de mélange (231) et un générateur de phase supplémentaire (270) apte à générer le troisième signal avec au moins deux phases différentes et à alimenter individuellement les phases différentes du troisième signal dans un ou plusieurs des au moins deux composants de mélange (231).
  13. Mélangeur passif (230) selon l'une quelconque des revendications précédentes, dans lequel le premier signal est un signal de radiofréquences, le troisième signal est un signal d'oscillateur local, et le deuxième signal est l'un d'un signal de fréquence intermédiaire et d'un signal de bande de base.
  14. Appareil émetteur-récepteur (110) comprenant un émetteur (130) destiné à émettre un signal d'émission de radiofréquences et un récepteur (120) destiné à recevoir un signal de réception de radiofréquences, dans lequel le récepteur (120) comprend :
    - un amplificateur à faible bruit (210) apte à amplifier le signal de réception de haute fréquence ; et
    - le mélangeur passif (230) selon l'une quelconque des revendications 1 à 13.
EP09749000.7A 2009-10-23 2009-10-23 Mélangeur passif doté d'une intermodulation réduite de second ordre Active EP2491647B1 (fr)

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PL15002353T PL2983289T3 (pl) 2009-10-23 2009-10-23 Mieszacz pasywny ze zmniejszoną intermodulacją drugiego rzędu
EP15002353.9A EP2983289B1 (fr) 2009-10-23 2009-10-23 Mélangeur passif avec intermodulation réduite de second ordre
EP18156694.4A EP3346606B1 (fr) 2009-10-23 2009-10-23 Mélangeur passif avec intermodulation réduite de second ordre
PL18156694T PL3346606T3 (pl) 2009-10-23 2009-10-23 Mieszacz pasywny o zredukowanej intermodulacji drugiego rzędu

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WO2011047703A1 (fr) 2011-04-28
US10411650B2 (en) 2019-09-10
PL2983289T3 (pl) 2018-09-28
US20120252374A1 (en) 2012-10-04
US10826433B2 (en) 2020-11-03
US20180076769A1 (en) 2018-03-15
DK2491647T3 (en) 2016-05-09
ES2675153T3 (es) 2018-07-09
EP3346606A1 (fr) 2018-07-11
US20190379327A1 (en) 2019-12-12
EP2983289B1 (fr) 2018-03-28
JP2013509056A (ja) 2013-03-07
ES2566754T3 (es) 2016-04-15
EP2491647A1 (fr) 2012-08-29
US9825590B2 (en) 2017-11-21
ES2776888T3 (es) 2020-08-03
JP5895198B2 (ja) 2016-03-30
EP3346606B1 (fr) 2019-12-04
PL3346606T3 (pl) 2020-07-13
EP2983289A1 (fr) 2016-02-10

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