EP0973359B1 - Elektronisches Vorschaltgerät mit Einschaltstrombegrenzung - Google Patents
Elektronisches Vorschaltgerät mit Einschaltstrombegrenzung Download PDFInfo
- Publication number
- EP0973359B1 EP0973359B1 EP99111406A EP99111406A EP0973359B1 EP 0973359 B1 EP0973359 B1 EP 0973359B1 EP 99111406 A EP99111406 A EP 99111406A EP 99111406 A EP99111406 A EP 99111406A EP 0973359 B1 EP0973359 B1 EP 0973359B1
- Authority
- EP
- European Patent Office
- Prior art keywords
- inverter
- electronic ballast
- winding
- reference potential
- storage capacitor
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
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Classifications
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
- H05B41/285—Arrangements for protecting lamps or circuits against abnormal operating conditions
- H05B41/2851—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
- H05B41/2856—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against internal abnormal circuit conditions
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
- Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10S315/00—Electric lamp and discharge devices: systems
- Y10S315/07—Starting and control circuits for gas discharge lamp using transistors
Definitions
- the invention relates to an electronic ballast for at least a fluorescent lamp according to the preamble of claim 1.
- Fluorescent lamps generally have an electronic ballast a harmonic filter connected to the mains voltage, to which a rectifier circuit connected with a boost converter. With this the rectified voltage usually with this particular group of power supplies approximately increased to the peak value of the feeding AC voltage and kept there.
- the step-up converter charges a storage capacitor defines up to the charge level specified thereby. This The storage capacitor thus forms a voltage-stabilized output stage the rectifier circuit.
- Another peculiarity of electronic Ballasts are used to supply the fluorescent lamp (s) Load circuit with a high frequency, possibly in its frequency also changing AC voltage. This is connected to the rectifier circuit an inverter connected, which will eventually use the load circuit said AC voltage in the form of a high-frequency pulse train fed.
- the inverter disclosed there is in the form of a push-pull chopper realized. This is from a vibration transmitter with two symmetrical Windings and switches connected to them.
- the published patent application WO 97/30569 discloses a ballast with a filter capacitor, which is connected to the output of a mains voltage rectifier and with an overvoltage limiting circuit that is connected in series to the filter capacitor is arranged around the inrush current flowing through the filter capacitor to limit.
- the overvoltage limiting circuit includes the Parallel connection of a resistor with a thyristor, which is between the filter capacitor and the ground reference potential is arranged.
- the invention is therefore based on the object of an electronic ballast to create the type mentioned, in which an active step-up converter is used is to be able to use its advantages, but at the same time an effective name Inrush current limitation is achieved with the simplest possible means.
- the current limitation is achieved by a simple limiting resistor reached, which is in series with the storage capacitor and also to the at low potential, the return path to the reference potential Rectifier assembly is connected.
- the advantage of such a simple circuit to limit the inrush current is in interaction with one from a half-bridge arrangement, inverters of the usual type today not to be exploited without further ado.
- This problem is solved in that the Inverter is designed as a converter network, through which already in the Switch-on phase a current path to the storage capacitor is closed.
- FIG. 1 is a block diagram of an electronic ballast for Fluorescent lamps shown.
- a rectifier arrangement 1 on the input side via a conventional mains switch SW1 to mains AC voltage u connected. This is done using a rectifier bridge rectified from diodes D1 to D4. At a high potential The output of this rectifier bridge is a charging choke in series L1 and a charging diode D5 polarized in the forward direction. The output of rectifier bridge D1 to D4 at low potential is placed on case ground.
- This is a defined reference potential Uref set for the entire electronic ballast. Is on the cathode side the charging diode D5 is connected to a storage capacitor C2, the second connection, is set to reference potential Uref, as in more detail will be presented.
- a series connection arranged out of the switching path of a second switch preferably an electronic switch SW2 and an ohmic resistor R0 exists.
- This second switch SW2 forms the switching element of one Rectifier of the rectifier order 1.
- the function is controlled this second switch SW2 via a control unit 4. Its inputs are at the high potential output of the rectifier bridge D1 to D4, an auxiliary winding assigned to the charging choke L1 L11, at the connection point of the second switch SW2 with that with it series resistance R0 or the high potential Connection of the storage capacitor C2 connected. Is on the output side this control unit 4 is connected to the control input of the second switch SW2.
- the rectifier arrangement 1 described above represents one in itself known basic circuit of an AC / DC converter active step-up converter for an electronic ballast. It requires therefore only a summary functional description, as follows.
- the rectifier bridge is connected to the outputs D1 to D4 emitted a pulsating DC voltage. This should by means of the storage capacitor forming the output stage of the rectifier arrangement 1 C2 transformed into a stabilized DC voltage U + become.
- An inverter 2 is connected to the rectifier arrangement 1 in this case designed as a transformer-controlled push-pull chopper is. This converts the one supplied by the rectifier arrangement 1 stabilized DC voltage U + into a high-frequency pulse train.
- a second choke L2 at the common connection point of two primary windings T1 / 1 or T1 / 2 of a vibration transmitter T1 connected.
- Second connections of these primary windings T1 / 1 and T1 / 2 are initially with each other via a resonance capacitor that is common to them C1 connected. Furthermore, these connections are each via the Switching distance of one of two further switches SW3 or SW4 to the reference potential Uref laid.
- a control network 5 is shown schematically in FIG. 1 specified for these two further switches SW3 and SW4, to the circuit details are shown in the further Figures 2 and 3, as still is to be described.
- the basic circuit shown in FIG. 1 for the inverter 2 with the symmetrically constructed vibration transmitter T1 it is known per se the function of the inverter 2 is therefore summarized as follows explain.
- the control unit 5 is designed so that it alternatively one of the two further switches SW3 and SW4 turns on.
- the Switch SW3 is conductive when the switching path is closed, so current overflows the other inductor L2 and the one, this currently conductive switch SW3 associated primary winding T1 / 1 of the vibration transmitter T1 back into the rectifier arrangement 1. This also becomes the resonance capacitor C1 charged, the voltage at the currently non-conductive Switch SW4 rises.
- a lamp load circuit 3 is via a secondary winding T1 / 4 of the vibration transmitter T1 inductively coupled to the inverter 2.
- a bipolar pulse train is in the lamp load circuit 3 coupled whose frequency through the switching periods of the two switches SW3 or SW4 of the inverter 2 is specified.
- two fluorescent lamps La1, La2 are provided in the lamp load circuit.
- La2 over one each Limiting capacitor C4 or C5 to one of the connections of the secondary winding T1 / 4 connected.
- the other filaments of the fluorescent lamps are together with the second connection of this secondary winding T1 / 4 directly connected.
- FIG. 1 also shows one associated with the storage capacitor C2 Network shown.
- This limiting resistance is in series with the storage capacitor C2, to the return branch lying at reference potential Uref in the Rectifier assembly 1 connected.
- the connection point of the storage capacitor C2 with the limiting resistor R1 is over one each Coupling diode D6 and D7 to the connection of the further switches SW3 or SW4 connected with the corresponding primary winding T1 / 1 or T1 / 2 of the vibration transmitter T1 is connected.
- Another diode is D8 the limiting resistor R1 connected in parallel.
- FIG 2 is another embodiment of the electronic ballast shown. This essentially corresponds to that already shown above with reference to Figure 1. Similar Circuit elements are identified by the same reference symbols. In the further description is therefore only on the differences from the embodiment according to Figure 1.
- FIG. 2 shows in more detail how the control unit 5 for the Both switches SW3 and SW4 of the inverter 2 can be configured.
- the vibration transmitter T1 has one further secondary winding T1 / 3, which has a connection immediately Reference potential Uref is set.
- Your second connection is via another Charging diode D9 connected to a second storage capacitor C3, the on the other hand is set to reference potential Uref.
- the cargo of this second Storage capacitor C3 supplies the supply voltages for the two Switches SW3 and SW4 of the inverter 2, which in this embodiment are designed as transistor switches.
- control inputs and are each one of the winding connections further secondary winding T1 / 5 of the vibration transmitter T1 on the one hand and via a further ohmic resistor R2 or R3 to the connection point of the second storage capacitor C3 with that assigned to it Charging diode D9 connected.
- This connection point is over one of these two resistors, in the example R2 and another resistor R5 to the output of the stabilized DC voltage U + Rectifier assembly 1 connected.
- The delivers in stationary operation with the basic connections of the switches SW3 or SW4 of the inverter 2 connected secondary winding T1 / 5 the commutator voltage to the alternative Activate these two switches.
- FIG. 3 shows a further embodiment of the electronic ballast shown, which is only of the embodiment in Figure 2 with regard to the control of the further, with its switching path Limiting resistor R1 distinguishes transistor switch Q1 connected in parallel.
- the two emitters are the transistor switches SW3, SW4 of the inverter 2 via a clamping diode D10 on the Reference potential Uref laid. This diode is also parallel to the emitter-base path of the further switching transistor Q1.
- the limiting resistor R1 limits the Inrush current during the start-up process. But as soon as the inverter 2 has started flows over the mutually conductive Transistor switch SW3 or SW4 current, which via the clamping diode D10 flows. The resulting voltage drop at the clamping diode D10 switches the further transistor switch Q1 conductive, which in turn the limiting resistor R1 shorts.
Landscapes
- Inverter Devices (AREA)
- Circuit Arrangements For Discharge Lamps (AREA)
- Rectifiers (AREA)
Description
- Figur 1
- ein Blockschaltbild eines elektronischen Vorschaltgerätes mit einer an Netzspannung liegenden Gleichrichteranordnung, die eine stabilisierte Gleichspannung einem angeschlossenen Wechselrichter zuführt, der seinerseits einen Lampenlastkreis mit einer hochfrequenten Impulsfolge versorgt, wobei der Gleichrichteranordnung eine Schaltung zur Einschaltstrombegrenzung in Form eines in ihrer Ausgangsstufe angeordneten Widerstandes zugeordnet ist,
- Figur 2, 3
- je eine weitere Ausführungsform des elektronischen Vorschaltgerätes nach Figur 1, wobei die Schaltung zur Einschaltstrombegrenzung jeweils einen Schalttransistor aufweist, dessen Schaltstrecke dem ohmschen Widerstand parallel liegt.
Claims (9)
- Elektronisches Vorschaltgerätmit einer durch Netzwechselspannung (u) gespeisten Gleichrichteranordnung (1) mit aktivem Hochsetzsteller, in deren Ausgangsstufe ein Speicherkondensator (C2) zwischen zwei, auf hohem Gleichspannungspotential (U+) bzw. auf Referenzpotential (Uref) liegenden Ausgängen angeordnet ist,mit einem an die Ausgänge der Gleichrichteranordnung angeschlossenen Wechselrichter (2) zum Umsetzen der darüber zugeführten Gleichspannung in eine hochfrequente Impulsfolge,mit einem auf der Ausgangsseite des Wechselrichters angeordneten Lastkreis (3) mit mindestens einer Leuchtstofflampe (La1 bzw. La2), undmit einem Netzwerk zum Begrenzen eines Einschaltstromes, das durch einen Begrenzungswiderstand (R1) gebildet ist, der in Serie mit dem Speicherkondensator (C2) liegend, mit seinem weiteren Anschluß auf Referenzpotential gelegt ist,der Wechselrichter (2) ein zwischen Gleichspannungspotential (U+) bzw. Referenzpotential (Uref) angeordnetes Umformernetzwerk (T1/1, T1/2, C1, SW3, SW4) mit zwei Brückenzweigen aufweist, die im stationären Betriebszustand alternativ auf das Referenzpotential durchgeschaltet sind, undder Verbindungspunkt des Speicherkondensators (C2) mit dem Begrenzungswiderstand (R1) mit den beiden Brückenzweigen des Umformernetzwerkes (T1/1, T1/2, C1, SW3, SW4) gekoppelt ist.
- Elektronisches Vorschaltgerät nach Anspruch 1, dadurch gekennzeichnet, daß der Wechselrichter (2), als Gegentaktinverter ausgebildet, einen symmetrischen Schwingübertrager (T1) mit zwei gleichartigen Primärwicklungen (T1/1, T1/2) besitzt, deren erste Wicklungsanschlüsse gemeinsam mit dem auf hohem Potential (U+) liegenden Ausgang des Hochsetzstellers (1) gekoppelt sind und deren zweite Wicklungsanschlüsse einerseits über einen Resonanzkondensator (C1) untereinander sowie andererseits über jeweils einen von zwei alternierend geschlossenen Schaltern (SW3 bzw. SW4) an Referenzpotential (Uref) liegen.
- Elektronisches Vorschaltgerät nach Anspruch 2, dadurch gekennzeichnet, daß die Schalter (SW3, SW4) des Wechselrichters (2) als bipolare Transistoren (Q2 bzw. Q3) ausgebildet sind, über deren Schaltstrecken jeweils die zweiten Wicklungsanschlüsse der beiden Wicklungen (T1/1, T1/2)) des Schwingübertragers (T1) auf Referenzpotential (Uref) gelegt sind und daß der Wechselrichter ferner ein transformatorisch an den Schwingübertrager angekoppeltes Ansteuernetzwerk (T1/3, T1/4, D7, C3, R2, R3, R5) für die beiden Transistoren aufweist.
- Elektronisches Vorschaltgerät nach Anspruch 3, dadurch gekennzeichnet, daß der Schwingübertrager (T1) eine dritte Wicklung (T1/3) aufweist, die mit einem ersten Wicklungsanschluß auf Referenzpotential (Uref) gelegt ist und deren zweiter Wicklungsanschluß über eine in Vörwärtsrichtung gepolte Diode (D9) sowie einen über einen Verbindungspunkt damit in Serie liegenden zweiten Speicherkondensator (C3) auf Referenzpotential gelegt ist, daß dieser Verbindungspunkt über je einen weiteren Widerstand (R2 bzw. R3) jeweils an die Basis eines der beiden Transistoren (SW3 bzw. SW4) sowie über einen dieser weiteren Widerstände (z. B. R2) an das hohe Gleichspannungspotential (U+) angeschlossen ist und daß eine weitere Wicklung (T1/5) des Schwingübertragers mit je einem ihrer Wicklungsanschlüsse an die Basis eines der beiden Transistoren angeschlossen ist.
- Elektronisches Vorschaltgerät nach einem der Ansprüche 2 bis 4, dadurch gekennzeichnet, daß der Schwingübertrager (T1) zum Ankoppeln des Lastkreises (3) an den Wechselrichter (2) eine weitere Wicklung (T1/4) aufweist und die mindestens eine Leuchtstofflampe (La1, La2) mit ihren Wendeln unmittelbar bzw. über einen Kondensator (C4 bzw. C5) mit beiden Wicklungsanschlüssen dieser weiteren Wicklung verbunden ist.
- Elektronisches Vorschaltgerät nach einem der Ansprüche 2 bis 5, dadurch gekennzeichnet, daß dem Begrenzungswiderstand (R1) eine in Gegenrichtung gepolte Diode (D8) parallel geschaltet ist.
- Elektronisches Vorschaltgerät nach einem der Ansprüche 2 bis 6, dadurch gekennzeichnet, daß ein Verbindungspunkt zwischen dem Speicherkondensator (C2) der Gleichrichteranordnung (1) und dem Begrenzungswiderstand (R1) über jeweils eine Koppeldiode (D6 bzw. D7) jeweils mit dem Anschluß der weiteren Schalter (SW3 bzw. SW4) verbunden ist, der an einen der zweiten Wicklungsanschlüsse der beiden Primärwicklungen (T1/1 bzw. T1/2) des Schwingübertragers (T1) angeschlossen ist.
- Elektronisches Vorschaltgerät nach einem der Ansprüche 4 bis 6, dadurch gekennzeichnet, daß in dem Netzwerk zum Begrenzen des Einschaltstromes ein bipolarer Schalttransistor (Q1) vorgesehen ist, der mit seiner Schaltstrecke dem Begrenzungswiderstand (R1) parallel liegend angeordnet ist und mit seiner Basis über einen weiteren Widerstand (R4) an den Verbindungspunkt des zweiten Speicherkondensators (C3) mit der diesem zugeordneten Diode (D9) angeschlossen ist.
- Elektronisches Vorschaltgerät nach einem der Ansprüche 4 bis 6, dadurch gekennzeichnet, daß die auf niedrigem Potential liegenden Anschlüsse der beiden bipolaren Transistoren (SW3 bzw. SW4) des Wechselrichters (2), parallel geschaltet, über eine weitere in Gegenrichtung gepolte Diode (D10) auf Referenzpotential (Uref) gelegt sind und daß in dem Netzwerk zum Begrenzen des Einschaltstromes ein bipolarer Schalttransistor (Q1) vorgesehen ist, der mit seiner Schaltstrecke dem Begrenzungswiderstand (R1) parallel liegend angeordnet ist und mit seiner Emitter-Basis-Strecke der weiteren Diode (D 10) parallel liegend angeordnet ist.
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
DE19830368A DE19830368A1 (de) | 1998-07-07 | 1998-07-07 | Elektronisches Vorschaltgerät mit Einschaltstrombegrenzung |
DE19830368 | 1998-07-07 |
Publications (3)
Publication Number | Publication Date |
---|---|
EP0973359A2 EP0973359A2 (de) | 2000-01-19 |
EP0973359A3 EP0973359A3 (de) | 2002-11-13 |
EP0973359B1 true EP0973359B1 (de) | 2004-08-25 |
Family
ID=7873250
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
EP99111406A Expired - Lifetime EP0973359B1 (de) | 1998-07-07 | 1999-06-11 | Elektronisches Vorschaltgerät mit Einschaltstrombegrenzung |
Country Status (4)
Country | Link |
---|---|
US (1) | US6078144A (de) |
EP (1) | EP0973359B1 (de) |
CA (1) | CA2276913C (de) |
DE (2) | DE19830368A1 (de) |
Families Citing this family (12)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US6366029B1 (en) * | 2000-05-31 | 2002-04-02 | Keith Billings | Lamp ballast for reducing interference current |
US6417629B1 (en) * | 2000-12-06 | 2002-07-09 | Koninklijke Philips Electronics N.V. | Push-pull based voltage-clamping electronic ballast |
DE10160790A1 (de) * | 2001-01-12 | 2002-08-08 | Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh | Schaltungsanordnung zum Einschalten einer Teilschaltungsanordnung |
DE10108138A1 (de) * | 2001-02-20 | 2002-08-29 | Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh | Schutzschaltung für eine Leuchstofflampe |
AUPR610801A0 (en) * | 2001-07-04 | 2001-07-26 | Briter Electronics | Controlling apparatus |
DE10325872A1 (de) * | 2003-06-06 | 2004-12-23 | Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH | Ansteuerschaltung für den Betrieb mindestens einer Lampe in einem dazugehörigen Lastkreis |
US7109668B2 (en) * | 2003-10-30 | 2006-09-19 | I.E.P.C. Corp. | Electronic lighting ballast |
US20070194721A1 (en) * | 2004-08-20 | 2007-08-23 | Vatche Vorperian | Electronic lighting ballast with multiple outputs to drive electric discharge lamps of different wattage |
US20100109554A1 (en) * | 2007-04-25 | 2010-05-06 | Osram Gesellschaft Mit Beschraenkter Haftung | Illumination device having inrush current limiting circuit |
US8294295B2 (en) * | 2010-05-24 | 2012-10-23 | Xiamen Lanxi Technology Co., Ltd. | Power supply method with parallel-connected batteries |
WO2012098632A1 (ja) * | 2011-01-17 | 2012-07-26 | 三菱電機株式会社 | スイッチング電源装置 |
DE102011089553A1 (de) * | 2011-12-22 | 2013-06-27 | Robert Bosch Gmbh | Elektronisches Vorschaltgerät für eine Gasentladungslampe |
Family Cites Families (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5343122A (en) * | 1989-07-27 | 1994-08-30 | Ken Hayashibara | Luminaire using incandescent lamp as luminous source |
DE3934577A1 (de) * | 1989-10-17 | 1991-04-18 | Philips Patentverwaltung | Stromversorgungseinrichtung mit einschaltstrombegrenzungsschaltung |
ES2123986T3 (es) * | 1994-06-28 | 1999-01-16 | Koninkl Philips Electronics Nv | Disposicion de circuito. |
WO1997012308A1 (en) * | 1995-09-29 | 1997-04-03 | Motorola Inc. | In-rush current reduction circuit for boost converters and electronic ballasts |
WO1997030569A1 (en) * | 1996-02-13 | 1997-08-21 | Energy Savings, Inc. | In-rush surge limiting electronic ballast |
-
1998
- 1998-07-07 DE DE19830368A patent/DE19830368A1/de not_active Withdrawn
-
1999
- 1999-06-11 DE DE59910327T patent/DE59910327D1/de not_active Expired - Fee Related
- 1999-06-11 EP EP99111406A patent/EP0973359B1/de not_active Expired - Lifetime
- 1999-07-02 US US09/346,913 patent/US6078144A/en not_active Expired - Fee Related
- 1999-07-06 CA CA002276913A patent/CA2276913C/en not_active Expired - Fee Related
Also Published As
Publication number | Publication date |
---|---|
CA2276913C (en) | 2008-09-02 |
DE59910327D1 (de) | 2004-09-30 |
EP0973359A3 (de) | 2002-11-13 |
DE19830368A1 (de) | 2000-02-03 |
CA2276913A1 (en) | 2000-01-07 |
US6078144A (en) | 2000-06-20 |
EP0973359A2 (de) | 2000-01-19 |
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