EP0860893A1 - Konzentrische Gruppe von Mikrowellenantennen - Google Patents

Konzentrische Gruppe von Mikrowellenantennen Download PDF

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Publication number
EP0860893A1
EP0860893A1 EP98400436A EP98400436A EP0860893A1 EP 0860893 A1 EP0860893 A1 EP 0860893A1 EP 98400436 A EP98400436 A EP 98400436A EP 98400436 A EP98400436 A EP 98400436A EP 0860893 A1 EP0860893 A1 EP 0860893A1
Authority
EP
European Patent Office
Prior art keywords
antenna
housing
assembly according
ring
center
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP98400436A
Other languages
English (en)
French (fr)
Inventor
Hervé Legay
Thierry Rostan
Frédéric Croq
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Alcatel Lucent SAS
Original Assignee
Alcatel SA
Alcatel Alsthom Compagnie Generale dElectricite
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Alcatel SA, Alcatel Alsthom Compagnie Generale dElectricite filed Critical Alcatel SA
Publication of EP0860893A1 publication Critical patent/EP0860893A1/de
Withdrawn legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
    • H01Q1/523—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas between antennas of an array
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/10—Resonant slot antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/40—Imbricated or interleaved structures; Combined or electromagnetically coupled arrangements, e.g. comprising two or more non-connected fed radiating elements
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/40—Imbricated or interleaved structures; Combined or electromagnetically coupled arrangements, e.g. comprising two or more non-connected fed radiating elements
    • H01Q5/42—Imbricated or interleaved structures; Combined or electromagnetically coupled arrangements, e.g. comprising two or more non-connected fed radiating elements using two or more imbricated arrays

Definitions

  • the invention relates to a set of antennas transmission or reception of waves in the microwave domain.
  • the antennas provided for a band frequencies are not optimized for another band of frequencies. This is why we usually provide an antenna by frequency band.
  • this multiplication of antennas poses problems of congestion, in particular for the space applications.
  • the invention starts from the observation that the purity of signals emitted by an assembly with at least two concentric antennas is not always satisfactory and that the origin of the disturbance is found in the antenna signal transmission central to the peripheral antenna.
  • the invention is characterized in that, between a indoor antenna, for example central, and an antenna concentric further from the center, a means is provided for prevent or attenuate the propagation of indoor antenna waves to the other antenna.
  • Said means is for example a quarter wave trap, tuned to the wavelength of the signals provided for the antenna interior.
  • each antenna has a conductive housing having walls extending substantially parallel to the axis of the antenna, the trap being formed in the interval separating the outer wall of the inner antenna housing of the wall inside the annular housing of the peripheral antenna.
  • the interval has a length, in the direction of the axis, about a quarter of the wavelength of signals to be transmitted by the indoor antenna.
  • the propagation of waves from the cavity housing the indoor antenna towards the cavity housing the other antenna limits the origin of the radiation of the upper band antenna.
  • the exterior wall of the interior antenna housing forms, in one embodiment, a single piece with the inner wall of the peripheral antenna housing. These two single-piece walls define a closed toroidal volume of side and open on the other. At the bottom of this toric volume, we can have a conductive crown to adjust the length of the trap.
  • the invention is not limited to the combination of two concentric antennas.
  • the antenna shown in Figure 1 is intended for receive or transmit microwave signals in two bands, namely, on the one hand, the S band at 2 GHz and, on the other hand, the UHF band at 400 MHz.
  • This antenna is mainly intended to be located on small satellites, such as satellites assigned to the location of objects or for missions measurement or remote control with conventional satellites. Because of this application, it must present a small footprint, wide angular coverage for both frequency bands as well as circular polarization with a suitable ellipticity rate over this wide angular coverage, especially for the most distant orientations from the axis.
  • the antenna 10 shown in FIG. 1 is of the type combined. It is formed by the association of two planar antennas concentric, respectively 14 and 16. Each of the antennas 14 and 16 and the assembly 10 have an axis 12 of symmetry of rotation.
  • the central antenna 14, of smaller dimensions, is for the 2 GHz S-band and the outdoor antenna 16, of larger dimensions, is intended for the UHF band at 400 MHz.
  • Each of the individual antennas 14, 16 has a dielectric substrate, respectively 18 and 20, on which is deposited a conductive ring, respectively 22 and 24. Both rings 22 and 24 are centered on axis 12.
  • Each of the substrates is enclosed in a metal housing of cylindrical shape with an axis 12.
  • the housing for the antenna 14 has the reference 25 and the housing for the antenna 16 has the reference 26.
  • the latter housing is limited, of a on the one hand, by a cylindrical outer wall 26 1 and, on the other hand, by an inner cylindrical wall 26 2 at a short distance from the wall of the housing 25.
  • the space 28 formed between the wall of the housing 25 and the wall 26 2 has a length (in the direction of the axis 12) equal to a quarter of the length of the S-band waves, that is to say 35 mm about. It is open, in 29, on the side where the emission occurs. It constitutes a trap intended to prevent the propagation of leakage currents from the ring 22 to the ring 24.
  • a metal filling ring 36 can be arranged at the bottom of the space 28 to adjust the length (parallel to axis 12) of this space 28 so that it is equal to the quarter of the wavelength of the S band.
  • the walls 25 and 26 2 can be formed from the same sheet of metal.
  • a metal ring or crown 30 Around the housing 26, substantially in the plane of the ring 24, and therefore perpendicular to the axis 12, is a metal ring or crown 30.
  • the inner rim 32 of the crown 30 is connected to a skirt 34 moving away, on the one hand, from the crown 30 in the direction from the bottom of the housing 26 and, on the other hand, from the axis 12.
  • the angle formed, in the plane of Figure 1, by the plane of the crown 30 and the skirt 34 is of the order of 45 °.
  • the ring 22 radiates in a cone of axis 12 of half angle at the top ⁇ equal to about 60 °. However, there is still a radiation outside this cone.
  • the purpose of crown 30 is to diffract waves deflected outward to increase omnidirectionality antenna 14.
  • the crown 30 tended to degrade the circular polarization of the radiation, that is, to degrade the rate of ellipticity.
  • the experience has shown that the skirt 34 made it possible to maintain a rate of ellipticity waves with circular polarization close to 1, especially for directions forming a large angle with axis 12.
  • the ellipticity rate can be adjusted empirically by varying the orientation of the skirt 34, that is to say the angle that it forms with the plane of the crown 30 as well as by making vary its dimensions.
  • the outer edge 34 1 of the skirt 34 is further from the axis 12 than the outer edge 30 1 of the crown 30.
  • the inside diameter of the crown 30 is 256 mm, its outside diameter 300 mm, while the outer diameter of the skirt 34 - which has a generally frustoconical shape - is 348 mm.
  • Skirt 34 is thought to create wave diffraction in S-band which opposes the negative effect of the diffracting crown 30 on the ellipticity rate of S-band waves
  • housings or cavities 25 and 26 contribute to symmetrizing the radiation diagram around axis 12 and to improve the ellipticity rate.
  • the dielectric substrates 18 and 20 have a relative dielectric permittivity ⁇ r of the order of 2.5. As indicated above, the higher this dielectric permittivity, the more the dimensions of the antennas can be reduced. However, the increase in the dielectric constant is unfavorable for maintaining the circular polarization. This is why, in the example, the constant ⁇ r does not exceed the value 2.5.
  • Figures 1a, 1b and 1c are diagrams allowing to highlight the advantages, on the one hand, of the quarter trap wave formed by the annular space 28 and, on the other hand, diffracting elements 30 and 34.
  • Figure 1a is a diagram for a similar antenna to that of Figure 1 but lacking, on the one hand, the quarter trap wave 28 and, on the other hand, diffracting elements 30 and 34.
  • Curve 40 corresponds to normal polarization and the curves 41 correspond to the cross polarization.
  • the purity of circular polarization is all the greater as large difference between curves 40 and 41.
  • the emission weakens appreciably as soon as moves away from axis 12.
  • Figure 1b corresponds to an antenna similar to that of figure 1, with a quarter-wave trap 28, however deprived diffracting elements 30 and 34.
  • FIG. 1c corresponds to the antenna shown in FIG. 1, with a quarter-wave trap 28, the crown 30 and the skirt 34. It can be seen, compared with FIG. 1b, that omnidirectionality is everything quite satisfactory up to an angle ⁇ of 60 °. In addition, the purity of circular polarization is significantly improved between the angles 30 ° and 60 °, the distance between the curves 40 2 and 41 2 being significantly greater.
  • the compactness of the antenna is increased by giving a crenellated shape or by meanders at rings 22 and 24.
  • the ring 22 comprises, regularly distributed around the axis 12, eight internal segments 46 1 to 46 8 alternated with eight external segments 48 1 to 48 8 . These segments 46 and 48 in the form of arcs of circles are connected at their ends by rectilinear segments 50, of radial directions. Thus, in this example, the radial segments are sixteen.
  • the ring 24 is homothetic with the ring 22.
  • the guided wavelength of the radiation to be transmitted is directly proportional to the electrical length of the ring resonant antenna 14 (14 ') or 16 (16'). This length electric is equal to the sum of the lengths of all segments 46, 48 and 50.
  • an antenna according to the invention has a smaller footprint than a shaped antenna simply circular. Indeed, we note that, compared to a circular ring with the same diameter as the circle on which are arranged the segments 48, the electrical length is increased by approximately the sum of the lengths of the segments 50.
  • the longer the length of the segments 50 is large and the more the efficiency of the antenna decreases.
  • the antenna radiation impedance decreases because the ribbon metallic further obscures the opening; so the proportion of energy dissipated in the conductor or the dielectric is more important. It is therefore preferable that the ratio between the diameter outside and inside diameter be at most around of two.
  • Figure 4 shows, in exploded perspective, the various components of the antenna combined with 22 'rings and 24 ′ of the type of those in FIG. 3.
  • the crown 30 and the skirt 34 inclined at 45 ° constitute a single piece holding 50.
  • the 24 'and 22' rings are made by engraving on dielectric substrates, respectively 18 and 20, of a material called "polypenco".
  • the rings 22 'and 24' separated from the substrates 18 and 20; but it goes from these rings are deposited on the respective substrates 18 and 20.
  • a coaxial cable 60 passes through the bottom 52 of the housing 25 to bring the excitation signal to the distributor 54.
  • the role of the latter is to distribute, with appropriate phase shifts, the excitation signal between the four exterior segments 48 'of the 14 'ring.
  • a distributor 58 is arranged between the bottom 56 of the housing 26 and the dielectric 20 .
  • a coaxial cable 62 crosses the bottom 56 to bring the UHF excitation signal to the distributor 58 which distributes, with appropriate phase shifts, this excitation signal between the four outer segments of the ring 24 '.
  • FIGS 5, 6 and 7 show the distributor 54.
  • the circuits 64 shown in FIGS. 5 and 6, allow, from the excitation signal provided by the coaxial 60, to obtain a circular polarization. To this end, they supply the four exterior segments 48 ′ with phase shifts successive 90 °.
  • the signal brought by the coaxial 60 is applied to an input 66 which, as shown in FIG. 5, is connected to the input of a 180 ° phase shifter 70 via a transformer 68.
  • the output 70 1 without phase shift of the phase shifter 70 is connected to a port 74 which is itself connected to a 90 ° phase shifter 78 via a transformer 76.
  • the output 70 2 with 180 ° phase shift from the phase shifter 70 is connected to a another port 80, which is connected to a second 90 ° phase shifter 84 by means of a transformer 82.
  • the output 78 1 without phase shift of the phase shifter 78 is connected to a first output 90 1 of the circuit 64 via a transformer 86 and an adapter 88.
  • the output 90 1 is connected to a first external segment of the 22 'ring.
  • the 90 ° phase shift output 78 2 of the phase shifter 78 is connected to a second output 90 2 , via another transformer and another adapter.
  • the outlet 90 2 is connected to a second outer segment of the ring 22 '.
  • phase-free output 84 1 of the phase shifter 84 is connected to the third output 90 3 via a transformer and an adapter.
  • This outlet 90 3 is connected to a third outer segment of the ring 22 '.
  • the output 84 2 of 90 ° phase shift from the phase shifter 84 is connected to the fourth output 90 4 of the circuit 64 by means of a transformer and an adapter.
  • This outlet 90 4 is connected to a fourth outer segment of the ring 22 '.
  • the signal on output 90 1 is in phase with the input signal on the first port 66, while the signals on outputs 90 2 , 90 3 and 90 4 are phase shifted by 90 °, 180 ° and 270 ° respectively. relative to the input signal.
  • the outlets 90 1 to 90 4 are located on the periphery of the cutouts and regularly distributed; these outputs are in line with the outer segments of the ring 22 'to which they are connected.
  • the cutouts metallic are sandwiched between dielectric distributors, 102 and 104 respectively.
  • each output 90 of circuit 64 is effected by means of a probe 92.
  • Four probes are therefore provided. In FIG. 7, the probe 92 1 is shown .
  • the distributor 64, 102, 104 is enclosed in a housing metallic 106 constituting a trap preventing excitation of surface waves on the distributor.
  • circuit 64 is made using metal engravings on a substrate.
  • a diffraction ring 30 surrounds the outermost antenna and this crown 30 is integral with a skirt 34 oriented substantially at 45 ° relative to the plane of the crown 30.
  • a quarter trap wave 28 prevents the propagation of a leakage current from the cavity excited towards the surrounding cavities.
  • a quarter wave trap 116 prevents the propagation of a current of leak to antenna 114.
  • the trap 116 is of greater length (along the axis) that the trap 28 because it is intended to eliminate lengths wave, those of the signals emitted by the antenna 112.
  • a number of antennas can be provided concentric greater than three.
  • FIG. 9 represents a resonant annular cavity which applies more particularly to a slot antenna.
  • this example could apply also to a resonant ring antenna formed by a conductor metallic.
  • the ring 130 is constituted by a slot 132 in a metallic conductor 134.
  • This ring 130 forms meanders each having substantially the shape of a petal. Number of petals is, in this embodiment, equal to 8.
  • the excitation be performed on the outer segments using a coaxial cable, it is also possible to provide excitation by coupling proximity with a microstrip line or with a slit in the ground plane, that is to say in a bottom of the cavity.

Landscapes

  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Waveguide Aerials (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
EP98400436A 1997-02-24 1998-02-23 Konzentrische Gruppe von Mikrowellenantennen Withdrawn EP0860893A1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR9702171 1997-02-24
FR9702171A FR2760131B1 (fr) 1997-02-24 1997-02-24 Ensemble d'antennes concentriques pour des ondes hyperfrequences

Publications (1)

Publication Number Publication Date
EP0860893A1 true EP0860893A1 (de) 1998-08-26

Family

ID=9504099

Family Applications (1)

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EP98400436A Withdrawn EP0860893A1 (de) 1997-02-24 1998-02-23 Konzentrische Gruppe von Mikrowellenantennen

Country Status (4)

Country Link
US (1) US5995058A (de)
EP (1) EP0860893A1 (de)
CA (1) CA2228637A1 (de)
FR (1) FR2760131B1 (de)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2826512A1 (fr) * 2001-06-22 2002-12-27 Thomson Licensing Sa Antenne compacte a fente annulaire

Families Citing this family (11)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6329950B1 (en) * 1999-12-06 2001-12-11 Integral Technologies, Inc. Planar antenna comprising two joined conducting regions with coax
GB2390225A (en) * 2002-06-28 2003-12-31 Picochip Designs Ltd Radio transceiver antenna arrangement
EP2003729B1 (de) * 2006-03-16 2012-11-28 Mitsubishi Electric Corporation Antennenanordnung und verfahren zu ihrer herstellung
US9184504B2 (en) * 2011-04-25 2015-11-10 Topcon Positioning Systems, Inc. Compact dual-frequency patch antenna
US9356353B1 (en) * 2012-05-21 2016-05-31 The Boeing Company Cog ring antenna for phased array applications
US9425516B2 (en) * 2012-07-06 2016-08-23 The Ohio State University Compact dual band GNSS antenna design
US10693218B2 (en) * 2014-07-01 2020-06-23 Microsoft Technology Licensing, Llc Structural tank integrated into an electronic device case
US9912050B2 (en) 2015-08-14 2018-03-06 The Boeing Company Ring antenna array element with mode suppression structure
US9985341B2 (en) 2015-08-31 2018-05-29 Microsoft Technology Licensing, Llc Device antenna for multiband communication
US10186773B2 (en) * 2016-11-02 2019-01-22 The United States Of America As Represented By Secretary Of The Navy Electrically conductive resonator for communications
FR3114195B1 (fr) * 2020-09-11 2023-11-03 Arianegroup Sas Antenne à couverture améliorée sur un domaine de fréquence élargi

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2791769A (en) * 1950-09-27 1957-05-07 Rca Corp Dual slot wide band antenna
US4208660A (en) * 1977-11-11 1980-06-17 Raytheon Company Radio frequency ring-shaped slot antenna
US4740795A (en) * 1986-05-28 1988-04-26 Seavey Engineering Associates, Inc. Dual frequency antenna feeding with coincident phase centers

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2522883A1 (fr) * 1982-03-05 1983-09-09 Thomson Csf Joint pivotant pour guides d'ondes hyperfrequences
US4740975A (en) * 1987-03-31 1988-04-26 American Telephone And Telegraph Company, At&T Bell Laboratories Congruently melting complex oxides
US4821040A (en) * 1986-12-23 1989-04-11 Ball Corporation Circular microstrip vehicular rf antenna
US5220337A (en) * 1991-05-24 1993-06-15 Hughes Aircraft Company Notched nested cup multi-frequency band antenna

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2791769A (en) * 1950-09-27 1957-05-07 Rca Corp Dual slot wide band antenna
US4208660A (en) * 1977-11-11 1980-06-17 Raytheon Company Radio frequency ring-shaped slot antenna
US4740795A (en) * 1986-05-28 1988-04-26 Seavey Engineering Associates, Inc. Dual frequency antenna feeding with coincident phase centers

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2826512A1 (fr) * 2001-06-22 2002-12-27 Thomson Licensing Sa Antenne compacte a fente annulaire
EP1271693A1 (de) * 2001-06-22 2003-01-02 Thomson Licensing S.A. Kompakte Ringschlitzantenne
US6670929B2 (en) 2001-06-22 2003-12-30 Thomson Licensing S.A. Compact annular-slot antenna
CN1393959B (zh) * 2001-06-22 2010-05-12 汤姆森许可贸易公司 紧凑型环状隙缝天线

Also Published As

Publication number Publication date
FR2760131A1 (fr) 1998-08-28
CA2228637A1 (fr) 1998-08-24
US5995058A (en) 1999-11-30
FR2760131B1 (fr) 1999-03-26

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