EP0369593B1

EP0369593B1 - Processing circuit for variable reluctance transducer

Info

Publication number: EP0369593B1
Application number: EP89310157A
Authority: EP
Inventors: Karl Edwards
Original assignee: Lucas Industries Ltd
Current assignee: ZF International UK Ltd
Priority date: 1988-10-06
Filing date: 1989-10-04
Publication date: 1993-12-22
Anticipated expiration: 2009-10-04
Also published as: DE68911655T2; US5012207A; EP0369593A2; JPH02222811A; EP0369593A3; DE68911655D1; ES2048294T3

Description

This invention relates to a circuit for processing the output signal from a variable reluctance transducer.
It is known to use variable reluctance transducers for monitoring the rotation of rotatably mounted elements. The variable reluctance transducer comprises a toothed wheel of magnetic material which is mounted for rotation with the element being monitored, and a sensor having a coil wound on a core and mounted so that in operation the successive teeth of the wheel pass the sensor. The gap between the wheel and the sensor varies as the wheel rotates, causing a corresponding variation in the reluctance of the magnetic path through the sensor core and therefore a corresponding variation in the current flowing through the sensor coil. The output from the sensor coil has a high frequency component representing the passage of the successive teeth of the transducer wheel past the sensor, and so dependent upon the rotary speed of the transducer wheel. However, the air gap between the transducer wheel and the sensor may vary cylically owing to an eccentricity in the transducer wheel, e.g. due to an inaccuracy in the mounting of the wheel or to an inaccuracy in its manufacture. As a result, a low frequency component is superimposed on the high frequency output from the sensor. It will be appreciated that the high frequency is equal to the low frequency times the number of teeth on the transducer wheel.
In some applications, especially when the rotary speed of the shaft or other element being monitored does not vary greatly, a high pass filter is sufficient to remove the low frequency component and provide an error-free output. In other applications however this simple technique is unsatisfactory.
In one application for example, the variable reluctance transducer is used to monitor the rotary speed of a roadwheel of a vehicle. The toothed wheel of the transducer is fitted to the roadwheel and the output signal from the transducer is fed to a microprocessor which determines the rotary speed and acceleration or deceleration of the roadwheel. The range over which the speeds need to be measured is typically from approximately 0.5 revolutions per second to 45 revolutions per second. This speed range gives rise to a low frequency signal component varying between 0.5 and 45 Hz and high frequency component varying between 22 and 1980 Hz (for a transducer wheel with 44 teeth). In monitoring the rotary speed of a road wheel, it is required to detect when the wheel is about to lock, but the overlap in the high and low frequency ranges means that the use of a high pass filter would not be satisfactory. In order to improve the resolution of speed calculation using a microprocessor, an output signal with a 50% mark/space is required. Owing to the safety critical application, monitoring of the sensor condition is required to detect abnormal resistance. High noise immunity is required to reject signal produced by locked wheel oscillation and brake squeal, in which cases noise amplitude can exceed the signal.
A circuit incorporating the features of the first part of claim 1 is known e.g. from US-A-4 575 677.
In accordance with this invention, there is provided a circuit for processing an output signal from a variable reluctance transducer, the transducer output signal varying at high frequency, the circuit comprising an operational amplifier having a first input to which said transducer is connected and a second input to which said transducer is connected via a low pass filter so that the operational amplifier provides an output signal representing the high frequency transducer signal and substantially unaffected by any low frequency component in the transducer signal, characterised in that the transducer is connected in a series path across a d.c. supply and has one end connected both to said first input and, via said low pass filter, to said second input, and in that the operational amplifier is connected as an integrator to integrate the difference between the signals received by its two inputs.
In this circuit, the integrator provides an output which is related to the difference between the signal received from the transducer and a signal representing the low frequency component of the transducer output. The output from the integrator thus represents the high frequency component of the transducer output and is unaffected by the low frequency component.
Preferably an output circuit is provided, for producing a square wave from the high frequency alternating output signal from the integrator. Preferably this output circuit comprises a pair of active clamps controlling the SET and RESET inputs of a bistable circuit, which provides a square wave output with 50% mark-space ratio. The active clamps have two functions. Firstly as the integrator output reaches each of the clamp levels, the state of the bistable is switched. Secondly, the clamps limit the voltage excursion of the integrator amplifier in both positive and negative directions. This defines a precise amount of integral hysteresis through which the output must travel when signal polarity changes, since both start and switched reference voltages are defined by the clamps.
Preferably the low pass filter, through which the transducer signal is passed to the second input of the operational amplifier, includes a shunt capacitor. The average charge on this capacitor corresponds to the series resistance of the sensor. A window detector monitors the capacitor voltage, to detect abnormal sensor resistances, but the system microprocessor only responds to this when the rotary speed is nil or below a low threshold.
Preferably a voltage limiting circuit is connected between the two inputs of the operational amplifier, having the effect of shunting the current, which normally flows from the transducer into the negative input node of the operational amplifier, via the limiter circuit and into the low pass capacitor, but only after sufficient signal has already caused the integrator output to reach the active clamp level producing a valid signal. This provides an additional charging source for the capacitor so increasing the corner frequency of the filter, but only after a valid integrator signal has been produced, preventing loss of low frequency operation. Also by setting of the voltage limiter value, and due to the correspondence of sensor output voltage amplitude with signal frequency, a threshold frequency can be set below which the voltage limiter ceases to operate, approximating to a frequency tracking low pass filter. Activation of the voltage limiter can be achieved by either sensing loss of control of the negative input relative to the positive input of the operational amplifier, or by activation of the integrator output active clamp.
An embodiment of this invention will now be described by way of example only and with reference to the accompanying drawings, in which:

FIGURE 1 is a diagram of a circuit for processing the output signal from a variable reluctance transducer; and
FIGURE 2 gives traces showing the waveforms at the input of the circuit, on the filter capacitor and at the output of an integrator of the circuit when the transducer wheel is turning.

Figure 1 shows an embodiment of circuit for processing the output signal from a variable reluctance transducer VR. The transducer comprises a rotatably mounted wheel of magnetic material having a plurality of radially projecting teeth equally spaced around its circumference, and a fixed sensor which comprises a small electrical coil wound on a core. In the example under discussion, the toothed wheel is fitted to a roadwheel of a vehicle and the transducer is used to determine the rotary speed of the roadwheel. However, in other examples, the transducer may be used for sensing the rotary speed of any other element, for example the toothed wheel may be mounted to a shaft driven by an internal combustion engine of a vehicle and used to determine the rotary speed of the crankshaft. As the transducer wheel rotates and its successive teeth pass the sensor, the air gap between itself and the sensor varies cyclically, and therefore the reluctance of the magnetic path through the core of the sensor coil varies in a corresponding cyclical manner. The current flowing through the sensor coil therefore includes a high frequency component corresponding to the teeth of the transducer wheel passing the sensor. But also the current flowing through the sensor coil includes a low frequency component due e.g. to any eccentricity in the mounting of the transducer wheel.
In the circuit of Figure 1, the sensor coil is represented by VR and has one end connected to ground and its other end connected to a supply rail by a series resistor R6. The junction between the transducer VR and resistor R6 is connected to the inverting input of an operational amplifier A1 via a series resistor R1, and is connected to the non-inverting input of the operational amplifier A1 via a low pass filter which comprises a series resistor R2 and a shunt capacitor C4. The operational amplifier A1 is connected as an integrator by means of a capacitor C3 connected between its output and its inverting input. A voltage limiting circuit VL is connected between the two inputs of the operational amplifier A1 and may comprise two diodes connected in anti-parallel, so that neither input can rise in voltage by more than one diode-drop above the other.
The output of the operational amplifier or integrator A1 is connected to a pair of active clamps each comprising an operational amplifier A2 or A3 and a diode D7 or D8. Thus, the output of the integrator A1 is connected to the inverting inputs of both operational amplifiers A2, A3, which have respectively high and low reference levels applied to their non-inverting inputs. The diodes D7 and D8 are oppositely poled relative to each other and connected between the output and inverting or signal input of the respective operational amplifier. A bistable circuit BC has its SET and RESET terminals connected to the outputs of the respective active clamps A2, D7 and A3, D8. Usually a buffer amplifier will be needed at each of the SET and RESET inputs to provide signals of adequate level to drive the bistable circuit BC.
The low pass filter capacitor C4 is connected to a window detector which comprises two operational amplifiers A4, A5 respectively connected as high and low threshold comparators. Thus, the capacitor C4 is connected to the non-inverting input of comparator A4 and to the inverting input of comparator A5, whilst the inverting input of comparator A4 and the non-inverting input of comparator A5 are connected respectively to high and low threshold levels V high and V low. In the example shown, the outputs of the two comparators A4, A5 are coupled together to give an output if the voltage on capacitor C4 either exceeds the high threshold level on A4 or falls below the low threshold level on A5. However instead the outputs may be taken separately from the two comparators, one giving an output only if the voltage on capacitor C4 exceeds the high threshold and the other giving a output only if the voltage on capacitor C4 falls below the low threshold level.
At power up the voltage at the junction between the transducer and resistor R6 rises to a level determined by the resistance of the sensor VR and also of resistor R6. Also, the voltage on the capacitor C4 rises, at a rate determined by the time constant of R2,C4, to a similar level. Then as the transducer wheel turns and its successive teeth pass the sensor, this causes the current through the sensor coil to vary cyclically and the voltage at the junction of the transducer with resistor R6 varies as shown at VR in Figure 2: thus there is a high frequency component corresponding to the passage of the successive teeth of the transducer wheel past the sensor, but there may also be a low frequency component due to an eccentricity in the transducer wheel. Both the high frequency and low frequency components pass to the inverting input of operational amplifier A1, but the low pass filter R2, C4 passes substantially only the low frequency component to the non-inverting input. As a consequence, the output of the integrating operational amplifier A1 represents the high frequency component and is substantially free of any low frequency component, as shown by trace VA1 in Figure 2. Further, the swing in voltage at the output of integrator A1 is limited in both directions by the respective active clamps A2, D7 and A3, D8: as limiting occurs in each direction, the bistable circuit BC switches states and the output from the bistable circuit is a square wave with 50% mark-space ratio. This is passed to a microprocessor which requires a waveform of this nature.
The circuit of Figure 1 provides a high level of noise immunity differentiating the wheel rotation from brake squeal and locked-wheel oscillations. Thus, both these conditions can produce vibrations of the sensor assembly within the frequency range of operation, corresponding to a voltage output from the sensor comparable in amplitude to a true signal of lower frequency. This is due to the circuit being able to discriminate on the basis of signal energy content, these conditions producing signals of insufficient integral content to swing the integrator across its output hysteresis.
The maximum frequency at which the low pass filter operates is extended by the voltage limiting circuit VL on the input of the integrator A1, when the input voltage exceeds the limited threshold. At low rotational speeds the input signal is small and the voltage limiter is not effective. But as the rotational speed increases the input signal voltage increases and when the integrator output is limited, its input is no longer controlled and tends towards the input signal. Instead, when the input voltage exceeds the threshold of the voltage limiter, it starts conducting, shunting the current flowing through R1 into the filter capacitor C4. This additional current path effectively reduces the resistance seen between the VR input and C4, so forming a low pass filter with a higher corner frequency. Since this only occurs after the integrator output has effectively saturated and produced an output edge, only a small loss of signal occurs whilst integrating due to R2, C4.
The voltage on the filter capacitor C4 varies as shown at VC4 in Figure 2 and thus substantially as the low frequency component in the signal from the transducer but with a high frequency ripple. The voltage on capacitor C4 is monitored by the window detector A4, A5. If the resistance of the transducer is abnormal, or the eccentricity of the toothed wheel is excessive, the transducer voltage and hence the voltage on C4 will exceed the window defined by A4, A5 to produce an output signal. This signal is passed to the microprocessor to indicate that the sensor is damaged and unreliable, but the microprocessor disregards the fault signal unless the detected rotary speed is nil or below a low threshold.

Claims

A circuit for processing an output signal from a variable reluctance transducer (VR), the transducer output signal varying at high frequency, the circuit comprising an operational amplifier (A1) having a first input to which said transducer (VR) is connected and a second input to which said transducer (VR) is connected via a low pass filter (R2,C4) so that the operational amplifier (A1) provides an output signal (VA1) representing the high frequency transducer signal and substantially unaffected by any low frequency component in the transducer signal, characterised in that the transducer (VR) is connected in a series path across a d.c. supply and has one end connected both to said first input and, via said low pass filter (R2,C4), to said second input, and in that the operational amplifier (A1) is connected as an integrator to integrate the difference between the signals received by its two inputs.
A circuit as claimed in claim 1, characterised by an output circuit (A2,A3,BC) which produces a square wave from the output signal from the integrator (A1).
A circuit as claimed in claim 2, characterised in that said output circuit comprises a pair of active clamps (A2,D7; A3,D8) controlling the SET and RESET inputs of a bistable circuit (BC).
A circuit as claimed in any preceding claim, characterised in that the low pass filter includes a shunt capacitor (C4), and a window detector (A4,A5) is provided to monitor the capacitor voltage (VC4).
A circuit as claimed in any preceding claim, characterised in that a voltage limiting circuit (VL) is connected between the two inputs of the operational amplifier (A1).