CN1679269A - 按特征模式应用选择性信道反转的已编码mimo*** - Google Patents
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Abstract
给出了在MIMO***中按特征模式执行选择性信道反转的技术,其能实现高频谱效率,而同时减少发射机和接收机处的复杂度。可用的传输信道被排列成多个组,每组都包括MIMO信道一相应特征模式的所有传输信道(或频率段)。总发射功率使用一特定的组功率分配方案被分配给多个组。然后为数据传输使用而选择的每个组独立地执行选择性信道反转。对于每个这样的组,选择组中的一个或多个传输信道供使用,并且为每个所选的信道确定一缩放因数,使该组的所有所选的信道都能实现相似的接收信号质量(例如接收SNR)。
Description
背景
技术领域
本发明一般涉及数据通信,尤其涉及为MIMO***按特征模式执行选择性信道反转的技术。
背景技术
多输入多输出(MIMO)通信***采用了多根(NT)发射天线和多根(NR)接收天线进行数据传输。由NT根发射天线和NR根接收天线形成的MIMO信道可以被分解成NS个独立信道,NS≤min{NT,NR}。NS个独立信道的每一个也都称作一空间子信道或MIMO信道的特征模式。
宽带MIMO***的空间子信道会遇到由于诸如衰落和多径等各个因素引起的不同信道条件。因此,每个空间子信道都会经历频率选择性的衰落,该衰落表征为在总***带宽不同频率下的不同信道增益。假定没有功率控制,这于是导致在每个空间子信道处不同频率下不同的信号对噪声和干扰比(SNR),于是能对于特定的性能级别(例如1%的分组差错率)支持不同的数据速率。
为了抵抗宽带信道中的频率选择性的衰落,可以使用正交频分复用(OFDM)来有效地把总***带宽分成多个(NF个)子频带,子频带也称为频率段或子信道。有了OFDM后,每个子频带都与根据其调制数据的相应的子载波相关联。对于使用OFDM的MIMO***而言(即MIMO-OFDM***),每个空间子信道的每个子频带都可以被视为一独立的传输信道。
已编码通信***的一个关键难题在于基于信道条件选择适当的数据速率及编码和调制方案供数据传输使用。***的主要目标是使频谱效率最大化,同时减少发射机和接收机两者的复杂度。
选择数据速率以及编码和调制方案的一种直接技术是按照***中每个传输信道的传输能力对其进行“比特加载”。然而,该技术具有几个主要缺点。首先,对每个传输信道独立地进行编码和调制会显著提高发射机和接收机处的处理复杂度。其次,对每个传输信道单独地编码会大大增加编码和解码延迟。
因此,本领域中需要这样的技术:能实现MIMO***中的高频谱效率,而不用同时对每个传输信道单独地编码。
发明内容
这里提供了技术在MIMO***中按特征模式来执行选择性的信道反转,以便实现高频谱效率而同时减少发射机和接收机处的复杂度。可用的传输信道被排列成多个组,每组都会包括MIMO信道一特征模式的所有传输信道(或频率段)。使用一特定的功率分配方案(例如均匀功率分配、注水等等)把总发射功率分配给多个组。然后对为数据传输用途而选择的每组独立地执行选择性的信道反转(即根据非零分配到的发射功率)。对于每个这样的组而言,选择组中的一个或多个传输信道供使用,并且为每个所选的信道确定一缩放因数,使得该组的所有所选信道都被反转,并且实现相似的接收信号质量(例如接收到的SNR)。
下面进一步详述本发明的各个方面和实施例。本发明进一步提供了方法、程序代码、数字信号处理器、发射机单元、接收机单元以及能实现本发明的各个方面、实施例和特征的其它装置和元件,如下进一步详述。
附图说明
从以下结合附图提出的详细描述中,本发明的特征、特性和优点将变得更为明显,附图中相同的参考数字标识了相同的元件,附图中:
图1图解说明了MIMO-OFDM***的特征值分解;
图2示出对于示例4×4 MIMO***而言,由三个传输方案所实现的平均频谱效率的曲线;
图3是MIMO-OFDM***中的接入点和用户终端的框图;
图4是接入点中发射机单元的框图;以及
图5是使用按特征模式的选择性信道反转来处理数据的流程图。
详细描述
在MIMO通信***中,比如多天线的无线通信***,从NT根发射天线发出的数据流在接收机处彼此干扰。一种对抗该干扰的技术是使MIMO信道“对角线化”以获得多个独立信道。
MIMO***的模式可表示为:
y=
Hx+
n, 公式(1)
其中
y是有NR个项的向量,{yi}对于i∈{1,...,NR},对于NR根接收天线所接收到的码元(即“接收到的”向量);
x是有NT个项的向量,{xi}对于j∈{1,...,NT},对于从NT根发射天线发出的码元(即“发射的”向量);
H是包含从NT根发射天线到NR根接收天线的传输函数(即复增益)的信道响应矩阵;以及
n是附加白高斯噪声(AWGN),均值向量为
0、协方差矩阵为
Λ n=σ2 I,其中
0是全零的向量,
I是对角线上为1、其余地方为0的单位矩阵,σ2是噪声方差。
为了简洁,假定一慢衰落的、窄带信道。该情况下,对于整个***带宽,信道响应可由一恒定复值来表示,信道响应矩阵
H的元素是标量。尽管这里为简洁而假定频率非选择性,然而这里所述的技术可扩展为频率选择性的信道。
通过对
H的相关矩阵进行特征值分解可以对角线化信道响应矩阵
H,所述相关矩阵为
R=
H H H。(NT×NT)相关矩阵
R的特征值分解可表示为:
R=
EDE H,
公式(2)
其中
E是一(NT×NT)的酉阵,它的列是
R的特征向量
e i,对于i∈{1,...,NT};
D是一(NT×NT)的对角矩阵,其对角线上的项对应于
R的特征值;以及
对于任何矩阵
M,
M H表示
M的共轭转置。
酉阵通过特性
E H E=
I来表示。
特征值分解也可以用奇异值分解(SVD)来执行,这是本领域公知的。
对角矩阵
D在沿对角线上包含非负实数值,在其它地方为零。这些对角线项被称为矩阵
R的特征值,并且表示MIMO信道的独立信道的功率增益。具有NT根发射天线和NR根接收天线的MIMO***的独立信道数是
R的非零特征值的数目,NS≤min{NT,NR}。这些非零特征值表示为{λi},对于i∈{1,...,NS}。
如果不考虑NT根发射天线的功率约束,可以通过用酉阵
E左乘(或“预调节”)“数据”向量
s以获得发射向量
x,从而使MIMO信道对角线化。发射机处的预调节可以表示为:
x=
Es
公式(3)
在接收机处,可以用
E H H H左乘(或“调节”)接收向量
y以获得数据向量
s的估计。调节以获得数据向量估计
可以表示为:
公式(4)
其中
是AWGN,其均值向量为
0、协方差矩阵为
如公式(4)所示,发射机处的预调节以及接收机处的调节导致数据向量
s通过矩阵
D所表示的实际信道响应而变换、以及噪声元素的缩放。由于
D是一对角矩阵,因此实际上有NS个非干扰的、平行信道。对于i∈{1,...,NS},每一个这些信道的功率增益都等于相应特征值的平方λi 2,噪声功率等于σ2λi,导致信噪比为λi/σ2。这样,每个这些信道的功率增益都等于特征值λi,对于i∈{1,...,NS}。平行信道i通常称为特征模式i或模式i。如果发射机带有信道响应矩阵
H或等效的信息,则可以实现公式(3)和(4)所示的MIMO信道的对角线化。
上述的特征值分解也可以为一宽带、频率选择性的信道而执行。对于MIMO-OFDM***而言,宽带信道被分成NF个慢衰落的正交频率段或子频带。然后可以为每个频率段k的信道响应矩阵
H(k)独立地执行特征值分解,以便为该频率段确定NS个空间子信道或特征模式。每个频率段的每个空间子信道也称为“传输”信道。
MIMO-OFDM***的模型可以表示为:
y(k)=
H(k)
x(k)+
n(k):对于k∈{1,...,N
F}.公式(5)
其中“(k)”表示第k个频率段。
每个频率段的相关矩阵
R(k)的特征值分解可以表示为:
R(k)=
E(k)
D(k)
E H(k)
公式(6)
R(k)的非零特征值表示为{λi(k)},对于i∈{1,...,NS}以及k∈{1,...,NF}。这样,对于MIMO-OFDM***而言,为NF个频率段的每一个执行特征模式分解会导致每个频率段的NS个空间子信道或特征模式,或总共NSNF个传输信道。
特征值可以以两种形式提供——“排序”形式和“随机顺序”形式。在排序形式中,每个频率段的NS个特征值以降序排序,使
其中
λi(k)是频率段k的最大特征值,λNS(k)是频率段k的最小特征值。在随机顺序形式中,特征值的排序是随机的,并进一步独立于频率。为使用而选择的特定形式,排序或随机顺序,影响了为数据传输所使用的特征模式的选择以及为每个所选特征模式使用的编码和调制方案的选择,如下详述。
图1图解说明了MIMO-OFDM***的特征值分解。对角矩阵集合
D(k)(对于k={1,...,NF})被示出沿着轴线110按顺序排列,轴线110表示频率大小。每个矩阵
D(k)的特征值{λi(k)}(对于i={1,...,NS})位于矩阵的对角线上。轴线112因此可被视为表示空间维数。所有频率段的特征模式i(或仅仅特征模式i)都与一元素集合{λi(k)}相关联,对于k={1,...,NF},该集合表示该特征模式的所有NF个频率段之间的频率响应。每个特征模式的元素集合{λi(k)}都用沿虚线114的阴影框示出。图1的每个阴影框都表示一传输信道。对于经受频率选择性衰落的每个特征模式而言,该特征模式的元素{λi(k)}对于不同的k值可能不同。
如果每个对角矩阵
D(k)内的特征值都以降序排序,则特征模式1(也称为主要特征模式)会包括每个矩阵内最大的特征值λi(k),特征模式NS会包括每个矩阵内最小的特征模式λNS(k)。
MIMO-OFDM***中每个频率段的特征值分解导致整个带宽上对于NSNF个传输信道总共有NSNF个特征值。每个传输信道会实现一不同的SNR,并且可能与不同的传输能力相关联。可以使用各种功率分配方案(或传输方案)把总发射功率分布给这些传输信道以实现高的总频谱效率,单位为比特/秒每赫兹(bps/Hz)。这些方案的一些在下面进一步详述。
1.
注水
“注水”或“倒水”方案可用来在传输信道间最佳地分布总发射功率,使得总频谱效率最大化,约束条件为发射机处的总发射功率被限制为Ptotal。注水方案在NSNF个传输信道间分布功率,使得SNR越来越高的信道会接收到总发射功率越来越多的部分。分配给一给定传输信道的发射功率由该信道的SNR确定,所述SNR给出为λi(k)/σ2,其中λi(k)是第k个频率段内第i个特征值。
执行注水的过程是本领域公知的,这里不再描述。注水的结果是向NSNF个传输信道的每一个分配一特定的发射功率,表示为Pi(k),对于i={1,...NS}以及k={1,...NF}。执行功率分配以满足下列条件:
公式(7)
其中L={1,...NS}以及K={1,...NF}。
基于Pi(k)所分配的发射功率,对于i={1,...NS}以及k={1,...NF},每个传输信道接收到的SNRγi(k)可以表示为:
对于i={1,...,NS}以及k={1,...,NF} 公式(8)
然后可以根据一连续、单调递增的容量对数函数来计算NSNF个传输信道的总频谱效率C,如下:
公式(9)
在一典型的通信***中,预期观察到的接收SNR的总范围可以被分成多个子范围。每个子范围于是与一特定的编码和调制方案相关联,该特定的编码和调制方案被选择用来为一给定的比特差错率(BER)、帧差错率(FER)和分组差错率(PER)产生最高的频谱效率。注水功率分配可能为NSNF个传输信道的每一个产生一个不同的接收SNR。这于是会导致为传输信道使用许多不同的编码/调制方案。在招致发射机和接收机处较大复杂度的前提下,每个传输信道的编码/调制提高了总频谱效率。
2.
应用于所有传输信道的选择性信道反转
“所有信道的SCI”方案对所有传输信道执行了选择性的信道反转(SCI),使得那些为使用而选择的信道在接收机处实现了近似相等的接收SNR。这于是能为所有所选的传输信道使用一共同的编码和调制方案。该方案与注水方案相比,大大减少了发射机和接收机的复杂度。通过首先选择NSNF个可用传输信道的全部和仅仅一个子集供数据传输使用,可以实现接收SNR的均衡。信道选择会导致消除低SNR的不良信道。然后以接收到的SNR对于所有所选传输信道近似相等的方式,在所选的传输信道间分布总发射功率Ptotal。
如果对于所有NSNF个可用传输信道执行了“全”信道反转,则可以分配总发射功率Ptotal,使对于所有这些信道接收到近似相等的信号功率。要向频率段k的特征模式i分配的发射功率Pi(k)的近似量可以表示为:
公式(10)
其中α是用于在可用传输信道间分布总发射功率的标准化因数。该标准化因数α可以表示为:
公式(11)
标准化因数α确保了对于所有传输信道近似相等的接收信号功率,给出为αPtotal。因此,总发射功率实际上根据信道功率增益而(不均匀地)分布在所有可用的传输信道间,由特征值λi(k)给出。
如果执行“选择性的”信道反转,则为了用于数据传输仅选择其接收功率等于特定阈值β或比总接收功率高一特定阈值β的传输信道。其接收功率低于该阈值的传输信道就被丢弃或不被使用。对于每个所选的传输信道,要被分配给该信道的发射功率可以如上确定,使得所有所选的传输信道都以近似相等的功率级被接收。可以选择阈值β使频谱效率最大化,或基于某些其它标准来选择阈值β。
供使用的传输信道的选择可如下执行。首先,为所有可用的传输信道计算一平均功率增益Pavg,并且表示为:
公式(12)
要分配给每个传输信道的发射功率于是可以表示为:
其中β为阈值,
是与公式(11)中的α相似的标准化因数。然而,标准化因数
仅在所选的传输信道上计算,并且表示为:
公式(14)
阈值β可以如下述导出(在3.2节)。
如公式(13)所示,如果一传输信道的特征值(或信道功率增益)大于或等于一功率阈值(即λi(k)≥βPavg),则选择该传输信道供使用。由于仅基于所选的传输信道来计算标准化因数
因此总发射功率Ptatal,基于信道增益而被分布给所选的传输信道,使所有所选的传输信道都有近似相等的接收功率,可以表示为
因此通过在所有所选的传输信道间不均匀地分布总发射功率,可以为这些传输信道实现接收SNR的均衡。于是,近似相等的接收SNR会允许为所有所选的传输信道使用单个数据速率和一共同的编码/调制方案,这会大大减少复杂度。
3.按特征模式应用的选择性信道反转
“按特征模式的SCI”方案为每个特征模式独立地执行选择性的信道反转以提供改进的性能。在一实施例中,NSNF个传输信道被安排到NS个组中,使得每个组包括一给定特征模式的所有NF个频率段(即组i包括特征模式i的所有NF个频率段的空间子信道)。因此对于每个特征模式有一个组。
按特征模式的SCI包括两步。在第一步中,基于一特定的组功率分配方案把总发射功率Ptotal分布到NS个组。在第二步中,为每个组独立地执行选择性的信道反转以便把该组分配到的发射功率分布给该组内的NF个频率段。这些步骤的每一步在下面详细描述。
3.1
多个组之间的功率分配
总发射功率Ptotal可以以各种方式分布给NS个组,某些方式在下面描述。
在第一实施例中,总发射功率Ptotal在所有NS个组间均匀分布,使它们都被分配到相等的功率。分配给每个组的发射功率PG(i)可以表示为:
对于i={1,...,NS} 公式(15)
在第二实施例中,总发射功率Ptotal基于所有可用传输信道间的注水而被分布给NS个组。对于该实施例,首先使用上述的注水把总发射功率Ptotal分布给所有NSNF个传输信道。每个传输信道都被分配到Pi(k),对于i∈{1,...NS}以及k∈{1,...NF}。然后可以通过对向每个组内的NF个传输信道分配的发射功率相加,从而确定分配给该组的发射功率。分配给组i的发射功率可以表示为:
对于i={1,...,NS} 公式(16)
在第三实施例中,总发射功率Ptotal基于所有组间的注水而被分布给NS个组,所述分布是使用它们的平均信道SNR进行的。首先,每组的平均信道SNRγavg(i)被确定为:
对于i={1,...,NS} 公式(17)然后执行注水以便在NS个组之间基于它们的平均信道SNR来分布总发射功率Ptotal。为NS个组的每一个分配的发射功率表示为PG(i),对于i∈{1,...NS}。
在第四实施例中,总发射功率Ptotal基于所有组间的注水而被分布给NS个组,所述分布是使用传输信道在信道反转后接收到的SNR进行的。对于该实施例,首先如上述公式(15)所示把总发射功率Ptatal均匀地分布给NS个组,使每组都分配到一初始发射功率
对于i∈{1,...NS}。然后对每个组独立地执行选择性信道反转以便为组中的每个频率段确定一初始功率分配
对于k∈{1,...NF}。接着如公式(8)所示,基于初始功率分配
确定每个频率段的接收SNR:
然后如下计算每组的平均接收SNR:
对于i={1,...,NS} 公式(18)
然后,总发射功率Ptotal使用注水基于NS个组的平均接收SNR
而被分布给NS个组,对于i∈{1,...NS}。注水功率分配的结果是NS个组的经修改的(即最终的)发射功率分配PG(i),对于i∈{1,...NS}。对每组再次执行选择性的信道反转以便把该组分配到的发射功率PG(i)分布给组内的频率段。每个频率段于是会通过第二次选择性信道反转被分配到发射功率Pi(k)。
如果满足以下条件,就无须为一给定的组执行第二次选择性信道反转:(1)通过注水分配给该组的经修改的发射功率大于初始均匀功率分配(即
)以及(2)组中的所有频率段都被选择以用于初始选择性信道反转。对于该特殊情况,组中每个频率段的新功率分配Pi(k)可以表示为:
对于k={1,...,NF} 公式(19)
使用公式(19)可能有以下原因:(1)组中的所有频率段都已被选来使用,并且即使该组经修改的功率分配PG(i)大于初始功率分配
也没有附加的频率段可被选择,以及(2)初始选择性信道反转已经确定向组中频率段的适当功率分布以便为这些信道实现近似相等的接收SNR。在所有其它情况下,都为每组再次执行选择性信道反转以便为组中的频率段确定发射功率分配Pi(k),对于k∈{1,...NF}。
3.2应用于每组的选择性信道反转
一旦使用上述的任一组功率分配方案把总发射功率Ptotal分布给了NS个组,则为NS个组的每一个并且在每组内的NF个频率段上独立地执行选择性信道反转。每组的选择性信道反转如下执行。
首先,确定每组的平均功率增益Pavg(i):
对于i={1,...NS} 公式(20)
分配给组i中频率段k的发射功率可以表示为:
公式(21)
公式(22)
公式(22)中反向信道功率增益的相加考虑到组i的所有所选频率段上的信道功率增益。
选择供每组中使用的频率段所用的阈值βi可以根据各种标准来设定,例如使频谱效率最优。在一实施例中,阈值βi基于信道功率增益(或特征值)来设定,所选频率段的频谱效率基于每组中频率段之间的均匀发射功率分配,如下所述。
对于该实施例,为组i导出阈值βi如下进行(其中为每组独立地执行导出过程)。首先,组中所有NF个频率段的特征值被分级并放置在一列表Gi(λ)中,对于λ∈{1,...NF},所述放置以降序实现:对于i∈{1,...NS},Gi(1)=max{λi(k)},Gi(NF)=min{λi(k)}。
对于每个λ,其中λ∈{1,...,NF},计算λ个最佳频率段的频谱效率,其中“最佳”是指具有最高功率增益Gi(λ)的频率段。这可以如下实现。首先,使用上述任一功率分配方案把该组可用的总发射功率PG(i)分布给λ个最佳频率段。为了简洁,使用均匀功率分配方案,λ个频率段中每一个的发射功率都是PG(i)/λ。接着,计算,λ个频率段中每一个的接收SNR:
对于j∈{1,...,λ} 公式(23)
组i中λ个最佳频率段的频谱效率Gi(λ)于是计算为:
公式(24)
其中ρ是用于解决为使用而选择的编码和调制方案中无效的缩放因数。
为每个λ值计算频谱效率Ci(λ),其中λ∈{1,...,NF),并且保存在一数组中。在已经为所选频率段的NF个可能组合计算了Ci(λ)的所有NF个值后,频谱效率的数组被遍历,并且确定Ci(λ)的最大值。于是,与最大Ci(λ)相对应的λ值λmax就是导致信道条件的最大频谱效率被评估并用均匀发射功率分配的频率段数目。
由于组i中NF个频率段的特征值在列表Gi(λ)中以降序排列,则在到达最优点以前,随着选择更多的频率段加以使用,频谱效率也增加,在到达最优点后频谱效率降低,这是因为该组的更多发射功率被分配给不良的频率段。这样,每个新λ值的频谱效率Ci(λ)可以与前一λ值的频谱效率Ci(λ-1)相比较,而不是计算所有可能λ值的频谱效率Ci(λ)。如果到达最优频谱效率,表示为Ci(λ)<Ci(λ-1),则该计算终止。
阈值βi于是可以表示为:
公式(25)
其中Pavg(i)如公式(20)所示地确定。
阈值βi也可以基于某些其它标准和某些其它功率分配方案(取代均匀分配)来设置。
选择性信道反转在以下三个美国专利申请中进一步详述:2001年5月17日提交的第09/860,274号专利申请、2001年6月14日提交的第09/881,610号专利申请以及2001年6月26日提交的第09/892,379号专利申请,这三个专利申请题目均为“Method and Apparatus for Processing Data for Transmission in aMulti-Channel Communication System Using Selective Channel Inversion”,这些专利申请被转让给本申请的受让人并且通过引用结合于此。
为每组独立地执行选择性信道反转会导致对于每组中NF个频率段有一组发射功率分配,Pi(k)对于k∈{1,...,NF}。选择性信道反转会导致为任一给定组的使用选择了少于NF个频率段。未选择的频率段不被分配到任何发射功率(即对于这些频率段Pi(k)=0)。所选频率段的功率分配使这些频率段实现近似相等的接收SNR。这于是能够为每组中的所有所选频率段使用单个数据速率和共同的编码/调制方案。
对于排序形式,每个对角矩阵
D(k)的特征值λi(k)(对于i∈{1,...,NS})被排序,使下标较小的对角元素一般较大。特征模式1于是和NF个对角矩阵中每一个的最大特征值相关联,特征模式2于是和第二大的特征值相关联,依此类推。对于排序形式,即使为每个特征模式的所有NF个频率段执行了信道反转,下标较小的特征模式不可能有过多的坏频率段(如果有的话),并且为坏频率段不使用过度的发射功率。
如果使用注水把总发射功率分布给NS个特征模式,则为使用而选择的特征模式数目会在低SNR时减少。因此,排序形式的优点在于:在低SNR下,通过减少为使用而选择的特征模式数目能进一步简化编码和调制。
对于随机顺序的形式,每个对角矩阵
D(k)的特征值是随机排序的。这会导致所有特征模式的平均接收SNR中的较小变化。在该情况下,可以为NS个特征模式使用少于NS个共同的编码和调制方案。
在一种传输方案中,如果一组要用于数据传输,则选择该组中的所有NF个频率段(即,任何活动的特征模式都需要成为一个完整的特征模式)。如果省略使用了一个或多个频率段,则会夸大特征模式的频率选择特性。该较大的频率选择衰落会造成较高级别的码元间干扰(ISI),ISI是接收信号中的每个码元都对接收信号中的后续码元造成失真的一种现象。然后在接收机处需要均衡来减轻ISI失真的有害效应。该均衡可以通过对被选择来使用的每个特征模式的所有频率段执行全信道反转来避免。该传输方案可以结合排序形式和注水功率分配有利地使用,因为如上所述,下标较小的特征模式不可能有过多的坏频率段。
图2示出对于总发射功率Ptotal=4的示例4×4 MIMO***,由三个传输方案实现的平均频谱效率的曲线。图2中示出三种传输方案的三条曲线:(1)所有传输信道上的注水功率分配,(2)应用于所有传输信道的选择性信道反转(所有信道的SCI),以及(3)独立应用于每个特征模式的选择性信道反转(按特征模式的SCI),其中总发射功率使用注水方案根据平均信道SNR分布在四个组中间。
图中平均频谱效率相对于工作SNR而绘制,工作SNR定义为γop=1/σ2。图2表示注水功率分配(曲线210)产生预期的最高频谱效率。在频谱效率15bps/Hz下,所有信道SCI方案的性能(曲线230)比最优注水方案的性能差大致2.5dB。然而,所有信道SCI方案为发射机和接收机导致低得多的复杂度,因为可以为所有选择的传输信道使用单个数据速率和一共同的编码/调制方案。在15bps/Hz频谱效率下,按特征模式SCI方案的性能(曲线220)比注水方案的性能差大致1.5dB,而比所有信道SCI方案的性能要好大致1.0dB。这个结果在期望中,因为按特征模式SCI方案结合了注水和选择性信道反转。尽管按特征模式SCI方案比所有信道SCI方案更为复杂,但它没有注水方案复杂,并能实现相当的性能。
图3是MIMO-OFDM***300中的接入点310和用户终端350的实施例框图。
在接入点310,把来自数据源312的话务数据(即信息比特)提供给发射(TX)数据处理器314,后者对数据进行编码、交织和调制以提供调制码元。TX MIMO处理器320进一步处理所述调制码元以提供经预调节的码元,经预调节的码元进一步与导频数据多路复用并被提供给NT个调制器(MOD)322a到322t,每个调制器用于一根发射天线。每个调制器322处理一相应的经预调节的码元流以生成已调信号,已调信号接着经由相应的天线324被发射。
在用户终端350,从NT根天线324a到324t发射的已调信号被NR根天线352a到352r所接收。从每根天线352接收到的信号被提供给相应的解调器(DEMOD)354。每个解调器354对接收信号进行调节(例如滤波、放大和下变频)和数字化以提供一采样流,并进一步处理这些采样以提供一接收码元流。然后,RX MIMO处理器360处理NR个接收码元流以提供NT个经恢复的码元流,经恢复的码元流是接入点所发送的调制码元的估计。
从用户终端到接入点的反向路径的处理会类似于、或不同于前向路径的处理。反向路径可用来把信道状态信息(CSI)从用户终端发回接入点。CSI在接入点用来选择供使用的正确编码和调制方案,并且用于执行选择性信道反转。
控制器330和370分别指引接入点和用户终端处的操作。存储器332和372分别为控制器330和370所使用的程序代码和数据提供存储。
图4是发射机单元400一实施例的框图,发射机单元400是图3中接入点的发射机部分的一个实施例。发射机单元400也可用于用户终端350。
在TX数据处理器314内,编码器/截短器412按照一个或多个编码方案来接收和编码话务数据(即信息比特)以提供已编码比特。然后,信道交织器414基于一个或多个交织方案来交织已编码比特,以提供时间、空间和/或频率分集的组合。接着,码元映射元件416按照一个或多个调制方案(例如QPSK、M-PSK、M-QAM等等)映射经交织的数据以提供调制码元。
NS个组的编码和调制可以各种方式执行。在一实施例中,为选择性信道反转所应用的每组传输信道使用一单独的编码和调制方案。对于该实施例,可以为每个组使用一组单独的编码器、交织器和码元映射元件。在另一实施例中,为所有的组使用一共同的编码方案,其后为每组使用一可变速率的截短器和一单独的调制方案。该实施例减少了发射机和接收机处的硬件复杂度。在其它实施例中,也可以使用网格编码和Turbo编码对信息比特进行编码。
在TX MIMO处理器320内,把对MIMO信道的脉冲响应的估计提供给快速傅立叶变换(FFT)单元422,作为一时域采样矩阵的序列
然后,FFT单元422对每组NF个矩阵
执行FFT以便提供一组相应的NF个所估计的信道频率响应矩阵
对于k∈{1,...,NF}。
然后,单元424对每个矩阵
执行特征值分解以便提供上述的酉阵
E(k)和对角矩阵
D(k)。对角矩阵
D(k)被提供给功率分配单元430,酉阵
E(k)被提供给空间处理器450。
功率分配单元430使用上述任一组功率分配方案把总发射功率Ptotal分布给NS个组。这导致对于NS个组的功率分配PG(i),对于i∈{1,...,NS}。然后,单元430根据每个组分配到的发射功率PG(i)为该组独立地执行选择性信道反转。这导致对于每组内NF个频率段有功率分配Pi(k)(对于k∈{1,...,NF}),其中对于组中的一个或多个频率段,Pi(k)等于零(如果不要求任何活动的特征模式是完整的特征模式)。单元432执行注水来分布总发射功率,单元434为每组执行选择性的信道反转。所有传输信道的功率分配Pi(k)都被提供给单独的缩放单元440。
单元440基于功率分配接收并缩放调制码元以提供经缩放的调制码元。每个调制码元的信号缩放可以表示为:
对于i={1,...,NS}以及k={1,...,NF} 公式(26)
接着,空间处理器450基于酉阵
E(k)对经缩放的调制码元进行预调节以提供经预调节的码元,如下:
对于k={1,...,NF} 公式(27)
其中
xi(k)是要在发射天线i的频率段k上被发送的经预调节的码元。如果NS<NT,则
会包括NS个非零项,其余NT-NS个项会是零。
多路复用器(MUX)452接收导频数据并将其与经预调节的码元多路复用。导频数据可以在所有传输信道或其一子集上被发射,并且在接收机处用来估计MIMO信道。多路复用器452把一个经预调节的码元流提供给每个OFDM调制器322。
在每个OFDM调制器322内,IFFT单元接收经预调节的码元流,并且对于NF个频率段的每组NF个码元执行逆FFT以获得相应的时域表示,该时域表示称为OFDM码元。对于每个OFDM码元,循环前缀生成器重复一部分的OFDM码元以形成一相应的传输码元。循环前缀确保了传输码元在存在多径延迟扩展时保留了其正交特性。于是,发射机单元把传输码元转换成一个或多个模拟信号,并进一步调节(例如放大、滤波和上变频)所述模拟信号以便生成一已调信号,该已调信号然后从相关的天线324发出。
图5是用按特征模式的选择性信道反转来处理数据的过程500一实施例的流程图。首先,基于一个或多个编码和调制方案对要被发射的数据进行编码和调制(步骤512)。
可用的传输信道被分成多个组,每组都包括一给定特征模式的所有频率段(步骤514)。(每组也可以被定义为包括多个特征模式的频率段,或仅包括单独特征模式的频率段的一个子集)。然后使用一特定的组功率分配方案把总发射功率分配给多个组(步骤516)。
然后为每个组独立地执行选择性信道反转。对于为使用而选择的每一组(即分配到的发射功率非零),基于分配给该组的发射功率选择组中的一个或多个频率段供数据传输使用(步骤518)。或者,如果要使用该组,则选择该组中的所有频率段。然后为每个所选的频率段确定一缩放因数,使得为每组选择的所有频率段都有相似的接收信号质量,接收信号质量可由接收SNR、接收功率或某些其它度量进行量化(步骤520)。
于是用频率段可用来发射该调制码元的缩放因数对每个调制码元进行缩放(步骤522)。经缩放的调制码元进一步经预调节以便使MIMO信道对角线化(步骤524)。经预调节的码元被进一步处理和发射。
为了清楚,上面已经描述了特定的实施例。根据这里所述的原理也能导出这些实施例的变化以及其它实施例。例如,不必要使用在发射机处进行空间处理(即预调节)的按特征模式SCI方案。其它技术也可以用来对角线化MIMO信道而无须在发射机处进行预调节。一些这样的技术在美国专利申请序列号09/993,087中描述,该申请题为“Multiple-Access Multiple-Input Multiple-Output(MIMO)Communication System”,于2001年11月6日提交,被转让给本申请的受让人并且通过引用被结合于此。如果在发射机处不执行空间处理,则可以按发射天线和某些其它组单元来应用选择性信道反转。
如上所述,选择性信道反转可以在发射机处基于所估计的信道响应矩阵来执行。选择性信道反转可以在接收机处基于信道增益、接收SNR和接收信号质量的某些其它度量来执行。在任一情况下,发射机都有任意形式的充分信道状态信息(CSI),使它能确定:(1)每个特征模式所使用的特定数据速率以及编码和调制方案,以及(2)每个所选传输信道使用的发射功率(和缩放因数),使每组内的信道在接收机处具有相似的信号质量(即反转所选的传输信道)。
这里描述的技术也可以用来对被定义为除单独特征模式外的某些模式的组执行选择性信道反转。例如,一组可以被定义为包括多个特征模式的频率段,或者仅包括一个或多个特征模式的某些频率段,等等。
为了清楚,特别为MIMO-OFDM***描述了用于按特征模式执行选择性信道反转的技术。这些技术也可用于不采用OFDM的MIMO***。此外,尽管特别为前向链路描述了特定的实施例,然而这些技术也可应用于反向链路。
这里描述的技术可以通过各种手段来实现。例如,这些技术可以用硬件、软件和它们的组合来实现。对于硬件实现而言,用于实现这些技术的任一或组合的元件可以在以下元件内实现:一个或多个专用集成电路(ASIC)、数字信号处理器(DSP)、数字信号处理设备(DSPD)、可编程逻辑器件(PLD)、现场可编程门阵列(FPGA)、处理器、控制器、微控制器、微处理器、被设计成执行这里所述功能的其它电子单元、或者它们的组合。
对于软件实现而言,这里描述的技术可以用执行这里所述功能的模块(例如程序、功能等等)来实现。软件代码可以被保存在存储器单元(例如图3中的存储器332或372)中,并由处理器(例如控制器330或370)执行。存储器单元可以在处理器内或处理器外实现,后一情况下它经由本领域公知的各种方式在通信上与处理器耦合。
这里包括的标题是为引用目的,并且帮助定位特定的章节。这些标题不是为了限制标题下面描述的概念的范围,这些概念可应用于整篇申请中的其它章节。
上述实施例的描述是提供给本领域技术人员来实现或使用本发明的。对这些实施例的各种修改对于本领域的技术人员都是显而易见的,这里定义的基本原理可以在不脱离本发明精神和范围的情况下应用于其它实施例。因此,本发明的保护范围并不被上述实施例所限,而应该符合与这里公开的原理和新颖性特征一致的最宽泛的范围。
Claims (21)
1.一种在多输入多输出MIMO通信***中对用于传输的数据进行处理的方法,包括:
把多个可用的传输信道排列到多个组中;以及
对于数据传输要使用的每组传输信道,
选择组中的一个或多个传输信道供使用,以及
为每个所选的传输信道确定一缩放因数,使每组中的一个或多个所选的传输信道具有相似的接收信号质量。
2.如权利要求1所述的方法,其特征在于,每组包括与MIMO信道的一个特定特征模式相对应的所有传输信道。
3.如权利要求1所述的方法,其特征在于还包括:
把总发射功率分布给多个组,其中至少部分基于分配给该组的发射功率来确定每组中一个或多个所选传输信道的一个或多个缩放因数。
4.如权利要求3所述的方法,其特征在于,所述总发射功率被均匀分配给所述多个组。
5.如权利要求3所述的方法,其特征在于,所述总发射功率基于注水被分配给所述多个组。
6.如权利要求5所述的方法,其特征在于,所述注水在多个可用的传输信道间执行,其中分配给每组的发射功率是基于分配给组中多个传输信道的发射功率。
7.如权利要求5所述的方法,其特征在于,所述注水基于所述多个组的平均信号对噪声和干扰比SNR来执行。
8.如权利要求5所述的方法,其特征在于,所述注水基于多个可用传输信道在信道反转后的信号对噪声和干扰比SNR来执行。
9.如权利要求1所述的方法,其特征在于,如果要为数据传输使用一组,则选择该组中的所有传输信道供使用。
10.如权利要求1所述的方法,其特征在于还包括:
基于一个或多个编码和调制方案对数据进行编码和调制以提供调制码元;以及
基于发射调制码元所用的传输信道的缩放因数来缩放每个调制码元。
11.如权利要求10所述的方法,其特征在于,每组传输信道的数据基于单独的编码方案被编码。
12.如权利要求10所述的方法,其特征在于,所有传输信道组的数据都基于一共同的编码方案被编码,其中每组的已编码数据用为该组选择的速率来截短。
13.如权利要求10所述的方法,其特征在于还包括:
对经缩放的调制码元进行预调节。
14.如权利要求1所述的方法,其特征在于,所述MIMO***实现了正交频分复用(OFDM)。
15.一种在实现正交频分复用(OFDM)的多输入多输出(MIMO)通信***中对用于传输的数据进行处理的方法,包括:
把多个可用传输信道排列到多个组中,其中每组都包括与MIMO信道的一特定特征模式相对应的所有传输信道;
把总发射功率分配给所述多个组;以及
对于数据传输要使用的每组传输信道,
选择组中的一个或多个传输信道供使用,以及
至少部分基于分配给该组的发射功率,为每个所选的传输信道确定一缩放因数,使每组中的一个或多个所选的传输信道具有相似的接收信号质量。
16.一种多输入多输出MIMO通信***中的发射机单元,包括:
TX数据处理器,用于基于一个或多个编码和调制方案对数据进行编码和调制以提供调制码元;以及
TX MIMO处理器,用于选择多个传输信道组的每一组中的一个或多个传输信道供数据传输使用,为每个所选的传输信道确定一缩放因数,使每组中一个或多个所选的传输信道具有相似的接收信号质量,并且基于发射调制码元所用的传输信道的缩放因数对每个调制码元进行缩放。
17.如权利要求16所述的发射机单元,其特征在于,TX MIMO处理器还用于把总发射功率分配给多个组,其中至少部分基于分配给该组的发射功率而确定每组中一个或多个所选传输信道的一个或多个缩放因数。
18.实现正交频分复用(OFDM)的多输入多输出(MIMO)通信***中的一种发射机单元,包括:
TX数据处理器,用于基于一个或多个编码和调制方案对数据进行编码和调制以提供调制码元;以及
TX MIMO处理器,用于:
把总发射功率分配给多个传输信道组,其中每组都包括与MIMO信道的一特定特征模式相对应的所有传输信道,
选择每组中的一个或多个传输信道供数据传输使用,
为每个所选的传输信道确定一缩放因数,使得每组中的一个或多个所选传输信道具有相似的接收信号质量,以及
基于发射调制码元所用的传输信道的缩放因数来缩放每个调制码元。
19.如权利要求18所述的发射机单元,其特征在于,所述TX MIMO处理器还用于对经缩放的调制码元进行预调节。
20.一种多输入多输出(MIMO)通信***中的装置,包括:
用于把多个可用传输信道排列到多个组中的装置;
选择每组中的一个或多个传输信道供数据传输使用的装置;以及
为每个所选传输信道确定一缩放因数使得每组中的一个或多个所选传输信道具有相似的接收信号质量的装置。
21.如权利要求20所述的装置,其特征在于还包括:
基于一个或多个编码和调制方案对数据进行编码和调制以提供调制码元的装置;以及
基于发射调制码元所用的传输信道的缩放因数对每个调制码元进行缩放的装置。
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CN102577294A (zh) * | 2009-10-16 | 2012-07-11 | Lg电子株式会社 | 用于在支持中继的无线通信***中发送多用户mimo参考信号的方法和装置 |
CN102577294B (zh) * | 2009-10-16 | 2014-12-10 | Lg电子株式会社 | 用于在支持中继的无线通信***中发送多用户mimo参考信号的方法和装置 |
US9059818B2 (en) | 2009-10-16 | 2015-06-16 | Lg Electronics Inc. | Method and apparatus for transmitting multi-user MIMO reference signal in wireless communication system for supporting relay |
CN113645684A (zh) * | 2020-05-11 | 2021-11-12 | 大唐移动通信设备有限公司 | 一种下行功率自适应分配方法、设备、装置和存储介质 |
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JP4386836B2 (ja) | 2009-12-16 |
RU2005108590A (ru) | 2005-08-27 |
US8194770B2 (en) | 2012-06-05 |
CN100370721C (zh) | 2008-02-20 |
WO2004021634A1 (en) | 2004-03-11 |
HK1083283A1 (en) | 2006-06-30 |
RU2328074C2 (ru) | 2008-06-27 |
US20040042556A1 (en) | 2004-03-04 |
MXPA05002229A (es) | 2005-07-05 |
EP1532762B1 (en) | 2006-12-06 |
CA2496619A1 (en) | 2004-03-11 |
AU2003265601B2 (en) | 2008-12-18 |
BR0313819A (pt) | 2007-09-11 |
EP1532762A1 (en) | 2005-05-25 |
TWI324862B (en) | 2010-05-11 |
JP2005537750A (ja) | 2005-12-08 |
IL166579A0 (en) | 2006-01-15 |
KR20050058333A (ko) | 2005-06-16 |
AU2003265601A1 (en) | 2004-03-19 |
UA84684C2 (ru) | 2008-11-25 |
TW200414708A (en) | 2004-08-01 |
DE60310237T2 (de) | 2007-06-28 |
DE60310237D1 (de) | 2007-01-18 |
KR100983231B1 (ko) | 2010-09-20 |
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