CN1205572A - Circuit arrangement for feeding load - Google Patents
Circuit arrangement for feeding load Download PDFInfo
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- CN1205572A CN1205572A CN 98115491 CN98115491A CN1205572A CN 1205572 A CN1205572 A CN 1205572A CN 98115491 CN98115491 CN 98115491 CN 98115491 A CN98115491 A CN 98115491A CN 1205572 A CN1205572 A CN 1205572A
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Abstract
A circuit arrangement for feeding a single-phase or multi-phase load from a sinusoidal alternating voltage energy supply mains. The circuit arrangement includes a full-wave rectifier stage for deriving a substantially sinusoidal intermediate circuit voltage, a modulation stage, for example, a single-phase or multi-phase inverter, which generates from the intermediate circuit voltage, under the control of a control signal whose frequency is high relative to the frequency of the mains alternating voltage, at least one high-frequency supply voltage which is applied to the load. The supply voltage (voltages) is determined from the product of the control signal and the intermediate circuit voltage. A high-frequency filter stage is coupled to the full-wave rectifier stage so as to suppress interference induced into the energy supply mains in a frequency range which includes the frequency of the control signal.
Description
The present invention relates to a kind of from the circuit arrangement of power supply power network to the power supply of single-phase or multiphase load, the sine-shaped basically at least power network alternating voltage of this power supply power network transmission.
When the electron energy converter when constituting the power supply network supply of single phase alternating current (A.C.) electric power net, use the full-wave bridge rectifier circuit that has the back energy storage capacitor usually in the power network side.This bridge rectifier is also referred to as lattice Ritz (Graetz) bridge circuit usually, its only guarantees during greater than the voltage at described energy storage capacitor two ends, just to have from the power supply power network mobile to the mains current that energy storage capacitor recharges at the instantaneous value of the voltage of power supply power network.Like this, just draw the electric current of tangible pulse type from the power supply power network, the mean value of described electric current is drawn the mean value of electric current from energy storage capacitor corresponding to load.Formed like this mains current of drawing from the power supply power network has higher harmonics content.If this Graetz bridge circuit is used to drive high power load, then harmonic content will surpass the limit of the highest allowance harmonic content of power network operator defined very fast.Consider power network operator's mandatory order, also consider most countries and European standard, do not allow to use the load that produces the mains current that higher harmonics content is arranged.
Know, connect smoothing choke in the downstream of Graetz bridge circuit; This choke realizes making the level and smooth effect of mains current, therefore reduces harmonic content., this choke becomes very huge and very heavy under high-power situation; This has adverse influence concerning the compactedness of the device that is equipped with this power subsystem and weight.
Siemens publishes, the publication of W.Hirschmann and A.Hauenstein " Schaltnetzteile ", and ISBN No.3-8009-1550-3, section 6.4, and pp441 to 444 has described the upconverter that has sine wave to draw electric current.This device is also referred to as preconditioner, and it comprises electronic power switch, high frequency choke coil and very fast switching diode.Described mains switch must drive with suitable control circuit, and the latter controls sine-shaped mains current, and can not cause intermediate circuit, promptly in the tangible pulsation of the voltage in the downstream of Graetz bridge circuit.When suitably designing described control circuit, the foregoing circuit configuration will start sinusoidal wave mains current, harmonic wave in described mains current will be quenchable at least basically, no matter the load that is connected to circuit arrangement how, and might as one man keep constant to the bearing power of described circuit arrangement with the voltage of minimum approximately constant on the intermediate circuit., need for this purpose than relatively large circuit arrangement.
In many cases, need not power to the load with constant in time power.Often be that for example pulsing with respect to mean value with the double frequency of power network frequency when the instantaneous value of this power also can meet the demands.In this case, above-mentioned preregulated use meeting is unfavorable especially.
An object of the present invention is to provide a kind of circuit arrangement, be used for powering to the load, and guarantee that when using simple mechanism mains current has only a spot of harmonic wave from the power supply power network.
According to the present invention, reach this purpose from the power supply power network to circuit arrangement single-phase or the multiphase load power supply by employing is a kind of like this, the minimum sinusoidal wave basically power network alternating voltage of this power supply power network transmission, under the operating frequency of this power network, described load has ohmic basically at least characteristic, and described circuit arrangement comprises:
Full wave rectification stage is used for obtaining sine-shaped basically at least intermediate circuit voltage,
Modulating stage, it is configured single-phase or polyphase inverter, under the control of control signal, produce minimum a kind of high frequency electric source voltage that is added to load from middle circuit voltage, the frequency of above-mentioned control signal is high with respect to the frequency of power network alternating voltage, and described supply voltage is decided by the product of control signal and intermediate circuit voltage and
The high frequency filter level, it is coupled to full wave rectification stage so that be suppressed at induct in the described power supply power network, the interference in the frequency range that comprises the control signal frequency.
The present invention has utilized the understanding to the following fact, promptly by cancelling in intermediate circuit, promptly be connected to the above-mentioned capacitor of Graetz bridge circuit, can be very simply obtain sinusoidal wave mains current as the Ohmic resistance in load downstream from power supply with Graetz bridge circuit.So the voltage of intermediate circuit always is rendered as the absolute value of the network voltage of power network, and the mains current ratio is in network voltage.For being rendered as ohmic basically load near the predetermined frequency range power network frequency, configuration also produces sinusoidal wave mains current in a circuit according to the invention.This load for example can be formed by the HF switch DC/DC transducer of strip resistance load, but also can be by the very fast motor with the power supply of AC/DC transducer, and for example asynchronous motor and permanent magnet motor form.Can select described load to be rendered as the frequency range of ohmic correspondence basically, for example from 0 to 2kHz.This selection is consistent with the relevant regulations of restriction harmonic wave.The upper limit of described relatively frequency range, for example the operating frequency of HF switch DC/DC transducer is high.
In a circuit according to the invention the configuration in, the power that load is drawn always ratio in the intermediate circuit voltage that is added to modulating stage as input voltage square.Because configuration does not contain the energy-storage travelling wave tube of the big energy of storage under power network frequency in a circuit according to the invention, therefore, network voltage and mains current are proportional.Like this, under sinusoidal wave network voltage situation, also will obtain sinusoidal wave mains current.Be coupled to the interference that the high frequency filter level of full-wave rectifier level only is used for suppressing to have the control signal frequency.This high frequency filter level preferably includes very little inductance and very little electric capacity, for example is connected to the downstream of full-wave rectifier level.If desired, inductance also can insert the coupling part between power supply power network and the full-wave rectifier level.Decide the size of described inductance and described electric capacity by this way, promptly their current components of drawing are little with respect to the ohms current that flows through load.
In this class circuit arrangement according to the present invention, often run into such problem, under the situation of low frequency, promptly under the power network frequency of power supply power network, the impedance of load is very low.For example comprise transformer in load, very fast motor or similarly during electrical equipment will this thing happens.Because these loads are usually operated at high frequency electric source voltage, so, must be low-impedance under most of situation under low frequency.
In disposing in a circuit according to the invention, decide the high frequency electric source voltage of load by the product of high-frequency controling signal and sinusoidal intermediate circuit voltage.Therefore, high frequency electric source voltage has sinusoidal envelope.This means that supply voltage has sideband, they distribute symmetrically with respect to the control signal frequency.These sidebands also contain low-down frequency.This is not pure on frequency spectrum because of sinusoidal intermediate circuit voltage for this, but has even comprise several times various components of power network frequency.The mix products of these spectrum components and control signal also is under the low-down frequency.In low-impedance load, these low-frequency spectral components can produce a certain size low-frequency current under low frequency.These electric currents have the opposite effect to full wave rectification stage by modulating stage, and they can be in the inhibitory action of full wave rectification stage counteracting to harmonic wave.
By sinusoidal wave network voltage directly is added to modulator, and, just can avoid this shortcoming without the sinusoidal voltage of intermediate circuit., in order to handle sinusoidal wave network voltage, modulating stage should comprise the mains switch that is applicable to each voltage and current direction.The sort circuit configuration is also referred to as direct interchange (AC) transducer., this class AC transducer certainly than the modulating stage complexity of having only a kind of curtage polarity many.
For fear of by the caused interference of the sinusoidal voltage of intermediate circuit, another embodiment of the present invention has the control signal inverter stages, and the symbol that this inverter stages makes control signal is anti-phase when half period is transformed into down half period at the power network alternating voltage.The result of this step is to reach the same effect that adopts direct AC transducer.The symbol of control signal is inverted at each zero crossing of power network alternating voltage.Because modulating stage resembles the multiplier and works, thus it have and following identical effect, just as if intermediate circuit voltage no longer change on sinusoid ground, and purely with the variation of sine wave.Like this, the sideband of the frequency spectrum of the supply voltage that modulating stage is sent is reduced to just two spectral lines, and described two spectral lines are in the both sides of control signal frequency, with the control signal frequency certain distance are arranged.Therefore, in these sidebands low frequency component appears no longer.So just in load, avoided low-frequency current, the result, also having avoided may be by changing via modulating stage in full-wave rectifier level, the interference that therefore produces in power network again.
The control signal inverter stages preferably includes: the symbol detection level is used to survey the instantaneous value of the polarity of power network alternating voltage, and is used to provide the mark signal of the relevant polarity of expression; And multiplication grade, be used for producing symbol Correction and Control signal by control signal and mark signal are multiplied each other.
Symbol detection level in this embodiment of the present invention plays a part measuring circuit, the polarity of its decision power network alternating voltage.The symbol detection level produces the signal corresponding to+1 or-1.This signal is added to multiplication grade, and in multiplication grade, this signal is used to the zero crossing of power network alternating voltage is responded, and makes control signal anti-phase.
In another embodiment of configuration in a circuit according to the invention, if control signal can be used as binary switching signal, for example it can directly be used as the switching signal of power transistor easily, so, the control signal inverter stages preferably has inverter, this inverter can be changed with mark signal, and controlled signal passes through (traversed).So, this convertible inverter has just replaced multiplication grade, and can constitute with exclusive-OR gate under the simplest situation.
After this, will describe embodiments of the invention with reference to the accompanying drawings in detail.At this, corresponding elements is represented with identical reference number.
Fig. 1 represents the first embodiment of the present invention,
Fig. 2 represents the second embodiment of the present invention,
Fig. 3 represent second embodiment a part another form and
Fig. 4 illustrates some waveform, so that the working condition of the circuit arrangement shown in explanation Fig. 1 and 2.
Fig. 1 represents that under the situation of present embodiment, this load 1 is threephase load from the circuit arrangement of power supply power network 2 to load 1 power supply, threephase motor for example, and power network is expressed as alternate voltage source in the form of the equivalent circuit diagram of simplifying.A full wave rectification stage 3, for example the Graetz bridge circuit is connected to power supply power network 2 by its voltage terminal 4,5.First direct voltage terminal 6 is flat at Graetz bridge circuit duration of work positively charged, is called the positive pole of Graetz bridge circuit from now on, and it is connected to first power supply voltage terminal 10 of modulating stage 11 by inductance 8.Second direct voltage terminal 7 of Graetz bridge circuit 3 is electronegative flat, is called negative pole 7 from now on, and it is connected to the second source voltage terminal 12 of modulating stage 11.In addition, electric capacity 9 in power supply voltage terminal 10,12 cross-over connections of modulating stage 11.The signal input end 15 that level 13 outputs 14 by it are connected to modulating stage 11 takes place in control signal.At circuit arrangement duration of work shown in Figure 1, Graetz bridge circuit 3 receives sine-shaped basically at least power network alternating voltage by voltage terminal 4,5.The Graetz bridge circuit passes through the power network alternating voltage of the sinusoidal intermediate circuit voltage of conduct after direct voltage terminal 6, the 7 output rectifications; This intermediate circuit voltage appears between the positive pole 6 and negative pole 7 of Graetz bridge circuit 3.Decide the size of inductance 8 like this, make under the frequency of power network alternating voltage and under the rated current of load, it is little that the voltage drop of this inductance is compared with the power network alternating voltage, and under the frequency of power network alternating voltage, it is little that electric capacity 9 formed electric currents are compared with load current.Like this, the time variation of 9 pairs of middle circuit voltages of inductance 8 and electric capacity only produces negligible influence.Like this, sinusoidal intermediate circuit voltage is not added to modulation the power supply voltage terminal 10,12 of modulating stage 11 basically.
Decide the size of inductance 8 and electric capacity 9 by this way, promptly their form high frequency filter level, are used to suppress the interference that takes place with the control signal frequency significantly.This interference that is caused by control signal is kept apart with power network effectively by high frequency filter level 8,9.
Because inductance 8 and electric capacity 9 do not play important energy storage effect for the frequency of power network alternating voltage, so the variation of intermediate circuit voltage is in close proximity to sine wave.For the resistance characteristic of load 1, the power that it consumed always is proportional to the instantaneous value of intermediate circuit voltage, promptly across the voltage of the power supply voltage terminal 10,12 of modulating stage 11 square.Therefore, power network alternating voltage and from the electric current drawn of power supply power network also direct ratio each other.Under the situation of sinusoidal wave power network alternating voltage, obtain from desired sinusoidal wave variation of the electric current drawn of power supply power network like this.
In the another kind of form of Fig. 1, also can inject inductance 8 at one of lead between power network 2 and the Graetz bridge circuit 3.
The another kind of form of the circuit arrangement of Fig. 2 presentation graphs 1; Fig. 1 has now replenished the control signal inverter stages.The control signal inverter stages comprises symbol detection level 16 and multiplication grade 17, the input of symbol detection level 16 is connected to the voltage terminal 4 of Graetz bridge circuit 3,5, and multiplication grade 17 is inserted in control signal and takes place in the connecting circuit between the signal input end 15 of the output 14 of level 13 and modulating stage 11.The input of multiplication grade 17 is connected to output 14, and signal input end 15 is connected to the output of multiplication grade 17.Second input of multiplication grade 17 is connected to the output of acquisition of signal level 16.
At circuit arrangement duration of work shown in Figure 2, the polarity of power network alternating voltage that is added to symbol detection level 16 is measured there.The mark signal of the polarity of symbol detection level 16 output expression power network alternating voltages.At multiplication grade 17, mark signal is multiplied by control signal, produces symbol Correction and Control signal, and it is sent to the signal input end 15 of modulating stage 11.In symbol Correction and Control signal, the polarity of control signal that the output 14 of level 13 takes place from control signal is inverted at each zero crossing of power network alternating voltage.
The work of control signal inverter stages 16,17 is described based on simplification example shown in Figure 4.Fig. 4 A represents sinusoidal wave power network alternating voltage; Fig. 4 B represents by the sinusoidal variations of full-wave rectification by the intermediate circuit voltage of sinusoidal wave power network alternating voltage generation.Fig. 4 C represents the square-wave variations of the high-frequency controling signal simplified, and it is drawn on the time shaft identical with 4B with Fig. 4 A.The control signal of the output 14 of level 13 takes place in the variation shown in Fig. 4 C corresponding to for example control signal.The signal that the signal multiplication of Fig. 4 B and 4C produces Fig. 4 D changes, and it represents with solid line, as the figure representative of the supply voltage of load 1.
In contrast to this, Fig. 4 E represents symbol Correction and Control signal, and its symbol changes when the power network alternating voltage zero passage of Fig. 4 A.When the sinusoidal intermediate circuit voltage of the symbol Correction and Control signal of Fig. 4 E and Fig. 4 B multiplies each other,, obtain the represented change in voltage of solid line of Fig. 4 F as synthetic supply voltage.The high frequency electric source voltage of Fig. 4 F is with respect to the variation shown in Fig. 4 D, zero passage place at the power network alternating voltage of Fig. 4 A has shown opposite symbol, makes the supply voltage shown in Fig. 4 D and the 4F change according to antiphase during whole second half-wave of power network alternating voltage.
Fig. 3 is illustrated in the special simple embodiment of multiplication grade 17 under the situation that control signal is a binary signal.This control signal from output 14 is not equal to the form diagramming of (for the sake of simplicity) square-wave signal of 1 in Fig. 3 with pulse duty factor.It is added to the first input end of multiplication grade 17.Be added to second input of multiplication grade 17 from the mark signal of symbol detection level 16, described mark signal also is a binary signal, and it is being changed between two signal levels at it during the power network alternating voltage zero passage.As a result, also anti-phase in the polarity of the symbol Correction and Control signal of the output of multiplication grade 17 (for example exclusive-OR gate).It changes the signal input end 15 that the sort signal that also is illustrated in Fig. 3 is added to modulating stage 11.
Claims (6)
1. one kind from the circuit arrangement of power supply power network to the power supply of single-phase or multiphase load, this power supply power network is carried sine-shaped basically at least power network alternating voltage, under the operating frequency of this power network, load has ohmic basically at least characteristic, it is characterized in that described circuit arrangement comprises:
Full wave rectification stage, being used for obtaining is sine-shaped intermediate circuit voltage at least basically,
Modulating stage, it constitutes with the form of single-phase or polyphase inverter, described inverter produces minimum a kind of high frequency electric source voltage that is added to load from middle circuit voltage under the control of control signal, the frequency of above-mentioned control signal is high with respect to the frequency of power network alternating voltage, and described supply voltage is decided by the product of control signal and intermediate circuit voltage and
The high frequency filter level, it is coupled to full wave rectification stage so that be suppressed at induct in the described power supply power network, in the interference of the frequency range that comprises the control signal frequency.
2. the circuit arrangement of claim 1 is characterized in that it comprises the control signal inverter stages, and the symbol that this inverter stages makes control signal is anti-phase when half period is transformed into down half period at the power network alternating voltage.
3. the circuit arrangement of claim 2 is characterized in that described control signal inverter stages comprises:
The symbol detection level is used to survey the instantaneous value of power network alternating voltage polarity, and be used to provide the relevant polarity of expression mark signal and
Multiplication grade is used for producing symbol Correction and Control signal by control signal and mark signal are multiplied each other.
4. claim 2 or 3 circuit arrangement, the form with the binary switch signal in this circuit arrangement forms described control signal, it is characterized in that: pass the inverter that can be changed by mark signal in control signal described in the described control signal inverter stages.
5. a drive unit that has brushless d.c.motor is characterized in that it comprises the circuit arrangement of a claim in the aforesaid right requirement, and described load is made of motor.
6. an electric device is characterized in that it comprises the desired drive unit of claim 5.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 98115491 CN1192471C (en) | 1997-07-11 | 1998-07-10 | Circuit arrangement for feeding load |
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| DE19729705A DE19729705A1 (en) | 1997-07-11 | 1997-07-11 | Circuit arrangement for feeding a load |
| DE19729705.6 | 1997-07-11 | ||
| CN 98115491 CN1192471C (en) | 1997-07-11 | 1998-07-10 | Circuit arrangement for feeding load |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN1205572A true CN1205572A (en) | 1999-01-20 |
| CN1192471C CN1192471C (en) | 2005-03-09 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 98115491 Expired - Fee Related CN1192471C (en) | 1997-07-11 | 1998-07-10 | Circuit arrangement for feeding load |
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|---|---|
| CN (1) | CN1192471C (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105406522A (en) * | 2014-03-25 | 2016-03-16 | 泉州七星电气有限公司 | Pulse type electricity acquiring method of line fault indicator |
-
1998
- 1998-07-10 CN CN 98115491 patent/CN1192471C/en not_active Expired - Fee Related
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105406522A (en) * | 2014-03-25 | 2016-03-16 | 泉州七星电气有限公司 | Pulse type electricity acquiring method of line fault indicator |
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| Publication number | Publication date |
|---|---|
| CN1192471C (en) | 2005-03-09 |
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