CN114070092A - High-order energy-taking power supply circuit topological structure and control method thereof - Google Patents
High-order energy-taking power supply circuit topological structure and control method thereof Download PDFInfo
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- CN114070092A CN114070092A CN202111415393.9A CN202111415393A CN114070092A CN 114070092 A CN114070092 A CN 114070092A CN 202111415393 A CN202111415393 A CN 202111415393A CN 114070092 A CN114070092 A CN 114070092A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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Abstract
The invention discloses a high-order energy-taking power supply circuit topological structure and a control method thereof.A voltage sampling module is output and compared with reference voltage to form an error signal, a PI regulator is used for outputting a voltage ring signal, a current signal of each branch is sampled by CT, a plurality of branch current sampling signals are superposed to be used as a carrier, the voltage ring output signal is compared with a current-limiting sampling signal to form a PWM (pulse-width modulation) driving signal, and when the output voltage is higher than a set target output voltage, the voltage ring signal is reduced, and the PWM driving duty ratio is reduced; when the output voltage is lower than the set target output voltage, the voltage ring signal is increased, and the PWM driving duty ratio is increased; finally, the output voltage is stabilized at the set target voltage, a scheme of one transformer and multiple primary windings is adopted, and the dynamic automatic voltage equalizing of the input voltage is realized by utilizing the electromagnetic induction principle of the transformer. The use of elements is reduced, the voltage sharing of the input capacitor is not needed artificially, the reliability can be improved, and the cost can be reduced.
Description
Technical Field
The invention belongs to the technical field of power electronics, and particularly relates to a high-order energy-taking power supply circuit topological structure and a control method thereof.
Background
The high-order energy-taking power supply is widely applied to high-voltage flexible direct-current transmission/distribution lines, is a special power supply applied to a VSC-HVDC converter valve, and has the problems in the prior energy-taking power supply technology:
in the flyback converter with high withstand voltage described in patent CN201810767207, since the high-voltage side loop is connected in series with a resistor, the resistor loss is large, and the efficiency is low. In the high-voltage power circuit described in patent CN201911368819, since the high-voltage side loop is connected in series with a resistor and a voltage-sharing transformer is connected in series at a common point, the scheme is complicated and the cost is high.
According to the MOSFET series circuit for the high-voltage input flyback switching power supply disclosed by the patent CN110518806, one path of driving signals controls the switch of a lower tube, and the upper tube is passively switched through the voltage division of an input resistor and the action of a voltage stabilizing tube circuit, so that the voltage withstanding problem of a switching tube is solved. Because the switch consistency of the switch tubes is not completely the same, a voltage-stabilizing tube needs to be connected in parallel between Vds of the lower tube to ensure that the voltage stress meets the requirements of the device. The success of the scheme depends on resistance voltage division and a voltage regulator tube circuit in real time, the requirement on the consistency of the device is high, and the reliability is poor.
According to the high-order energy-taking power circuit and the control method thereof disclosed in patent CN111969858, since the total current of all n input branches is collected at the front end of the input capacitor, in the dynamic starting process, the current of the internal branch of the system cannot be accurately controlled, and the switch tube is over-current and explodes. The main power branch circuits all need series diodes to realize voltage sharing, and the circuit is loaded and has high cost. The scheme is based on a single tube flyback circuit topology, and the RCD absorption circuit is too large in loss, so that the efficiency is low.
Disclosure of Invention
The invention aims to provide a high-order energy-taking power supply circuit topological structure and a control method thereof, and solves the problems of complex circuit, large volume, low efficiency, low reliability and high cost in the prior art.
In order to achieve the purpose, the invention adopts the following technical scheme:
a high-order energy taking power supply circuit topological structure comprises a main power circuit and a control circuit, wherein the main power circuit comprises a secondary side branch and a plurality of parallel primary side branches, primary side windings of the plurality of parallel primary side branches form a flyback transformer T1, the primary side branches are connected with a direct current bus, and secondary side windings of the secondary side branches are arranged on one side of the primary side windings; the control circuit comprises an output voltage division sampling unit, a PI regulator unit, a current sampling processing unit and a PWM (pulse-width modulation) wave-sending control unit, wherein the output voltage division sampling unit is connected to the output voltage of a secondary side branch and used for collecting the output voltage, the output voltage is compared with a reference voltage to form a voltage error signal, the voltage error signal outputs a voltage ring control signal to the PWM wave-sending control unit through the PI regulator unit, the current sampling processing unit is used for collecting input current signals of all branches on a primary side and transmitting the input current signals to the PWM wave-sending control unit, and the PWM wave-sending control unit generates a PWM driving signal with a dynamically adjusted duty ratio according to the input current signals and the voltage error signal and outputs the PWM driving signal to an isolation driving unit connected to the primary side branch.
Further, the primary side branch comprises a diode Dn1, a diode Dn2, a switching tube Qn1, a switching tube Qn2, a primary side winding Npn, a capacitor Cn, a resistor Rn, a sampling capacitor CTn and a primary side winding NPj, the drain of the switching tube Qn1 is connected with one end of the capacitor Cn, one end of the resistor Rn and the cathode of the diode Dn1, and the source of the switching tube Qn1 is connected with the cathode of the diode Dn2 and the same-name end of the primary side winding NPj; the drain electrode of the switching tube Qn2 is connected with the synonym terminal of the primary winding NPj and the anode of the diode Dn1, the source electrode of the switching tube Qn2 is connected with the anode of the diode Dn1 and one end of the sampling capacitor Cs1, and the other end of the sampling capacitor Cs1 is connected with the other end of the capacitor Cn and the other end of the resistor Rn.
Further, the switching tube Qn1 and the switching tube Qn2 both use fully-controlled semiconductor devices.
Further, the voltage error signal is output to a voltage loop control signal through a PI regulator unit, an input current signal is sampled and processed by a current sampling processing unit to form an Isample signal, a current peak value control chip is adopted, Isample is used as a carrier signal, the voltage loop control signal is compared with the carrier signal Isample, and a PWM driving signal with the duty ratio dynamically regulated is generated.
Furthermore, the other end of the capacitor Cn in two adjacent primary side branches is connected with one end of a capacitor Cn + 1.
Further, the number of turns of the primary windings of the primary branches is equal.
Furthermore, the output load is connected with a voltage-dividing resistor module in parallel, the output end of the voltage-dividing resistor module is connected with the input end of the PI regulator unit, the output end of the PI regulator unit is connected with an optical coupling signal isolation module, and the output end of the optical coupling signal isolation module is connected with the PWM wave-emitting control unit.
Furthermore, the current sampling processing unit adopts a current peak value control chip.
Further, the secondary branch comprises a secondary winding Ns1, a diode Ds1 and an output load which are sequentially connected in series, and the output load is connected with a sampling capacitor Cs1 in parallel.
A high-order energy-taking power circuit control method comprises the following steps:
the current sampling processing unit is used for collecting input current signals of all branches of the primary side and transmitting the input current signals to the PWM wave-sending control unit, meanwhile, the output voltage of the secondary side branch is collected by the output voltage dividing and sampling unit, the output voltage is compared with a reference voltage to form a voltage error signal, the voltage error signal is used for outputting a voltage ring control signal through the PI regulator unit, and a PWM driving signal with a duty ratio dynamically regulated is generated according to the input current signals and the voltage error signal and is output to the isolation driving unit connected to the primary side branch.
Compared with the prior art, the invention has the following beneficial technical effects:
the invention relates to a high-order energy-taking power supply circuit topological structure, which is characterized in that an output voltage sampling module is compared with reference voltage to form an error signal, a PI regulator is used for outputting a voltage ring signal, a current signal of each branch is sampled through CT, a plurality of branch current sampling signals are superposed to be used as a carrier, a voltage ring output signal is compared with a current-limiting sampling signal to form a PWM (pulse width modulation) driving signal, and when the output voltage is higher than a set target output voltage, the voltage ring signal is reduced, and the PWM driving duty ratio is reduced; when the output voltage is lower than the set target output voltage, the voltage ring signal is increased, and the PWM driving duty ratio is increased; finally, the output voltage is stabilized at the set target voltage, a scheme of one transformer and multiple primary windings is adopted, and the dynamic automatic voltage equalizing of the input voltage is realized by utilizing the electromagnetic induction principle of the transformer. The use of elements is reduced, the voltage sharing of the input capacitor is not needed artificially, the reliability can be improved, and the cost can be reduced.
Furthermore, the primary side and the secondary side of the high-level energy-taking power supply are isolated by adopting a transformer, and the circuit has a good high-voltage isolation effect. The input capacitor is connected with the static voltage-sharing resistor in parallel, and the effect of starting the input voltage-sharing in the initial state is achieved.
Furthermore, high-voltage input voltage division is realized through multiple primary windings, and the withstand voltage of the switching tubes in each group of converter branches is reduced.
Drawings
Fig. 1 is a schematic diagram of a high-order energy-taking power circuit according to an embodiment of the present invention.
Fig. 2 is a schematic diagram of the operating principle of the high-order energy-taking power circuit according to the embodiment of the present invention (driving on state).
Fig. 3 is a schematic diagram of the operating principle of a high-level energy-taking power circuit according to an embodiment of the present invention (driving off state).
Fig. 4 is a schematic diagram illustrating a control principle of a high-order energy-taking power circuit according to an embodiment of the present invention.
Fig. 5 is a schematic diagram of a high-order energy-taking power circuit based on single-tube flyback in the embodiment of the present invention.
Detailed Description
The invention is described in further detail below with reference to the accompanying drawings:
in order to make the objects and technical solutions of the present invention clearer and easier to understand. The present invention will be described in further detail with reference to the following drawings and examples, wherein the specific examples are provided for illustrative purposes only and are not intended to limit the present invention.
In the description of the present invention, it is to be understood that the terms "center", "longitudinal", "lateral", "up", "down", "front", "back", "left", "right", "vertical", "horizontal", "top", "bottom", "inner", "outer", and the like, indicate orientations or positional relationships based on those shown in the drawings, and are used only for convenience in describing the present invention and for simplicity in description, and do not indicate or imply that the referenced devices or elements must have a particular orientation, be constructed and operated in a particular orientation, and thus, are not to be construed as limiting the present invention. Furthermore, the terms "first", "second" and "first" are used for descriptive purposes only and are not to be construed as indicating or implying relative importance or implicitly indicating the number of technical features indicated. Thus, a feature defined as "first" or "second" may explicitly or implicitly include one or more of that feature. In the description of the present invention, "a plurality" means two or more unless otherwise specified. In the description of the present invention, it should be noted that, unless otherwise explicitly specified or limited, the terms "mounted," "connected," and "connected" are to be construed broadly, e.g., as meaning either a fixed connection, a removable connection, or an integral connection; can be mechanically or electrically connected; they may be connected directly or indirectly through intervening media, or they may be interconnected between two elements. The specific meanings of the above terms in the present invention can be understood in specific cases to those skilled in the art.
As shown in fig. 1, a high-order energy-taking power supply circuit topology structure includes a main power circuit and a control circuit, the main power circuit includes a secondary branch and a plurality of parallel primary branches, a flyback transformer T1 is composed of primary windings of the plurality of parallel primary branches, the primary branches are connected to a dc bus, and secondary windings of the secondary branches are arranged on one side of the primary windings; the control circuit comprises an output voltage dividing and sampling unit, a PI regulator unit, a current sampling and processing unit and a PWM (pulse width modulation) wave-emitting control unit, wherein the output voltage dividing and sampling unit is connected to the output voltage of a secondary side branch and used for collecting the output voltage Vo, the output voltage Vo is compared with a reference voltage to form a voltage error signal, the voltage error signal outputs a voltage ring control signal to the PWM wave-emitting control unit through the PI regulator unit, the current sampling and processing unit is used for collecting input current signals of all branches on a primary side and transmitting the input current signals to the PWM wave-emitting control unit, and the PWM wave-emitting control unit generates a PWM driving signal with a dynamically adjusted duty ratio according to the input current signals and the voltage error signal and outputs the PWM driving signal to an isolation driving unit connected to the primary side branch.
The primary side branch comprises a diode Dn1, a diode Dn2, a switching tube Qn1, a switching tube Qn2, a primary side winding Npn, a capacitor Cn, a resistor Rn, a sampling capacitor CTn and a primary side winding NPj, the drain electrode of the switching tube Qn1 is connected with one end of the capacitor Cn, one end of the resistor Rn and the cathode of the diode Dn1, and the source electrode of the switching tube Qn1 is connected with the cathode of the diode Dn2 and the same-name end of the primary side winding NPj; the drain electrode of the switching tube Qn2 is connected with the synonym terminal of the primary winding NPj and the anode of the diode Dn1, the source electrode of the switching tube Qn2 is connected with the anode of the diode Dn1 and one end of the sampling capacitor Cs1, and the other end of the sampling capacitor Cs1 is connected with the other end of the capacitor Cn and the other end of the resistor Rn.
The switch tube Qn1 and the switch tube Qn2 both adopt fully-controlled semiconductor devices, specifically adopt MOSFET (metal oxide semiconductor field effect transistor) tubes or IGBT (insulated gate bipolar transistor) tubes and type-selection low-voltage MOSFET devices, and reduce the cost.
Specifically, the voltage error signal is output as a voltage loop control signal through the PI regulator unit, the input current signal is sampled and processed by the current sampling processing unit to form an Isample signal, a current peak value control chip is adopted, Isample is used as a carrier signal, the voltage loop control signal is compared with the carrier signal Isample to generate a PWM driving signal with dynamically adjusted duty ratio, and the duty ratio of the fully-controlled semiconductor device is controlled to achieve a preset output voltage value and stabilize the output voltage value.
The other end of the capacitor Cn in two adjacent primary side branches is connected with one end of the capacitor Cn +1, so that the parallel connection of the primary side branches is realized. The number of turns of the primary windings of the primary branches is equal.
The current sampling processing unit collects input currents of a plurality of parallel primary side branches as Ip1, Ip2, … and Ipn, and n is a natural number not less than 2.
The secondary branch circuit comprises a secondary winding Ns1, a diode Ds1 and an output load which are sequentially connected in series, and the output load is connected with a sampling capacitor Cs1 in parallel.
The output load is connected with a voltage-dividing resistor module in parallel, the output end of the voltage-dividing resistor module is connected with the input end of a PI regulator unit, the output end of the PI regulator unit is connected with an optical coupler signal isolation module, the output of the optical coupler signal isolation module is connected with a PWM wave-emitting control unit, the output of the PWM wave-emitting control unit is connected with an isolation driving unit, the output of the isolation driving unit is connected with a gate driving port of a switch tube, current sampling signals of N branches at the primary side are connected with a current sampling processing unit, and the current sampling processing unit is connected with the PWM wave-emitting control unit.
The currents Ip1, Ip2, …, Ipn of the n branches of the primary side are sampled, and the output voltage Vo is sampled. The output voltage Vo is subjected to resistor voltage division sampling and then is compared with the reference voltage to obtain an output voltage error signal, and the output voltage error signal passes through the PI regulator to output a voltage loop signal Icomp. The reference voltage adopts TL431, and the reference is 2.5V or 1.24V.
The current sampling processing unit adopts a current peak value control chip, specifically adopts UCX84X series and NCP series, and superposes n branch current sampling signals, wherein Isampe is K (Ip1+ Ip2+ … + Ipn), and K is a current proportionality coefficient. And taking the current sampling signal as a carrier, and comparing the voltage loop output signal Icomp with the current-limiting sampling signal Isample to form a PWM (pulse-width modulation) driving signal. When the output voltage is higher than the set target output voltage, the voltage loop signal Icomp is reduced, and the PWM driving duty ratio is reduced; when the output voltage is lower than the set target output voltage, the voltage loop signal Icom is increased, and the PWM driving duty ratio is increased; finally, the output voltage is stabilized at the set target voltage.
Example one
A primary side branch j is formed by a primary side winding Npj, a diode Dj1, a diode Dj2, a switching tube Qj1, a switching tube Qj2, a primary side winding Npj, a capacitor Cj, a resistor Rj, a sampling capacitor CTj and a primary side winding NPj, wherein j is1, 2, … and n; the secondary winding Ns1 and the diode Ds1 are connected with the output load in series to form a secondary branch.
One end of a primary side branch is connected with one end of a capacitor C1 and a direct current bus Vin +; the other end of the primary side branch is connected with the other end of the capacitor C1 and one end of the other branch; one end of the primary ith branch is connected with one end of a capacitor Ci and the other end of the primary i-1 branch, the other end of the primary ith branch is connected with the other end of the capacitor Ci and one end of the (i + 1) th branch, and i is more than or equal to 2 and less than or equal to n-1; one end of the nth branch of the primary side is connected with the capacitor Cn and the other end of the (n-1) th branch; the other end of the nth branch is connected with the other end of the capacitor Cn and the direct current bus Vin-; the different name end of the secondary winding Ns1 is connected with the anode of the diode Ds1, the same name end of the secondary winding Ns1 is connected with the secondary output voltage Vo-, the cathode of the diode Ds1 is connected with one end of an output load and the output voltage Vo +, and the other end of the load is connected with the output voltage Vo-.
Referring to fig. 1, the main power circuit includes a diode D11, a diode D12, a diode D21, a diode D22, …, a diode Dn1, a diode Dn1, a fully controlled semiconductor device Q11, a fully controlled semiconductor device Q12, a fully controlled semiconductor device Q21, a fully controlled semiconductor device Q22, …, a fully controlled semiconductor device Qn1, a fully controlled semiconductor device Qn2, a capacitor C1, a capacitor C2, a capacitor … Cn, and a capacitor Cs 1; the flyback transformer T1 comprises a primary winding Np1, primary windings Np2 and …, a primary winding Npn and a secondary winding Ns1, the number of turns of all the primary windings of the flyback transformer T1 is equal, and n is a natural number not less than 2;
the primary side capacitors C1, C2, … and Cn are sequentially connected in series; one end of the primary side 1-th branch is connected with one end of a capacitor C1 and a direct current bus Vin +; the other end of the primary side branch is connected with the other end of the capacitor C1 and one end of the other branch; the drain D of the full-control switch Q11 is connected with one end of the C1, and the source S of the full-control switch Q11 is connected with the cathode of the diode D12; the anode of the diode D12 is connected with the right 1 pin of the CT 1; the cathode of the diode D11 is connected with one end of the C1, the anode of the diode D11 is connected with the drain D of the fully-controlled switch Q12, and the source of the fully-controlled switch Q12 is connected with the right 1 pin of the CT 1; the left 2-foot of the CT1 is connected to the other end of the C1. The dotted terminal of the primary winding Np1 is connected to the source S of the fully controlled switch Q11, and the dotted terminal of the primary winding Np1 is connected to the drain D of the fully controlled switch Q12.
One end of the primary side 2 nd branch is connected with one end of a capacitor C2 and the other end of a capacitor C1; the other end of the primary side 2 nd branch is connected with the other end of the capacitor C2 and one end of the 3 rd branch; the drain D of the full-control switch Q21 is connected with one end of the C2, and the source S of the full-control switch Q21 is connected with the cathode of the diode D22; the anode of the diode D22 is connected with the right 1 pin of the CT 2; the cathode of the diode D21 is connected with one end of the C2, the anode of the diode D21 is connected with the drain D of the fully-controlled switch Q22, and the source S of the fully-controlled switch Q22 is connected with the right 1 pin of the CT 2; the left 2-foot of the CT2 is connected to the other end of the C2. The dotted terminal of the primary winding Np2 is connected to the source S of the fully controlled switch Q21, and the dotted terminal of the primary winding Np2 is connected to the drain D of the fully controlled switch Q22.
One end of the j-th branch of the primary side is connected with one end of a capacitor Cj and the other end of the capacitor Cj-1; the other end of the j-th branch of the primary side is connected with the other end of the capacitor Cj and one end of the j + 1-th branch; the drain D of the fully-controlled switch tube Qj1 is connected with one end of Cj, and the source S of the fully-controlled switch tube Qj1 is connected with the cathode of a diode Dj 2; the anode of diode Dj2 is connected to the right 1 pin of CTj; the cathode of the diode Dj1 is connected with one end of Cj, the anode of the diode Dj1 is connected with the drain D of the fully-controlled switch tube Qj2, and the source S of the fully-controlled switch tube Qj2 is connected with the right pin 1 of CTj; CTj is connected to the other end of Cj by the left 2 leg. The dotted terminal of the primary winding Npj is connected to the source S of the fully-controlled switch tube Qj1, and the dotted terminal of the primary winding Npj is connected to the drain D of the fully-controlled switch tube Qj 2.
One end of the nth branch of the primary side is connected with one end of a capacitor Cn and the other end of the capacitor Cn-1; the other end of the nth branch of the primary side is connected with the other end of the capacitor Cn and Vin < - >; the drain D of the fully-controlled switch tube Qn1 is connected with one end Cn, and the source S of the fully-controlled switch tube Qn1 is connected with the cathode of a diode Dn 2; the anode of the diode Dn2 is connected with the right 1 pin of the CTn; the cathode of the diode Dn1 is connected with one end Cn, the anode of the diode Dn1 is connected with the drain D of the fully-controlled switch tube Qn2, and the source S of the fully-controlled switch tube Qn2 is connected with the right 1 pin of CTn; the left 2-foot of the CTn is connected to the other end of Cn. The dotted terminal of the primary winding Npn is connected to the source S of the fully-controlled switch tube Qn1, and the dotted terminal of the primary winding Npn is connected to the drain D of the fully-controlled switch tube Qn 2.
The secondary winding Ns1 is connected with a diode Ds1 in series and then connected with an output load (R and C are equivalent in parallel) in series to form a secondary branch;
the synonym end of a secondary winding Ns1 of a secondary side branch is connected with the anode of a diode Ds1, the homonymous end of the secondary side winding is connected with a secondary side output voltage Vo-, the cathode of the diode Ds1 is connected with one end of an output load, the connected terminal is connected with the output voltage Vo +, and the other end of the load is connected with the output voltage Vo-;
the invention particularly limits the number of turns of the primary winding Np1, the primary windings Np2 and … and the primary winding Npn of the flyback transformer T1: np1 ═ Np2 ═ … ═ Npn; secondary winding coil turns Ns 1; the transformation ratio n for the transformer is Np1/Ns 1. The following relationship should be satisfied: vo Np1/Ns1 is less than or equal to Vin/n;
the working principle of this embodiment is explained below:
in the following explanation of the operation principle, according to the previous description, the control terminals of the fully-controlled semiconductor devices Q11 and Q12, Q21, Q22 and …, and the nth fully-controlled semiconductor devices Qn1 and Qn2 input the same PWM signals, i.e., Q11, Q12 and …, and Qn1 and Qn2 are turned on and off at the same time.
To better explain the dynamic automatic voltage-sharing function in the patent solution, the first branch capacitor C1 is set to have a voltage higher than the voltages of the other branch capacitors at a certain time, and the fully-controlled switching devices Q11, Q12, …, Qn1 and Qn2 are turned on simultaneously, as shown in fig. 2.
For the double-tube flyback converter of the first branch, when the fully-controlled switching tubes Q11 and Q12 obtain driving signals and are turned on simultaneously, the voltage on the capacitor C1 is applied to the primary winding Np1 through the switching tubes Q11, Q12 and CT1, according to the electromagnetic induction theorem and the KVL theorem, the voltage in the same direction as the voltage on the winding Np1 is induced on the winding Np1 of the transformer, the voltage on the same-name end of the primary winding Np1 is positive, which is equivalent to the input voltage applied to the inductor Np1 winding, and the current is increased linearly. According to the electromagnetic induction principle, due to the fact that key parameters of primary windings are the same (the number of turns is equal), voltage equal to that of a C1 capacitor is induced on a branch Np2 winding on a second branch Np2 winding, at the moment, the voltage of the transformer Np2 winding is higher than that of the C2 capacitor, under the action of potential difference, energy stored in the transformer flows out through a dotted terminal of an Np2 winding, a follow current loop (a body diode) passing through a full-control type switching tube Q21 and a follow current loop (a body diode) of an input capacitor C2, a CT2 and a Q22 form a follow current loop, the energy in the transformer is fed back to the C2 capacitor, and the voltage of the C2 capacitor is increased. Since the current of C1 flows out of the positive terminal of the C1 capacitor, the C1 voltage decreases.
For the 3 rd branch dual-tube flyback converter, the voltage on the capacitor C3 is lower than that of the capacitor C1. Under the above conditions, according to the electromagnetic induction principle, since the primary winding has the same key parameters (the number of turns is the same), a voltage equal to that of the C1 capacitor is induced on the Np3 winding of the 3 rd branch, at this time, the voltage of the Np3 winding of the transformer is higher than that of the C3 capacitor, under the action of the potential difference, the energy stored in the transformer flows out through the dotted terminal of the Np3 winding, the freewheeling circuit (body diode) passing through the fully-controlled switching tube Q31 and the freewheeling circuit (body diode) of the input capacitors C3, CT3 and Q32 form a freewheeling circuit, the energy in the transformer is fed back to the C3 capacitor, and the voltage of the C3 capacitor is increased. Since the current of C1 flows out of the positive terminal of the C1 capacitor, the C1 voltage decreases.
For the nth branch double-tube flyback converter, the voltage on the Cn capacitor is lower than the voltage of the C1 capacitor. Under the above conditions, according to the electromagnetic induction principle, since the primary winding has the same key parameters (the number of turns is the same), a voltage equal to the capacitance of C1 is induced on the n-th branch Npn winding, at this time, the voltage of the transformer Npn winding is higher than the voltage of the Cn capacitance, under the action of the potential difference, the energy stored in the transformer flows out through the dotted terminal of the Npn winding, and forms a freewheeling circuit through the freewheeling circuit (body diode) of the fully-controlled switching tube Qn1 and the freewheeling circuit (body diode) of the input capacitances Cn, CTn and Qn2, and the energy in the transformer is fed back to the Cn capacitance, so that the voltage of the Cn capacitance is increased. Since the current of C1 flows out of the positive terminal of the C1 capacitor, the C1 voltage decreases.
In summary, assuming that the voltage of the input capacitor C1 is higher than the voltages of all other capacitors, when the switching tube is turned on, the input capacitor C1 outputs energy to the transformer, and the C1 discharges; for other branches, the induced voltage of the primary winding is higher than the voltage of the input capacitor, and according to the electromagnetic induction principle, the energy stored in the transformer is fed back to the input capacitor, so that the discharge of C1 is finally realized, and the voltage of C1 is reduced; for other branch input capacitors, the voltage is increased due to charging caused by energy feedback, so that the dynamic automatic voltage equalization of the input voltage in the switching-on process of the switching tube is realized.
Based on the above dynamic automatic voltage-sharing principle, the voltage Vc1 ═ Vc2 ═ Vc … ═ Vcn on the input voltage. Because the key parameters (the number of turns, the inductance and the winding resistance) of the primary winding of each branch are equal, the driving turn-on time is equal, and the primary current is equal. Ip1 ═ Ip2 ═ … ═ Ipn (Vc1 ═ Lp1 ═ Ip/ton)
After the fully-controlled switching tube is driven to be closed, the energy stored in the transformer forms a current loop through the secondary winding Ns1, the diode Ds1 and the output capacitor Cs1, and is released on the secondary capacitor Cs and the load resistor. As shown in fig. 3. After the primary side switching tube Is turned off, the magnetic flux Is continuous according to ampere loop law, namely Np1 × Ip1+ Np2 × Ip2+ … + Npn × Ipn-Ns 1 × Is1, and the secondary side current can be calculated.
The secondary diode Ds1 can be connected in parallel with a snubber circuit to reduce the voltage stress of the diode. The buffer circuit can be in the form of a capacitor c, a resistor-capacitor series RC and a resistor-capacitor diode RCD.
The output voltage sampling module can adopt a resistance voltage division form;
the output voltage loop PI regulator module adopts a 431 chip, takes feedback voltage and 431 reference voltage as error signals, and outputs a voltage loop signal after passing through the PI regulator;
the voltage loop signal is isolated from the primary side driving signal, and the voltage loop signal is transmitted to the PWM wave-generating controller by adopting an optical coupler, so that the optical coupler works in a linear region, and the size of the voltage loop signal is controlled;
the PWM wave-transmitting control chip can be realized by UCCX84X series and NCP series control chips of TI manufacturers, and the maximum input power is realized by adopting a current peak value control mode.
Sampling primary side current of each branch, selecting CT to sample current of a switching tube of each branch, Ip1, Ip2, … and Ipn, wherein the current sent to the PWM wave-generating control chip is Isample ═ (Ip1+ Ip2+ … + Ipn)/n;
the current sampling signal is the carrier of the PWM signal, and the voltage ring signal is compared with the carrier signal to form a PWM driving signal with adjustable duty ratio.
In order to realize simultaneous on and off of all the switch tube driving signals and reduce delay difference between the drives, the same driving transformer is selected to output a plurality of paths of driving signals.
The control principle block diagram is shown in the following figure 4. The present invention also uses a single tube flyback converter topology as shown in fig. 5 below.
Finally, it should be noted that: the technical solutions of the present invention are only illustrated in conjunction with the above-mentioned embodiments, and not limited thereto. Those of ordinary skill in the art will understand that: modifications and equivalents may be made to the embodiments of the invention by those skilled in the art, which modifications and equivalents are within the scope of the claims appended hereto.
Claims (10)
1. A high-order energy taking power supply circuit topological structure is characterized by comprising a main power circuit and a control circuit, wherein the main power circuit comprises a secondary side branch and a plurality of parallel primary side branches, primary side windings of the plurality of parallel primary side branches form a flyback transformer T1, the primary side branches are connected with a direct current bus, and secondary side windings of the secondary side branches are arranged on one side of the primary side windings; the control circuit comprises an output voltage division sampling unit, a PI regulator unit, a current sampling processing unit and a PWM (pulse-width modulation) wave-sending control unit, wherein the output voltage division sampling unit is connected to the output voltage of a secondary side branch and used for collecting the output voltage, the output voltage is compared with a reference voltage to form a voltage error signal, the voltage error signal outputs a voltage ring control signal to the PWM wave-sending control unit through the PI regulator unit, the current sampling processing unit is used for collecting input current signals of all branches on a primary side and transmitting the input current signals to the PWM wave-sending control unit, and the PWM wave-sending control unit generates a PWM driving signal with a dynamically adjusted duty ratio according to the input current signals and the voltage error signal and outputs the PWM driving signal to an isolation driving unit connected to the primary side branch.
2. The topological structure of a high-level energy-taking power supply circuit according to claim 1, wherein the primary side branch comprises a diode Dn1, a diode Dn2, a switching tube Qn1, a switching tube Qn2, a primary side winding Npn, a capacitor Cn, a resistor Rn, a sampling capacitor CTn and a primary side winding NPj, the drain of the switching tube Qn1 is connected with one end of the capacitor Cn, one end of the resistor Rn and the cathode of the diode Dn1, and the source of the switching tube Qn1 is connected with the cathode of the diode Dn2 and the same-name end of the primary side winding NPj; the drain electrode of the switching tube Qn2 is connected with the synonym terminal of the primary winding NPj and the anode of the diode Dn1, the source electrode of the switching tube Qn2 is connected with the anode of the diode Dn1 and one end of the sampling capacitor Cs1, and the other end of the sampling capacitor Cs1 is connected with the other end of the capacitor Cn and the other end of the resistor Rn.
3. The topology of claim 1, wherein the transistors Qn1 and Qn2 are fully-controlled semiconductor devices.
4. The topological structure of the high-order energy-taking power supply circuit according to claim 1, wherein the voltage error signal is subjected to a PI regulator unit to output a voltage loop control signal, the input current signal is subjected to sampling processing by a current sampling processing unit to form an Isample signal, a current peak control chip is adopted, the Isample is used as a carrier signal, and the voltage loop control signal is compared with the carrier signal Isample to generate a PWM driving signal with a dynamically adjusted duty ratio.
5. The topology of claim 1, wherein the other end of the capacitor Cn in two adjacent primary branches is connected to one end of a capacitor Cn + 1.
6. The topology of claim 5, wherein the primary windings of the primary branches have equal number of turns.
7. The topological structure of the high-order energy-taking power supply circuit according to claim 1, wherein the output load is connected in parallel with a voltage-dividing resistor module, the output end of the voltage-dividing resistor module is connected with the input end of the PI regulator unit, the output end of the PI regulator unit is connected with an optical coupling signal isolation module, and the output of the optical coupling signal isolation module is connected with the PWM wave-generating control unit.
8. The topology structure of claim 1, wherein the current sampling processing unit is a current peak control chip.
9. The topology structure of the high-order energy-taking power supply circuit as claimed in claim 1, wherein the secondary branch comprises a secondary winding Ns1, a diode Ds1 and an output load which are connected in series in sequence, and the output load is connected with a sampling capacitor Cs1 in parallel.
10. A high-order energy-taking power supply circuit control method based on the high-order energy-taking power supply circuit topology structure of claim 1, characterized by comprising the following steps:
the current sampling processing unit is used for collecting input current signals of all branches of the primary side and transmitting the input current signals to the PWM wave-sending control unit, meanwhile, the output voltage of the secondary side branch is collected by the output voltage dividing and sampling unit, the output voltage is compared with a reference voltage to form a voltage error signal, the voltage error signal is used for outputting a voltage ring control signal through the PI regulator unit, and a PWM driving signal with a duty ratio dynamically regulated is generated according to the input current signals and the voltage error signal and is output to the isolation driving unit connected to the primary side branch.
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