CN113225117A - 一种多用户Massive MIMO***信号发送和接收方法 - Google Patents
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Abstract
本发明属于无线通信技术领域,具体为一种多用户Massive MIMO***信号发送和接收方法。本发明的方案直接对信道的CSI(Channel State Information)进行波束赋形,通过基于迫零的波束赋形技术对所发信号进行波束赋形或预编码操作。在此架构下,发送端可将所有的信息比特放入一个数据流中进行传输,并且可利用发端和收端所有天线,在发端获得波束赋形增益,在接收端通过所有接收天线联合检测获得接受分集增益。本发明在多用户SM‑MIMO***中既实现了发射机的发射波束赋形增益,又实现了接收机的空间分集增益,可以在单个数据流中注入更多比特,从而实现较高的传输数据速率和良好的性能。
Description
技术领域
本发明属于无线通信技术领域,具体为一种多用户Massive MIMO***信号发送和接收方法。
背景技术
多输入多输出(MIMO)技术可以在不增加发射功率和频谱资源的情况下显著提高频谱效率。其中,空间复用和空间分集备受关注,比如垂直分层时空(V-BLAST)和Alamouti空时分组编码(STBC)等。此外,波束赋形技术是一种高效的MIMO传输技术,起源于阵列信号处理技术,通过对不同天线的发射信号进行称重和梳理,形成能量聚焦波束,发射定向的强波束来降低接收机的高传输损耗以提高接收机的信噪比,是空间滤波的一种重要手段,现已成为5G及5G以外移动通信***的关键技术和研究热点。目前移动通信***中最常用的波束形成方法包括最大比传输(Maximum Ratio Transmission,MRT),迫零(Zero Forcing,ZF),最小均方误差(Minimum Mean Square Error,MMSE),块对角化(BlockDiagonalization,BD)和信漏噪比(Signal to Leakage and Noise Ratio,SLNR)。到目前为止,对于不同MIMO场景下波束形成矢量的设计和优化已经有了广泛的研究。同时,空间调制作为一种新的MIMO技术,近年来引起了广泛的讨论,它具有单一的射频特性和独特的开关结构,简化了发射和接收的实现。此外,空间移位键控(SSK)是一种与SM类似但更简化的方法,仅利用天线的索引来调制单个射频的信息,实现更低的实际实现复杂性和成本。利用信道状态信息(CSI)在发送端进行预处理可以进一步提高SM***的性能。
考虑到性能、计算复杂度和实际应用,特别是在大规模MIMO场景下,如何利用波束赋形技术提高SM-MIMO***的频谱效率和性能,同时实现其实际应用仍是一个热点和悬而未决的课题。
发明内容
针对上述问题,本发明基于CSI辅助MIMO***的巨大优势,提出一种用于多用户SM/SSK MIMO***的迫零波束赋形辅助的单层传输技术,本发明中将其定义为MU-SZF-SM/MU-SZF-SSK,本发明的方案直接对信道的CSI(Channel State Information)进行波束赋形,通过基于迫零的波束赋形技术对所发信号进行波束赋形或预编码操作。在此架构下,发送端可将所有的信息比特放入一个数据流中进行传输,并且可利用发端和收端所有天线,在发端获得波束赋形增益,在接收端通过所有接收天线联合检测获得接受分集增益。
本发明的技术方案是:
本发明采用的基本技术方案是采用多输入多输出***二进制数字信号空间调制方法,并假设发射端已知信道状态信息。所述***具有s个用户,每个用户有Nt根发射天线,Nr根接收天线,用于传输每组b1+b2比特的数字信号。其中前b1比特映射为天线序号,即空间调制后要激活的天线,最后b2比特映射为APM符号,对所得信号进行预编码处理后,在接收端进行最大似然检测并译码输出。
在传统基于迫零的多用户MIMO技术(MIMO-ZF)中,其适用于满流传输,即每用户传输流数等于接收天线数,因此其频谱效率即每一流的星座阶数乘上总的流数。而当传统MIMO-ZF每用户传输流数小于接收天线数时,会使得接收端某些天线无法接收信号,造成接收天线无法完全利用的问题。尤其当传统多用户MIMO-ZF进行其单流传输时更无法实现接收分集增益,因为这种情况下只有一个目标天线能够接收信号,因此无法对所有接收信号进行联合检测。本方案的创新之处在于,在传统多用户MIMO-ZF技术中融入空间调制技术,直接对信道的CSI信息进行波束赋形,并且对于每个用户,将所有的信息位放入一个数据流中进行传输,通过迫零的波束赋形技术对所发信号进行预编码操作,并在接收端利用所有天线联合检测。
发送端
在MU-SZF-SM中,比特信息通过分组分别映射成发射天线序号和星座点符号,假设采用M阶调制,此时***的频谱效率B=s*(log2(Nt)+log2(M)),其中s为用户数。前log2(Nt)比特二进制转十进制,其转化后的数值用来选择激活第1个用户的发射天线i1的序号,接下来的log2(M)比特二进制转十进制,其转化后的数值用来选择发送的星座点符号x1j,接着的log2(Nt)比特映射成选择激活第2个用户的发射天线i2的序号,再log2(M)比特二进制转十进制,其转化后的数值映射为用户2选择发送的星座点符号x2j,以此类推,第s个用户的发射天线is被激活,选择发送的星座点符号为xsj,这些传统的调制星座可以是多级相移键控星座(PSK)或正交调幅星座(QAM),于是被激活的发送天线矩阵和选择发送的星座点符号矩阵表示如下:
i=[i1,i2,…,im,…is]T#(1)
在多用户MIMO配置下,整个***的信道矩阵H具有Nt根发射天线,(Nr*s)根接收天线,其中每用户配置Nr根接收天线,因此是一个(Nr*s)*Nt维的矩阵,表示如下:
H=[H1,H2,…,Hm,…Hs]T#(3)
此***在波束赋形前的发射符号表示如下:
x=[x1,x2,…xm,…,xs]T#(6)
其中,式中为第m个用户的第im根发射天线到所有接收天线的信道列向量。中的每个元素都服从独立的高斯分布CN(0,1),是第m个用户的APM星座的映射符号,是发射功率。如果那么就是MU-SZF-SSK***,如果是一个传统的APM符号,那么就是一个MU-SZF-SM***。第m个用户在MU-SZF-SM/MU-SZF-SSK MIMO***下的传输信号xm是一个Nr×1的向量,它是由一个含有log2(Nt)以及log2(M)比特的单流信号组成的。值得注意的是,对于每个用户而言,所有信息位都被放在一个数据流上,在这点上与传统多用户MIMO-ZF满流传输不同。具体来说,对于本发明提出的方案,每个用户的发送层不会随着Nr的增加而增加,这与传统多用户MIMO-ZF***有很大的不同,因为传统多用户MIMO-ZF中每个用户的发送层通常与接收天线Nr相关。对于接收天线为Nr的多用户MIMO-ZF***中的每个用户,生成Nr×1维传输矢量,由Nr个不同的APM符号组成,视为Nr流传输,传输的信息量为Nr×log2M比特。但是,本发明提出的MU-SZF-SM/MU-SZF-SSK中每个用户的传输流数并不会随着Nr的变化而变化,因为发射信号的log2(Nt)+log2(M)比特信息只与发射天线数Nt和调制阶数M有关。因此,发送信号x在MU-SZFSM/MU-SZF-SSK MIMO***中是一个矢量,它传递的是s个log2(Nt)+log2(M)比特的单层数据流,这种结构可以避免严重的干扰,从而获得良好的性能。另外,对每个用户来说,发出的信号不仅包括APM符号还包括空间信道发射机将信道信息直接发送到接收机,仍利用空间信道来传递信息。
然后需要对发射符号进行预编码处理,假设采用最简单的迫零(ZF)预编码算法,其预编码矩阵如下:
W=HH(HHH)-1#(8)
因此经历迫零波束赋形后得到每个用户的发射信号可以被表示为
接收端
对每个用户而言,经过信道后接收端得到的信号可以表达为如下形式:
其中n为(s*Nr)×1维高斯白噪声向量,元素服从CN(0,1),为发射功率,矩阵是MIMO***下Nr×Nr的功率归一化矩阵,在这里 被认为是修正后的发射稀疏信号向量。待功率归一化后,接下来对接收端得到的信号进行最大似然法检测:
对于MIMO-ZF的传统波束赋形,即使在接收端有多个天线的情况下,也很难实现接收分集增益。这是因为多流传输的多用户MIMO-ZF的预处理是通过预先消除发射机处的干扰来实现的,而不需要接收端多个天线之间进行联合检测。因此,MIMO-ZF采用多流传输,每个接收天线获得事先在发射机处形成的目标APM符号而不受干扰。
本发明的有益效果是:本发明提出的MU-SZF-SM/MU-SZF-SSK是针对单流传输精心设计的,在多用户SM-MIMO***中既实现了发射机的发射波束赋形增益,又实现了接收机的空间分集增益。由于MU-SZF-SM/MU-SZF-SSK具有显著的波束形成增益和接收分集增益,可以在单个数据流中注入更多比特,从而实现较高的传输数据速率和良好的性能。
附图说明
图1为基于本发明的MIMO配置***模型示意图;
图2为32发2用户4收MU-MIMO-ZF与MU-SZF-SSK对比图。
具体实施方式
下面结合附图和实施例,详细描述本发明的技术方案:
如图1所示,简要展示了本发明提出的MU-SZF-SM/MU-SZF-SSK的MIMO配置***模型,该模型大概分为四个模块,预编码模块,CSI构造的空间符号模块,发射端模块,接收端模块。
实施例
本例中***采用SSK调制,发射天线数量Nt=32,用户数目为2,接收天线数数量Nr=4,所以***的总频谱效率为B=s*(log2(Nt)+log2(M))=10bps/Hz,于是被激活的发送天线矩阵和选择发送的星座点符号矩阵表示如下:
i=[i1,i2]T#(12)
在MU-MIMO配置下,整个***的信道矩阵H具有32根发射天线,8根接收天线,其中每用户配置4根接收天线,因此是一个8*32维的矩阵。发射端通过反馈链路得知信道状态信息为:
H=[H1,H2]T#(15)
若第2个用户待传输的比特数据为b=00101,根据映射规则可知,这5个比特00101为空间比特,映射为空间符号h25=[h1,25 h2,25 … h4,25]T,由于采用SSK调制,所以确定待发射的符号为
其中,式中h25为第2个用户的第5根发射天线到所有接收天线的信道列向量。h25中的每个元素都服从独立的高斯分布CN(0,1),是第2个用户的APM星座的映射符号,是发射功率。第2个用户在MU-SZF-SM/MU-SZF-SSK MIMO***下的传输信号x2是一个4×1的向量,它是由一个含有log2(32)=5以及log2(2)=1比特的单流信号组成的。值得注意的是,对于用户2而言,所有信息位都被放在一个数据流上,在这点上与传统多用户MIMO-ZF满流传输不同。具体来说,在以上提出的MU-SZF-SSK例子中,因为发射信号的log2(32)+log2(2)比特信息只与发射天线数和调制阶数有关。因此,发送信号x在MU-SZFSM/MU-SZF-SSKMIMO***中是一个矢量,它传递的是2个log2(32)+log2(2)比特的单层数据流,这种结构可以避免严重的干扰,从而获得良好的性能。另外,对用户2来说,发出的信号不仅包括APM符号还包括空间信道h25,发射机将信道信息h25直接发送到接收机,仍利用空间信道来传递信息。
接下来进行预编码,预编码矩阵为W=HH(HHH)-1,并设α为功率归一化因子,则α=|Wh25|2,所以发射端的最终发射信号形式为:
通过以上的步骤实现了***的调制和预编码过程,经过信道之后接收信号在除去功率归一化因子后的形式如下:
由最后的式子可以看出,此***作为2用户32发4收的MIMO***,通过结合波束赋形技术引入了性能增益,从接收端看来,只有第i2根天线需要被检测。该方案对收发天线数量没有限制,比较灵活,且能够带来较大的性能提升。下面结合仿真结果具体分析本发明发明对误码性能的提升。
图2为本发明所提出方案在发射天线数量为32,用户数为2,接收天线数量为4情况下的误码率对比,采用SSK调制,使得频谱效率为B=s*(log2(Nt)+log2(M))=10bps/Hz,而MU-MIMO-ZF***的在此情况下满流传输,频谱效率为B=s*Nr=8bps/Hz。总体上来看,本发明方案误码率的变化随信噪比改变较为缓慢,在低信噪比(6dB以下)情况下,本方案频谱效率比传统MU-MIMO-ZF高,而且误码率较传统MU-MIMO-ZF更低,其性能更好。
Claims (1)
1.一种多用户Massive MIMO***信号发送和接收方法,***中有s个用户,每个用户有Nt根发射天线,Nr根接收天线,用于传输每组b1+b2比特的数字信号,其中前b1比特映射为天线序号,后b2比特映射为APM符号;其特征在于,包括:
发送端
假设采用M阶调制,则***的频谱效率B=s*(log2(Nt)+log2(M)),前log2(Nt)比特二进制转十进制,其转化后的数值用来选择激活第1个用户的发射天线i1的序号,接下来的log2(M)比特二进制转十进制,其转化后的数值用来选择发送的星座点符号x1j,接着的log2(Nt)比特映射成选择激活第2个用户的发射天线i2的序号,再接着的log2(M)比特二进制转十进制,其转化后的数值映射为用户2选择发送的星座点符号x2j,以此类推,第s个用户的发射天线is被激活,选择发送的星座点符号为xsj,调制星座可为多级相移键控星座或正交调幅星座,被激活的发送天线矩阵和选择发送的星座点符号矩阵表示为:
i=[i1,i2,…,im,…is]T
***的信道矩阵H为:
H=[H1,H2,…,Hm,…Hs]T
在波束赋形前的发射符号为:
x=[x1,x2,…xm,…,xs]T
其中,为第m个用户的第im根发射天线到所有接收天线的信道列向量,中的每个元素都服从独立的高斯分布,xjm是第m个用户的APM星座的映射符号,是发射功率;第m个用户的传输信号xm是一个Nr×1的向量,它是由一个含有log2(Nt)以及log2(M)比特的单流信号组成的,对每个用户,所有信息位都被放在一个数据流上;
W=HH(HHH)-1
接收端
对每个用户,经过信道后接收端得到的信号为:
对接收端得到的信号进行最大似然法检测:
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