CN111817622A - Brush motor long tail type H-bridge driving circuit - Google Patents
Brush motor long tail type H-bridge driving circuit Download PDFInfo
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- CN111817622A CN111817622A CN202010612322.7A CN202010612322A CN111817622A CN 111817622 A CN111817622 A CN 111817622A CN 202010612322 A CN202010612322 A CN 202010612322A CN 111817622 A CN111817622 A CN 111817622A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
- H02P7/03—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors
- H02P7/04—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors by means of a H-bridge circuit
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
- H02P7/03—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors
- H02P7/05—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors by means of electronic switching
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
- H02P7/06—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current
- H02P7/18—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power
- H02P7/24—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices
- H02P7/28—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices
- H02P7/285—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only
- H02P7/292—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only using static converters, e.g. AC to DC
- H02P7/295—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only using static converters, e.g. AC to DC of the kind having one thyristor or the like in series with the power supply and the motor
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Abstract
The invention discloses a brush motor long tail type H-bridge driving circuit, which comprises an H-shaped reversing bridge circuit, a field effect transistor grid driving power circuit, a long tail type PWM width modulation circuit and a high-voltage constant-current voltage-stabilizing power supply circuit, wherein the H-shaped reversing bridge circuit is connected with the field effect transistor grid driving power circuit; the field effect transistor grid driving power supply circuit provides a driving power supply for the H-shaped reversing bridge circuit, the long tail type PWM width modulation circuit is connected with the H-shaped reversing bridge circuit in series, and the high-voltage constant-current voltage-stabilizing power supply circuit supplies power for the long tail type PWM width modulation circuit; the invention simplifies the circuit design and also improves the overall reliability of the circuit essentially; the speed regulation with 100% duty ratio can be realized, only one path of PWM signals is needed for driving and speed regulation, and the condition that 'pipe explosion' occurs when the upper pipe and the lower pipe of the H bridge are simultaneously conducted due to the fact that a plurality of paths of PWM signal waves have problems due to phase positions and a time sequence generating circuit or software is completely avoided.
Description
Technical Field
The invention relates to a brush motor driving circuit related to a railway passenger car, a locomotive windscreen wiper driving motor, a car coupler motor, an automatic door motor and the like, in particular to a brush motor long tail type H-bridge driving circuit, belonging to the technical field of motors and the technical field of railway passenger car manufacturing.
Background
In recent years, the passenger train manufacturing industry has been developed dramatically, and a large number of automatic devices are applied to each functional unit of a vehicle, wherein a rotating motor is usually used as an execution element; at present, the motor forms commonly used for vehicles are a direct current brushless motor and a direct current brush motor, the direct current brushless motor has the obvious advantages of the direct current brushless motor, the driving of the direct current brushless motor usually depends on a driver and internal software, the driving logic of the direct current brushless motor is complex, and the problems of software runaway, hardware damage and the like are easy to occur; the problems of low-speed performance and small starting torque are particularly prominent on a non-inductive brushless motor; because many devices on the vehicle, such as a wiper driving motor, a coupler motor and an automatic door motor, the static resistance of the devices is very large, and the starting of a brushless motor is often caused to be problematic when the brushless motor runs, the driving motors adopted by the important devices are almost all brush direct current motors, and the requirements of the working conditions of the railway vehicle can be well met by the excellent mechanical characteristics, the simple and reliable driving and speed regulating modes of the driving motors.
In the field of direct current brush motor driving, when speed regulation requirements exist in application, H-bridge driving circuits formed by MOSFET field effect transistors are almost adopted; the existing design adopts a special H-bridge driving chip or a discrete element for driving, such as IR2110 and other special H-bridge driving chips, and the upper tube driving of the special H-bridge driving chip depends on the bootstrap voltage established by the alternate conduction of the upper tube and the lower tube to realize the driving of the upper tube; part of special modules adopt a built-in charge pump form to realize upper tube driving; however, the built-in charge pump module must be built in an H bridge or a half-arm H bridge, and the highest applicable voltage is low, which is far from meeting the requirement of the highest voltage of the driving motor DC145V of the passenger train equipment; the IR2110 class bootstrap dedicated chip usually needs to be driven by at least two PWM signals or four PWM signals with a phase difference of 180 degrees between every two PWM signals, and a duty ratio of 2-5% must be reserved in each driving pulse period for driving the lower tube to conduct, so as to establish a bootstrap voltage required for driving the upper tube, in order to ensure that two tubes are not conducted simultaneously in the process of driving the upper tube and the lower tube to conduct alternately, a dead time with a certain width needs to be reserved on the driving signals of the upper tube and the lower tube, and a multipath PWM signal with a complex phase and timing relationship causes complex design and debugging, and seriously reduces the reliability of the system, which is contrary to the first purpose of reliability of the railway passenger car equipment.
Disclosure of Invention
In order to overcome the defects of the prior art, the invention provides the brush motor long tail type H-bridge drive circuit, which simplifies the circuit design and improves the overall reliability of the circuit essentially; the speed regulation with 100% duty ratio can be realized, only one path of PWM signals is needed for driving and speed regulation, and the condition that 'pipe explosion' occurs when the upper pipe and the lower pipe of the H bridge are simultaneously conducted due to the fact that a plurality of paths of PWM signal waves have problems due to phase positions and a time sequence generating circuit or software is completely avoided.
The technical scheme adopted by the invention is as follows:
a brush motor long tail type H bridge driving circuit comprises an H-shaped reversing bridge circuit, a field effect transistor grid driving power circuit, a long tail type PWM width modulation circuit and a high-voltage constant-current voltage-stabilizing power supply circuit; the field-effect tube grid driving power supply circuit provides a driving power supply for the H-shaped reversing bridge circuit, the long tail type PWM width-adjusting circuit is connected with the H-shaped reversing bridge circuit in series, and the high-voltage constant-current voltage-stabilizing power supply circuit supplies power for the long tail type PWM width-adjusting circuit.
As a further preferred aspect of the present invention, the field effect transistor gate driving power supply circuit includes a motor reverse rotation control isolated driving power supply circuit and a motor forward rotation control isolated driving power supply circuit; the motor reverse rotation control isolated driving power circuit and the motor forward rotation control isolated driving power circuit jointly provide driving power for the H-shaped reversing bridge circuit;
the motor reverse rotation control isolation type driving power supply circuit comprises a power supply conversion circuit consisting of an isolation type switch power supply integrated circuit U1, a resistor R3, a resistor R4, a diode D4, a voltage stabilizing diode Z1 and a switch transformer T1, wherein the power supply conversion circuit converts a power supply at a power supply end into two independent power supplies, and after one independent power supply is rectified and filtered by a diode D1 and a capacitor C1, a grid discharge circuit consisting of a PNP triode Q1, a diode D2 and a resistor R1 outputs to a VG1+ end and a VG 1-end; the other path of independent power supply is rectified and filtered by a diode D3 and a capacitor C2, and then a grid discharge circuit consisting of a PNP triode Q2, a diode D5 and a resistor R2 outputs to a VG3+ end and a VG 3-end;
the motor forward rotation control isolation type driving power supply circuit comprises a power supply conversion circuit consisting of an isolation type switch power supply integrated circuit U2, a resistor R7, a resistor R8, a diode D8, a voltage stabilizing diode Z2 and a switch transformer T2, wherein the power supply conversion circuit converts a power supply at a power supply end into two independent power supplies, and a grid discharge circuit consisting of a PNP triode Q3, a diode D6 and a resistor R5 outputs to a VG2+ end and a VG 2-end after one independent power supply is rectified and filtered by a diode D7 and a capacitor C3; and the other path of independent power supply is rectified and filtered by a diode D10 and a capacitor C4, and then the grid discharge circuit consisting of a PNP triode Q4, a diode D9 and a resistor R6 outputs to a VG4+ end and a VG 4-end.
As a further preferred aspect of the present invention, the H-shaped commutation bridge circuit includes a field effect transistor Q5, a field effect transistor Q6, a field effect transistor Q7, a field effect transistor Q8, a gate resistor R9, a gate resistor R10, a gate resistor R12, a gate resistor R13, a gate resistor R14, a gate resistor R15, a gate resistor R16, and a gate resistor R17;
one end of the grid resistor R9 is connected with the grid of the field effect transistor Q6, and the other end is connected with the output end VG1+ of the grid driving power supply circuit of the field effect transistor; one end of the grid resistor R13 is connected with the grid of a field effect transistor Q6, and the other end is connected with the source of the field effect transistor Q6 and the output end VG 1-of the field effect transistor grid driving power circuit; the drain electrode of the field effect tube Q6 is connected with the anode of a power supply of the motor; the source electrode of the field effect transistor Q6 is connected with the drain electrode of the field effect transistor Q7 and is simultaneously connected with one end of the power supply end of the motor; one end of the grid resistor R14 is connected with the grid of the field effect transistor Q7, the other end is connected with the output end VG2+ of the grid drive power circuit of the field effect transistor, one end of the grid resistor R16 is connected with the grid of the field effect transistor Q7, and the other end is connected with the source of the field effect transistor Q7 and the output end VG 2-of the grid drive power circuit of the field effect transistor;
one end of the grid resistor R10 is connected with the grid of the field effect transistor Q5, and the other end is connected with the output end VG4+ of the grid driving power supply circuit of the field effect transistor; one end of the grid resistor R12 is connected with the grid of a field effect transistor Q5, and the other end is connected with the source of the field effect transistor Q5 and the output end VG 4-of the field effect transistor grid driving power circuit; the drain electrode of the field effect tube Q5 is connected with the anode of a power supply of the motor; the source electrode of the field effect transistor Q5 is connected with the drain electrode of the field effect transistor Q8 and is simultaneously connected with the other end of the power supply end of the motor; one end of the grid resistor R15 is connected with the grid of the field effect transistor Q8, the other end is connected with the output end VG3+ of the grid drive power circuit of the field effect transistor, one end of the grid resistor R17 is connected with the grid of the field effect transistor Q8, and the other end is connected with the source of the field effect transistor Q8 and the output end VG 3-of the grid drive power circuit of the field effect transistor;
and the source electrode of the field effect transistor Q7 is connected with the source electrode of the field effect transistor Q8 and then connected with a long tail type PWM width modulation circuit.
As a further preferred embodiment of the present invention, the long tail PWM width modulation circuit includes an overcurrent protection circuit.
As a further preferred embodiment of the present invention, the long tail PWM width modulation circuit includes a driving chip U5, a resistor R18, a resistor R19, a resistor R20, a resistor R21, a resistor R22, a resistor R23, a resistor R24, a field effect transistor Q9, a capacitor C6, a capacitor C7, a capacitor C8, a diode D12, and a zener diode Z4;
one end of the resistor R21 is connected with the pin 3 of the driving chip U5, the other end of the resistor R24 is connected with the pin 5 ground of the driving chip U5, one end of the resistor R24 is connected with the pin 1 of the driving chip U5, and the other end of the resistor R3578 is connected with the pin 5 ground of the driving chip U5; the capacitor C7 is connected in parallel with the resistor R24, one end of the resistor R18 is connected with pin 1 of the driving chip U5, the other end is connected with pin 8 of the power supply end of the driving chip U5, and pin 8 of the power supply end of the driving chip U5 is connected with a high-voltage constant-current voltage-stabilizing power supply circuit; the capacitor C6 is connected in parallel between the pin 8 and the pin 5 of the driving chip U5; the 6 pin and the 7 pin of the driving chip U5 are connected and then connected with the cathode of the diode D12, and the anode of the diode D12 is connected with the grid of the field effect transistor Q9; the resistor R19 is connected with the diode D12 in parallel, the anode of the voltage-stabilizing diode Z4 is connected with the source electrode of the field-effect tube Q9, the cathode of the voltage-stabilizing diode Z4 is connected with the grid electrode of the field-effect tube Q9, the resistor R20 is connected with the voltage-stabilizing diode Z4 in parallel, one end of the resistor R23 is connected with the source electrode of the field-effect tube Q9, and the other end of the resistor R23 is connected with the 5-pin ground of; one end of the resistor R22 is connected with the source electrode of the field effect transistor Q9, and the other end is connected with the 2 feet of the driving chip U5; one end of the capacitor C8 is connected with the 2 pin of the driving chip U5, and the other end is connected with the 5 pin ground of the driving chip U5; the source electrode of the field effect transistor Q7 is connected with the source electrode of the field effect transistor Q8 and then connected with the drain electrode of the field effect transistor Q9.
As a further preferable aspect of the present invention, the high-voltage constant-current voltage-stabilizing power supply circuit includes a diode D11, a constant-current tube U3, a resistor R11, a capacitor C5, and a zener diode Z3;
the anode of the diode D11 is connected with the anode of a power supply of the motor, and the cathode of the diode D11 is connected with the pin 1 of the constant current tube U3; a pin 2 of the constant current tube U3 is connected with the cathode of the voltage stabilizing diode Z3, one end of the resistor R11 is connected with a pin 3 of the constant current tube U3, and the other end is connected with the cathode of the voltage stabilizing diode Z3; the capacitor C5 is connected with the Zener diode Z3 in parallel; the cathode of the voltage-stabilizing diode Z3 is connected with the power supply end pin 8 of the driving chip U5, and the anode of the voltage-stabilizing diode Z3 is grounded.
The invention has the beneficial effects that: only one universal driving chip is used, which is far less than the problem that a common H bridge needs two or four universal or special driving integrated circuits, thereby simplifying the circuit design and essentially improving the overall reliability of the circuit; meanwhile, as the number of chips is reduced, a simple high-voltage constant-current circuit can be adopted, and the power is directly taken from a power supply of the motor, so that the driving and the isolation of the chips are simple, four field effect transistors in the H-shaped reversing bridge circuit are only responsible for the reversing work of the motor, the field effect transistors can be fully conducted by adopting fixed grid driving voltage, the field effect transistors work in a complete conduction state by the fixed grid driving voltage, the switching loss is not generated, and the heating of the field effect transistors is greatly reduced; meanwhile, the possibility of simultaneous conduction of the upper tube and the lower tube during switching is avoided, and the phenomenon of tube explosion is avoided; the invention adopts a field effect tube and a common general single-stage low-side field effect tube driving integrated circuit to form a typical PWM width adjusting circuit, only one path of PWM control signal is needed, thereby saving the resource of a control singlechip, simplifying the control time sequence and logic, avoiding the problems of simultaneous conduction of an upper tube and a lower tube and setting dead time for controlling the PWM signal, leading the reliability of the system to reach the theoretical maximum value in the design of controlling the rotating speed of a motor by PWM, leading the duty ratio of the PWM control signal to be from 0 to 100 percent, and ensuring that the motor can run at full speed within the rated power supply voltage range of a vehicle; the speed regulation with 100% duty ratio is realized, only one PWM signal is needed for driving and speed regulation, and the condition that the upper tube and the lower tube of the H bridge are simultaneously conducted to cause 'tube explosion' caused by the problem of a phase position and a time sequence generating circuit or software in a plurality of paths of PWM signal waves is completely avoided.
Drawings
FIG. 1 is a circuit diagram of the present invention.
Detailed Description
The present invention will be described in detail with reference to the accompanying drawings and examples.
As shown in fig. 1: the embodiment is a brush motor long tail type H bridge driving circuit, which comprises an H-shaped reversing bridge circuit, a field effect transistor grid driving power circuit, a long tail type PWM width modulation circuit and a high-voltage constant-current voltage-stabilizing power supply circuit; the field effect transistor grid driving power supply circuit provides a driving power supply for the H-shaped reversing bridge circuit, the long tail type PWM width modulation circuit is connected with the H-shaped reversing bridge circuit in series, and the high-voltage constant-current voltage-stabilizing power supply circuit supplies power for the long tail type PWM width modulation circuit.
In this embodiment, the field effect transistor gate drive power supply circuit includes a motor reverse rotation control isolated drive power supply circuit and a motor forward rotation control isolated drive power supply circuit; the motor reverse rotation control isolated driving power circuit and the motor forward rotation control isolated driving power circuit jointly provide driving power for the H-shaped reversing bridge circuit;
the motor reverse rotation control isolation type driving power supply circuit comprises a power supply conversion circuit consisting of an isolation type switch power supply integrated circuit U1, a resistor R3, a resistor R4, a diode D4, a voltage stabilizing diode Z1 and a switch transformer T1, wherein the power supply conversion circuit converts a power supply at a power supply end into two independent power supplies, one independent power supply is rectified and filtered by a diode D1 and a capacitor C1, and a grid discharge circuit consisting of a PNP triode Q1, a diode D2 and a resistor R1 outputs to a VG1+ end and a VG 1-end; the other path of independent power supply is rectified and filtered by a diode D3 and a capacitor C2, and then a grid discharge circuit consisting of a PNP triode Q2, a diode D5 and a resistor R2 outputs to a VG3+ end and a VG 3-end; the circuit is used for driving a corresponding field effect transistor in an H-shaped commutation bridge circuit, and when a pin 1 of an isolated switching power supply integrated circuit U1 is at a high level, the power supply starts to output; when pin 1 of the isolated switching power supply integrated circuit U1 is low, the power supply stops outputting.
The motor forward rotation control isolation type driving power supply circuit comprises a power supply conversion circuit consisting of an isolation type switch power supply integrated circuit U2, a resistor R7, a resistor R8, a diode D8, a voltage stabilizing diode Z2 and a switch transformer T2, wherein the power supply conversion circuit converts a power supply at a power supply end into two independent power supplies, and a grid discharge circuit consisting of a PNP triode Q3, a diode D6 and a resistor R5 outputs to a VG2+ end and a VG 2-end after one independent power supply is rectified and filtered by a diode D7 and a capacitor C3; the other path of independent power supply is rectified and filtered by a diode D10 and a capacitor C4, and then a grid discharge circuit consisting of a PNP triode Q4, a diode D9 and a resistor R6 outputs to a VG4+ end and a VG 4-end; the circuit is used for driving a corresponding field effect transistor in an H-shaped commutation bridge circuit, and when a pin 1 of an isolated switching power supply integrated circuit U2 is at a high level, the power supply starts to output; when pin 1 of the isolated switching power supply integrated circuit U2 is low, the power supply stops outputting.
In this embodiment, the H-shaped commutation bridge circuit includes a field effect transistor Q5, a field effect transistor Q6, a field effect transistor Q7, a field effect transistor Q8, a gate resistor R9, a gate resistor R10, a gate resistor R12, a gate resistor R13, a gate resistor R14, a gate resistor R15, a gate resistor R16, and a gate resistor R17;
one end of the grid resistor R9 is connected with the grid of the field effect transistor Q6, and the other end is connected with the output end VG1+ of the grid driving power supply circuit of the field effect transistor; one end of the grid resistor R13 is connected with the grid of the field effect transistor Q6, and the other end is connected with the source of the field effect transistor Q6 and the output end VG 1-of the field effect transistor grid driving power circuit; the drain electrode of the field effect tube Q6 is connected with the anode of a power supply of the motor, and the power supply of the motor is 110V in the embodiment; the source electrode of the field effect transistor Q6 is connected with the drain electrode of the field effect transistor Q7 and is simultaneously connected with one end of the power supply end of the motor; one end of the grid resistor R14 is connected with the grid of the field effect transistor Q7, the other end is connected with the output end VG2+ of the grid drive power circuit of the field effect transistor, one end of the grid resistor R16 is connected with the grid of the field effect transistor Q7, and the other end is connected with the source of the field effect transistor Q7 and the output end VG 2-of the grid drive power circuit of the field effect transistor;
one end of the grid resistor R10 is connected with the grid of the field effect transistor Q5, and the other end is connected with the output end VG4+ of the grid driving power supply circuit of the field effect transistor; one end of the grid resistor R12 is connected with the grid of the field effect transistor Q5, and the other end is connected with the source of the field effect transistor Q5 and the output end VG 4-of the field effect transistor grid driving power circuit; the drain electrode of the field effect tube Q5 is connected with the anode of a power supply of the motor, and the power supply of the motor is 110V in the embodiment; the source electrode of the field effect transistor Q5 is connected with the drain electrode of the field effect transistor Q8 and is simultaneously connected with the other end of the power supply end of the motor; one end of the grid resistor R15 is connected with the grid of the field effect transistor Q8, the other end is connected with the output end VG3+ of the grid drive power circuit of the field effect transistor, one end of the grid resistor R17 is connected with the grid of the field effect transistor Q8, and the other end is connected with the source of the field effect transistor Q8 and the output end VG 3-of the grid drive power circuit of the field effect transistor;
and the source electrode of the field effect transistor Q7 is connected with the source electrode of the field effect transistor Q8 and then connected with a long tail type PWM width modulation circuit.
In this embodiment, the long tail PWM width modulation circuit includes an overcurrent protection circuit; the long-tail PWM width modulation circuit comprises a driving chip U5, a resistor R18, a resistor R19, a resistor R20, a resistor R21, a resistor R22, a resistor R23, a resistor R24, a field-effect tube Q9, a capacitor C6, a capacitor C7, a capacitor C8, a diode D12 and a voltage stabilizing diode Z4;
one end of the resistor R21 is connected with the pin 3 of the driving chip U5, the other end is connected with the pin 5 ground of the driving chip U5, one end of the resistor R24 is connected with the pin 1 of the driving chip U5, and the other end is connected with the pin 5 ground of the driving chip U5; the capacitor C7 is connected in parallel with the resistor R24, one end of the resistor R18 is connected with pin 1 of the driving chip U5, the other end is connected with pin 8 of the power supply end of the driving chip U5, and pin 8 of the power supply end of the driving chip U5 is connected with a high-voltage constant-current voltage-stabilizing power supply circuit; the capacitor C6 is connected in parallel between the pin 8 and the pin 5 of the driving chip U5; the 6 pin and the 7 pin of the driving chip U5 are connected and then connected with the cathode of the diode D12, and the anode of the diode D12 is connected with the grid of the field effect transistor Q9; the resistor R19 is connected with the diode D12 in parallel, the anode of the voltage-stabilizing diode Z4 is connected with the source electrode of the field-effect tube Q9, the cathode of the voltage-stabilizing diode Z4 is connected with the grid electrode of the field-effect tube Q9, the resistor R20 is connected with the voltage-stabilizing diode Z4 in parallel, one end of the resistor R23 is connected with the source electrode of the field-effect tube Q9, and the other end of the resistor R23 is connected with the 5-pin ground of; one end of the resistor R22 is connected with the source electrode of the field effect transistor Q9, and the other end is connected with the 2 feet of the driving chip U5; one end of the capacitor C8 is connected with the 2 pin of the driving chip U5, and the other end is connected with the 5 pin ground of the driving chip U5; the source electrode of the field effect transistor Q7 is connected with the source electrode of the field effect transistor Q8 and then connected with the drain electrode of the field effect transistor Q9.
In this embodiment, the high-voltage constant-current voltage-stabilizing power supply circuit includes a diode D11, a constant-current tube U3, a resistor R11, a capacitor C5, and a zener diode Z3;
the anode of the diode D11 is connected with the anode of the power supply of the motor, and the cathode is connected with the pin 1 of the constant current tube U3; a pin 2 of the constant current tube U3 is connected with the cathode of the voltage stabilizing diode Z3, one end of the resistor R11 is connected with a pin 3 of the constant current tube U3, and the other end is connected with the cathode of the voltage stabilizing diode Z3; the capacitor C5 is connected with the Zener diode Z3 in parallel; the cathode of the voltage-stabilizing diode Z3 is connected with the power supply end pin 8 of the driving chip U5, and the anode of the voltage-stabilizing diode Z3 is grounded.
In this embodiment, the isolated switching power supply integrated circuits U1 and U2 adopt an isolated program-controlled enabled isolated switching power supply integrated circuit LT8300, the constant current tube U3 adopts SM2082GA, and the driver chip U5 adopts an EG3002 chip with conventional overcurrent protection.
The circuit principle of the embodiment is as follows:
when the 1 pin FWD of the isolated switch power supply integrated circuit U1 is at a high level "1", VG1+ and VG1-, VG3+ and VG 3-respectively output DC12V voltage, the voltage between VG1+ and VG 1-is applied between the gate and the source of the FET Q6 through a resistor R9, the FET Q6 is turned on, the voltage between VG3+ and VG 3-is applied between the gate and the source of the FET Q8 through a resistor R15, and the FET Q8 is turned on; when the duty ratio of the 3-pin PWM control signal of the driving chip U5 is more than or equal to 1%, the field effect transistor Q9 is conducted, and the motor rotates reversely.
When the 1 pin REV of the isolated switching power supply integrated circuit U2 is at a high level "1", VG2+ and VG2-, VG4+ and VG 4-respectively output a DC12V voltage, a voltage between VG2+ and VG 2-is applied between the gate and the source of the fet Q7 through the resistor R14, the fet Q7 is turned on, a voltage between VG4+ and VG 4-is applied between the gate and the source of the fet Q5 through the resistor R10, and the fet Q5 is turned on; when the duty ratio of the 3-pin PWM control signal of the driving chip U5 is more than or equal to 1%, the field effect transistor Q9 is conducted, and the motor rotates forwards.
When the duty ratio of the 3-pin PWM control signal of the driving chip U5 is equal to 0, namely 3-pin of the driving chip U5 is low level 0, the field effect transistor Q9 is cut off; at this time, when the pin FWD 1 of the isolated switching power supply integrated circuit U1 is at the high level "1" and the pin REV 1 of the isolated switching power supply integrated circuit U2 is also at the high level "1", the motor performs dynamic braking; when the 1 pin FWD of the isolated switching power supply integrated circuit U1 is low "0" and the 1 pin REV of the isolated switching power supply integrated circuit U2 is also low "0", the motor is stalled.
According to the invention, a universal field effect transistor is adopted to drive the chip U5, and because the energy consumption of a control chip is very low, the diode D11 and the constant current tube U3 are used for directly getting electricity from a main power supply of the H-shaped commutation bridge circuit, and the voltage of the obtained DC12V is used for supplying power for the drive chip U5; the design of the power supply circuit of the switching circuit is greatly simplified.
In the embodiment, the field effect tube Q9 is connected with the lower end of the H-shaped commutation bridge circuit; in practical application, the fet Q9 may also be connected to the upper end of the H-shaped commutation bridge circuit, and the principle still falls into the scope of the long tail H-bridge driving circuit of the present invention.
The invention only uses one universal driving chip, which is far less than the problem that the common H bridge needs two or four universal or special driving integrated circuits, thereby simplifying the circuit design and essentially improving the overall reliability of the circuit; meanwhile, as the number of the chips is reduced and the power consumption is low, a simple high-voltage constant-current circuit can be adopted, and the power is directly taken from a power supply of the motor, the driving and the isolation of the chips are simple.
The three driving signals are simple in logic, and the control unit and the driving unit can be electrically isolated through a simple optical coupling isolation circuit; the driving chip U5 is a universal chip with a protection turn-off function, and in the implementation process, a single-path low-side driving chip of any manufacturer and model can be competent without harsh requirements as long as the chip has the turn-off protection function; the circuit can work in a wide voltage range, theoretically is not affected by any parameter of the control circuit, the conventional bootstrap boost H-bridge driving circuit is avoided, special adjustment is not needed, and the circuit can work normally as long as the withstand voltage of five field effect transistors can be borne.
In the embodiment, the long-tail PWM width-adjusting circuit is connected with the H-shaped commutation bridge circuit in series to form the long-tail structure driving circuit, compared with the prior art, four field effect tubes in the H-shaped commutation bridge circuit are only responsible for the commutation work of a motor, the field effect tubes can be fully conducted by adopting fixed grid driving voltage, the field effect tubes can work in a complete conduction state by the fixed grid driving voltage, the switching loss is not generated, and the heating of the field effect tubes is greatly reduced; meanwhile, the possibility of simultaneous conduction of the upper pipe and the lower pipe during switching is avoided, and the phenomenon of pipe explosion is avoided.
The invention adopts a field effect tube and a common general single-stage low-side field effect tube driving integrated circuit to form a typical PWM width adjusting circuit, only one path of PWM control signal is needed, thereby saving the resource of a control singlechip, simplifying the control time sequence and logic, avoiding the problems of simultaneous conduction of an upper tube and a lower tube and setting dead time for controlling the PWM signal, leading the reliability of the system to reach the theoretical maximum value in the design of controlling the rotating speed of a motor by PWM, leading the duty ratio of the PWM control signal to be from 0 to 100 percent, and ensuring that the motor can run at full speed within the rated power supply voltage range of a vehicle.
The invention adopts a universal field effect transistor low-side driving integrated circuit, simplifies an overcurrent protection circuit, and can arbitrarily set a protection value; the problem that the protection current cannot be accurately set because the D-S voltage of the lower tube of the H bridge is measured for protection in the traditional H bridge driving circuit is solved; by the control circuit, during the H bridge commutation, the field effect tube Q9 in the long tail type PWM width modulation circuit is closed, and zero impact is ensured when each field effect tube of an H bridge arm commutates; after the commutation is finished, after the corresponding field effect tube is fully opened, the PWM control signal gradually opens the field effect tube Q9 in the long-tail PWM width modulation circuit, thereby effectively improving the reliability of the circuit and avoiding the defect that the conventional H bridge is easy to be damaged by commutation impact during commutation; the energy-consumption braking system has the function of supporting energy-consumption braking, the energy-consumption braking can be realized only by applying simple logic control signals, and the field-effect tube Q9 is closed during braking, so that any operation for braking cannot cause the damage to the H-shaped reversing bridge circuit and the field-effect tube Q9.
The above description is only a preferred embodiment of the present patent, and it should be noted that, for those skilled in the art, several modifications and decorations can be made without departing from the inventive concept, and these modifications and decorations should also be regarded as the protection scope of the present patent.
Claims (6)
1. The utility model provides a there is brush motor long tail formula H bridge drive circuit which characterized in that: the high-voltage constant-current voltage-stabilizing power supply circuit comprises an H-shaped reversing bridge circuit, a field-effect tube grid driving power supply circuit, a long-tail PWM width modulation circuit and a high-voltage constant-current voltage-stabilizing power supply circuit; the field-effect tube grid driving power supply circuit provides a driving power supply for the H-shaped reversing bridge circuit, the long tail type PWM width-adjusting circuit is connected with the H-shaped reversing bridge circuit in series, and the high-voltage constant-current voltage-stabilizing power supply circuit supplies power for the long tail type PWM width-adjusting circuit.
2. The brush motor long tail H-bridge drive circuit according to claim 1, wherein the fet gate drive power supply circuit comprises a motor reverse rotation control isolated drive power supply circuit and a motor forward rotation control isolated drive power supply circuit; the motor reverse rotation control isolated driving power circuit and the motor forward rotation control isolated driving power circuit jointly provide driving power for the H-shaped reversing bridge circuit;
the motor reverse rotation control isolation type driving power supply circuit comprises a power supply conversion circuit consisting of an isolation type switch power supply integrated circuit U1, a resistor R3, a resistor R4, a diode D4, a voltage stabilizing diode Z1 and a switch transformer T1, wherein the power supply conversion circuit converts a power supply at a power supply end into two independent power supplies, and after one independent power supply is rectified and filtered by a diode D1 and a capacitor C1, a grid discharge circuit consisting of a PNP triode Q1, a diode D2 and a resistor R1 outputs to a VG1+ end and a VG 1-end; the other path of independent power supply is rectified and filtered by a diode D3 and a capacitor C2, and then a grid discharge circuit consisting of a PNP triode Q2, a diode D5 and a resistor R2 outputs to a VG3+ end and a VG 3-end;
the motor forward rotation control isolation type driving power supply circuit comprises a power supply conversion circuit consisting of an isolation type switch power supply integrated circuit U2, a resistor R7, a resistor R8, a diode D8, a voltage stabilizing diode Z2 and a switch transformer T2, wherein the power supply conversion circuit converts a power supply at a power supply end into two independent power supplies, and a grid discharge circuit consisting of a PNP triode Q3, a diode D6 and a resistor R5 outputs to a VG2+ end and a VG 2-end after one independent power supply is rectified and filtered by a diode D7 and a capacitor C3; and the other path of independent power supply is rectified and filtered by a diode D10 and a capacitor C4, and then the grid discharge circuit consisting of a PNP triode Q4, a diode D9 and a resistor R6 outputs to a VG4+ end and a VG 4-end.
3. The brush motor long tail type H-bridge driving circuit according to claim 2, wherein the H-shaped commutation bridge circuit comprises a field effect transistor Q5, a field effect transistor Q6, a field effect transistor Q7, a field effect transistor Q8, a gate resistor R9, a gate resistor R10, a gate resistor R12, a gate resistor R13, a gate resistor R14, a gate resistor R15, a gate resistor R16 and a gate resistor R17;
one end of the grid resistor R9 is connected with the grid of the field effect transistor Q6, and the other end is connected with the output end VG1+ of the grid driving power supply circuit of the field effect transistor; one end of the grid resistor R13 is connected with the grid of a field effect transistor Q6, and the other end is connected with the source of the field effect transistor Q6 and the output end VG 1-of the field effect transistor grid driving power circuit; the drain electrode of the field effect tube Q6 is connected with the anode of a power supply of the motor; the source electrode of the field effect transistor Q6 is connected with the drain electrode of the field effect transistor Q7 and is simultaneously connected with one end of the power supply end of the motor; one end of the grid resistor R14 is connected with the grid of the field effect transistor Q7, the other end is connected with the output end VG2+ of the grid drive power circuit of the field effect transistor, one end of the grid resistor R16 is connected with the grid of the field effect transistor Q7, and the other end is connected with the source of the field effect transistor Q7 and the output end VG 2-of the grid drive power circuit of the field effect transistor;
one end of the grid resistor R10 is connected with the grid of the field effect transistor Q5, and the other end is connected with the output end VG4+ of the grid driving power supply circuit of the field effect transistor; one end of the grid resistor R12 is connected with the grid of a field effect transistor Q5, and the other end is connected with the source of the field effect transistor Q5 and the output end VG 4-of the field effect transistor grid driving power circuit; the drain electrode of the field effect tube Q5 is connected with the anode of a power supply of the motor; the source electrode of the field effect transistor Q5 is connected with the drain electrode of the field effect transistor Q8 and is simultaneously connected with the other end of the power supply end of the motor; one end of the grid resistor R15 is connected with the grid of the field effect transistor Q8, the other end is connected with the output end VG3+ of the grid drive power circuit of the field effect transistor, one end of the grid resistor R17 is connected with the grid of the field effect transistor Q8, and the other end is connected with the source of the field effect transistor Q8 and the output end VG 3-of the grid drive power circuit of the field effect transistor;
and the source electrode of the field effect transistor Q7 is connected with the source electrode of the field effect transistor Q8 and then connected with a long tail type PWM width modulation circuit.
4. The brush motor long tail H-bridge drive circuit according to claim 1 or 3, wherein the long tail PWM width modulation circuit comprises an overcurrent protection circuit.
5. The brush motor long tail type H bridge drive circuit according to claim 4, wherein the long tail type PWM width modulation circuit comprises a drive chip U5, a resistor R18, a resistor R19, a resistor R20, a resistor R21, a resistor R22, a resistor R23, a resistor R24, a field effect transistor Q9, a capacitor C6, a capacitor C7, a capacitor C8, a diode D12 and a zener diode Z4;
one end of the resistor R21 is connected with the pin 3 of the driving chip U5, the other end of the resistor R24 is connected with the pin 5 ground of the driving chip U5, one end of the resistor R24 is connected with the pin 1 of the driving chip U5, and the other end of the resistor R3578 is connected with the pin 5 ground of the driving chip U5; the capacitor C7 is connected in parallel with the resistor R24, one end of the resistor R18 is connected with pin 1 of the driving chip U5, the other end is connected with pin 8 of the power supply end of the driving chip U5, and pin 8 of the power supply end of the driving chip U5 is connected with a high-voltage constant-current voltage-stabilizing power supply circuit; the capacitor C6 is connected in parallel between the pin 8 and the pin 5 of the driving chip U5; the 6 pin and the 7 pin of the driving chip U5 are connected and then connected with the cathode of the diode D12, and the anode of the diode D12 is connected with the grid of the field effect transistor Q9; the resistor R19 is connected with the diode D12 in parallel, the anode of the voltage-stabilizing diode Z4 is connected with the source electrode of the field-effect tube Q9, the cathode of the voltage-stabilizing diode Z4 is connected with the grid electrode of the field-effect tube Q9, the resistor R20 is connected with the voltage-stabilizing diode Z4 in parallel, one end of the resistor R23 is connected with the source electrode of the field-effect tube Q9, and the other end of the resistor R23 is connected with the 5-pin ground of; one end of the resistor R22 is connected with the source electrode of the field effect transistor Q9, and the other end is connected with the 2 feet of the driving chip U5; one end of the capacitor C8 is connected with the 2 pin of the driving chip U5, and the other end is connected with the 5 pin ground of the driving chip U5; the source electrode of the field effect transistor Q7 is connected with the source electrode of the field effect transistor Q8 and then connected with the drain electrode of the field effect transistor Q9.
6. The brush motor long tail type H-bridge driving circuit according to claim 5, wherein the high voltage constant current voltage stabilization power supply circuit comprises a diode D11, a constant current tube U3, a resistor R11, a capacitor C5 and a voltage stabilization diode Z3;
the anode of the diode D11 is connected with the anode of a power supply of the motor, and the cathode of the diode D11 is connected with the pin 1 of the constant current tube U3; a pin 2 of the constant current tube U3 is connected with the cathode of the voltage stabilizing diode Z3, one end of the resistor R11 is connected with a pin 3 of the constant current tube U3, and the other end is connected with the cathode of the voltage stabilizing diode Z3; the capacitor C5 is connected with the Zener diode Z3 in parallel; the cathode of the voltage-stabilizing diode Z3 is connected with the power supply end pin 8 of the driving chip U5, and the anode of the voltage-stabilizing diode Z3 is grounded.
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| CN202010612322.7A CN111817622A (en) | 2020-06-30 | 2020-06-30 | Brush motor long tail type H-bridge driving circuit |
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| CN202010612322.7A CN111817622A (en) | 2020-06-30 | 2020-06-30 | Brush motor long tail type H-bridge driving circuit |
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