CN110957916B - 一种半桥llc变换器的数字同步整流方法 - Google Patents

一种半桥llc变换器的数字同步整流方法 Download PDF

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CN110957916B
CN110957916B CN201910036658.0A CN201910036658A CN110957916B CN 110957916 B CN110957916 B CN 110957916B CN 201910036658 A CN201910036658 A CN 201910036658A CN 110957916 B CN110957916 B CN 110957916B
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王川
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Henan Jiachen Intelligent Control Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33515—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with digital control
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    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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Abstract

本发明提供一种半桥LLC变换器的数字同步整流方法。该方法依据半桥LLC变换器原边主功率管Q1的开关频率fs与谐振频率fr的大小关系将该LLC变换器的ZVS工作区分成两个子区域，其中
Figure DDA0001946138730000011
Lr为谐振电感的电感值、Cr为谐振电容的电容值。然后、根据该半桥LLC变换器的实际工作时的所属的子区域，确定其副边MOS开关管的驱动信号。通过本发明提出方案可以直接确定LLC变换器副边MOS开关管的驱动信号，而无需设置用于检测所述副边MOS开关管两端电压的检测电路。

Description

一种半桥LLC变换器的数字同步整流方法
技术领域
本发明提供一种半桥LLC变换器的数字同步整流方法及装置。具体涉及谐振变换器的驱动控制领域。通过本发明提供的技术方案可以在无需设置用于检测LLC变换器副边MOS开关管两端电压的检测电路的前提下，直接确定所述述副边MOS开关管的驱动信号。
背景技术
现有的半桥LLC变换器的数字同步整流电路如图2所示，MOS管M1、M2设置在半桥LLC变换器副边；FAN6248的VD1、VS1引脚用于MOS管M1漏源两端的电压，VD2、VS2引脚用于检测MOS管M2漏源两端的电压；通过比较检测到的MOS管漏源两端的电压与预设开启电压阈值和关断电压阈值的大小确定MOS管的驱动信号。如图2、3所示、通过检测MOS管M2漏源电压VDrian，比较其与设定开启电压VTH_ON和关断电压VTH_OFF之间的关系来决定MOS管的驱动信号VGATE_SR。当VDrian≤VTH_ON时，MOS管M2的栅极驱动电压VGATE_SR为高电平、MOS管M1的栅极驱动电压为低电平，MOS管M2导通、MOS管M1关闭；VDrian≥VTH_OFF时，MOS管M2的栅极驱动电压VGATE_SR变为低电平、MOS管M1的栅极驱动电压变为高电平，MOS管M2关闭、MOS管M1导通。由图3可知，当MOS管栅极驱动电压VGATE_SR变为低电平到对应MOS管的漏源电流ISD_SR变为零，还具有一定的时差-TDEAD。MOS管两端的电压VDrian通常在mv级别，如此微弱的电压对检测芯片的检测精度具有较高的要求，并且很难保证驱动的精确性
发明内容
针对现有技术中需要增设电压检测电路，以确定半桥LLC变换器的数字同步整流电路副边MOS管的驱动信号这一缺点，本发明提供一种半桥LLC变换器的数字同步整流方法。该方法将该半桥LLC变换器的ZVS工作区分成两个子区域，根据其实际工作时原边主功率开关管的开关频率确定对应的子区域进而确定其副边MOS开关管的驱动信号。
本发明提供一种本发明的目的通过如下技术方案来实现：
一种半桥LLC变换器的数字同步整流方法，该方法具体为：结合半桥LLC变换器原边主功率管Q1的开关频率fs与谐振频率fr的大小关系将该LLC变换器的ZVS工作区分成两个子区域，其中
Figure BDA0001946138710000021
其中Lr为谐振电感的电感值、Cr为谐振电容的电容值；根据半桥LLC变换器的实际工作时原边主功率开关管的频率确定其对应的子区域，进而确定其副边MOS开关管的驱动信号。
进一步地，将所述LLC变换器的ZVS工作区中、开关频率fs大于谐振频率fr的部分划分为子区域1；将所述LLC变换器的ZVS工作区中关频率fs小于或等于谐振频率fr的部分划分为子区域2。当确定所述LLC变换器工作在子区域1时，其副边MOS开关管SR2的驱动信号与主功率开关管Q1的驱动信号一致,副边MOS开关管SR1与MOS开关管SR2的驱动信号为反相关系；当确定所述LLC变换器工作在子区域2时，副边MOS开关管SR2的驱动信号关闭其自身的时间相对于主功率管Q1关闭的时间提前Tsr，
Figure BDA0001946138710000022
附图说明
图1为现有的半桥LLC变换器的电路图；
图2为现有的半桥LLC变换器的数字同步整流电路；
图3为图1所示的半桥LLC变换器的数字同步整流电路的驱动信号时序图；
图4为本发明的技术方案中对半桥LLC变换器的工作区域划分示意图；
图5为半桥LLC变换器的输出以及相关开关管在子区域1的工作波形图；
图6为为半桥LLC变换器的输出以及相关开关管在子区域2工作波形图。
具体实施方式
以下将通过特定的具体实例说明本发明的实施方式。以下示例性实施例中所描述的实施方式并不代表与本发明公开的技术方案所有的实施方式。相反、它们仅用于帮助本领域技术人员了解本发明的实质。
参考图4，本发明提供一种半桥LLC变换器的数字同步整流方法，该方法用于对如图1所示的半桥LLC变换器的副边开关管SR1、SR2的驱动信号进行控制。图1中、半桥LLC变换器原边主功率管Q1的开关频率为fs，谐振电感Lr和谐振电容Cr组成的谐振电路的谐振频率为fr，其中、
Figure BDA0001946138710000031
其中Lr为谐振电感的电感值、Cr为谐振电容的电容值。半桥LLC变换器的工作区域分为ZVS(零电压开通)区和ZCS(零电流关断)区。为了能保证***稳定运行，半桥LLC变换器应该工作在ZVS区。如图4所示，根据fs与fr的关系可以将桥LLC变换器的ZVS区分成两个子区域，开关频率fs大于谐振频率fr的部分划分为子区域Region1；将半桥LLC变换器的ZVS工作区中开关频率fs小于或等于谐振频率fr的部分划分为子区域Region2。图4中的区域Region3为半桥LLC变换器的ZCS工作区域。根据半桥LLC变换器实际工作时主功率开关管Q1的驱动信号的频率fr确定其对应所属的子区域。当确定所述LLC变换器工作在子区域Region1时，副边MOS开关管SR2的驱动信号与主功率管Q1的驱动信号一致；当确定所述LLC变换器工作在子区域Region2时，副边MOS开关管SR2的驱动信号关闭其自身的时间相对于主功率管Q1关闭的时间提前Tsr，
Figure BDA0001946138710000032
半桥LLC变换器副边MOS开关管SR1与MOS开关管SR2的驱动信号为反相关系。
设定谐振频率fr＝120kHz，开关频率fs在[80,180]kHz范围内工作，具体的电路参数这里不再赘述。图5为半桥LLC变换器的输出以及相关开关管在子区域Region1的工作波形图。其中、pwm信号为主功率开关管Q1的驱动信号，VO为半桥LLC变换器的输出电压，Ir为流经过谐振电感Lr或者谐振电容Cr的电流，Isr流经LLC副边开关管SR2的电流，Im为流经励磁电感Lm的电流。在子区域Region1工作时，励磁电感Lm两端的电压钳位为输出电压VO，励磁电感Lm并不会与电容Cr进行谐振。当主功率开关管Q1关闭时，变压器Tr原边绕组两端的电压由正值变为负值，此时，副边续流MOS管应该由开关管SR2切换为开关管SR1。因此，副边MOS管SR2的驱动信号设置为与对应的主功率开关管Q1的驱动信号一致。图6为半桥LLC变换器的输出以及相关开关管在子区域Region2的工作波形图。在某一时间，经过谐振电感Lr的电流等于流经励磁电感Lm上的电流，此时励磁电感Lm、谐振电感Lr与谐振电容Cr形成谐振回路。由于无电流流经变压器Tr的原边绕组，副边MOS管SR2断流。因此，副边MOS管SR2的驱动信号要提前对应的主功率管的驱动信号关闭。相对于主功率开关管Q1的驱动信号，副边MOS管驱动信号提前关闭的时间Tsr的计算公式为：
Figure BDA0001946138710000041
本发明提供的数字同步整流方法的适用范围并不限于以上具体的半桥LLC变换器，还包括其他形式的谐振变换器。

Claims (1)

1.一种半桥LLC变换器的数字同步整流方法，该方法用于对半桥LLC变换器的副边开关管SR1、SR2的驱动信号进行控制，所述LLC变换器包括原边主功率管Q1和原边主功率管Q2，所述原边主功率管Q1和原边主功率管Q2串联后与输入电源Vin并联，两个谐振电容Cr串联后与原边主功率管Q1及原边主功率管Q2并联，所述原边主功率管Q1和原边主功率管Q2间的第一连接点连接谐振电感Lr的一端，谐振电感Lr连接励磁电感Lm和变压器Tr的原边线圈的一端，所述励磁电感Lm的另一端以及变压器Tr的原边线圈的另一端共同连接两个谐振电容Cr串联后的第二连接点，变压器副边线圈分别连接开关管SR1、开关管SR2以及电解电容的一端，开关管SR1、开关管SR2以及电解电容的另一端接地，负载Rload连接在电解电容的两端；
该方法具体为：根据半桥LLC变换器原边主功率管Q1的开关频率fs与谐振频率fr的大小关系将该LLC变换器的ZVS工作区分成两个子区域，其中
Figure FDA0003522437850000011
其中Lr为谐振电感的电感值、Cr为谐振电容的电容值；依据该半桥LLC变换器的实际工作时原边主功率开关管Q1的开关频率fr确定对应的子区域，根据所述对应的子区域确定其副边MOS开关管的驱动信号；
其中所述根据半桥LLC变换器原边主功率管Q1的开关频率fs与谐振频率fr的大小关系将该LLC变换器的ZVS工作区分成两个子区域，具体为：将所述LLC变换器的ZVS工作区中，开关频率fs大于谐振频率fr的部分划分为子区域1；将所述LLC变换器的ZVS工作区中关频率fs小于或等于谐振频率fr的部分划分为子区域2；
其中根据所述对应的子区域确定其副边MOS开关管的驱动信号，具体为：当确定所述LLC变换器工作在子区域1时，励磁电感Lm两端的电压钳位为输出电压VO，励磁电感Lm不会与电容Cr进行谐振，当主功率开关管Q1关闭时，变压器Tr原边绕组两端的电压由正值变为负值，副边续流MOS管应该由开关管SR2切换为开关管SR1，副边MOS开关管SR2的驱动信号与主功率管Q1的驱动信号一致,另一个副边MOS开关管SR1的驱动信号与MOS开关管SR2的驱动信号为反相关系；当确定所述LLC变换器工作在子区域2时，副边MOS开关管SR2的驱动信号关闭其自身的时间相对于主功率管Q1关闭的时间提前Tsr，
Figure FDA0003522437850000012
谐振频率fr＝120kHz，开关频率fs在[80,180]kHz范围内工作。
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