CN110138246B - Impedance remodeling method based on three-level Dual-Buck circuit - Google Patents
Impedance remodeling method based on three-level Dual-Buck circuit Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
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Abstract
The invention discloses an impedance remodeling topology based on a three-level Dual-Buck circuit, which comprises a modular power electronic transformer, a Dual-Buck circuit and a load, wherein the output end of the modular power electronic transformer is connected with the load, and the Dual-Buck circuit is connected between the modular power electronic transformer and the load. The impedance remodeling is realized by controlling the inductive current in the Dual-Buck circuit to change the parallel damping controller, the system is ensured to change the output impedance value of the source converter according to the output power, the crossing with the load input impedance is avoided, the stability margin of the cascade system is further improved, and the problems of large power consumption and internal structure change caused by adding a passive device in the prior art are solved.
Description
Technical Field
The invention belongs to the technical field of impedance remodeling, and particularly relates to an impedance remodeling method based on a three-level Dual-Buck circuit.
Background
In a multi-converter power electronic system, the stability problem of a cascade system is always a serious one, Middlebrook proposes to judge the stability of the system through an impedance ratio in the early period, under a typical cascade system structure, the ratio of output impedance of a source converter to input impedance of a load converter is equivalent to a gain loop of the system, and indicates that if the source converter and the load converter are stable respectively, and Z is0Less than Z over the entire frequency rangeinThen the stability of the cascade system will be guaranteed, referred to as the Middlebrook criterion. In order to meet the requirement of impedance comparison, how to change the impedance of the source converter and the load converter becomes a hot issue of concern. Conventional approaches often employ passive devices such as: the system load dynamic characteristics can be modified by adding the resistive load to improve the stability of the system, but the power consumption of the system can be increased, the internal structure of a source or load converter can be changed, the problems of long design period, high cost and the like exist, and the system is not favorableAnd (5) modularization. In order to solve the problem that the output/input resistance is changed without changing the internal structure of a system submodule, the invention provides a method for controlling inductive current on the basis of a three-level Dual-Buck type circuit, and the inductive current carries out impedance remodeling along with the change of load power.
Disclosure of Invention
The invention aims to provide an impedance remodeling topology based on a three-level Dual-Buck type circuit, which ensures that a system changes the output impedance value of a source converter according to output power, avoids the intersection with load input impedance, further improves the stability margin of a cascade system, and solves the problems of large power consumption and internal structure change caused by adding a passive device in the prior art.
The invention also aims to provide an impedance reshaping method based on the three-level Dual-Buck type circuit.
The technical scheme includes that the impedance remodeling topology based on the three-level Dual-Buck circuit comprises a modular power electronic transformer, a Dual-Buck circuit and a load, wherein the output end of the modular power electronic transformer is connected with the load, and the Dual-Buck circuit is connected between the modular power electronic transformer and the load.
Yet another feature of the present invention is that,
the Dual-Buck circuit includes a fully-controlled power switch S1Full-control power switch tube S1Are respectively connected with a diode D1Cathode lead-out port and filter capacitor Ca1One terminal, diode D1Anode and full-controlled power switch tube S2Is connected to the drain of diode D1Anode and full-controlled power switch tube S2Between the drain electrodes of the two-phase current transformer and the separation inductor L2Connecting, full-control type power switch tube S1Source and diode D2Cathode connected, full-controlled power switch tube S1Source and diode D2Lead-out port and separation inductance L between cathodes1Connecting and disconnecting inductor L1And a separation inductance L2The other end of the first and second electrodes are connected to form an output port I, the output port I and a filter capacitor CfOne end of the power switch is connected with a fully-controlled power switchClosing pipe S2Are respectively connected with a diode D2Anode and diode D3Cathode of (2), diode D2Anode connected filter capacitor Ca1The other end and a full-control type power switch tube S3Leakage stage, full control type power switch tube S3Are respectively connected with a filter capacitor Ca2And a diode D3Cathode of (2), full-control type power switch tube S3Source electrode of (2) is connected with a diode D4Cathode of (2), full-control type power switch tube S3Source and diode D4The lead-out port between the cathodes is connected with a separation inductor a and a diode D4The anodes of the two capacitors are respectively connected with a filter capacitor Ca2Another end of the power switch tube S and a full-control type power switch tube S4Source electrode of, full-control type power switch tube S4Drain connected diode D3Anode of (2), full-control type power switch tube S4And diode D3The other end of the separation inductor a is connected with the other end of the separation inductor b to form an output port II, and the output port II is connected with a filter capacitor CfAnother terminal of (1), a filter capacitor CfAre connected between the modular power electronic transformer and the load.
The other technical scheme of the invention is an impedance remodeling method based on a three-level Dual-Buck circuit, which adopts the impedance remodeling topology based on the three-level Dual-Buck circuit and realizes impedance remodeling by controlling inductive current in the Dual-Buck circuit to change a parallel damping controller, and the specific process comprises the following steps:
and 3, connecting the virtual impedance of the parallel damping controller obtained in the step 2 with the output impedance of the modular power electronic transformer or the input impedance of the load side in parallel to realize the remodeling of the output/input impedance.
Preferably, the specific process of step 1 is as follows:
in order to obtain an equivalent capacitance element in the parallel damping controller, a high-pass filter is adopted to process the voltage of the direct current bus, and the voltage on the direct current bus is defined as Vbus，VbusExtracting high-frequency fluctuation through a high-pass filter, comparing the high-frequency fluctuation with an expected fluctuation reference value, and obtaining the maximum amplitude i of the fluctuation current reference value through a PI regulatorh_refAs can be seen from equation 1, the virtual capacitance is realized by differentiating the dc bus voltage;
in the formula, wherein Cv，ωLRespectively the cut-off frequency of the equivalent capacitor in the parallel damper and the high-pass filter, s is the frequency domain representation form obtained after time domain differential Laplace transform, HdIs a complex function; cvThe output impedance of the modular power electronic transformer side can be changed, and fluctuation of the direct current bus voltage under large disturbance can be avoided.
Preferably, the specific process of step 2 is as follows:
voltage V at two ends of filter capacitor in Dual-Buck type circuitdaMust be greater than the voltage across the output terminals of the modular power electronic transformer by VbusIs realized by voltage outer loop control, and is VdaAnd a voltage reference value V at two ends of the output filter capacitorda-refComparing, and obtaining an inductive current reference value i after the adjustment of a PI regulatorL_refI is toh_refAnd iL_refThe sum of the two is used as a current reference value to be compared with the actual current, and a modulation wave d is obtained through a PI regulatoraControlling the on-off of a corresponding switch tube in the Dual-Buck type circuit to realize the control of the inductive current;
from equation 1, it can be known that the effect of the equivalent capacitor is limited by the cut-off frequency, and the relationship between the output inductor current compensation current i and the equivalent capacitor of the parallel damping controller is shown in equation (2):
meanwhile, the cut-off frequency of the current control loop influences the dynamic characteristic of the parallel active damper, and if the closed loop dynamic is similar to a first-order inertia link
Then the resultant current iLsAs shown in the formula (3),
in the formula of omegacThe cut-off frequency of the current control loop;
the formula (2) is substituted into the formula (3),
c of formula (4) in equivalent seriesv，Lv，rvThe form is shown as a formula (5),
therefore, the high-pass filter and the virtual resistance r caused by the cut-off frequency of the current control loopvAnd a virtual inductance LvAs shown in formula (6):
preferably, voltage-sharing control is added in the step 2, so that the phenomenon that the output voltage and current waveform is distorted and the circuit performance is deteriorated due to the fact that the potential of the midpoint of the voltage-dividing capacitor is drifted is avoided.
The impedance remodeling method based on the three-level Dual-Buck circuit has the advantages that the system is ensured to change the output impedance value of the source converter according to the output power, the crossing with the input impedance of the load is avoided, the stability margin of the cascade system is further improved, and the problems of large power consumption and internal structure change caused by adding a passive device in the prior art are solved. Compared with the traditional passive device which is adopted to change the source output impedance, the problems of changing the internal structure and the dynamic characteristic of the load are solved; the extra power consumption caused by adopting a passive device is reduced; the modular design of the system is facilitated; the stability and the dynamic characteristic of the cascade system are better ensured.
Drawings
FIG. 1 is a schematic diagram of a topological structure adopted by an impedance reshaping method based on a three-level Dual-Buck type circuit of the invention;
FIG. 2 is a schematic of a modular power electronic transformer topology of the present invention;
FIG. 3 is a control block diagram of the parallel damping controller of the present invention;
fig. 4 is an equivalent simplified circuit diagram of the parallel damping controller of the present invention.
Detailed Description
The present invention will be described in detail below with reference to the accompanying drawings and specific embodiments.
The impedance remodeling topology based on the three-level Dual-Buck circuit comprises a modular power electronic transformer, a Dual-Buck circuit and a load, wherein the output end of the modular power electronic transformer is connected with the load, and the Dual-Buck circuit is connected between the modular power electronic transformer and the load.
As shown in fig. 2, the modular power electronic transformer topology structure includes a cascaded H-bridge Converter (CHB) and a dual active bridge circuit (DAB), in the CHB of the full-bridge module structure, a DAB circuit is connected to a dc energy storage capacitor of each full-bridge module, and DAB output sides of each power module of the upper and lower bridge arms are respectively connected in parallel to generate a bipolar dc bus;
the Dual-Buck circuit adopts 4 full-control power switch tubes MOSFETs, can improve switching speed and system efficiency, and the full-control power switch tube S1Are respectively connected with a diode D1Cathode lead-out port and filter capacitor Ca1One terminal, diode D1Anode and full-controlled power switch tube S2Is connected to the drain of diode D1Anode and full-controlled power switch tube S2Between the drain electrodes of the two-phase current transformer and the separation inductor L2Connecting, full-control type power switch tube S1Source and diode D2Cathode connected, full-controlled power switch tube S1Source and diode D2Lead-out port and separation inductance L between cathodes1Connecting and disconnecting inductor L1And a separation inductance L2The other end of the first and second electrodes are connected to form an output port I and a filter capacitor CfOne end of the power switch tube is connected with a fully-controlled power switch tube S2Are respectively connected with a diode D2Anode and diode D3Cathode of (2), diode D2Anode connected filter capacitor Ca1The other end and a full-control type power switch tube S3Leakage stage, full control type power switch tube S3Are respectively connected with a filter capacitor Ca2And a diode D3Cathode of (2), full-control type power switch tube S3Source electrode of (2) is connected with a diode D4Cathode of (2), full-control type power switch tube S3Source and diode D4The lead-out port between the cathodes is connected with a separation inductor a and a diode D4The anodes of the two capacitors are respectively connected with a filter capacitor Ca2Another end of the power switch tube S and a full-control type power switch tube S4Source electrode of, full-control type power switch tube S4Drain connected diode D3Anode of (2), full-control type power switch tube S4And diode D3The other end of the separation inductor a is connected with the other end of the separation inductor b to form an output port II, and the output port II is connected with a filter capacitor CfAnother terminal of (1), a filter capacitor CfAre connected between the modular power electronic transformer and the load.
The impedance remodeling method based on the three-level Dual-Buck circuit disclosed by the invention is characterized in that as shown in figure 3, impedance remodeling is realized by controlling inductive current in the Dual-Buck circuit to change a parallel damping controller, and the specific process comprises the following steps:
the specific process of step 1 is as follows:
in order to obtain an equivalent capacitance element in the parallel damping controller, a high-pass filter is adopted to process the voltage of the direct current bus, and the voltage on the direct current bus is defined as Vbus，VbusExtracting high-frequency fluctuation through a high-pass filter, comparing the high-frequency fluctuation with an expected reference value, and obtaining the maximum amplitude i of a fluctuation current reference value through a PI regulatorhrefAs can be seen from equation 1, the dummy capacitor is realized by differentiating the dc bus voltage;
in the formula, wherein Cv，ωLRespectively the cut-off frequency of an equivalent capacitor in the parallel damper and the cut-off frequency of a high-pass filter, s is a frequency domain representation form obtained after time domain differential Laplace transform, and Hd is a complex variable function; cvThe output impedance of the modular power electronic transformer side can be changed, and the fluctuation of the direct current bus voltage under large disturbance can be avoided;
the specific process of step 2 is as follows:
voltage V at two ends of filter capacitor in Dual-Buck type circuitdaMust be greater than the voltage across the output terminals of the modular power electronic transformer by VbusIs realized by voltage outer loop control, and is VdaAnd a voltage reference value V at two ends of the output filter capacitorda-refComparing, and obtaining an inductive current reference value i after the adjustment of a PI regulatorL_refI is toh_refAnd iL_refThe sum of the two is used as a current reference value, and a modulation wave d is obtained through a PI regulatoraControl of Dual-Buck type of electricityThe on-off of the corresponding four switching tubes in the circuit realizes the control of the inductive current;
from equation 1, it can be known that the effect of the equivalent capacitance is limited by the cut-off frequency, and the relationship between the output inductor current compensation current i and the equivalent capacitance of the parallel damper is shown in equation (2):
meanwhile, the cut-off frequency of the current control loop influences the dynamic characteristic of the parallel damper, and if the closed loop dynamic can approximate to a first-order inertia link
Then the inductor current i is synthesizedLsAs shown in the formula (3),
in the formula of omegacThe cut-off frequency of the current control loop;
the formula (2) is substituted into the formula (3),
equation (4) is equivalent to series C in FIG. 4v，Lv，rvAn element in the form of a sheet of material,
therefore, the virtual resistance and the virtual inductance caused by the cut-off frequency of the HPF (high pass filter) and the current control loop can be expressed as shown in equation (6):
and 2, voltage-sharing control is added in the step 2, so that the phenomenon that the output voltage and current waveform are distorted and the circuit performance is deteriorated due to the potential drift of the midpoint of the voltage-dividing capacitor is avoided.
And 3, connecting the virtual impedance of the parallel damping controller obtained in the step 2 with the output impedance of the modular power electronic transformer or the input impedance of the load side in parallel to realize the remodeling of the output/input impedance.
Claims (2)
1. The impedance remodeling method based on the three-level Dual-Buck circuit is characterized in that impedance remodeling topology based on the three-level Dual-Buck circuit is adopted, and impedance remodeling is realized by controlling inductive current in the Dual-Buck circuit to change a parallel damping controller;
the impedance remodeling topology based on the three-level Dual-Buck circuit comprises a modular power electronic transformer, a Dual-Buck circuit and a load, wherein the output end of the modular power electronic transformer is connected with the load, and the Dual-Buck circuit is connected between the modular power electronic transformer and the load;
the Dual-Buck circuit comprises a fully-controlled power switch tube S1The said full-control type power switch tube S1Are respectively connected with a diode D1Cathode lead-out port and filter capacitor Ca1One end of the diode D1Anode and full-controlled power switch tube S2Of the diode D, the diode D1And the fully-controlled power switch tube S2Between the drain electrodes of the two-phase current transformer and the separation inductor L2Connected, the said full-control type power switch tube S1Source and diode D2Cathode connection, said fully-controlled power switch tube S1And said diode D2Lead-out port and separation inductance L between cathodes1Connection, said separation inductance L1And the separation inductance L2The other end of the first and second electrodes are connected to form an output port I, the output port I and a filter capacitor CfIs connected with one end of the full-control type power switch tube S2Are respectively connected with the diodes D2Anode and diode D3Of the heartPole, the diode D2The anode is connected with the filter capacitor Ca1The other end and a full-control type power switch tube S3The said fully-controlled power switch tube S3Are respectively connected with a filter capacitor Ca2And the diode D3The said full-controlled power switch tube S3Source electrode of (2) is connected with a diode D4The said full-controlled power switch tube S3And said diode D4The lead-out port between the cathodes is connected with a separation inductor a, and the diode D4Are respectively connected with the filter capacitors Ca2Another end of the power switch tube S and a full-control type power switch tube S4Source electrode of, the full-control type power switch tube S4Is connected with the diode D3The said full-control type power switch tube S4And said diode D3The anode is connected with a separation inductor b through a leading-out port, the other end of the separation inductor a is connected with the other end of the separation inductor b to form an output port II, and the output port II is connected with the filter capacitor CfThe other end of said filter capacitor CfAre connected between the modular power electronic transformer and the load;
the specific process comprises the following steps:
step 1, a modularized power electronic transformer is used as a direct current bus, and the voltage ripple on the direct current bus controls the inductive current in a Dual-Buck type circuit, so as to change the equivalent virtual element of a parallel damping controller; the specific process of step 1 is as follows:
in order to obtain an equivalent capacitance element in the parallel damping controller, a high-pass filter is adopted to process the voltage of the direct current bus, and the voltage on the direct current bus is defined as Vbus，VbusExtracting high-frequency fluctuation through a high-pass filter, comparing the high-frequency fluctuation with an expected fluctuation reference value, and obtaining the maximum amplitude i of the fluctuation current reference value through a PI regulatorh_refAs can be seen from equation 1, the dummy capacitor is realized by differentiating the dc bus voltage;
in the formula, wherein Cv，ωLRespectively the cut-off frequency of the equivalent capacitor in the parallel damper and the high-pass filter, s is the frequency domain representation form obtained after time domain differential Laplace transform, HdIs a complex function; cvThe output impedance of the modular power electronic transformer side can be changed, and the fluctuation of the direct current bus voltage under large disturbance can be avoided;
step 2, controlling the voltage at two ends of an output filter capacitor in the Dual-Buck type circuit through the parallel damping controller to further control the inductive current, and obtaining a mathematical model of the parallel damping controller; the specific process of step 2 is as follows:
the voltage V at two ends of the filter capacitor in the Dual-Buck type circuitdaMust be greater than the voltage across the output terminals of the modular power electronic transformer by VbusIs realized by voltage outer loop control, and is VdaAnd a voltage reference value V at two ends of the output filter capacitorda-refComparing, and obtaining an inductive current reference value i after the adjustment of a PI regulatorL_refI is toh_refAnd iL_refThe sum of the two is used as a current reference value to be compared with the actual current, and a modulation wave d is obtained through a PI regulatoraControlling the on-off of the corresponding switch tube in the Dual-Buck type circuit to realize the control of the inductive current;
from equation 1, it can be known that the effect of the equivalent capacitor is limited by the cut-off frequency, and the relationship between the output inductor current compensation current i and the equivalent capacitor of the parallel damping controller is shown in equation (2):
meanwhile, the cut-off frequency of the current control loop influences the dynamic characteristic of the parallel active damper, and if the closed loop dynamic is similar to a first-order inertia link
Then the resultant currentisAs shown in the formula (3),
in the formula of omegacThe cut-off frequency of the current control loop;
the formula (2) is substituted into the formula (3),
c of formula (4) in equivalent seriesv，Lv，rvAn element in the form shown in formula (5),
therefore, the high-pass filter and the virtual resistance r caused by the cut-off frequency of the current control loopvAnd a virtual inductance LvAs shown in formula (6):
and 3, connecting the virtual impedance of the parallel damping controller obtained in the step 2 with the output impedance of the modular power electronic transformer or the input impedance of the load side in parallel to realize the remodeling of the output/input impedance.
2. The impedance reshaping method based on the three-level Dual-Buck circuit as claimed in claim 1, wherein a voltage-sharing control is added in the step 2 to avoid the voltage-sharing control from causing the midpoint potential of the voltage-dividing capacitor to drift, thereby causing the distortion of the output voltage and current waveforms and the deterioration of the circuit performance.
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| CN1901348A (en) * | 2006-07-27 | 2007-01-24 | 武汉大学 | Multiple level changing method and its used multiple level circuit |
| CN103684347A (en) * | 2012-09-11 | 2014-03-26 | 瑞昱半导体股份有限公司 | Adjustable impedance circuit and impedance setting method |
| CN108173288A (en) * | 2018-02-09 | 2018-06-15 | 合肥工业大学 | Inhibit the voltage-type impedance adapter control method of multi-inverter grid-connected system resonance |
| CN109687507A (en) * | 2018-11-27 | 2019-04-26 | 国网山东省电力公司青岛供电公司 | Towards energy internet alternating current-direct current mixing microgrid coordinating and optimizing control method and system |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN1901348A (en) * | 2006-07-27 | 2007-01-24 | 武汉大学 | Multiple level changing method and its used multiple level circuit |
| CN103684347A (en) * | 2012-09-11 | 2014-03-26 | 瑞昱半导体股份有限公司 | Adjustable impedance circuit and impedance setting method |
| CN108173288A (en) * | 2018-02-09 | 2018-06-15 | 合肥工业大学 | Inhibit the voltage-type impedance adapter control method of multi-inverter grid-connected system resonance |
| CN109687507A (en) * | 2018-11-27 | 2019-04-26 | 国网山东省电力公司青岛供电公司 | Towards energy internet alternating current-direct current mixing microgrid coordinating and optimizing control method and system |
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