CN109038854B - Automatic tuning wireless energy transmitting system based on inductance compensation - Google Patents
Automatic tuning wireless energy transmitting system based on inductance compensation Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
- H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
- H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
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Abstract
The invention discloses an automatic tuning wireless energy emission system based on inductance compensation, which belongs to the technical field of electronic technology and is structurally provided with an alternating current-direct current conversion circuit (1), a high-frequency inverter circuit (2), an inductance compensation circuit (3), a switch control circuit (4), a single chip microcomputer (5), an amplitude detection circuit (6) and an analog-digital conversion circuit (7). The invention has the advantages of wide load application range, high transmission efficiency, flexible use, high system stability and reliability and the like.
Description
Technical Field
The invention belongs to the technical field of electronic technology. In particular to an automatic tuning wireless energy transmitting system based on inductance compensation.
Background
After the electric power enters human life, the electric wire is almost ubiquitous as a medium for transmitting the electric energy, and brings great convenience for daily life of people. However, the wired energy transmission mode is limited by space occupation and potential safety hazards brought by contact of electric equipment. The wireless energy transmission system has no direct electrical connection, can realize energy supply without space limitation of wireless equipment, and has the advantages of no plug-in link, no exposed conductor, no electric leakage and no electric shock hazard and the like. Wireless power transmission is, of course, increasingly playing an important role in charging or powering electrical devices such as electric vehicles, mobile phones, tablet computers, biomedicine, and the like.
In the wireless charging technology, the magnetic coupling resonance mode has been widely focused on due to its advantages of high transmission efficiency, high power, convenient structure, and the like. The principle is that the 220V/50Hz commercial power is rectified into direct current stabilized voltage, then the direct current stabilized voltage is inverted into 50kHz high-frequency alternating current by a high-frequency inverter circuit, a transmitting coil (in an inductive state) is matched with a proper capacitor for frequency-selective resonance, electric energy is converted into magnetic energy, then the receiving coil receives the energy in a magnetic coupling resonance mode, and finally the energy received by the coil is converted into constant voltage or constant current by a subsequent rectifying and filtering circuit of the receiving coil to supply power for equipment at a receiving end or charge a storage battery. In order to ensure transmission efficiency and power, the above system requires that the primary loop in which the transmitting coil is located must be resonant and the secondary loop in which the receiving coil is located must be resonant. It is known that when a transmitting coil and a receiving coil are coupled, a secondary loop has an effect on a primary loop, and the effect can be equivalent to connecting a reflecting impedance in series in the primary loop, wherein the reflecting impedance includes a reflecting resistance and a reflecting reactance, and the reflecting reactance (inductive or capacitive) has a serious effect on the resonance degree of the primary loop, so that the parameter effect of the receiving system must be considered when designing the transmitting system.
The existing magnetic coupling resonance wireless transmission system is generally designed for a fixed receiving loop, once the parameters of the receiving loop change, the equivalent reflected impedance of the receiving loop also changes in a transmitting loop, the original resonance state of the transmitting loop is destroyed, and the phenomenon of detuning occurs, so that the important parameters of the transmitting loop, such as current, power, efficiency and the like, rapidly deteriorate. In fact, even in the same type of electric equipment, the receiving circuit has different parameters due to different product models and manufacturers, so that the compatibility of the existing wireless energy transmission system generally has the problem of poor compatibility, and one transmitting system can only provide energy transmission for the same fixed-model product.
In summary, in order to widen the application range of different electric products, improve the compatibility of the system, and ensure the transmission efficiency of the system, the existing wireless energy transmission system needs to be improved.
Disclosure of Invention
The invention aims to solve the technical problem of providing an automatic tuning wireless energy transmitting system based on inductance compensation aiming at the defects in the prior art. The system can automatically adjust the parameters of the transmitting loop according to the difference of the receiving loop so as to achieve the purposes of automatically matching different loads and improving the transmission efficiency.
The purpose of the invention is realized by the following technical scheme:
an automatic tuning wireless energy transmitting system based on inductance compensation is structurally provided with an alternating current-direct current conversion circuit 1, a high-frequency inverter circuit 2 and a single chip microcomputer 5, and is characterized in that the automatic tuning wireless energy transmitting system is structurally provided with an inductance compensation circuit 3, a switch control circuit 4, an amplitude detection circuit 6 and an analog-to-digital conversion circuit 7; the input end of the alternating current-direct current conversion circuit 1 is connected with a mains supply, the output end of the alternating current-direct current conversion circuit 1 is connected with the power supply input end of the high-frequency inverter circuit 2, the sampling output end of the high-frequency inverter circuit 2 is connected with the input end of the amplitude detection circuit 6, the output end of the amplitude detection circuit 6 is connected with the input end of the analog-digital conversion circuit 7, the output end of the analog-digital conversion circuit 7 is connected with the single chip microcomputer 5, the single chip microcomputer 5 is also connected with the control input end of the high-frequency inverter circuit 2 and the input end of the switch control circuit 4 respectively, the output end of the switch control circuit 4 is connected with the input end of the inductance compensation circuit 3 and the enabling control end of the amplitude detection circuit 6 respectively, and;
the high-frequency inverter circuit 2 is structurally characterized in that the anode of a diode D1 is connected with a +12V power supply, the cathode of a diode D1 is connected with one end of a resistor R1, the emitter of a triode Q1 and one end of a capacitor C1, the other end of a resistor R1 is connected with the base of a triode Q1 and the collector of a triode Q2, the base of a triode Q2 is connected with one end of a resistor R2, the other end of the resistor R2 is connected with a +5V direct-current power supply, the emitter of a triode Q2 is connected with one end of a resistor R3, the other end of the resistor R3 serves as a first control input end of the high-frequency inverter circuit 2 and is marked as a port MCU-in1 and is connected with a single chip microcomputer 5, the collector of the triode Q1 is connected with the anode of a diode D2, the base of a triode Q3 and one end of a resistor R4, the other end of a resistor R4 is, The drain electrode of a field effect transistor Q8, one end of an inductor L and the source electrode of a field effect transistor Q4 are connected, the emitter electrode of a triode Q3 is connected with the cathode of a diode D2, the cathode of a voltage stabilizing diode D3 and the grid electrode of a field effect transistor Q4, the drain electrode of a field effect transistor Q4 is connected with the drain electrode of a field effect transistor Q9 and serves as the power supply input end of a high-frequency inverter circuit 2, which is marked as a port Vs-in and is connected with the direct current voltage output end of an alternating current-direct current conversion circuit 1, the grid electrode of the field effect transistor Q8 is connected with one end of a resistor R8 and the collector electrode of a triode Q7, the other end of a resistor R8 is connected with the collector electrode of a triode Q5, the emitter electrode of a triode Q5 is connected with one end of a resistor R5 and a +12V direct current power supply, the other end of the resistor R5 is connected with the base electrode of the triode Q5 and the, an emitter of the triode Q6 is connected with one end of a resistor R7, the other end of the resistor R7 is connected with one end of a resistor R9, and is used as a second control input end of the high-frequency inverter circuit 2 and is recorded as a port MCU-in2 to be connected with the singlechip 5, the other end of the resistor R9 is connected with a base of the triode Q7, an emitter of the triode Q7 is connected with a source of a field-effect tube Q8 and is grounded, the other end of an inductor L is connected with one end of a capacitor Cs1, the other end of the capacitor Cs1 is connected with one end of a capacitor Cs2, the other end of a capacitor Cs2 is used as a compensation input end of the high-frequency inverter circuit 2 and is recorded as a port Ladj-in1 to be connected with a port Ladj; one end of a sampling resistor Rs is used as the other compensation input end of the high-frequency inverter circuit 2, and is also used as a sampling output end of the high-frequency inverter circuit 2, and is marked as a port Rs-out1, the port is connected with a port Ladj-out2 of the inductance compensation circuit 3, and is also connected with a port Rs-in1 of the amplitude detection circuit 6, the other end of the sampling resistor Rs is connected with the drain of the field-effect tube Q13, the source of the field-effect tube Q9, the anode of a voltage-regulator diode D4, the collector of the triode Q10, one end of a resistor R10 and one end of a capacitor C2, and is marked as the other sampling output end of the high-frequency inverter circuit 2, and is connected with a port Rs-in2 of the amplitude detection circuit 6, the gate of the field-effect tube Q9 is connected with the cathode of a voltage-regulator diode D4, the emitter of the triode Q10 and the cathode of a diode D5, the base of, The anode of a diode D5 is connected with the collector of a triode Q11, the emitter of a triode Q11 is connected with the other end of a capacitor C2, one end of a resistor R11 and the cathode of a diode D6, the anode of a diode D6 is connected with a +12V direct-current power supply, the base of a triode Q11 is connected with the other end of a resistor R11 and the collector of a triode Q12, the base of a triode Q12 is connected with one end of a resistor R12, the other end of a resistor R12 is connected with a +5V direct-current power supply, the emitter of a triode Q12 is connected with one end of a resistor R13, the other end of a resistor R13 serves as a third control input end of the high-frequency inverter circuit 2 and is marked as a port MCU-in; the source of a field effect transistor Q13 is connected with the emitter of a triode Q14 and is grounded, the gate of the field effect transistor Q13 is connected with one end of a resistor R14 and the collector of a triode Q14, the base of the triode Q14 is connected with one end of a resistor R15, the other end of the resistor R15 is connected with one end of a resistor R17, the resistor R15 serves as a fourth control input end of the high-frequency inverter circuit 2 and is marked as a port MCU-in4 and is connected with the single chip microcomputer 5, the other end of the resistor R14 is connected with the collector of a triode Q15, the emitter of the triode Q15 is connected with one end of the resistor R16 and a +12V direct-current power supply, the base of the triode Q15 is connected with the other end of the resistor R16 and the collector of the triode Q16, the emitter of the triode Q16 is connected with the other end of the resistor R17, the base of the triode Q16 is;
the structure of the amplitude detection circuit 6 is that one end of a resistor R19 is connected with a movable contact of a relay Ks, is used as an input end of the amplitude detection circuit 6, is recorded as a port Rs-in1, and is connected with a port Rs-out1 of the high-frequency inverter circuit 2; the other end of the resistor R19 is connected with the non-inverting input end of the operational amplifier U1 and one end of the resistor R20, and the other end of the resistor R20 is grounded; the static contact of the relay Ks is connected with one end of a resistor R21, is used as the other input end of the amplitude detection circuit 6, is recorded as a port Rs-in2, and is connected with a port Rs-out2 of the high-frequency inverter circuit 2; one end of the relay coil is grounded, and the other end of the relay coil is used as an enabling control end of the amplitude detection circuit 6, is recorded as a port Rins, and is connected with the output end of a ninth relay drive circuit in the switch control circuit 4; the other end of the resistor R21 is connected with the non-inverting input end of the operational amplifier U2 and one end of the resistor R22, and the other end of the resistor R22 is grounded; the inverting end of the resistor operational amplifier U2 is connected with one end of the resistor R23, one end of the resistor R25 and one end of the resistor R24, the other end of the resistor R23 is grounded, the positive power input end of the operational amplifier U2 is connected with a +5V direct-current power supply, the negative power input end of the operational amplifier U2 is connected with a-5V direct-current power supply, and the output end of the operational amplifier U2 is connected with one end of the resistor R26 and the other end of the resistor R25; the inverting input end of the operational amplifier U1 is connected with the other end of the resistor R24, the other end of the resistor R26 and one end of the resistor R27, the negative power supply input end of the operational amplifier U1 is connected with a-5V direct-current power supply, the positive power supply input end of the operational amplifier U1 is connected with a +5V direct-current power supply, and the output end of the operational amplifier U is connected with the other end of the resistor R27 and the anode of the diode D7; the cathode of the diode D7 is connected to one end of the capacitor C3 and one end of the resistor R28, serves as the output end of the amplitude detection circuit 6, is recorded as a port Amp-out, and is connected to the analog signal input end of the analog-to-digital conversion circuit 7, and the other end of the resistor R28 and the other end of the capacitor C3 are grounded;
the inductance compensation circuit 3 has a structure that one end of each of coils of relays K1, K2, K3, K4, K5, K6, K7 and K8 is grounded, the other end is used as eight input ends of the inductance compensation circuit 3, which are sequentially marked as ports Rin1, Rin2, Rin3, Rin4, Rin5, Rin6, Rin7 and Rin8, and are respectively connected with eight output ends of first to eighth relay driving circuits in the switch control circuit 4, one ends of inductors L1, L2, L3, L4 and L5 are connected with one end of an inductor L6 and a movable contact of a relay K5, the other ends of inductors L2, L2 and L2 are sequentially connected with movable contacts of relays K2, K2 and K2, the other ends of inductors L2, K2, and K2 are connected with a high frequency compensation port, and a high frequency compensation circuit Ladj 2 is marked as an inverter port, the other end of the inductor L6 is connected to one end of an inductor L7, a fixed contact of a relay K5 and a movable contact of a relay K6, the other end of the inductor L7 is connected to one end of an inductor L8, a fixed contact of a relay K6 and a movable contact of a relay K7, the other end of the inductor L8 is connected to one end of an inductor L9, a fixed contact of a relay K7 and a movable contact of a relay K8, and the other end of the inductor L9 is connected to a fixed contact of a relay K8, and serves as another output end of the inductance compensation circuit 3, which is recorded as a port Ladj-out2, and is connected to a port Rs-out1 of the high-frequency inverter circuit 2.
The switch control circuit 4 is composed of 9 relay drive circuits from the first relay drive circuit to the ninth relay drive circuit, wherein the output ends of the first relay drive circuit to the eighth relay drive circuit are respectively connected with eight input ends of the inductance compensation circuit 3, the output end of the ninth relay drive circuit is connected with the enabling control end of the amplitude detection circuit 6, and the input ends of the first relay drive circuit to the ninth relay drive circuit are respectively connected with nine different I/O ports of the singlechip 5;
the first relay driving circuit to the ninth relay driving circuit are identical in structure, and the specific structure is that one end of a resistor R29 is connected with a +5V direct-current power supply, the other end of the resistor R29 is connected with the anode of a light-emitting diode in an optocoupler U4, the cathode of the light-emitting diode in the optocoupler U4 is used as the input end of the relay driving circuit, is recorded as a port MCU-in and is connected with the singlechip 5; an emitter of a phototriode in the optocoupler U4 is grounded, a collector of the phototriode is connected with one end of a resistor R30 and one end of a resistor R31, the other end of the resistor R30 is connected with a +12V power supply, the other end of the resistor R31 is connected with a base electrode of a triode Q17, an emitter of a triode Q17 is connected with the +12V power supply, a collector of the phototriode is connected with a cathode of a diode D8 and serves as an output end of a relay driving circuit and is recorded as a port Rout, and an anode of a diode D.
In the high-frequency inverter circuit 2, the inductance L preferably takes 285uH and the withstand voltage 400V, and the capacitance Cs1 and the capacitance Cs2 preferably take 51nF and 110nF, and the withstand voltage 400V, respectively;
in the amplitude detection circuit 6, the resistance value of the sampling resistor Rs is preferably 1 ohm.
In the inductance compensation circuit 3, the value of each inductance is preferably set as follows, inductance L1: 1uH, inductance L2: 250nH, inductance L3: 670nH, inductance L4: 1.5uH, inductance L5: 4uH, inductance L6 and inductance L7: 1uH, inductance L8: 2uH, inductance L9: 5 uH;
the ac-dc conversion circuit 1 is a circuit capable of converting 220V commercial power into dc voltage and outputting the dc voltage, and preferably outputs the dc voltage of 200V.
The analog-to-digital conversion circuit 7 is a circuit that can convert an analog signal into a digital signal, which is a conventional technique.
The bidirectional constant current source circuit has the following beneficial effects:
1. the invention judges the resonance degree of the system to the load through amplitude detection, and further automatically adjusts the compensating reactance, so that the system can keep real-time resonance when transmitting energy to different receiving circuits, thereby greatly improving the working efficiency of the system and the application range of the system to the load.
2. The invention adopts special driving design for the power tube in the high-frequency inverter circuit, reduces energy loss in the conversion process and can improve the power and efficiency of the whole system.
3. In the inductance compensation circuit, the inductance compensation network is skillfully designed, and a small number of components are used for realizing the selection of various inductance values.
4. In the relay driving circuit, the optical coupling is adopted to isolate the singlechip from the main loop, so that the signal electricity and the power electricity of the system are not influenced mutually, and the stability and the reliability of the system are improved.
5. The invention designs the enabling control function for the sampling resistor and the amplitude detection circuit, and can separate the sampling resistor and the amplitude detection circuit from the main loop after the initialization is completed, thereby reducing the influence of the sampling resistor on the main loop in the charging process and further improving the efficiency.
Drawings
Fig. 1 is a block diagram of the overall architecture of the present invention.
Fig. 2 is a functional block diagram of the switch control circuit 4.
Fig. 3 is a schematic circuit diagram of the high-frequency inverter circuit 2.
Fig. 4 is a schematic circuit diagram of the amplitude detection circuit 6.
Fig. 5 is a circuit schematic of the inductance compensation circuit 3.
Fig. 6 is a schematic circuit diagram of a relay.
Detailed Description
The operation principle of the present invention is further explained by the following embodiments with reference to the accompanying drawings, wherein the component parameters indicated in the drawings are preferred parameters of the embodiments, but are not limiting to the implementation of the present invention.
EXAMPLE 1 Overall Structure of the invention
The overall structure of the invention is shown in figure 1, and comprises an alternating current-direct current conversion circuit 1, a high-frequency inverter circuit 2, an inductance compensation circuit 3, a switch control circuit 4, a singlechip 5, an amplitude detection circuit 6 and an analog-digital conversion circuit 7; the input end of the alternating current-direct current conversion circuit 1 is connected with a mains supply, the output end of the alternating current-direct current conversion circuit 1 is connected with the power input end of the high-frequency inverter circuit 2, the sampling output end of the high-frequency inverter circuit 2 is connected with the input end of the amplitude detection circuit 6, the output end of the amplitude detection circuit 6 is connected with the input end of the analog-digital conversion circuit 7, the output end of the analog-digital conversion circuit 7 is connected with the single chip microcomputer 5, the single chip microcomputer 5 is further connected with the control input end of the high-frequency inverter circuit 2 and the input end of the switch control circuit 4 respectively, the output end of the switch control circuit 4 is connected with the input end of the inductance compensation circuit 3 and the enabling control end of the amplitude detection circuit 6 respectively, and the.
The structure of the high-frequency inverter circuit 2 adopted in the invention is shown in fig. 3, the anode of a diode D1 is connected with a +12V power supply, the cathode of a diode D1 is connected with one end of a resistor R1, the emitter of a triode Q1 and one end of a capacitor C1, the other end of the resistor R1 is connected with the base of a triode Q1 and the collector of a triode Q2, the base of a triode Q2 is connected with one end of a resistor R2, the other end of the resistor R2 is connected with a +5V direct-current power supply, the emitter of a triode Q2 is connected with one end of a resistor R3, the other end of the resistor R3 is used as a first control input end of the high-frequency inverter circuit 2 and is marked as a port MCU-in1 and is connected with the singlechip 5, the collector of the triode Q1 is connected with the anode of a diode D2, the base of a triode Q3 and one end of a resistor R4, the other end of the resistor, The drain electrode of a field effect transistor Q8, one end of an inductor L and the source electrode of a field effect transistor Q4 are connected, the emitter electrode of a triode Q3 is connected with the cathode of a diode D2, the cathode of a voltage stabilizing diode D3 and the grid electrode of a field effect transistor Q4, the drain electrode of a field effect transistor Q4 is connected with the drain electrode of a field effect transistor Q9 and serves as the power supply input end of a high-frequency inverter circuit 2, which is marked as a port Vs-in and is connected with the direct current voltage output end of an alternating current-direct current conversion circuit 1, the grid electrode of the field effect transistor Q8 is connected with one end of a resistor R8 and the collector electrode of a triode Q7, the other end of a resistor R8 is connected with the collector electrode of a triode Q5, the emitter electrode of a triode Q5 is connected with one end of a resistor R5 and a +12V direct current power supply, the other end of the resistor R5 is connected with the base electrode of the triode Q5 and the, an emitter of the triode Q6 is connected with one end of a resistor R7, the other end of the resistor R7 is connected with one end of a resistor R9, and is used as a second control input end of the high-frequency inverter circuit 2 and is recorded as a port MCU-in2 to be connected with the singlechip 5, the other end of the resistor R9 is connected with a base of the triode Q7, an emitter of the triode Q7 is connected with a source of a field-effect tube Q8 and is grounded, the other end of an inductor L is connected with one end of a capacitor Cs1, the other end of the capacitor Cs1 is connected with one end of a capacitor Cs2, the other end of a capacitor Cs2 is used as a compensation input end of the high-frequency inverter circuit 2 and is recorded as a port Ladj-in1 to be connected with a port Ladj; one end of a sampling resistor Rs is used as the other compensation input end of the high-frequency inverter circuit 2, and is also used as a sampling output end of the high-frequency inverter circuit 2, and is marked as a port Rs-out1, the port is connected with a port Ladj-out2 of the inductance compensation circuit 3, and is also connected with a port Rs-in1 of the amplitude detection circuit 6, the other end of the sampling resistor Rs is connected with the drain of the field-effect tube Q13, the source of the field-effect tube Q9, the anode of a voltage-regulator diode D4, the collector of the triode Q10, one end of a resistor R10 and one end of a capacitor C2, and is marked as the other sampling output end of the high-frequency inverter circuit 2, and is connected with a port Rs-in2 of the amplitude detection circuit 6, the gate of the field-effect tube Q9 is connected with the cathode of a voltage-regulator diode D4, the emitter of the triode Q10 and the cathode of a diode D5, the base of, The anode of a diode D5 is connected with the collector of a triode Q11, the emitter of a triode Q11 is connected with the other end of a capacitor C2, one end of a resistor R11 and the cathode of a diode D6, the anode of a diode D6 is connected with a +12V direct-current power supply, the base of a triode Q11 is connected with the other end of a resistor R11 and the collector of a triode Q12, the base of a triode Q12 is connected with one end of a resistor R12, the other end of a resistor R12 is connected with a +5V direct-current power supply, the emitter of a triode Q12 is connected with one end of a resistor R13, the other end of a resistor R13 serves as a third control input end of the high-frequency inverter circuit 2 and is marked as a port MCU-in; the source of a field effect transistor Q13 is connected with the emitter of a triode Q14 and is grounded, the gate of the field effect transistor Q13 is connected with one end of a resistor R14 and the collector of the triode Q14, the base of the triode Q14 is connected with one end of a resistor R15, the other end of the resistor R15 is connected with one end of a resistor R17 and serves as a fourth control input end of the high-frequency inverter circuit 2 and is marked as a port MCU-in4 to be connected with the single-chip microcomputer 5, the other end of the resistor R14 is connected with the collector of the triode Q15, the emitter of the triode Q15 is connected with one end of the resistor R16 and a +12V direct-current power supply, the base of the triode Q15 is connected with the other end of the resistor R16 and the collector of the triode Q16, the emitter of the triode Q16 is connected with the other end of the resistor R17, the base of the triode Q16 is connected with one end.
In the structure, 4 field effect transistors Q4, Q8, Q9 and Q13 form an inverter bridge for inverting a direct current signal output by the alternating current-direct current conversion circuit 1 into a high-frequency alternating current signal and providing energy for a transmitting coil (namely an inductor L in the figure), and a grid electrode of each field effect transistor also adopts a specially designed driving circuit, so that energy attenuation in the conversion process can be reduced, and the system can be ensured to achieve high output power and efficiency.
The principle circuit of the amplitude detection circuit 6 of the invention is shown in fig. 4, one end of a resistor R19 is connected with a movable contact of a relay Ks, and is taken as an input end of the amplitude detection circuit 6, and is marked as a port Rs-in1 and connected with a port Rs-out1 of a high-frequency inverter circuit 2; the other end of the resistor R19 is connected with the non-inverting input end of the operational amplifier U1 and one end of the resistor R20, and the other end of the resistor R20 is grounded; the static contact of the relay Ks is connected with one end of a resistor R21, is used as the other input end of the amplitude detection circuit 6, is recorded as a port Rs-in2, and is connected with a port Rs-out2 of the high-frequency inverter circuit 2; one end of the relay coil is grounded, and the other end of the relay coil is used as an enabling control end of the amplitude detection circuit 6, is recorded as a port Rins, and is connected with the output end of a ninth relay drive circuit in the switch control circuit 4; the other end of the resistor R21 is connected with the non-inverting input end of the operational amplifier U2 and one end of the resistor R22, and the other end of the resistor R22 is grounded; the inverting end of the resistor operational amplifier U2 is connected with one end of the resistor R23, one end of the resistor R25 and one end of the resistor R24, the other end of the resistor R23 is grounded, the positive power input end of the operational amplifier U2 is connected with a +5V direct-current power supply, the negative power input end of the operational amplifier U2 is connected with a-5V direct-current power supply, and the output end of the operational amplifier U2 is connected with one end of the resistor R26 and the other end of the resistor R25; the inverting input end of the operational amplifier U1 is connected with the other end of the resistor R24, the other end of the resistor R26 and one end of the resistor R27, the negative power supply input end of the operational amplifier U1 is connected with a-5V direct-current power supply, the positive power supply input end of the operational amplifier U1 is connected with a +5V direct-current power supply, and the output end of the operational amplifier U is connected with the other end of the resistor R27 and the anode of the diode D7; the cathode of the diode D7 is connected to one end of the capacitor C3 and one end of the resistor R28, serves as the output end of the amplitude detection circuit 6, is recorded as a port Amp-out, and is connected to the analog signal input end of the analog-to-digital conversion circuit 7, and the other end of the resistor R28 and the other end of the capacitor C3 are grounded;
the detection circuit is used for detecting the amplitude of alternating voltage at two ends of the sampling resistor Rs, and the detection result is converted into a digital signal by the analog-to-digital conversion circuit 7 at the later stage and then sent to the singlechip 5 for storage. The sampling resistor Rs is used for converting the main loop current in the high-frequency inverter circuit 2 into voltage, and the sampling resistor is a high-power and small-resistance precision resistor which can ensure that excessive energy is not consumed in the sampling process. Because the sampling resistor Rs is positioned at the output of the bridge of the high-frequency inverter circuit 2, the highest electric potential at two ends can reach the magnitude close to Vs (about 200V) when in work, the invention adopts voltage reduction and differential processing on the voltage at two ends of Rs, so that the signals at two ends of Rs are more convenient for amplitude detection. Meanwhile, in order to make the use of the invention more flexible, the amplitude detection circuit 6 also utilizes the relay Ks to realize the enabling control function, in the system initialization stage, in order to detect the resonance condition of the transmitting loop, the switch of the relay Ks can be disconnected, the sampling resistor Rs is effective, the amplitude detection circuit 6 carries out detection, after the initialization is completed, the system starts to normally work after selecting proper compensation inductance according to the detection result, because the detection is not needed, the switch of the relay Ks is closed, the sampling resistor Rs and the subsequent amplitude detection circuit 6 are short-circuited together, so that the sampling resistor continuously consumes energy in the working process is avoided, and the transmission efficiency of the system is further improved.
Wherein, the structure of the inductance compensation circuit 3 is shown in fig. 5, one end of the coils of the relays K1, K2, K3, K4, K5, K6, K7 and K8 are all grounded, the other end is used as eight input ends of the inductance compensation circuit 3, which are sequentially marked as ports Rin1, Rin2, Rin3, Rin4, Rin5, Rin6, Rin7 and Rin8, and are respectively connected with eight output ends of the first to eighth relay driving circuits in the switch control circuit 4, one ends of the inductors L1, L2, L3, L4 and L5 are connected with one end of the inductor L6 and the movable contact of the relay K5, the other ends of the inductors L2, L2 and L2 are sequentially connected with the movable contacts of the relays K2 and K2, the other ends of the inductors L2 and the inductors L2 are connected with the fixed contacts of the high frequency compensation circuits lak 2, lak 36d3672, and lak 2, and lak 36d3672 are connected with the output ends of the high frequency compensation circuits, the other end of the inductor L6 is connected with one end of an inductor L7, a fixed contact of a relay K5 and a movable contact of a relay K6, the other end of the inductor L7 is connected with one end of an inductor L8, a fixed contact of a relay K6 and a movable contact of a relay K7, the other end of the inductor L8 is connected with one end of an inductor L9, a fixed contact of a relay K7 and a movable contact of a relay K8, the other end of the inductor L9 is connected with a fixed contact of a relay K8, and the other end of the inductor L9 serves as the other output end of the inductor compensation circuit 3, is recorded as a port Ladj-out2 and is connected with a port Rs-out1 of the; the circuit realizes that the total inductance value takes 0.2uH as an interval and changes from 0.2uH to 10uH by selectively connecting different inductors, and a small number of elements provide 50 optional compensation inductors for the high-frequency inverter circuit 2. The load adaptation range of the invention is greatly widened.
As shown in fig. 2, the switch control circuit 4 of the present invention is composed of 9 relay driving circuits, namely, a first relay driving circuit to a ninth relay driving circuit, wherein output terminals of the first relay driving circuit to the eighth relay driving circuit are respectively connected to eight input terminals of the inductance compensation circuit 3, an output terminal of the ninth relay driving circuit is connected to an enable control terminal of the amplitude detection circuit 6, and input terminals of the first relay driving circuit to the ninth relay driving circuit are respectively connected to nine different I/O ports of the single chip microcomputer 5.
The switch control circuit 4 is used for controlling the driving of the switches of the relays in the amplitude detection circuit 6 and the inductance compensation circuit 3 under the control of the single chip microcomputer so as to select or shield different inductances and control whether the amplitude detection circuit 6 works or not. All the relay driving circuits have the same structure, as shown in fig. 6, one end of a resistor R29 is connected with a +5V direct-current power supply, the other end of the resistor R29 is connected with the anode of a light emitting diode in an optocoupler U4, and the cathode of the light emitting diode in the optocoupler U4 is used as the input end of the relay driving circuit, is marked as a port MCU-in, and is connected with the single chip microcomputer 5; an emitter of a phototriode in the optocoupler U4 is grounded, a collector of the phototriode is connected with one end of a resistor R30 and one end of a resistor R31, the other end of the resistor R30 is connected with a +12V power supply, the other end of the resistor R31 is connected with a base electrode of a triode Q17, an emitter of a triode Q17 is connected with the +12V power supply, a collector of the phototriode is connected with a cathode of a diode D8 and serves as an output end of a relay driving circuit and is recorded as a port Rout, and an anode of a diode D. The drive circuit adopts the optical coupler to isolate between the single chip microcomputer 5 and the relay, and effectively prevents the influence of large current in a relay coil or a high-frequency inverter circuit 2 on the single chip microcomputer 5.
Example 5 working principle of the invention
The working principle and the working process of the invention are further explained with reference to the accompanying drawings 1-6 as follows: before the system of the invention utilizes a transmitting coil (namely an inductance L in a high-frequency inverter circuit 2) to transmit energy to a receiving coil (positioned in a receiving circuit needing to receive energy, not shown in the figure), an initialization process is firstly carried out, a singlechip 5 controls a switch control circuit 4 to further control an inductance compensation circuit 3, a compensation inductance is selected to be connected into a main circuit, the compensation inductance is superposed with the inductance L of the transmitting coil to form a total inductance, the circuit is tried to be resonant, an amplitude detection circuit 6 detects the amplitude of alternating voltage at two ends of a sampling resistor Rs and is converted into a digital signal by an analog-to-digital conversion circuit 7 to be sent into the singlechip 5 for storage, then the singlechip 5 controls the inductance compensation circuit 3 to change the value of the compensation inductance, the process is repeated, and after all compensation inductances with different values are tried, the singlechip 5 compares all amplitude detection results, to determine the optimal compensation scheme (which may be different when the receiving loops at the receiving end are different). After the initialization process is completed, the singlechip 5 selects the optimal compensation inductor and connects the optimal compensation inductor to the main loop, and controls the relay Ks in the amplitude detection circuit 6 to close the switch, so that the sampling resistor Rs and the amplitude detection circuit 6 are separated from the resonant loop, and then energy is transmitted to the receiving end. The initialization process enables the transmitting loop to be in a resonance state when the system transmits energy to different receiving loops, and can effectively ensure that high transmission power and efficiency can be achieved under different loads.
Claims (4)
1. An automatic tuning wireless energy transmitting system based on inductance compensation is structurally provided with an alternating current-direct current conversion circuit (1), a high-frequency inverter circuit (2) and a single chip microcomputer (5), and is characterized by further comprising an inductance compensation circuit (3), a switch control circuit (4), an amplitude detection circuit (6) and an analog-to-digital conversion circuit (7); the input end of the alternating current-direct current conversion circuit (1) is connected with a mains supply, the sampling output end of the high-frequency inverter circuit (2) is connected with the input end of the amplitude detection circuit (6), the output end of the amplitude detection circuit (6) is connected with the input end of the analog-digital conversion circuit (7), the output end of the analog-digital conversion circuit (7) is connected with the single chip microcomputer (5), the single chip microcomputer (5) is also connected with the control input end of the high-frequency inverter circuit (2) and the input end of the switch control circuit (4) respectively, the output end of the switch control circuit (4) is connected with the input end of the inductance compensation circuit (3) and the enabling control end of the amplitude detection circuit (6) respectively, and the output end of the inductance compensation circuit (3) is connected with the compensation input end of the high-frequency inverter circuit (2;
the high-frequency inverter circuit (2) is structurally characterized in that the anode of a diode D1 is connected with a +12V power supply, the cathode of a diode D1 is connected with one end of a resistor R1, the emitter of a triode Q1 and one end of a capacitor C1, the other end of a resistor R1 is connected with the base of a triode Q1 and the collector of a triode Q2, the base of a triode Q2 is connected with one end of a resistor R2, the other end of the resistor R2 is connected with a +5V direct-current power supply, the emitter of a triode Q2 is connected with one end of a resistor R3, the other end of the resistor R3 serves as a first control input end of the high-frequency inverter circuit (2) and is recorded as a port MCU-in1 and is connected with a single chip microcomputer (5), the collector of the triode Q1 is connected with the anode of a diode D2, the base of a triode Q3 and one end of a resistor R4, the other end of a resistor R4 is connected, The drain electrode of a field effect tube Q8, one end of an inductor L and the source electrode of a field effect tube Q4 are connected, the emitter electrode of a triode Q3 is connected with the cathode of a diode D2, the cathode of a voltage stabilizing diode D3 and the grid electrode of a field effect tube Q4, the drain electrode of a field effect tube Q4 is connected with the drain electrode of a field effect tube Q9 and serves as the power supply input end of a high-frequency inverter circuit (2) which is marked as a port Vs-in and is connected with the direct current voltage output end of an alternating current-direct current conversion circuit (1), the grid electrode of the field effect tube Q8 is connected with one end of a resistor R8 and the collector electrode of a triode Q7, the other end of a resistor R8 is connected with the collector electrode of a triode Q5, the emitter electrode of a triode Q5 is connected with one end of a resistor R5 and a +12V direct current power supply, the other end of the resistor R5 is connected with the base electrode of the triode Q5 and the collector electrode, an emitter of the triode Q6 is connected with one end of a resistor R7, the other end of the resistor R7 is connected with one end of a resistor R9, the emitter of the triode Q7 is connected with a source electrode of a field effect transistor Q8 and is grounded, the other end of an inductor L is connected with one end of a capacitor Cs1, the other end of the capacitor Cs1 is connected with one end of a capacitor Cs2, the other end of the capacitor Cs2 is used as a compensation input end of the high-frequency inverter circuit (2) and is marked as a port Ladj-in1, and the port Ladj-out1 of the inductor compensation circuit (3); one end of a sampling resistor Rs is used as the other compensation input end of the high-frequency inverter circuit (2), and is also used as a sampling output end of the high-frequency inverter circuit (2) and is marked as a port Rs-out1, the port is connected with a port Ladj-out2 of the inductance compensation circuit (3), and is also connected with a port Rs-in1 of the amplitude detection circuit (6), the other end of the sampling resistor Rs is connected with the drain of a field-effect tube Q13, the source of the field-effect tube Q9, the anode of a voltage-stabilizing diode D4, the collector of a triode Q10, one end of a resistor R10 and one end of a capacitor C7, and is used as the other sampling output end of the high-frequency inverter circuit (2) and is marked as a port Rs-out2 and is connected with a port Rs-in2 of the amplitude detection circuit (6), the grid of the field-effect tube Q9 is connected with the cathode 5393 of the voltage-stabilizing diode D4, the emitter of, the base electrode of a triode Q10 is connected with the other end of a resistor R10, the anode of a diode D5 and the collector of a triode Q11, the emitter electrode of a triode Q11 is connected with the other end of a capacitor C2, one end of a resistor R11 and the cathode of a diode D6, the anode of a diode D6 is connected with a +12V direct-current power supply, the base electrode of a triode Q11 is connected with the other end of a resistor R11 and the collector of a triode Q12, the base electrode of a triode Q12 is connected with one end of a resistor R12, the other end of a resistor R12 is connected with a +5V direct-current power supply, the emitter electrode of a triode Q12 is connected with one end of a resistor R13, the other end of a resistor R13 is used as a third control input end of a high-frequency inverter circuit (2); the source of a field effect transistor Q13 is connected with the emitter of a triode Q14 and is grounded, the gate of the field effect transistor Q13 is connected with one end of a resistor R14 and the collector of a triode Q14, the base of the triode Q14 is connected with one end of a resistor R15, the other end of the resistor R15 is connected with one end of a resistor R17, the resistor R15 serves as the fourth control input end of a high-frequency inverter circuit (2) and is marked as a port MCU-in4 and is connected with a single chip microcomputer (5), the other end of the resistor R14 is connected with the collector of a triode Q15, the emitter of the triode Q15 is connected with one end of the resistor R16 and a +12V direct-current power supply, the base of the triode Q15 is connected with the other end of the resistor R16 and the collector of the triode Q16, the emitter of the triode Q16 is connected with the other end of the resistor R17, the base of the triode Q16 is connected;
the structure of the amplitude detection circuit (6) is that one end of a resistor R19 is connected with a movable contact of a relay Ks, is used as an input end of the amplitude detection circuit (6), is recorded as a port Rs-in1 and is connected with a port Rs-out1 of the high-frequency inverter circuit (2); the other end of the resistor R19 is connected with the non-inverting input end of the operational amplifier U1 and one end of the resistor R20, and the other end of the resistor R20 is grounded; the static contact of the relay Ks is connected with one end of a resistor R21, is used as the other input end of the amplitude detection circuit (6), is recorded as a port Rs-in2, and is connected with a port Rs-out2 of the high-frequency inverter circuit (2); one end of the relay coil is grounded, and the other end of the relay coil is used as an enabling control end of the amplitude detection circuit (6), is recorded as a port Rins and is connected with the output end of a ninth relay drive circuit in the switch control circuit (4); the other end of the resistor R21 is connected with the non-inverting input end of the operational amplifier U2 and one end of the resistor R22, and the other end of the resistor R22 is grounded; the inverting end of the resistor operational amplifier U2 is connected with one end of the resistor R23, one end of the resistor R25 and one end of the resistor R24, the other end of the resistor R23 is grounded, the positive power input end of the operational amplifier U2 is connected with a +5V direct-current power supply, the negative power input end of the operational amplifier U2 is connected with a-5V direct-current power supply, and the output end of the operational amplifier U2 is connected with one end of the resistor R26 and the other end of the resistor R25; the inverting input end of the operational amplifier U1 is connected with the other end of the resistor R24, the other end of the resistor R26 and one end of the resistor R27, the negative power supply input end of the operational amplifier U1 is connected with a-5V direct-current power supply, the positive power supply input end of the operational amplifier U1 is connected with a +5V direct-current power supply, and the output end of the operational amplifier U is connected with the other end of the resistor R27 and the anode of the diode D7; the cathode of the diode D7 is connected with one end of the capacitor C3 and one end of the resistor R28, is used as the output end of the amplitude detection circuit (6), is recorded as a port Amp-out, is connected with the analog signal input end of the analog-to-digital conversion circuit (7), and the other end of the resistor R28 and the other end of the capacitor C3 are grounded;
the inductance compensation circuit (3) is structured in such a way that one end of each of coils of relays K1, K2, K3, K4, K5, K6, K7 and K8 is grounded, the other end is used as eight input ends of the inductance compensation circuit (3), which are sequentially marked as ports Rin1, Rin2, Rin3, Rin4, Rin5, Rin6, Rin7 and Rin8, and are respectively connected with eight output ends of first to eighth relay driving circuits in a switch control circuit (4), one ends of inductors L1, L2, L3, L4 and L5 are connected with one end of an inductor L6 and a movable contact of a relay K5, the other ends of inductors L2, L2 and L2, the other ends of the inductors L2 and L2 are sequentially connected with movable contacts of relays K2 and Ladj 2, the other ends of the inductors are connected with high-frequency compensation circuit (Ladj, and Ladj) are respectively connected with an output end of the inverter circuit 2 and are respectively marked as a high frequency compensation circuit 2 and a high frequency switch, the other end of the inductor L6 is connected with one end of an inductor L7, a fixed contact of a relay K5 and a movable contact of a relay K6, the other end of the inductor L7 is connected with one end of an inductor L8, a fixed contact of a relay K6 and a movable contact of a relay K7, the other end of the inductor L8 is connected with one end of an inductor L9, a fixed contact of a relay K7 and a movable contact of a relay K8, the other end of the inductor L9 is connected with a fixed contact of a relay K8, and the other output end of the inductor compensation circuit (3) is recorded as a port Ladj-out2 and is connected with a port Rs-out1 of the high-frequency inverter circuit (2);
the switch control circuit (4) is composed of 9 relay drive circuits from the first relay drive circuit to the ninth relay drive circuit, wherein the output ends of the first relay drive circuit to the eighth relay drive circuit are respectively connected with eight input ends of the inductance compensation circuit (3), the output end of the ninth relay drive circuit is connected with the enabling control end of the amplitude detection circuit (6), and the input ends of the first relay drive circuit to the ninth relay drive circuit are respectively connected with nine different I/O ports of the singlechip (5);
the first relay driving circuit to the ninth relay driving circuit are identical in structure, and the specific structure is that one end of a resistor R29 is connected with a +5V direct-current power supply, the other end of the resistor R29 is connected with the anode of a light-emitting diode in an optocoupler U4, the cathode of the light-emitting diode in the optocoupler U4 is used as the input end of the relay driving circuit, is recorded as a port MCU-in and is connected with a singlechip (5); an emitter of a phototriode in the optocoupler U4 is grounded, a collector of the phototriode is connected with one end of a resistor R30 and one end of a resistor R31, the other end of the resistor R30 is connected with a +12V power supply, the other end of the resistor R31 is connected with a base electrode of a triode Q17, an emitter of a triode Q17 is connected with the +12V power supply, a collector of the phototriode is connected with a cathode of a diode D8 and serves as an output end of a relay driving circuit and is recorded as a port Rout, and an anode of a diode D.
2. The automatic tuning wireless energy emission system based on inductance compensation according to claim 1, characterized in that in the high frequency inverter circuit (2), the inductance L is 285uH and the withstand voltage is 400V, and the capacitance Cs1 and the capacitance Cs2 are 51nF and 110nF respectively and the withstand voltage is 400V.
3. An automatic tuning wireless energy transmission system based on inductance compensation according to claim 1, characterized in that, in the amplitude detection circuit (6), the resistance value of the sampling resistor Rs is 0.1 ohm.
4. The automatic tuning wireless energy emission system based on inductance compensation according to any one of claims 1 to 3, wherein in the inductance compensation circuit (3), the value of each inductance is that inductance L1: 1uH, inductance L2: 250nH, inductance L3: 670nH, inductance L4: 1.5uH, inductance L5: 4uH, inductance L6 and inductance L7: 1uH, inductance L8: 2uH, inductance L9: 5 uH.
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Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102969776A (en) * | 2012-12-03 | 2013-03-13 | 中国科学院电工研究所 | Wireless charging device of electronic automobile |
| CN103560593A (en) * | 2013-11-07 | 2014-02-05 | 重庆大学 | Electric field coupled power transfer system and control method based on novel topology |
| CN105634081A (en) * | 2016-03-30 | 2016-06-01 | 吉林大学 | Laser ranging-based adaptive electric vehicle wireless power supply mobile platform |
| CN105720701A (en) * | 2016-01-28 | 2016-06-29 | 北京理工大学 | Inductive coupling type wireless energy transmission system and active disturbance rejection control method thereof |
| CN106532980A (en) * | 2016-12-13 | 2017-03-22 | 西南交通大学 | Non-contact type dynamic power supply system coil for trains in rail transit |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102969776A (en) * | 2012-12-03 | 2013-03-13 | 中国科学院电工研究所 | Wireless charging device of electronic automobile |
| CN103560593A (en) * | 2013-11-07 | 2014-02-05 | 重庆大学 | Electric field coupled power transfer system and control method based on novel topology |
| CN105720701A (en) * | 2016-01-28 | 2016-06-29 | 北京理工大学 | Inductive coupling type wireless energy transmission system and active disturbance rejection control method thereof |
| CN105634081A (en) * | 2016-03-30 | 2016-06-01 | 吉林大学 | Laser ranging-based adaptive electric vehicle wireless power supply mobile platform |
| CN106532980A (en) * | 2016-12-13 | 2017-03-22 | 西南交通大学 | Non-contact type dynamic power supply system coil for trains in rail transit |
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