CN107727931B - Ultrasonic power supply phase difference detection device and method based on combined controller - Google Patents

Ultrasonic power supply phase difference detection device and method based on combined controller Download PDF

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CN107727931B
CN107727931B CN201710872505.0A CN201710872505A CN107727931B CN 107727931 B CN107727931 B CN 107727931B CN 201710872505 A CN201710872505 A CN 201710872505A CN 107727931 B CN107727931 B CN 107727931B
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程鑫
陈强
胡业发
吴华春
王晓光
张�林
王博
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Wuhan University of Technology WUT
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Abstract

The invention discloses an ultrasonic power supply phase difference detection device based on a combined controller, wherein the output end of a current sensor is grounded through a sampling resistor R3, the first input end of a phase detection circuit is connected with the output end of the current sensor, and the first output end of the phase detection circuit is connected with one input end of an FPGA chip; the second input end of the phase detection circuit is connected with the output end of the voltage sensor circuit, and the second output end of the phase detection circuit is connected with the other input end of the FPGA chip; the output end of the current sensor and the output end of the voltage sensor are also connected with two input ends of the DSP chip, and the FPGA chip and the DSP chip are mutually connected. The invention also discloses an ultrasonic power supply phase difference detection method based on the combined controller. The FPGA is used for filtering the voltage phase feedback signal, so that the circuit for extracting the phase difference by adopting a logic gate is prevented from generating errors, the phase difference signal is effectively measured, and an accurate basis is provided for compensating the phase difference.

Description

Ultrasonic power supply phase difference detection device and method based on combined controller
Technical Field
The invention belongs to the technical field of accurate detection of current and voltage phase differences of power ultrasonic transducers, and particularly relates to an ultrasonic power supply phase difference detection device and method based on a DSP (digital signal processor) and an FPGA (field programmable gate array).
Background
Ultrasonic power sources are widely used in modern industries, mainly including cleaning, spraying, food processing, welding, machining, and the like. The ultrasonic power supply provides ultrasonic frequency alternating current signals to the ultrasonic transducer, the ultrasonic transducer converts electric energy into sound energy, namely mechanical vibration, the core problem of the ultrasonic driving technology is to improve the conversion efficiency of ultrasonic driving, and accurate acquisition of phase signals of the ultrasonic transducer is a premise of realizing constant power regulation and automatic frequency tracking of the power supply and is also a key for ensuring stable work of an ultrasonic power supply system, so that the accurate measurement of phase difference signals of the ultrasonic transducer is particularly important. Meanwhile, in the working process of the ultrasonic power supply, the phase detection control frequency is needed to keep the voltage and current phases of the transducer the same. At present, two following technologies for high-frequency ultrasonic power supply are available at home and abroad, one adopts analog control, and the other adopts digital control.
The phase difference detection of the circuit is realized by utilizing the analog control high-frequency ultrasonic power supply, a large number of complex control circuits need to be designed, and the problems of easy aging of circuit elements, serious temperature drift, inconvenient parameter adjustment, unsatisfactory aspects of dynamic response, control precision and the like, large power loss, poor universality, inflexible control and the like exist; due to the fact that the lag of the voltage phase detection circuit is inconsistent with that of the current phase detection circuit, the frequency following of the current digital high-frequency ultrasonic power supply cannot be detected accurately.
The invention content is as follows:
in order to overcome the above-mentioned drawbacks of the background art, the present invention provides an apparatus and method for detecting a phase difference of an ultrasonic power supply based on a combination controller, which can effectively measure a phase difference.
In order to solve the technical problems, the invention adopts the technical scheme that:
the current sensor circuit comprises a current sensor, the output end of the current sensor is grounded through a sampling resistor R3, and the voltage sensor circuit comprises a voltage sensor and a differential amplification circuit; the first input end of the phase detection circuit is connected with the output end of the current sensor, and the first output end of the phase detection circuit is connected with one input end of the FPGA chip; the second input end of the phase detection circuit is connected with the output end of the voltage sensor circuit, and the second output end of the phase detection circuit is connected with the other input end of the FPGA chip; the output end of the current sensor and the output end of the voltage sensor are also connected with two input ends of the DSP chip, and the FPGA chip and the DSP chip are mutually connected.
Preferably, the input end of the current sensor is used for connecting a current amplifier, and the input end of the voltage sensor is used for connecting a controlled voltage source or a signal generator.
Preferably, the phase detection circuit includes a first impedance isolation circuit, a first bias circuit, a first voltage comparator circuit, and a first level shifter circuit, which are sequentially disposed between the first input terminal and the first output terminal;
preferably, the circuit further comprises a second impedance isolation circuit, a second bias circuit, a second voltage comparator circuit and a second level shifter circuit which are sequentially arranged between the second input end and the second output end.
The invention also provides an ultrasonic power supply phase difference detection method based on the combined controller, which comprises the following steps:
step 1, connecting the input end of a current sensor and the input end of a voltage sensor in parallel at the output end of a controlled voltage source or a signal generator, inputting a sweep frequency voltage signal with a fixed amplitude and a current signal into the current sensor and the voltage sensor, acquiring a phase-frequency characteristic curve of an input voltage signal and an output voltage signal, and acquiring a phase difference of an input voltage and a phase signal of an output voltage of a phase detection circuit
Figure BDA0001417401350000031
Wherein k isUProportional coefficient of frequency vs. phase lag, bUIs a constant term in the relational expression; and the phase difference between the input current signal and the output current phase signal
Figure BDA0001417401350000032
Wherein k isIProportional coefficient of frequency vs. phase lag, bIIs a constant term in the relation.
Step 2, respectively inputting fixed-frequency sinusoidal voltage signals and current signals with different amplitudes at a voltage phase detection circuit through a controlled voltage source and a current source, respectively detecting the phase lag of the input voltage signal and the output voltage phase signal, and detecting the phase lag of the input current signal and the output current phase signal; firstly, sinusoidal voltage signals with different amplitudes are input to the input end of a voltage sensor through a signal generator, and corresponding voltage amplitudes and voltage phase lags are recorded to obtain a first group of data
Figure BDA0001417401350000033
Inputting sinusoidal current signal at the input end of the current sensor through the current amplifier, recording corresponding current amplitude and current phase lag, and obtaining a second group of data
Figure BDA0001417401350000041
Wherein U is0To UmIs the amplitude of the input voltage signal,
Figure BDA0001417401350000042
to
Figure BDA0001417401350000043
For detecting the hysteresis of the current in the voltage phase, I0To ImIs the amplitude of the input current signal,
Figure BDA0001417401350000044
to
Figure BDA0001417401350000045
M is a hysteresis value of the current phase detection circuit, and m is the data measured in the mth measurement;
the first group of data and the second group of data are plotted and fitted to obtain expressions of phase lags and input signal amplitudes of the voltage phase feedback branch and the current phase feedback branch respectively as follows:
Figure BDA0001417401350000046
Figure BDA0001417401350000047
wherein U is the amplitude of the voltage signal, I is the amplitude of the current signal, n is any positive integer, kUnCoefficient, k, for the term of degree n in the expression of voltage phase lagInAs a coefficient of the current phase lag expression corresponding to the n-th order term, bUC，bICConstant terms of the voltage and current phase lag expressions respectively to obtain the expression of phase lag error in the working of the transducer
Figure BDA0001417401350000048
Step 3, the DSP respectively samples the output ends of the voltage sensor and the current sensor through AD to obtain the amplitudes of the voltage U and the current I, and the amplitudes are substituted into phase lag errors in the working of the transducer
Figure BDA0001417401350000049
The expression (c) obtains the value of the phase difference to be compensated, and detects the actual phase difference
Figure BDA00014174013500000410
Then the true voltage current phase difference
Figure BDA00014174013500000411
Preferably, the method further comprises a step of compensating the detection result, specifically comprising:
judging the actual voltage current phase difference of the result obtained in the step 3
Figure BDA00014174013500000412
If it is equal to 0, if so, keeping the PWM frequency output, if not,
further determining the real voltage current phase difference
Figure BDA0001417401350000051
And if the phase difference exceeds the effective range of the phase difference control, the frequency is swept again and locked, and if not, PID operation is carried out to accurately adjust the output frequency of the PWM.
The invention has the beneficial effects that: the FPGA is used for filtering the voltage phase feedback signal, so that the error of a circuit for extracting the phase difference by adopting a logic gate is avoided, the phase lag inconsistency existing in a current and voltage phase detection circuit is accurately measured, the phase difference signal can be converted into a digital quantity in real time and sent to the DSP through an XINTF external expansion bus, the speed of the DSP for processing the phase difference signal is improved, the controller is simplified, the phase difference signal is effectively measured, and the accurate basis is provided for compensating the phase difference.
Drawings
FIG. 1 is a schematic structural diagram according to a first embodiment of the present invention;
FIG. 2 is a flow chart of the control of the high frequency ultrasound power supply;
fig. 3 is an overall structure diagram of the ultrasonic power supply.
In the figure: the circuit comprises a current sensor 1, a voltage sensor 2, a FPGA3, a DSP4, a impedance isolation circuit 5, a first bias circuit 6, a first voltage comparator circuit 7, a first level conversion circuit 8, a second impedance isolation circuit 9, a second bias circuit 10, a second voltage comparator circuit 11, a second level conversion circuit 12, a transducer 13, a matching inductor 14, a bootstrap driving circuit 15, a full-bridge inverter circuit 16 and a high-frequency transformer 17.
Detailed Description
The invention is further described below with reference to the accompanying drawings and examples.
Example one
The circuit comprises a current sensor 1 circuit and a voltage sensor 2 circuit as shown in FIG. 1, wherein the current sensor 1 circuit comprises a current sensor 1, the output end of the current sensor 1 is grounded through a sampling resistor R3, and the voltage sensor 2 circuit comprises a voltage sensor 2 and a differential amplifying circuit; the first input end of the phase detection circuit is connected with the output end of the current sensor 1, and the first output end of the phase detection circuit is connected with one input end of the FPGA3 chip; the second input end of the phase detection circuit is connected with the output end of the voltage sensor 2 circuit, and the second output end of the phase detection circuit is connected with the other input end of the FPGA3 chip; the output end of the current sensor 1 and the output end of the voltage sensor 2 are also connected with two input ends of a DSP4 chip, and an FPGA3 chip and a DSP4 chip are mutually connected.
The input end of the current sensor 1 is used for connecting a current amplifier, and the input end of the voltage sensor 2 is used for connecting a controlled voltage source or a signal generator.
The phase detection circuit comprises a first impedance isolation circuit 5, a first bias circuit 6, a first voltage comparator circuit 7 and a first level conversion circuit 8 which are sequentially arranged between a first input end and a first output end;
and the circuit further comprises a second impedance isolation circuit 9, a second bias circuit 10, a second voltage comparator circuit 11 and a second level shift circuit 12 which are sequentially arranged between the second input end and the second output end.
An input voltage signal of the transducer 13 passes through the linear optocoupler voltage sensor 2, and then is output to the FPGA3 after passing through the second impedance isolation circuit, the second bias circuit 10, the second voltage comparator and the second level conversion circuit 12. Finally, the FPGA3 converts the phase difference signal into a digital quantity, which is sent to the DSP4 via a bus.
The first impedance isolation circuit 5, the second impedance isolation circuit 9, the first bias circuit 6 and the second bias circuit 10 are all implemented by using an operational amplifier chip powered by two terminals, and the operational amplifier chip powered by two terminals is in the model of LM318 in this embodiment; in the first bias circuit 6 and the second bias circuit 10, taking a bias circuit of a current signal as an example, by adjusting the resistance values of the resistors R1, R2 or R4, R5, the bias voltage and the bias ratio can be changed. In practice, R1 ═ R2 and R4 ═ R5 are generally used. The first voltage comparison circuit and the second voltage comparison circuit are both realized by using a voltage comparator chip, and the voltage comparator chip in the embodiment adopts a type TLV 3202; the first level shift circuit 8 and the second level shift circuit 12 are implemented by using three-state gate chips, and the model number adopted in the present embodiment is SN74LVC1G 125. (the actual chip type selects the corresponding device according to the designed working frequency). Current and voltage signals with different amplitudes are respectively input to the input ends of the voltage sensor 2 and the current sensor 1 through an alternating current source and a voltage source, the phase detection circuit is calibrated by utilizing the specific steps as described in the second embodiment, and a function relation between the amplitude and the phase lag of the detection loop is obtained, so that a corresponding compensation function relation is obtained. The amplitude values of voltage and current are detected by an AD conversion module in the DSP4, a compensation function relation of the amplitude value and phase lag is specifically programmed by a software algorithm, the phase lag of a voltage signal and the phase lag of a current signal caused by flowing through a phase detection circuit are respectively calculated through the current and the voltage amplitude, and then the phase difference between the voltage signal and the current signal is obtained, and the DSP4 is communicated with the FPGA3 through an external bus.
As shown in fig. 3, after the whole circuit of the ultrasonic power supply is powered on, the PWM signal generated by the DSP4 is phase-shifted by the FPGA3, and is connected to the bootstrap drive circuit 15 to drive the full-bridge inverter circuit 16 to operate, so as to invert the smooth dc into a high-frequency ac square wave current; the high-frequency alternating current square wave is isolated by a high-frequency transformer 17 and output to Vin in the figure, and high-frequency sinusoidal alternating current is output to act on the transducer 13 through resonance transformation of the matching network, and the transducer 13 converts electric energy into ultrasonic mechanical vibration and outputs the ultrasonic mechanical vibration. Meanwhile, a voltage signal Vin and a current signal of the transducer 13 are respectively acquired through a voltage detection circuit and a current detection circuit, the DSP4 determines a phase difference compensation amount through detecting the amplitudes of the voltage signal and the current signal, and the data are transmitted to the DSP4 through detecting quantization and compensating the phase difference in the FPGA3 through communication with the FPGA 3.
Example two
A method for detecting the phase difference of an ultrasonic power supply based on a combined controller comprises the following steps:
step 1, connecting the input end of a current sensor 1 and the input end of a voltage sensor 2 in parallel at the output end of a controlled voltage source or a signal generator, inputting a sweep frequency voltage signal with a fixed amplitude and a current signal into the current sensor 1 and the voltage sensor 2, acquiring a phase-frequency characteristic curve of an input voltage signal and an output voltage signal, and detecting the input voltage and the phasePhase difference of output voltage phase signal of measuring circuit
Figure BDA0001417401350000081
Wherein k isUProportional coefficient of frequency vs. phase lag, bUIs a constant term in the relational expression; and the phase difference between the input current signal and the output current phase signal
Figure BDA0001417401350000082
Wherein k isIProportional coefficient of frequency vs. phase lag, bIIs a constant term in the relation.
Step 2, respectively inputting fixed-frequency sinusoidal voltage signals and current signals with different amplitudes at a voltage phase detection circuit through a controlled voltage source and a current source, respectively detecting the phase lag of the input voltage signal and the output voltage phase signal, and detecting the phase lag of the input current signal and the output current phase signal; firstly, sinusoidal voltage signals with different amplitudes are input to the input end of the voltage sensor 2 through a signal generator, and corresponding voltage amplitudes and voltage phase lags are recorded to obtain a first group of data
Figure BDA0001417401350000091
Inputting a sinusoidal current signal at the input of the current sensor 1 through a current amplifier, recording the corresponding current amplitude and current phase lag, and obtaining a second set of data
Figure BDA0001417401350000092
Wherein U is0To UmIs the amplitude of the input voltage signal,
Figure BDA0001417401350000093
to
Figure BDA0001417401350000094
For detecting the hysteresis of the current in the voltage phase, I0To ImIs the amplitude of the input current signal,
Figure BDA0001417401350000095
to
Figure BDA0001417401350000096
M is a hysteresis value of the current phase detection circuit, and m is the data measured in the mth measurement;
the first group of data and the second group of data are plotted and fitted to obtain expressions of phase lags and input signal amplitudes of the voltage phase feedback branch and the current phase feedback branch respectively as follows:
Figure BDA0001417401350000097
Figure BDA0001417401350000098
wherein U is the amplitude of the voltage signal, I is the amplitude of the current signal, n is any positive integer, kUnCoefficient, k, for the term of degree n in the expression of voltage phase lagmAs a coefficient of the current phase lag expression corresponding to the n-th order term, bUC，bICConstant terms of the voltage and current phase lag expressions, respectively, to obtain an expression of the phase lag error in the operation of the transducer 13
Figure BDA0001417401350000099
Step 3, the DSP4 samples the output ends of the voltage sensor 2 and the current sensor 1 respectively through AD to obtain the amplitudes of the voltage U and the current I, and the amplitudes are substituted into the phase lag error in the working process of the transducer 13
Figure BDA0001417401350000101
The expression (c) obtains the value of the phase difference to be compensated, and detects the actual phase difference
Figure BDA0001417401350000102
Then the true voltage current phase difference
Figure BDA0001417401350000103
The compensation function is programmed in a DSP4 controller, and the FPGA3 is controlled, so that the accurate measurement of the phase difference can be realized, and the accurate control of the ultrasonic power supply is finally realized.
The embodiment further includes a step of compensating the detection result, which specifically includes:
judging the actual voltage current phase difference of the result obtained in the step 3
Figure BDA0001417401350000104
If it is equal to 0, if so, keeping the PWM frequency output, if not,
further determining the real voltage current phase difference
Figure BDA0001417401350000105
And if the phase difference exceeds the effective range of the phase difference control, the frequency is swept again and locked, and if not, PID operation is carried out to accurately adjust the output frequency of the PWM.
As shown in fig. 2, the whole control process of the ultrasonic power supply of the present embodiment is implemented in the DSP4, and specifically includes: first, the DSP4 drives the full-bridge inverter circuit 16 through the hardware circuit shown in fig. 3 by outputting a frequency-swept PWM signal, so as to excite the matching inductor 14 and the transducer 13 in fig. 3. Meanwhile, the current value of the transducer 13 is detected, the frequency point at which the maximum value of the current is determined is recorded as fmax, and the frequency point is set as the operating frequency. The phase difference between the input voltage and the output current of the transducer 13 is then detected
Figure BDA0001417401350000106
And a phase-voltage current amplitude error detection compensation function based on the detection circuit of fig. 1 is introduced to carry out AD detection through the DSP4, the voltage amplitude U at the two ends of the transducer 13 and the current amplitude I flowing through the transducer 13 are detected and substituted into the obtained compensation function to obtain more accurate phase difference
Figure BDA0001417401350000107
And the phase difference can be accurately detected. Taking the phase difference as input, and when the phase difference is unequal to 0, if the phase difference exceeds the effective range of phase difference control, re-sweeping the frequency to lock the frequency; if the output frequency does not exceed the effective range, PID operation (proportional-integral-derivative operation) is carried out to accurately adjust the output frequency of the PWM. When the phase difference is 0, the PWM frequency output is maintained. Precise control of the resonant frequency of the transducer 13 is achieved. Steps 1 to 3 in this embodiment are specific methods for obtaining the compensation function relation between the phase difference and the voltage and current amplitude in fig. 2.
In the whole working process of the ultrasonic power supply circuit, a voltage signal of the energy converter 13 is obtained through the voltage dividing circuit, and the voltage signal is processed by the linear optical coupler voltage sensing circuit, then is output to the FPGA3 after being subjected to impedance isolation, bias, zero-crossing comparison and level conversion in sequence; the current sensor 1 is used for acquiring a current signal of the transducer 13, converting the current signal into a voltage signal through a sampling resistor, and outputting the voltage signal to the FPGA3 after impedance isolation, bias, zero-crossing comparison and level conversion. Due to the fact that the phase lags of the current and the voltage are inconsistent due to the fact that the response speeds of all links are different, the linear relation between the amplitudes of the current and the voltage and the phase lags of the current and the voltage is obtained through calibrating the characteristics of the detection loop, effective algorithm operation processing is conducted in the DSP4 and the FPGA3, the phase lags can be obtained through detecting the amplitudes of the voltage and the current through an AD module of the DSP4, the lags are compensated in the FPGA3, and the phase difference of the current and the voltage is accurately and effectively detected.
It will be understood that modifications and variations can be made by persons skilled in the art in light of the above teachings and all such modifications and variations are intended to be included within the scope of the invention as defined in the appended claims.

Claims (5)

1. An ultrasonic power supply phase difference detection method based on a combined controller is characterized by comprising the following steps:
step 1, connecting the input end of a current sensor (1) and the input end of a voltage sensor (2) in parallel with the output end of a controlled voltage source or a signal generator to ensure that the sweep with a fixed amplitude valueThe frequency voltage signal and the current signal are input into the current sensor (1) and the voltage sensor (2), the phase-frequency characteristic curve of the input voltage signal and the output voltage signal is obtained, and the phase difference between the input voltage and the phase signal of the output voltage of the phase detection circuit is obtained
Figure FDA0002260922480000011
Wherein k isUProportional coefficient of frequency vs. phase lag, bUIs a constant term in the relational expression; and the phase difference between the input current signal and the output current phase signal
Figure FDA0002260922480000012
Wherein k isIProportional coefficient of frequency vs. phase lag, bIIs a constant term in the relational expression;
step 2, respectively inputting fixed-frequency sinusoidal voltage signals and current signals with different amplitudes at a voltage phase detection circuit through a controlled voltage source and a current source, respectively detecting the phase lag of the input voltage signal and the output voltage phase signal, and detecting the phase lag of the input current signal and the output current phase signal; firstly, sinusoidal voltage signals with different amplitudes are input to the input end of a voltage sensor (2) through a signal generator, and corresponding voltage amplitude values and voltage phase values are recorded to obtain a first group of data
Figure FDA0002260922480000013
Inputting a sinusoidal current signal at the input of the current sensor (1) through a current amplifier, recording the corresponding current amplitude and current phase lag, and obtaining a second set of data
Figure FDA0002260922480000021
Wherein U is0To UmIs the amplitude of the input voltage signal,
Figure FDA0002260922480000022
to
Figure FDA0002260922480000023
For detecting the hysteresis of the current in the voltage phase, I0To ImIs the amplitude of the input current signal,
Figure FDA0002260922480000024
to
Figure FDA0002260922480000025
M is a hysteresis value of the current phase detection circuit, and m is the data measured in the mth measurement;
the first group of data and the second group of data are plotted and fitted to obtain expressions of phase lags and input signal amplitudes of the voltage phase feedback branch and the current phase feedback branch respectively as follows:
Figure FDA0002260922480000026
Figure FDA0002260922480000027
wherein U is the amplitude of the voltage signal, I is the amplitude of the current signal, n is any positive integer, kUnCoefficient, k, for the term of degree n in the expression of voltage phase lagInAs a coefficient of the current phase lag expression corresponding to the n-th order term, bU0，bI0Constant terms of the voltage and current phase lag expressions respectively, to obtain the expression of the phase lag error in the operation of the transducer (13)
Figure FDA0002260922480000028
Step 3, the DSP (4) respectively samples the output ends of the voltage sensor (2) and the current sensor (1) to obtain the amplitudes of the voltage U and the current I, and the amplitudes are substituted into phase lag errors in the working of the transducer (13)
Figure FDA0002260922480000029
The expression (c) obtains the value of the phase difference to be compensated, and detects the actual phase difference
Figure FDA00022609224800000210
Then the true voltage current phase difference
Figure FDA00022609224800000211
2. The ultrasonic power phase difference detection method based on the combined controller according to claim 1, further comprising a step of compensating the detection result, specifically comprising:
judging the actual voltage current phase difference of the result obtained in the step 3
Figure FDA0002260922480000031
If it is equal to 0, if so, keeping the PWM frequency output, if not,
further determining the real voltage current phase difference
Figure FDA0002260922480000032
And if the phase difference exceeds the effective range of the phase difference control, the frequency is swept again and locked, and if not, PID operation is carried out to accurately adjust the output frequency of the PWM.
3. An apparatus for ultrasonic power supply phase difference detection based on a combined controller using the method of claim 1 or 2, wherein: the current sensor circuit comprises a current sensor (1), the output end of the current sensor (1) is grounded through a sampling resistor R3, and the voltage sensor circuit comprises a voltage sensor (2) and a differential amplification circuit; the first input end of the phase detection circuit is connected with the output end of the current sensor (1), and the first output end of the phase detection circuit is connected with one input end of the FPGA (3) chip; the second input end of the phase detection circuit is connected with the output end of the voltage sensor circuit, and the second output end of the phase detection circuit is connected with the other input end of the FPGA (3) chip; the output end of the current sensor (1) and the output end of the voltage sensor (2) are further connected with two input ends of a DSP (4) chip, and the FPGA (3) chip and the DSP (4) chip are connected with each other.
4. The ultrasonic power supply phase difference detection device based on the combined controller according to claim 3, characterized in that: the input end of the current sensor (1) is used for being connected with a current amplifier, and the input end of the voltage sensor (2) is used for being connected with a controlled voltage source or a signal generator.
5. The ultrasonic power supply phase difference detection device based on the combined controller according to claim 3, characterized in that:
the phase detection circuit comprises a first impedance isolation circuit (5), a first bias circuit (6), a first voltage comparator circuit (7) and a first level conversion circuit (8) which are sequentially arranged between the first input end and the first output end;
the circuit also comprises a second impedance isolation circuit (9), a second bias circuit (10), a second voltage comparator circuit (11) and a second level conversion circuit (12) which are sequentially arranged between the second input end and the second output end.
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