CN106936306B

CN106936306B - Multi-state totem PFC circuit

Info

Publication number: CN106936306B
Application number: CN201511026504.1A
Authority: CN
Inventors: 武志贤
Original assignee: Huawei Technologies Co Ltd
Current assignee: Huawei Technologies Co Ltd
Priority date: 2015-12-30
Filing date: 2015-12-30
Publication date: 2020-02-21
Anticipated expiration: 2035-12-30
Also published as: CN106936306A

Abstract

The invention provides a multi-state totem PFC circuit, which comprises an input power supply, a rectifier inductor and a multi-state switch; one end of the rectifying inductor is connected with an input power supply, and the other end of the rectifying inductor is connected with the multi-state switch; the multi-state switch comprises a coupling inductor and at least a first switch bridge arm and a second switch bridge arm which are connected in parallel; the coupling inductor comprises at least a first winding and a second winding which are coupled with each other, and the other end of the rectifying inductor is connected with one ends of the first winding and the second winding; the other end of the first winding is connected with the first switch bridge arm, and the other end of the second winding is connected with the second switch bridge arm; the multi-state totem PFC circuit further comprises a magnetic balance control circuit, and the magnetic balance control circuit is used for carrying out magnetic balance control on the coupling inductor. The multi-state totem PFC circuit can realize the magnetic balance control of the coupling inductor and has higher efficiency.

Description

Multi-state totem PFC circuit

Technical Field

The invention relates to the technical field of power conversion, in particular to a multi-state totem PFC circuit.

Background

In the field of power conversion technology, high efficiency and high power density are always the development directions pursued by power converters. In order to improve the efficiency and power density of the power module, the method adopted generally is to reduce the volume of passive devices such as capacitors and inductors by adopting a high-frequency switching tube, and although the volume and loss of the passive devices are reduced by adopting the high-frequency switching tube, the switching loss of the switching tube is increased, and the efficiency improvement effect is not obvious. The best approach is to increase the inductor-capacitor frequency while keeping the switching frequency low, which reduces both the switching losses and the inductor-capacitor volume. The multi-state switch technology can simultaneously meet the conditions, the effect of staggered parallel connection is realized through the coupling inductors, the frequency of the inductance-capacitance passive device is increased by times under the condition of keeping low switching frequency, the loss of the switch and the volume of the passive device can be reduced, and the efficiency and the power density of the power converter are effectively improved.

Currently, in the application of Power converters, a Power Factor Correction (PFC) circuit is one of the single-phase PFC topologies with higher efficiency. Therefore, multi-state switching techniques can be combined with totem PFC circuits to further increase the efficiency and power density of the power converter. Under the condition that the multi-state totem PFC circuit is completely symmetrical, the primary and secondary windings of the coupling inductor have the same number of turns, so that the multi-state totem PFC circuit theoretically has the characteristic of natural current equalization, but direct current bias can be generated in the current of the coupling inductor winding due to the existence of factors such as different dead time, different switching speeds, different series equivalent impedances, noise introduced by a feedback loop and the like. The dc bias increases the losses of the winding and the core, causing the coupling inductor to heat up severely, resulting in reduced efficiency. When the bias exceeds the hysteresis variation range allowed by the magnetic core, the coupling inductor is saturated magnetically, and the magnetic saturation can cause the problems of damage of the coupling inductor, damage of a connected power switch tube and the like.

In the magnetic balance control of the multi-state switch coupling inductor, the common practice is to increase the air gap of the magnetic core and increase the volume of the coupling inductor to avoid saturation, which cannot meet the purpose of improving the power density. Therefore, the magnetic balance control of the coupling inductance in the multi-state totem PFC circuit is one problem to be solved by applying the multi-state switch.

Disclosure of Invention

The invention provides a multi-state totem PFC circuit, which aims to reduce direct current bias, improve the magnetic balance of coupling inductance in the multi-state totem PFC circuit, avoid magnetic core saturation as much as possible and further improve the efficiency and power density of the multi-state totem PFC circuit.

The invention provides a multi-state totem PFC circuit in a first aspect, which comprises an input power supply, a rectifier inductor, a multi-state switch, a first rectifier diode and a second rectifier diode; one end of the rectifying inductor is connected with one end of the input power supply, and the other end of the rectifying inductor is connected with the multi-state switch; the multi-state switch comprises a coupling inductor and at least a first switch bridge arm and a second switch bridge arm which are connected in parallel; the coupling inductor comprises at least a first winding and a second winding which are coupled with each other, wherein the other end of the rectifying inductor is connected with one ends of the first winding and the second winding; the first switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a first node is arranged between the upper switch tube and the lower switch tube of the first switch bridge arm; the second switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a second node is arranged between the upper switch tube and the lower switch tube of the second switch bridge arm; the other end of the first winding is connected with the first node, and the other end of the second winding is connected with the second node; the anode of the first rectifier diode is connected with the other end of the input power supply, and the cathode of the first rectifier diode is connected with one ends of the first switch bridge arm and the second switch bridge arm; the anode of the second rectifier diode is connected with the other ends of the first switch bridge arm and the second switch bridge arm, and the cathode of the second rectifier diode is connected with the other end of the input power supply; the multi-state totem PFC circuit further comprises a magnetic balance control circuit, wherein the magnetic balance control circuit comprises a feedback control module, a wave-generating module and a magnetic balance control module which are sequentially connected;

the feedback control module is also connected with two ends of the input power supply and is used for acquiring an input voltage sampling value and an input current sampling value of the multi-state totem PFC circuit; the feedback control module is also connected with two ends of the first switch bridge arm and the second switch bridge arm and is used for acquiring an output voltage sampling value of the multi-state totem PFC circuit; the feedback control module is also used for carrying out difference operation on the output voltage sampling value and the output voltage reference value, further carrying out output voltage compensation operation on a difference operation result to obtain an amplitude value of an output current reference value, further multiplying the amplitude value of the input current reference value by the input voltage sampling value, and dividing the amplitude value by the square of the input voltage sampling value to obtain an input current compensation value by calculation;

the wave generation module is further connected with the first switch bridge arm and is used for generating a first pulse width modulation signal and a second pulse width modulation signal by taking the input current compensation value as a modulation wave, wherein the first pulse width modulation signal is used for driving an upper switch tube of the first switch bridge arm, the second pulse width modulation signal is used for driving a lower switch tube of the first switch bridge arm, the first pulse width modulation signal and the second pulse width modulation signal are complementary, and a certain dead time exists between the first pulse width modulation signal and the second pulse width modulation signal, so that the upper switch tube and the lower switch tube of the first switch bridge arm can be driven to be alternately conducted through the first pulse width modulation signal and the second pulse width modulation signal;

the magnetic balance control module is also connected with the second switch bridge arm and is used for phase shifting the first pulse width modulation signal by a preset angle to obtain a third pulse width modulation signal with the same duty ratio as the first pulse width modulation signal, and phase-shifting the second pulse width modulation signal by a preset angle to obtain a fourth pulse width modulation signal with the same duty ratio as the second pulse width modulation signal, the third pulse width modulation signal is used for driving an upper switching tube of the second switching bridge arm, the fourth pulse width modulation signal is used for driving a lower switching tube of the second switching bridge arm, and similarly, the third pulse width modulation signal is complementary with the fourth pulse width modulation signal, and a certain dead time exists between the third pulse width modulation signal and the fourth pulse width modulation signal, therefore, the upper switching tube and the lower switching tube of the second switching bridge arm can be driven to be alternately conducted through the third pulse width modulation signal and the fourth pulse width modulation signal.

The multi-state totem PFC circuit phase-shifts the first pulse width modulation signal by a preset angle through the magnetic balance control module to obtain a third pulse width modulation signal with the same duty ratio, and phase-shifting the second pulse width modulation signal by a preset angle to obtain a fourth pulse width modulation signal with the same duty ratio, so that the duty ratio of the driving signal of the upper switching tube of the first switching bridge arm is the same as that of the driving signal of the upper switching tube of the second switching bridge arm, and the duty ratio of the driving signal of the lower switching tube of the first switching bridge arm is the same as that of the driving signal of the lower switching tube of the second switching bridge arm, therefore, the differential mode current in the first winding and the second winding of the coupling inductor can be effectively reduced, the flux linkage balance of the coupling inductor is ensured, the magnetic core loss of the coupling inductor is reduced, and the efficiency of the multi-state totem circuit is improved.

With reference to the first aspect, it should be noted that the feedback control module includes a first difference operator, an output voltage compensator, a reference current calculator, a second difference operator, and an input current compensator, which are connected in sequence;

the first difference operator is used for performing difference operation on the output voltage sampling value and the output voltage reference value;

the output voltage compensator is used for carrying out output voltage compensation operation on the output of the first difference value operator to obtain the amplitude of the input current reference value;

the reference current calculator is used for multiplying the amplitude of the input current reference value by the input voltage sampling value and dividing the multiplied amplitude by the square of the input voltage sampling value to obtain an input current reference value;

the second difference operator is used for performing difference operation on the input current reference value and the input current sampling value;

and the input current compensator is used for performing input current compensation operation on the output of the second difference value operator to obtain an input current compensation value.

Further, the reference current calculator comprises a gain operator, a square operator, a multiplier and a divider, wherein the gain operator is used for performing gain operation on the input voltage sampling value to obtain a gain value of the input voltage sampling value; the square arithmetic unit is used for carrying out square arithmetic on the input voltage sampling value to obtain the square of the input voltage sampling value; the multiplier is used for calculating the product of the gain value of the input voltage sampling value and the amplitude value of the input current reference value; the divider is used for dividing the product of the gain value of the input voltage sampling value and the amplitude value of the input current reference value by the square of the input voltage sampling value to obtain the input current reference value.

With reference to the first aspect, it should be noted that the wave-sending module includes a first output end and a second output end, where the first output end is configured to output the first pulse width modulation signal, and the second output end is configured to output the second pulse width modulation signal; the magnetic balance control module comprises a first delayer and a second delayer; the first delayer is connected with the first output end and is used for phase shifting the first pulse width modulation signal by a preset angle to obtain a third pulse width modulation signal with the same duty ratio; and the second delayer is connected with the second output end and used for phase shifting the second pulse width modulation signal by a preset angle to obtain a fourth pulse width modulation signal with the same duty ratio.

Optionally, the wave-sending module includes a first output end and a second output end, where the first output end is configured to output the third pwm signal, and the second output end is configured to output the fourth pwm signal; the magnetic balance control module comprises a first delayer and a second delayer, the first delayer is connected with the first output end, the second delayer is connected with the second output end, the first delayer is used for phase-shifting the third pulse width modulation signal by a preset angle to obtain a first pulse width modulation signal with the same duty ratio, and the second delayer is used for phase-shifting the fourth pulse width modulation signal by a preset angle to obtain a second pulse width modulation signal with the same duty ratio.

With reference to the first aspect, it may be understood that the multi-state switch may include N switch bridge arms connected in parallel, the coupling inductor includes N windings coupled to each other, the N windings are respectively connected to the N switch bridge arms in a one-to-one correspondence, and a phase shift between driving signals of two adjacent switch bridge arms is 360/N degrees, where N is an integer greater than or equal to 2.

Optionally, the multi-state switch includes N switch bridge arms connected in parallel, the coupling inductor includes N windings coupled to each other, the N windings are respectively connected to the N switch bridge arms in a one-to-one correspondence, and a phase shift between carriers of driving signals of two adjacent switch bridge arms is 360/N degrees, where N is an integer greater than or equal to 2.

When the multi-state switch comprises N switch bridge arms which are mutually connected in parallel, the duty ratio of a driving signal of one switch bridge arm is fixed to be unchanged, and then the driving signals with the fixed duty ratio are sequentially phase-shifted by N-1 360/N degrees to obtain the driving signals of the other N-1 switch bridge arms which are mutually connected in parallel, so that the driving signals of the upper switch tubes of the N switch bridge arms have the same duty ratio, and the driving signals of the lower switch tubes of the N switch bridge arms also have the same duty ratio, thereby effectively reducing the magnitude of differential mode current in the coupling inductor, ensuring the magnetic chain balance of the coupling inductor, reducing the magnetic core loss of the coupling inductor and improving the efficiency of the multi-state totem PFC circuit.

The invention provides a coupling inductance magnetic balance control method of a multi-state totem PFC circuit, wherein the multi-state totem PFC circuit comprises an input power supply, a rectifier inductance, a multi-state switch, a first rectifier diode and a second rectifier diode; one end of the rectifying inductor is connected with one end of the input power supply, and the other end of the rectifying inductor is connected with the multi-state switch; the multi-state switch comprises a coupling inductor and at least a first switch bridge arm and a second switch bridge arm which are connected in parallel; the coupling inductor comprises at least a first winding and a second winding which are coupled with each other, wherein the other end of the rectifying inductor is connected with one ends of the first winding and the second winding; the first switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a first node is arranged between the upper switch tube and the lower switch tube of the first switch bridge arm; the second switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a second node is arranged between the upper switch tube and the lower switch tube of the second switch bridge arm; the other end of the first winding is connected with the first node, and the other end of the second winding is connected with the second node; the anode of the first rectifier diode is connected with the other end of the input power supply, and the cathode of the first rectifier diode is connected with one ends of the first switch bridge arm and the second switch bridge arm; the anode of the second rectifier diode is connected with the other ends of the first switch bridge arm and the second switch bridge arm, and the cathode of the second rectifier diode is connected with the other end of the input power supply; the method comprises the following steps:

obtaining an input voltage sampling value, an input current sampling value and an output voltage sampling value of the multi-state totem PFC circuit, performing difference operation on the output voltage sampling value and the output voltage reference value, further performing output voltage compensation operation on a difference operation result to obtain an amplitude value of the output current reference value, further multiplying the amplitude value of the input current reference value and the input voltage sampling value, and dividing the multiplication value by the square of the input voltage sampling value to obtain an input current compensation value;

generating a first pulse width modulation signal and a second pulse width modulation signal by taking the input current compensation value as a modulation wave, wherein the first pulse width modulation signal is used for driving an upper switching tube of the first switching bridge arm, and the second pulse width modulation signal is used for driving a lower switching tube of the first switching bridge arm, the first pulse width modulation signal and the second pulse width modulation signal are complementary, and a certain dead time exists between the first pulse width modulation signal and the second pulse width modulation signal, so that the upper switching tube and the lower switching tube of the first switching bridge arm can be driven to be alternately conducted through the first pulse width modulation signal and the second pulse width modulation signal;

the first pulse width modulation signal is subjected to phase shift by a preset angle to obtain a third pulse width modulation signal with the same duty ratio as the first pulse width modulation signal, the second pulse width modulation signal is subjected to phase shift by a preset angle to obtain a fourth pulse width modulation signal with the same duty ratio as the second pulse width modulation signal, the third pulse width modulation signal is used for driving an upper switching tube of the second switching bridge arm, the fourth pulse width modulation signal is used for driving a lower switching tube of the second switching bridge arm, similarly, the third pulse width modulation signal is complementary to the fourth pulse width modulation signal, and a certain dead time exists between the third pulse width modulation signal and the fourth pulse width modulation signal, so that the upper switching tube and the lower switching tube of the second switching bridge arm can be driven to be alternately conducted through the third pulse width modulation signal and the fourth pulse width modulation signal.

The coupling inductance magnetic balance control method of the multi-state totem PFC circuit obtains a third pulse width modulation signal with the same duty ratio by phase-shifting the first pulse width modulation signal by a preset angle, and phase-shifting the second pulse width modulation signal by a preset angle to obtain a fourth pulse width modulation signal with the same duty ratio, so that the duty ratio of the driving signal of the upper switching tube of the first switching bridge arm is the same as that of the driving signal of the upper switching tube of the second switching bridge arm, and the duty ratio of the driving signal of the lower switching tube of the first switching bridge arm is the same as that of the driving signal of the lower switching tube of the second switching bridge arm, therefore, the differential mode current in the first winding and the second winding of the coupling inductor can be effectively reduced, the flux linkage balance of the coupling inductor is ensured, the magnetic core loss of the coupling inductor is reduced, and the efficiency of the multi-state totem circuit is improved.

With reference to the second aspect, it should be noted that the calculating the input current compensation value includes:

performing difference operation on the output voltage sampling value and the output voltage reference value, and obtaining the amplitude of the input current reference value through output voltage compensation operation;

multiplying the amplitude of the input current reference value by the input voltage sampling value, and dividing by the square of the input voltage sampling value to obtain an input current reference value;

and carrying out difference operation on the input current reference value and the input current sampling value, and obtaining an input current compensation value through input current compensation operation.

Further, the multiplying the amplitude of the input current reference value by the input voltage sampling value and dividing by the square of the input voltage sampling value to obtain the input current reference value includes:

performing gain operation on the input voltage sampling value to obtain a gain value of the input voltage sampling value;

carrying out square operation on the input voltage sampling value to obtain the square of the input voltage sampling value;

calculating the product of the gain value of the input voltage sampling value and the amplitude value of the input current reference value;

and dividing the product of the gain value of the input voltage sampling value and the amplitude value of the input current reference value by the square of the input voltage sampling value to obtain the input current reference value.

With reference to the second aspect, it can be understood that the multi-state switch may include N switch bridge arms connected in parallel, the coupling inductor includes N windings coupled to each other, the N windings are respectively connected to the N switch bridge arms in a one-to-one correspondence, and a phase shift between driving signals of two adjacent switch bridge arms is 360/N degrees, where N is an integer greater than or equal to 2.

When the multi-state switch comprises N switch bridge arms which are mutually connected in parallel, the duty ratio of a driving signal of one switch bridge arm is fixed to be unchanged, and then the driving signals with the fixed duty ratio are sequentially phase-shifted by N-1 360/N degrees to obtain the driving signals of the other N-1 switch bridge arms which are mutually connected in parallel, so that the driving signals of the upper switch tubes of the N switch bridge arms have the same duty ratio, and the driving signals of the lower switch tubes of the N switch bridge arms also have the same duty ratio, thereby effectively reducing the magnitude of differential mode current in the coupling inductor, ensuring the magnetic chain balance of the coupling inductor, reducing the magnetic core loss of the coupling inductor and improving the efficiency of the multi-state totem circuit.

The invention provides a multi-state totem PFC circuit in a third aspect, which comprises an input power supply, a rectifier inductor, a multi-state switch, a first rectifier diode and a second rectifier diode; one end of the rectifying inductor is connected with one end of the input power supply, and the other end of the rectifying inductor is connected with the multi-state switch; the multi-state switch comprises a coupling inductor and at least a first switch bridge arm and a second switch bridge arm which are connected in parallel; the coupling inductor comprises at least a first winding and a second winding which are coupled with each other, wherein the other end of the rectifying inductor is connected with one ends of the first winding and the second winding; the first switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a first node is arranged between the upper switch tube and the lower switch tube of the first switch bridge arm; the second switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a second node is arranged between the upper switch tube and the lower switch tube of the second switch bridge arm; the other end of the first winding is connected with the first node, and the other end of the second winding is connected with the second node; the anode of the first rectifier diode is connected with the other end of the input power supply, and the cathode of the first rectifier diode is connected with one ends of the first switch bridge arm and the second switch bridge arm; the anode of the second rectifier diode is connected with the other ends of the first switch bridge arm and the second switch bridge arm, and the cathode of the second rectifier diode is connected with the other end of the input power supply; the multi-state totem PFC circuit further comprises a magnetic balance control circuit, wherein the magnetic balance control circuit comprises a feedback control module, a wave-generating module and a magnetic balance control module which are sequentially connected;

the wave sending module is used for generating a first pulse width modulation signal, a second pulse width modulation signal, a third pulse width modulation signal and a fourth pulse width modulation signal by taking the input current compensation value as a modulation wave; the first pulse width modulation signal is used for driving an upper switching tube of the first switching bridge arm, the second pulse width modulation signal is used for driving a lower switching tube of the first switching bridge arm, the third pulse width modulation signal is used for driving an upper switching tube of the second switching bridge arm, and the fourth pulse width modulation signal is used for driving a lower switching tube of the second switching bridge arm; the first pulse width modulation signal and the second pulse width modulation signal are complementary, a certain dead time exists between the first pulse width modulation signal and the second pulse width modulation signal, the third pulse width modulation signal and the fourth pulse width modulation signal are complementary, and a certain dead time exists between the third pulse width modulation signal and the fourth pulse width modulation signal, so that the upper switching tube and the lower switching tube of the first switching bridge arm can be driven to be alternately conducted through the first pulse width modulation signal and the second pulse width modulation signal, and the upper switching tube and the lower switching tube of the second switching bridge arm can be driven to be alternately conducted through the third pulse width modulation signal and the fourth pulse width modulation signal;

the magnetic balance control module comprises a differential mode current compensation submodule, an adjustment meter operator module and a duty ratio adjustment submodule which are sequentially connected; the differential mode current compensation submodule is also connected with the first winding and the second winding and is used for acquiring differential mode current sampling values of the first winding and the second winding, performing differential operation on the differential mode current sampling values and a differential mode current reference value, further performing differential mode current regulation operation on the result of the differential operation, and calculating to obtain a differential mode current compensation value;

the regulating quantity operator module is also connected with the feedback control module and is used for calculating the duty ratio regulating quantity of each switching tube in the first switching bridge arm or/and the second switching bridge arm according to the direction of the differential mode current sampling value, the positive and negative of the input voltage sampling value and the differential mode current compensation value;

the duty ratio adjusting submodule is also connected with the wave sending module, the first switch bridge arm and the second switch bridge arm and is used for respectively superposing the duty ratio adjusting quantity of each switch tube of the first switch bridge arm on the first pulse width modulation signal and the second pulse width modulation signal so as to drive the upper switch tube and the lower switch tube of the first switch bridge arm to be alternately conducted; and/or respectively superposing the duty ratio regulating quantity of each switching tube in the second switching bridge arm on the third pulse width modulation signal and the fourth pulse width modulation signal so as to drive the upper switching tube and the lower switching tube of the second switching bridge arm to be alternately conducted.

The multi-state totem PFC circuit is characterized in that the duty ratio of a driving signal of a switching tube of one of the at least first switching bridge arm and the second switching bridge arm is fixed to be unchanged, a differential mode current sampling value in the coupling inductor is obtained and is combined with a differential mode current reference value to calculate a differential mode current compensation value, and then the duty ratio regulating quantity of the driving signal of the switching tube of the other switching bridge arm in the at least first switching bridge arm and the second switching bridge arm is calculated according to the direction of the differential mode current sampling value, the positive and negative of the input voltage sampling value and the differential mode current compensation value, and is respectively superposed to the driving signal corresponding to each switching tube in the other switching bridge arms; or directly calculating the duty ratio regulating quantity of the driving signal of the switching tube in each of the at least first switching bridge arm and the second switching bridge arm according to the direction of the differential mode current sampling value, the positive and negative of the input voltage sampling value and the differential mode current compensation value, and respectively superposing the duty ratio regulating quantity to the driving signal corresponding to each switching tube of each switching bridge arm, so that the difference between the duty ratios of the driving signals of the upper switching tubes of two adjacent switching bridge arms is effectively reduced, the difference between the duty ratios of the driving signals of the lower switching tubes of two adjacent switching bridge arms is reduced, the differential mode current in the coupling inductor is further effectively reduced, the coupling inductor is ensured to have better magnetic chain balance, the magnetic core loss of the coupling inductor is reduced, and the efficiency of the multi-state totem PFC circuit is improved.

With reference to the third aspect, it should be noted that the feedback control module includes a first difference operator, an output voltage compensator, a reference current calculator, a second difference operator, and an input current compensator, which are connected in sequence;

With reference to the third aspect, it should be noted that the differential mode current compensation submodule includes a third difference operator, a fourth difference operator, and a differential mode current controller, which are connected in sequence;

the third difference operator is used for performing difference operation on the first current on the first winding and the second current on the second winding to obtain a differential mode current sampling value;

the fourth difference operator is used for performing difference operation on the differential mode current sampling value and the differential mode current reference value;

and the differential mode current controller is used for carrying out differential mode current regulation operation on the output of the fourth difference value operator to obtain a differential mode current compensation value.

Optionally, the differential mode current compensation submodule includes a third difference operator, a differential mode current controller, a fourth difference operator and a gain operator, which are connected in sequence;

the differential mode current controller is used for carrying out differential mode current regulation operation on the differential mode current sampling value;

the fourth difference operator is used for performing difference operation on the output of the differential mode current controller and the differential mode current reference value;

and the gain arithmetic unit is used for carrying out gain arithmetic on the output of the fourth difference arithmetic unit to obtain a differential mode current compensation value.

With reference to the third aspect, it should be noted that the adjustment amount operator module includes a sign determination unit, an input voltage state determination unit, a truth table unit, and a multiplication unit;

the sign judgment unit is used for judging the direction of the differential mode current sampling value;

the input voltage state judging unit is used for judging the positive and negative of the input voltage sampling value;

the truth table unit is used for determining the truth table output state of a switching tube needing duty ratio adjustment in the first switching bridge arm or/and the second switching bridge arm according to the direction of the differential mode current sampling value and the positive and negative of the input voltage sampling value;

and the multiplication operation unit is used for multiplying the truth table output state by the differential mode current compensation value to obtain the duty ratio regulating quantity of each switching tube in the first switching bridge arm or/and the second switching bridge arm.

With reference to the third aspect, it can be understood that the flux linkage change of the coupling inductor caused by the differential mode current corresponding to the differential mode current sampling value is equal to the accumulation of the difference of the duty ratios of the driving signals of the switching tubes at the same position of the first switching leg and the second switching leg in one switching period; the switching tubes at the same position refer to upper switching tubes of the first switching arm and the second switching arm or lower switching tubes of the first switching arm and the second switching arm, and the switching period refers to the period of the driving signal.

The multi-state totem PFC circuit can control the positive and negative and the magnitude of differential mode current by controlling the difference of the duty ratios of the driving signals of the switching tubes at the same positions of the first switching bridge arm and the second switching bridge arm in the same switching period, and further can reduce the magnitude of the differential mode current by reducing the difference of the duty ratios of the driving signals of the switching tubes at the same positions of the first switching bridge arm and the second switching bridge arm in the same switching period, so that the coupling inductor is ensured to have better magnetic chain balance, the magnetic core loss of the coupling inductor is reduced, and the efficiency of the multi-state totem PFC circuit is improved.

The fourth aspect of the invention provides a coupling inductance magnetic balance control method of a multi-state totem PFC circuit, wherein the multi-state totem PFC circuit comprises an input power supply, a rectifier inductance, a multi-state switch, a first rectifier diode and a second rectifier diode; one end of the rectifying inductor is connected with one end of the input power supply, and the other end of the rectifying inductor is connected with the multi-state switch; the multi-state switch comprises a coupling inductor and at least a first switch bridge arm and a second switch bridge arm which are connected in parallel; the coupling inductor comprises at least a first winding and a second winding which are coupled with each other, wherein the other end of the rectifying inductor is connected with one ends of the first winding and the second winding; the first switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a first node is arranged between the upper switch tube and the lower switch tube of the first switch bridge arm; the second switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a second node is arranged between the upper switch tube and the lower switch tube of the second switch bridge arm; the other end of the first winding is connected with the first node, and the other end of the second winding is connected with the second node; the anode of the first rectifier diode is connected with the other end of the input power supply, and the cathode of the first rectifier diode is connected with one ends of the first switch bridge arm and the second switch bridge arm; the anode of the second rectifier diode is connected with the other ends of the first switch bridge arm and the second switch bridge arm, and the cathode of the second rectifier diode is connected with the other end of the input power supply; the method comprises the following steps:

generating a first pulse width modulation signal, a second pulse width modulation signal, a third pulse width modulation signal and a fourth pulse width modulation signal by using the input current compensation value as a modulation wave, wherein the first pulse width modulation signal is used for driving an upper switching tube of the first switching bridge arm, the second pulse width modulation signal is used for driving a lower switching tube of the first switching bridge arm, the third pulse width modulation signal is used for driving an upper switching tube of the second switching bridge arm, and the fourth pulse width modulation signal is used for driving a lower switching tube of the second switching bridge arm; the first pulse width modulation signal and the second pulse width modulation signal are complementary, a certain dead time exists between the first pulse width modulation signal and the second pulse width modulation signal, the third pulse width modulation signal and the fourth pulse width modulation signal are complementary, and a certain dead time exists between the third pulse width modulation signal and the fourth pulse width modulation signal, so that the upper switching tube and the lower switching tube of the first switching bridge arm can be driven to be alternately conducted through the first pulse width modulation signal and the second pulse width modulation signal, and the upper switching tube and the lower switching tube of the second switching bridge arm can be driven to be alternately conducted through the third pulse width modulation signal and the fourth pulse width modulation signal;

obtaining differential mode current sampling values of the first winding and the second winding, performing difference operation on the differential mode current sampling values and a differential mode current reference value, further performing differential mode current regulation operation on a result of the difference operation, and calculating to obtain a differential mode current compensation value;

calculating the duty ratio regulating quantity of each switching tube in the first switching bridge arm or/and the second switching bridge arm according to the direction of the differential mode current sampling value, the positive and negative of the input voltage sampling value and the differential mode current compensation value;

and respectively superposing the duty ratio regulating quantity of each switching tube of the first switching bridge arm on the first pulse width modulation signal and the second pulse width modulation signal, or/and respectively superposing the duty ratio regulating quantity of each switching tube of the second switching bridge arm on the third pulse width modulation signal and the fourth pulse width modulation signal.

The method for controlling the coupling inductance magnetic balance of the multi-state totem PFC circuit comprises the steps of fixing the duty ratio of a driving signal of a switching tube of one of at least a first switching bridge arm and a second switching bridge arm to be unchanged, obtaining a differential mode current sampling value in the coupling inductance, calculating a differential mode current compensation value by combining a differential mode current reference value, further calculating duty ratio regulating quantities of the driving signals of the switching tubes of the other switching bridge arms of the at least first switching bridge arm and the second switching bridge arm according to the direction of the differential mode current sampling value, the positive and negative of the input voltage sampling value and the differential mode current compensation value, and respectively superposing the duty ratio regulating quantities to the driving signals corresponding to each switching tube of the other switching bridge arms; or directly calculating the duty ratio regulating quantity of the driving signal of the switching tube in each of the at least first switching bridge arm and the second switching bridge arm according to the direction of the differential mode current sampling value, the positive and negative of the input voltage sampling value and the differential mode current compensation value, and respectively superposing the duty ratio regulating quantity to the driving signal corresponding to each switching tube of each switching bridge arm, so that the difference between the duty ratios of the driving signals of the upper switching tubes of two adjacent switching bridge arms is effectively reduced, the difference between the duty ratios of the driving signals of the lower switching tubes of two adjacent switching bridge arms is reduced, the differential mode current in the coupling inductor is further effectively reduced, the coupling inductor is ensured to have better magnetic chain balance, the magnetic core loss of the coupling inductor is reduced, and the efficiency of the multi-state totem PFC circuit is improved.

With reference to the fourth aspect, it should be noted that the calculating the input current compensation value includes:

With reference to the fourth aspect, it should be noted that the calculating the differential mode current compensation value includes:

performing difference operation on the first current on the first winding and the second current on the second winding to obtain a differential mode current sampling value;

and carrying out difference operation on the differential mode current sampling value and the differential mode current reference value, and obtaining a differential mode current compensation value through differential mode current regulation operation.

Optionally, the calculating the differential mode current compensation value includes:

and carrying out differential mode current regulation operation on the differential mode current sampling value, carrying out differential operation on the differential mode current regulation operation result and a differential mode current reference value, and further obtaining a differential mode current compensation value through gain operation.

With reference to the fourth aspect, it should be noted that the calculating a duty ratio adjustment amount of each switching tube in the first switching leg or/and the second switching leg includes:

judging the direction of the differential mode current sampling value and the positive and negative of the input voltage sampling value;

inquiring a preset truth table according to the direction of the differential mode current sampling value and the positive and negative of the input voltage sampling value, and determining the truth table output state of a switching tube needing to adjust the duty ratio in the first switching bridge arm or/and the second switching bridge arm;

and multiplying the output state of the truth table by the differential mode current compensation value to obtain the duty ratio regulating quantity of each switching tube in the first switching bridge arm or/and the second switching bridge arm.

With reference to the fourth aspect, it can be understood that the flux linkage change of the coupling inductor caused by the differential mode current corresponding to the differential mode current sampling value is equal to the accumulation of the difference of the duty ratios of the driving signals of the switching tubes at the same position of the first switching leg and the second switching leg in one switching period; the switching tubes at the same position refer to upper switching tubes of the first switching arm and the second switching arm or lower switching tubes of the first switching arm and the second switching arm, and the switching period refers to the period of the driving signal.

According to the method, the positive and negative of the differential mode current can be controlled and the magnitude of the differential mode current can be controlled by controlling the difference of the duty ratios of the driving signals of the switching tubes at the same positions of the first switching bridge arm and the second switching bridge arm in the same switching period, and further the magnitude of the differential mode current can be reduced by reducing the difference of the duty ratios of the driving signals of the switching tubes at the same positions of the first switching bridge arm and the second switching bridge arm in the same switching period, so that the coupling inductance is ensured to have better flux linkage balance, the magnetic core loss of the coupling inductance is reduced, and the efficiency of the multi-state totem PFC circuit is improved.

The fifth aspect of the invention provides a multi-state totem PFC circuit, which comprises an input power supply, a rectifier inductor, a multi-state switch, a first rectifier diode and a second rectifier diode; one end of the rectifying inductor is connected with one end of the input power supply, and the other end of the rectifying inductor is connected with the multi-state switch; the multi-state switch comprises a coupling inductor and at least a first switch bridge arm and a second switch bridge arm which are connected in parallel; the coupling inductor comprises at least a first winding and a second winding which are coupled with each other, wherein the other end of the rectifying inductor is connected with one ends of the first winding and the second winding; the first switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a first node is arranged between the upper switch tube and the lower switch tube of the first switch bridge arm; the second switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a second node is arranged between the upper switch tube and the lower switch tube of the second switch bridge arm; the other end of the first winding is connected with the first node, and the other end of the second winding is connected with the second node; the anode of the first rectifier diode is connected with the other end of the input power supply, and the cathode of the first rectifier diode is connected with one ends of the first switch bridge arm and the second switch bridge arm; the anode of the second rectifier diode is connected with the other ends of the first switch bridge arm and the second switch bridge arm, and the cathode of the second rectifier diode is connected with the other end of the input power supply; the multi-state totem PFC circuit further comprises a magnetic balance control circuit, the magnetic balance control circuit comprises a feedback control module, a magnetic balance control module, a modulating wave generation module and a wave sending module, and the feedback control module and the magnetic balance control module are connected with the wave sending module through the modulating wave generation module;

the magnetic balance control module is also connected with the first winding and the second winding and is used for acquiring differential mode current sampling values of the first winding and the second winding, performing difference operation on the differential mode current sampling values and a differential mode current reference value, further performing differential mode current regulation operation on a result of the difference operation, and calculating to obtain a differential mode current compensation value;

the modulation wave generation module is used for superposing the differential mode current compensation value on the input current compensation value to generate a modulation wave;

the wave sending module is further connected with the first switch bridge arm and the second switch bridge arm and is used for generating a first pulse width modulation signal, a second pulse width modulation signal, a third pulse width modulation signal and a fourth pulse width modulation signal according to the modulation wave, wherein the first pulse width modulation signal is used for driving an upper switch tube of the first switch bridge arm, the second pulse width modulation signal is used for driving a lower switch tube of the first switch bridge arm, the third pulse width modulation signal is used for driving an upper switch tube of the second switch bridge arm, and the fourth pulse width modulation signal is used for driving a lower switch tube of the second switch bridge arm; the first pulse width modulation signal and the second pulse width modulation signal are complementary, a certain dead time exists between the first pulse width modulation signal and the second pulse width modulation signal, the third pulse width modulation signal and the fourth pulse width modulation signal are complementary, and a certain dead time exists between the third pulse width modulation signal and the fourth pulse width modulation signal, so that the upper switching tube and the lower switching tube of the first switching bridge arm can be driven to be alternately conducted through the first pulse width modulation signal and the second pulse width modulation signal, and the upper switching tube and the lower switching tube of the second switching bridge arm can be driven to be alternately conducted through the third pulse width modulation signal and the fourth pulse width modulation signal.

The multi-state totem PFC circuit obtains a differential mode current compensation value by obtaining differential mode current sampling values of the first winding and the second winding and combining with a differential mode current reference value to calculate, further superimposes the differential mode current compensation value on the input current compensation value as a modulation wave, generates the driving signals for driving the first switch bridge arm and the second switch bridge arm so as to change the modulation wave according to the change of the differential mode current sampling values, adjusts the duty ratio of each switch tube of the first switch bridge arm and the second switch bridge arm according to the change of the modulation wave, reduces the difference between the duty ratio of the driving signal of the upper switch tube of the first switch bridge arm and the duty ratio of the driving signal of the upper switch tube of the second switch bridge arm, and reduces the difference between the duty ratio of the driving signal of the lower switch tube of the first switch bridge arm and the duty ratio of the driving signal of the lower switch tube of the second switch bridge arm, and then effectively reduce the magnitude of differential mode current in the first winding and the second winding of the coupling inductor, ensure that the coupling inductor has better flux linkage balance, reduce the magnetic core loss of the coupling inductor, and improve the efficiency of the multi-state totem PFC circuit.

With reference to the fifth aspect, it should be noted that the feedback control module includes a first difference operator, an output voltage compensator, a reference current calculator, a second difference operator, and an input current compensator, which are connected in sequence;

With reference to the fifth aspect, it should be noted that the magnetic balance control module includes a third difference operator, a fourth difference operator, and a differential mode current controller, which are connected in sequence;

Optionally, the magnetic balance control module includes a third difference operator, a differential mode current controller, a fourth difference operator and a gain operator, which are connected in sequence;

With reference to the fifth aspect, it can be understood that a flux linkage change of the coupling inductor caused by a differential mode current corresponding to the differential mode current sampling value is equal to an accumulation of a difference of duty ratios of driving signals of switching tubes at the same position of the first switching leg and the second switching leg in one switching period; the switching tubes at the same position refer to upper switching tubes of the first switching arm and the second switching arm or lower switching tubes of the first switching arm and the second switching arm, and the switching period refers to the period of the driving signal.

The multi-state totem PFC circuit obtains the differential mode current sampling value, performs difference value operation on the differential mode current sampling value and the differential mode current reference value, further performs differential mode current regulation operation on the difference value operation result, calculates to obtain a differential mode current compensation value, further superimposes the differential mode current compensation value on the input current compensation value to serve as a modulation wave, and accordingly changes the modulation wave to regulate the difference of duty ratios of driving signals of the switching tubes at the same positions of the first switch bridge arm and the second switch bridge arm, further controls the magnitude of differential mode current in the coupling inductor, ensures that the coupling inductor has good magnetic chain balance, reduces the magnetic core loss of the coupling inductor, and improves the efficiency of the multi-state totem PFC circuit.

A sixth aspect of the present invention provides a method for controlling the magnetic balance of a coupling inductor of a multi-state totem PFC circuit, where the multi-state totem PFC circuit includes an input power supply, a rectifier inductor, a multi-state switch, a first rectifier diode, and a second rectifier diode; one end of the rectifying inductor is connected with one end of the input power supply, and the other end of the rectifying inductor is connected with the multi-state switch; the multi-state switch comprises a coupling inductor and at least a first switch bridge arm and a second switch bridge arm which are connected in parallel; the coupling inductor comprises at least a first winding and a second winding which are coupled with each other, wherein the other end of the rectifying inductor is connected with one ends of the first winding and the second winding; the first switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a first node is arranged between the upper switch tube and the lower switch tube of the first switch bridge arm; the second switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a second node is arranged between the upper switch tube and the lower switch tube of the second switch bridge arm; the other end of the first winding is connected with the first node, and the other end of the second winding is connected with the second node; the anode of the first rectifier diode is connected with the other end of the input power supply, and the cathode of the first rectifier diode is connected with one ends of the first switch bridge arm and the second switch bridge arm; the anode of the second rectifier diode is connected with the other ends of the first switch bridge arm and the second switch bridge arm, and the cathode of the second rectifier diode is connected with the other end of the input power supply; the method comprises the following steps:

superposing the differential mode current compensation value on the input current compensation value to generate a modulation wave;

generating a first pulse width modulation signal, a second pulse width modulation signal, a third pulse width modulation signal and a fourth pulse width modulation signal according to the modulation wave, wherein the first pulse width modulation signal is used for driving an upper switching tube of the first switching bridge arm, the second pulse width modulation signal is used for driving a lower switching tube of the first switching bridge arm, the third pulse width modulation signal is used for driving an upper switching tube of the second switching bridge arm, and the fourth pulse width modulation signal is used for driving a lower switching tube of the second switching bridge arm; the first pulse width modulation signal and the second pulse width modulation signal are complementary, a certain dead time exists between the first pulse width modulation signal and the second pulse width modulation signal, the third pulse width modulation signal and the fourth pulse width modulation signal are complementary, and a certain dead time exists between the third pulse width modulation signal and the fourth pulse width modulation signal, so that the upper switching tube and the lower switching tube of the first switching bridge arm can be driven to be alternately conducted through the first pulse width modulation signal and the second pulse width modulation signal, and the upper switching tube and the lower switching tube of the second switching bridge arm can be driven to be alternately conducted through the third pulse width modulation signal and the fourth pulse width modulation signal.

The coupling inductance magnetic balance control method of the multi-state totem PFC circuit comprises the steps of obtaining differential mode current sampling values of the first winding and the second winding, calculating to obtain differential mode current compensation values by combining with differential mode current reference values, further superposing the differential mode current compensation values on the input current compensation values to serve as modulation waves, generating driving signals for driving the first switch bridge arm and the second switch bridge arm, changing the modulation waves according to changes of the differential mode current sampling values, adjusting the duty ratio of each switch tube of the first switch bridge arm and the second switch bridge arm through changes of the modulation waves, reducing the difference between the duty ratio of the driving signals of the upper switch tube of the first switch bridge arm and the duty ratio of the driving signals of the upper switch tube of the second switch bridge arm, and reducing the difference between the duty ratio of the driving signals of the lower switch tube of the first switch bridge arm and the duty ratio of the driving signals of the lower switch tube of the second switch bridge arm The difference between the first winding and the second winding of the coupling inductor is effectively reduced, the coupling inductor is ensured to have better flux linkage balance, the magnetic core loss of the coupling inductor is reduced, and the efficiency of the multi-state totem PFC circuit is improved.

With reference to the sixth aspect, it should be noted that the calculating the input current compensation value includes:

With reference to the sixth aspect, it should be noted that the calculating the differential mode current compensation value includes:

With reference to the sixth aspect, it can be understood that the flux linkage change of the coupling inductor caused by the differential mode current corresponding to the differential mode current sampling value is equal to the accumulation of the difference of the duty ratios of the driving signals of the switching tubes at the same position of the first switching leg and the second switching leg in one switching period; the switching tubes at the same position refer to upper switching tubes of the first switching arm and the second switching arm or lower switching tubes of the first switching arm and the second switching arm, and the switching period refers to the period of the driving signal.

According to the method, the differential mode current sampling value is obtained, the differential mode current sampling value and the differential mode current reference value are subjected to difference value operation, then the differential mode current adjusting operation is carried out on the difference value operation result, the differential mode current compensation value is obtained through calculation, the differential mode current compensation value is superposed on the input current compensation value to serve as a modulation wave, the modulation wave is changed to adjust the difference of duty ratios of driving signals of the switching tubes at the same positions of the first switch bridge arm and the second switch bridge arm, the magnitude of the differential mode current in the coupling inductor is controlled, the coupling inductor is guaranteed to have good magnetic chain balance, the magnetic core loss of the coupling inductor is reduced, and the efficiency of the multi-state totem PFC circuit is improved.

Drawings

In order to more clearly illustrate the technical solutions in the embodiments of the present invention, the drawings used in the description of the embodiments will be briefly introduced below.

Fig. 1 is a schematic structural diagram of a multi-state totem PFC circuit according to an embodiment of the present invention;

fig. 2A-2D are equivalent circuit schematic diagrams of the multi-state totem PFC circuit shown in fig. 1 for four switching states;

fig. 3 is an equivalent schematic diagram of the current path of the multi-state totem PFC circuit shown in fig. 1;

fig. 4 is a schematic diagram of the differential mode current versus differential mode voltage for the multi-state totem PFC circuit shown in fig. 1;

fig. 5A-5B are schematic waveforms of the carrier, modulation wave, duty cycle, and bridge arm midpoint voltage of the switching bridge arm drive signal of the multi-state totem PFC circuit shown in fig. 1;

fig. 6 is a schematic structural diagram of a multi-state totem PFC circuit according to an embodiment of the present invention;

fig. 7 is a schematic diagram of the magnetic balance control circuit of the multi-state totem PFC circuit shown in fig. 6;

fig. 8 is a flowchart of a coupled inductor magnetic balance control method of a multi-state totem PFC circuit according to an embodiment of the present invention;

fig. 9 is a schematic structural diagram of a multi-state totem PFC circuit according to an embodiment of the present invention;

fig. 10A-10B are schematic structural diagrams of the magnetic balance control circuit of the multi-state totem PFC circuit shown in fig. 9;

FIG. 11 is a schematic diagram of an alternative configuration of the differential mode current compensation submodule of the magnetic balance control circuit of FIGS. 10A-10B;

fig. 12 is a flowchart of a coupled inductor magnetic balance control method of a multi-state totem PFC circuit according to an embodiment of the present invention;

fig. 13 is a schematic structural diagram of a multi-state totem PFC circuit according to an embodiment of the present invention;

fig. 14 is a schematic diagram of the magnetic balance control circuit of the multi-state totem PFC circuit of fig. 13;

fig. 15 is a flowchart of a coupled inductor magnetic balance control method of a multi-state totem PFC circuit according to an embodiment of the present invention;

fig. 16A to fig. 16E are schematic structural diagrams of a PFC circuit applying the coupled inductor magnetic balance control method according to an embodiment of the present invention;

fig. 17A-17B are schematic simulated waveforms of the coupling inductance magnetic balance control method of the multi-state totem PFC circuit according to the embodiment of the present invention.

Detailed Description

The technical solutions in the embodiments of the present invention will be described below with reference to the drawings in the embodiments of the present invention.

Referring to fig. 1, in an embodiment of the invention, a multi-state totem Power Factor Correction (PFC) circuit 10 includes an input power source Vss, a rectifying inductor Lin, a bus capacitor Co, a multi-state switch 110, a first rectifying diode D1, and a second rectifying diode D2. The multi-state switch 110 includes a first connection end a, a second connection end b, a third connection end c, a coupling inductor T, and a first switch leg 111 and a second switch leg 113 connected in parallel between the second connection end b and the third connection end c. The first switch bridge arm 111 comprises an upper switch tube S1, a lower switch tube S2 and a first node a between the upper switch tube S1 and the lower switch tube S2, wherein the upper switch tube S1 and the lower switch tube S2 are connected in series, and the first node a is the bridge arm midpoint of the first switch bridge arm 111; the second switch bridge arm 113 comprises an upper switch tube S3 and a lower switch tube S4 which are connected in series, and a second node B which is located between the upper switch tube S3 and the lower switch tube S4 and is the bridge arm midpoint of the second switch bridge arm 113; the coupling inductor T comprises a first winding L1 and a second winding L2 coupled and connected with each other, one end of the first winding L1 and one end of the second winding L2 are connected with the first connection end a, and the other end of the first winding L1 and the other end of the second winding L2 are respectively connected with the first node a and the second node B in a one-to-one correspondence manner. One end of the rectifying inductor Lin is connected with one end of the input power supply Vss, and the other end of the rectifying inductor Lin is connected with the first connection end a. The anode of the first rectifying diode D1 is connected to the other end of the input power source Vss, and the cathode of the first rectifying diode D1 is connected to the second connection terminal b; the anode of the second rectifying diode D2 is connected to the third connection terminal c, and the cathode of the second rectifying diode D2 is connected to the other end of the input power source Vss. The bus capacitor Co is connected between the second connection terminal b and the third connection terminal c.

The input power supply Vss is used for providing an alternating input voltage Vs for the multi-state totem PFC circuit 10. The first rectifying diode D1 and the second rectifying diode D2 form a rectifying bridge arm which operates at a low frequency in the positive and negative half periods of the input voltage Vs. The upper switch tube and the lower switch tube in the first switch bridge arm 111 and the second switch bridge arm 113 are respectively driven by a group of high-frequency transformed pulse width modulation signals, the drive signals of the upper switch tube and the lower switch tube in each switch bridge arm are complementary, and a certain dead time is reserved to prevent the upper switch tube and the lower switch tube from being conducted simultaneously. The phase shift between the driving signal of the second switch bridge arm 113 and the driving signal of the first switch bridge arm 111 is a certain angle, so as to realize staggered parallel connection and counteract the harmonic of specific times. In this embodiment, the phase shift between the driving signal of the second switching leg 113 and the driving signal of the first switching leg 111 is 180 degrees.

Taking a positive half cycle of the input voltage Vs as an example, equivalent circuits of the multi-state totem PFC circuit 10 under different switch combinations are respectively shown in fig. 2A-2D. Fig. 2A is a schematic diagram of an equivalent circuit when the lower switch tube S2 of the first switch leg 111 and the lower switch tube S4 of the second switch leg 113 are turned on; fig. 2B is a schematic equivalent circuit diagram when the upper switch tube S1 of the first switch leg 111 and the upper switch tube S3 of the second switch leg 113 are turned on; fig. 2C is a schematic diagram of an equivalent circuit when the lower switch tube S2 of the first switch leg 111 and the upper switch tube S3 of the second switch leg 113 are turned on; fig. 2D is a schematic diagram of an equivalent circuit when the upper switch tube S1 of the first switch leg 111 and the lower switch tube S4 of the second switch leg 113 are turned on. Fig. 2C and fig. 2D are actually the same equivalent circuits. Therefore, the multi-state totem PFC circuit 10 includes three equivalent switching states, in which two upper switching tubes are simultaneously turned on, two lower switching tubes are simultaneously turned on, and the upper switching tube in one switching leg and the lower switching tube in the other switching leg are simultaneously turned on.

Referring to fig. 3, fig. 3 is an equivalent schematic diagram of a current path of the multi-state totem PFC circuit 10 under three equivalent switching states. The voltages of the first node A and the second node B change at high frequency, the current Is input current, and the currents I1 and I2 are currents flowing through the first winding L1 and the second winding L2 respectively. Each of the currents I1 and I2 includes a common mode current and a differential mode current of 0.5 Is. The existence of the differential mode current can cause the flux linkage of the coupling inductor T to change, and the magnetic core loss of the coupling inductor T is increased, so that the coupling inductor generates heat seriously, and the power conversion efficiency is reduced. When the differential mode current in the coupling inductor T exceeds the hysteresis transformation range allowed by the magnetic core, the coupling inductor T may be magnetically saturated, and the coupling inductor T and the switching tube may be damaged. Therefore, it is necessary to control the differential mode current in the coupling inductor to improve the magnetic balance of the coupling inductor.

Fig. 4 is a schematic diagram of a relationship between a differential-mode voltage and a differential-mode current in the coupling inductor T of the multi-state totem PFC circuit 10. Wherein, V_A、V_BCorresponding differential mode voltages at the first node a and the second node B, respectively, Id is the differential mode current in the first winding L1 and the second winding L2. The differential mode current flows only between the first winding L1 and the second winding L2, and between the first switching leg 111 and the second switching leg 113, and does not flow to the rectifier inductor Lin. In the present embodiment, the direction indicated by the arrow in fig. 4 is defined as the positive direction of the differential mode current Id, and Lmag is the self-inductance of the first winding L1 and the second winding L2.

The following is a theoretical derivation of the relationship between the differential mode current Id in the coupling inductor T and the flux linkage of the coupling inductor T. Referring to fig. 5A and 5B, C1 is a carrier of the driving signal of the upper switch tube S1 of the first switch bridge arm 111, and m1 is a corresponding modulation wave; c3 is a carrier of the driving signal of the upper switching tube S3 of the second switching leg 113, and m3 is a corresponding modulation wave; d1 is the duty ratio of the driving signal of the upper switch tube S1 of the first switch arm 111, and D3 is the duty ratio of the driving signal of the upper switch tube S3 of the second switch arm 113; VA and VB are respectively the midpoint voltages of the first switch leg 111 and the second switch leg 113; vdc + is the positive bus voltage and Vdc-is the negative bus voltage. Assuming that the phase shift angle between the carriers C1, C3 of the driving signals of the upper switching tubes S1, S3 of the first switching leg 111 and the second switching leg 113 is 180 degrees, the duty ratios D1 and D3 of the driving signals of the switching tubes S1, S3 have three relationships, i.e., D1 < 0.5 and D3 < 0.5, or D1 ═ D3 ═ 0.5, or D1 > 0.5 and D3 > 0.5, wherein D1 ═ D3 ═ 0.5is the critical state of the other two relationships, so the theoretical derivation is only performed here on the relationship between the differential mode current Id in the coupling inductance T and the magnetic chain of the coupling inductance T in the two cases of D1 < 0.5, D3 < 0.5 and D1 > 0.5, and D3 > 0.5.

When D1 < 0.5 and D3 < 0.5, the waveforms of the carrier wave, the modulation wave, the duty cycle and the bridge arm midpoint voltage of the driving signal in one switching period of the upper switching tubes S1 and S3 of the first switching leg 111 and the second switching leg 113 of the multi-state totem PFC circuit 10 are as shown in fig. 5A. Assuming that one switching period is Ts and the self-inductance L of the coupling inductor is 2Lmag, the system of the volt-second equation of the coupling inductor T at each transient in one switching period Ts can be listed as follows:

substituting the differential mode voltages VA and VB of the corresponding bridge arm midpoint under each transient state in fig. 5A into the equation set (1) respectively, an equation set can be obtained:

similarly, when D1 is greater than 0.5 and D3 is greater than 0.5, the equation set can be obtained according to the differential mode voltages VA and VB at the midpoint of the corresponding bridge arm in each transient state in fig. 5B:

by collating equation set (2) or equation set (3), the equations can be derived:

further integrating t over one switching period by equation (4) yields the equation:

from equation (5), it can be seen that the flux linkage variation LI of the coupling inductance caused by the differential mode current Id_dAnd the difference of the duty ratios of the driving signals of the upper switching tube S1 of the first switching bridge arm and the upper switching tube S3 of the second switching bridge arm 113 is accumulated in one switching period Ts. It is understood that the above theory is also applicable to the derivation of the relationship between the differential mode current Id in the coupling inductor T and the flux linkage of the coupling inductor T with reference to the duty cycle of the driving signals of the following switching transistors S2, S4. It can therefore be derived from equation (5) that the flux linkage variation LI in the coupling inductance T is caused by the differential mode current Id_dThe accumulation of the difference of the duty ratios of the driving signals of the switching tubes at the same positions of the front and rear switching arms in a switching period Ts is equal to that of the difference of the duty ratios of the driving signals of the switching tubes at the same positions of the front and rear switching arms in the same switching period Ts, namely the positive, negative and large of the differential mode current Id can be controlled by controlling the difference of the duty ratios of the driving signals of the switching tubes at the same positions of the. The switching tubes at the same position refer to upper switching tubes of the front and rear switching bridge arms or lower switching tubes of the front and rear switching bridge arms, and the switching period Ts is the period of the driving signal.

Referring to fig. 6 and 7 together, in an embodiment of the present invention, a multi-state totem Power Factor Correction (PFC) circuit 100 is provided, which further includes a magnetic balance control circuit 130, relative to the multi-state totem PFC circuit 10 shown in fig. 1, where the magnetic balance control circuit 130 includes a feedback control module 131, a wave-generating module 133, and a magnetic balance control module 135, which are sequentially connected.

The feedback control module 131 Is further connected to two ends of the input power supply Vss, and Is configured to obtain an input voltage sampling value Vs and an input current sampling value Is of the multi-state totem PFC circuit; the feedback control module 131 is further connected to two ends of the first switch leg 111 and the second switch leg 113, and is configured to obtain an output voltage sampling value Vo of the multi-state totem PFC circuit 100; the feedback control module 131 Is further configured to calculate an input current compensation value Iscom according to the input voltage sampling value Vs, the input current sampling value Is, and the output voltage sampling value Vo, and in combination with the output voltage reference value Vo _ ref.

The wave generating module 133 is further connected to the first switch leg 111, and configured to generate a first pulse width modulation signal D1 'and a second pulse width modulation signal D2' by using the input current compensation value Iscom as a modulation wave, where the first pulse width modulation signal D1 'and the second pulse width modulation signal D2' are used to drive the upper switch tube S1 and the lower switch tube S2 of the first switch leg 111 to be alternately turned on. The first pulse width modulation signal D1 'is used as a first driving signal Drv1 for driving the upper switch tube S1 of the first switch leg 111, and the second pulse width modulation signal D2' is used as a second driving signal Drv2 for driving the lower switch tube S2 of the first switch leg 111.

The magnetic balance control module 135 is further connected to the second switch leg 113, and is configured to phase-shift the first pulse width modulation signal D1 'by a preset angle to obtain a third pulse width modulation signal D3' with the same duty ratio, phase-shift the second pulse width modulation signal D2 'by a preset angle to obtain a fourth pulse width modulation signal D4' with the same duty ratio, where the third pulse width modulation signal D3 'and the fourth pulse width modulation signal D4' are configured to drive an upper switch tube S3 and a lower switch tube S4 of the second switch leg 113 to be alternately turned on. The third pwm signal D3 'is used as the third driving signal Drv3 for driving the upper switch tube S3 of the second switch leg 113, and the fourth pwm signal D4' is used as the fourth driving signal Drv4 for driving the lower switch tube S4 of the second switch leg 113.

The feedback control module 131 comprises a first difference operator 1311, an output voltage compensator 1313, a reference current calculator 1315, a second difference operator 1317 and an input current compensator 1319 which are connected in sequence;

the first difference operator 1311 is configured to perform a difference operation on the output voltage sampling value Vo and the output voltage reference value Vo _ ref;

the output voltage compensator 1313 is configured to perform output voltage compensation operation on the output of the first difference operator 1311 to obtain an amplitude B of the input current reference value;

the reference current calculator 1315 is configured to multiply the amplitude B of the input current reference value by the input voltage sample value Vs, and divide by the square C of the input voltage sample value Vs to obtain an input current reference value Isref;

the second difference operator 1317 Is configured to perform a difference operation on the input current reference value Isref and the input current sampling value Is;

the input current compensator 1319 is configured to perform an input current compensation operation on the output of the second difference operator 1317 to obtain an input current compensation value Iscom.

Wherein the reference current calculator 1315 comprises a gain operator K and a square operator X²The gain arithmetic unit K is used for carrying out gain operation on the input voltage sampling value Vs to obtain a gain value A of the input voltage sampling value Vs; the square arithmetic unit X²The square operation is carried out on the input voltage sampling value Vs to obtain the square C of the input voltage sampling value Vs; the multiplier is used for calculating the product of the gain value A of the input voltage sampling value Vs and the amplitude value B of the input current reference value; the divider is used for dividing the product of the gain value A of the input voltage sampling value Vs and the amplitude value B of the input current reference value by the square C of the input voltage sampling value Vs to obtain the input current reference value Isref.

The wave-sending module 133 comprises a first output terminal 1331 and a second output terminal 1333, wherein the first output terminal 1331 is used for outputting the first pulse width modulation signal D1 ', and the second output terminal 1333 is used for outputting the second pulse width modulation signal D2'; the magnetic balance control module 135 includes a first delayer 1351 and a second delayer 1353; the first delay 1351 is connected to the first output port 1331, and is configured to phase-shift the first pwm signal D1 'by a preset angle to obtain a third pwm signal D3' with the same duty ratio; the second delay 1353 is connected to the second output 1333, and is configured to phase-shift the second pwm signal D2 'by a preset angle to obtain a fourth pwm signal D4' with the same duty ratio.

It is understood that, in an embodiment of the present invention, the first output terminal 1331 may be further configured to output the third pwm signal D3 ', the second output terminal 1333 may be further configured to output the fourth pwm signal D4', the first delay 1351 is configured to phase-shift the third pwm signal D3 'by a preset angle to obtain the first pwm signal D1' with the same duty ratio, and the second delay 1353 is configured to phase-shift the fourth pwm signal D4 'by a preset angle to obtain the second pwm signal D2' with the same duty ratio.

It is understood that the first delayer 1351 and the second delayer 1353 can be implemented by hardware circuits, and can also be implemented by software modules.

It is understood that, in an embodiment of the present invention, the multi-state switch 110 includes N switch bridge legs connected in parallel, the coupling inductor T includes N windings coupled to each other, the N windings are respectively connected to the N switch bridge legs in a one-to-one correspondence, and a phase shift between driving signals of two adjacent switch bridge legs is 360/N degrees, or a phase shift between carriers of driving signals of two adjacent switch bridge legs is 360/N degrees. Wherein N is an integer greater than or equal to 2.

In this embodiment, the first pulse width modulation signal D1 'is used as the first driving signal Drv1 for driving the upper switch tube S1 of the first switch bridge arm 111, the second pulse width modulation signal D2' is used as the second driving signal Drv2 for driving the lower switch tube S2 of the first switch bridge arm 111, the duty ratios of the first driving signal Drv1 and the second driving signal Drv2 of the first switch bridge arm 111 are fixed, the magnetic balance control module 135 phase-shifts the first driving signal Drv1 by a preset angle to obtain the third driving signal Drv3 for driving the upper switch tube S3 of the second switch bridge arm 113, and the second driving signal Drv2 is phase-shifted by a preset angle to obtain the fourth driving signal Drv4 for driving the lower switch tube S4 of the second switch bridge arm 113, so that the duty ratios of the upper switch tube S1 of the first switch bridge arm 111 and the second driving signal Drv3 of the second switch bridge arm 113 are the same, and the duty ratio of the driving signal of the lower switch tube S2 of the first switch bridge arm 111 is the same as the duty ratio of the driving signal of the lower switch tube S4 of the second switch bridge arm 113, so that the magnitude of differential mode current in the first winding L1 and the second winding L2 of the coupling inductor T can be effectively reduced, the flux linkage balance of the coupling inductor T is ensured, the magnetic core loss of the coupling inductor is reduced, and the efficiency of the multi-state totem PFC circuit is improved.

Referring to fig. 8, in an embodiment of the invention, a method for controlling the magnetic balance of the coupling inductor of the multi-state totem PFC circuit is provided, and is applied to the multi-state totem PFC circuit 100 shown in fig. 7-8, so as to implement the magnetic balance control of the coupling inductor T of the multi-state totem PFC circuit 100. The method comprises the following steps:

step S101: acquiring an input voltage sampling value, an input current sampling value and an output voltage sampling value of the multi-state totem PFC circuit, and calculating an input current compensation value by combining an output voltage reference value;

step S102: the input current compensation value is used as a modulation wave to generate a first pulse width modulation signal and a second pulse width modulation signal, and the first pulse width modulation signal and the second pulse width modulation signal are used for driving a switching tube of the first switching bridge arm to be alternately conducted;

step S103: and phase-shifting the first pulse width modulation signal by a preset angle to obtain a third pulse width modulation signal with the same duty ratio, and phase-shifting the second pulse width modulation signal by a preset angle to obtain a fourth pulse width modulation signal with the same duty ratio, wherein the third pulse width modulation signal and the fourth pulse width modulation signal are used for driving the switching tubes of the second switching bridge arm to be alternately switched on.

In one embodiment of the present invention, the calculating the input current compensation value includes:

In an embodiment of the present invention, the multi-state switch includes N switch bridge arms connected in parallel, the coupling inductor includes N windings coupled to each other, the N windings are respectively connected to the N switch bridge arms in a one-to-one correspondence, and a phase shift between driving signals of two adjacent switch bridge arms is 360/N degrees, or a phase shift between triangular carriers of driving signals of two adjacent switch bridge arms is 360/N degrees. Wherein N is an integer greater than or equal to 2.

It can be understood that, in the embodiment, each step and specific execution of the method for controlling the coupling inductance magnetic balance of the multi-state totem PFC circuit may also refer to the related description in the embodiments shown in fig. 7 to 8, and are not described herein again.

Referring to fig. 9 and 10A together, in an embodiment of the invention, a multi-state totem PFC circuit 200 is provided, which further includes a magnetic balance control circuit 230, compared to the multi-state totem PFC circuit 10 shown in fig. 1, where the magnetic balance control circuit 230 includes a feedback control module 231, a wave generating module 233 and a magnetic balance control module 235, which are connected in sequence.

The feedback control module 231 Is further connected to two ends of the input power supply Vss, and Is configured to obtain an input voltage sampling value Vs and an input current sampling value Is of the multi-state totem PFC circuit 200; the feedback control module 231 is further connected to two ends of the first switch leg 111 and the second switch leg 113, and is configured to obtain an output voltage sampling value Vo of the multi-state totem PFC circuit 200; the feedback control module 231 Is further configured to calculate an input current compensation value Iscom according to the input voltage sampling value Vs, the input current sampling value Is, and the output voltage sampling value Vo, and in combination with the output voltage reference value Vo _ ref.

The wave generation module 233 is configured to use the input current compensation value Iscom as a modulation wave to generate a first pulse width modulation signal D1 ', a second pulse width modulation signal D2', a third pulse width modulation signal D3 ', and a fourth pulse width modulation signal D4', where the first pulse width modulation signal D1 'and the second pulse width modulation signal D2' are configured to drive an upper switch tube S1 and a lower switch tube S2 of the first switch leg 111 to be alternately turned on, and the third pulse width modulation signal D3 'and the fourth pulse width modulation signal D4' are configured to drive an upper switch tube S3 and a lower switch tube S4 of the second switch leg 113 to be alternately turned on.

The first pulse width modulation signal D1 'is used as a first driving signal Drv1 for driving the upper switch tube S1 of the first switch bridge arm 111, and the second pulse width modulation signal D2' is used as a second driving signal Drv2 for driving the lower switch tube S2 of the first switch bridge arm 111; the third pwm signal D3 'is used as the third driving signal Drv3 for driving the upper switch tube S3 of the second switch leg 113, and the fourth pwm signal D4' is used as the fourth driving signal Drv4 for driving the lower switch tube S4 of the second switch leg 113.

The magnetic balance control module 235 includes a differential mode current compensation submodule 2351, an adjustment meter operator module 2353 and a duty ratio adjustment submodule 2355, which are connected in sequence.

The differential mode current compensation sub-module 2351 is further connected to the first winding L1 and the second winding L2, and is configured to obtain a differential mode current sampling value Id of the first winding L1 and the second winding L2, and calculate a differential mode current compensation value Idcom by combining the differential mode current reference value Id _ ref.

The regulating quantity operator module 2353 is further connected to the feedback control module 231, and is configured to calculate duty ratio regulating quantities Δ D1 and Δ D2 of each switching tube in the first switching leg 111 and duty ratio regulating quantities Δ D3 and Δ D4 of each switching tube in the second switching leg 113 according to the direction of the differential mode current sampling value Id, the positive and negative of the input voltage sampling value Vs, and the differential mode current compensation value Idcom. Δ D1 is the duty ratio adjustment amount of the upper switch tube S1 of the first switch arm 111, Δ D2 is the duty ratio adjustment amount of the lower switch tube S2 of the first switch arm 111, Δ D3 is the duty ratio adjustment amount of the upper switch tube S3 of the second switch arm 113, and Δ D4 is the duty ratio adjustment amount of the lower switch tube S4 of the second switch arm 113.

The duty ratio adjusting submodule 2355 is further connected to the wave generating module 233, the first switch bridge arm 111 and the second switch bridge arm 113, and is configured to superimpose the duty ratio adjusting quantity Δ D1 on the first pulse width modulation signal D1'; superimposing the duty ratio adjustment amount Δ D2 on the second pwm signal D2 ', superimposing the duty ratio adjustment amount Δ D3 on the third pwm signal D3 ', and superimposing the duty ratio adjustment amount Δ D4 on the fourth pwm signal D4 '.

The feedback control module 231 includes a first difference operator 2311, an output voltage compensator 2313, a reference current calculator 2315, a second difference operator 2317 and an input current compensator 2319, which are connected in sequence;

the first difference operator 2311 is configured to perform a difference operation on the output voltage sampling value Vo and the output voltage reference value Vo _ ref;

the output voltage compensator 2313 is configured to perform output voltage compensation operation on the output of the first difference operator 2311 to obtain an amplitude B of an input current reference value;

the reference current calculator 2315 is configured to multiply the amplitude B of the input current reference value by the input voltage sampling value Vs, and divide by the square C of the input voltage sampling value Vs to obtain an input current reference value Isref;

the second difference operator 2317 Is configured to perform a difference operation on the input current reference value Isref and the input current sampling value Is;

the input current compensator 2319 is configured to perform an input current compensation operation on the output of the second difference operator 2317 to obtain an input current compensation value Iscom.

The structure of the reference current calculator 2315 is the same as that of the reference current calculator 1315 shown in fig. 7, and reference may be specifically made to the description related to the embodiment shown in fig. 7, which is not repeated herein.

The differential mode current compensation submodule 2351 comprises a third difference value operator 3511, a fourth difference value operator 3513 and a differential mode current controller 3515 which are connected in sequence;

the third difference operator 3511 is configured to perform a difference operation on the first current I1 on the first winding L1 and the second current I2 on the second winding L2 to obtain a differential mode current sample value Id;

the fourth difference operator 3513 is configured to perform a difference operation on the differential mode current sampling value Id and the differential mode current reference value Id _ ref;

the differential mode current controller 3515 is configured to perform differential mode current adjustment operation on the output of the fourth difference operator 3513 to obtain a differential mode current compensation value Idcom.

The regulation amount operator module 2353 comprises a sign judgment unit 3531, an input voltage state judgment unit 3533, a truth table unit 3535 and a multiplication unit 3537;

the sign judgment unit 3531 is configured to judge a direction of the differential mode current sampling value Id;

the input voltage state judgment unit 3533 is used for judging the positive and negative of the input voltage sampling value Vs;

the truth table unit 3535 is configured to determine a truth table output state of a switching tube of the first switching leg 111 and the second switching leg 113, which needs to adjust a duty ratio, according to a direction of the differential mode current sampling value Id and a positive and a negative of the input voltage sampling value Vs. The truth table unit 3535 includes four true value outputs of 1, 2, 3 and 4, and the output values of the four true value outputs are respectively used for indicating the duty ratio adjustment states of the switching tubes S1, S2, S3 and S4, for example, output 1 indicates that the duty ratio needs to be adjusted, and output 0 indicates that the duty ratio does not need to be adjusted.

The multiplication operation unit 3537 is configured to multiply the truth table output state by the differential mode current compensation value Idcom to obtain a duty ratio adjustment amount of each switching tube in the first switching leg 111 and the second switching leg 113. In this embodiment, the multiplication unit 3537 includes four parallel multipliers, one input of each of which is connected to the output of the differential mode current compensation submodule 2351, and the other input of each of which is connected to a true value output of the truth table unit 3535.

The wave-transmitting module 233 includes four

output terminals

2331, 2332, 2333 and 2334, which are respectively configured to output the first pulse width modulation signal D1 ', the second pulse width modulation signal D2', the third pulse width modulation signal D3 'and the fourth pulse width modulation signal D4'. The duty ratio adjusting sub-module 2355 includes four adders connected in parallel, a first input end of each adder is connected to an output end of the wave generating module 233, and a second input end of each adder is connected to an output end of one multiplier, so as to superimpose the duty ratio adjusting amounts Δ D1, Δ D2, Δ D3, and Δ D4 of each switching tube in the first switching leg 111 and the second switching leg 113, which are calculated by the multiplication unit 3537, onto the first pulse width modulation signal D1 ', the second pulse width modulation signal D2', the third pulse width modulation signal D3 ', and the fourth pulse width modulation signal D4', respectively.

Specifically, a truth table of the relationship of the switching tube that needs to adjust the duty ratio when the direction of the differential mode current sampling value Id is different when the input voltage sampling value Vs is in the positive and negative half cycles can be derived according to equation (5), as shown in table one. The truth table unit 3535 can determine the truth table output state of the switching tubes of the first switching leg 111 and the second switching leg 113, which need to adjust the duty ratio, by looking up the corresponding relationship in the first table according to the direction of the differential mode current sampling value Id and the positive and negative of the input voltage sampling value Vs, and further the multiplication unit 3537 multiplies the truth table output state by the differential mode current compensation value Idcom to obtain the duty ratio adjustment amount of each switching tube of the first switching leg 111 and the second switching leg 113.

Table one relation truth table of switching tube needing duty ratio regulation

Wherein, under the column of the positive and negative judgment (1/0) of the input voltage, 0 represents that the sampling value Vs of the input voltage is in the negative half cycle, and 1 represents that the sampling value Vs is in the positive half cycle; in the column of the differential mode current direction determination (1/0), 0 indicates that the differential mode current sampling value Id is in a negative direction, and 1 indicates that the differential mode current sampling value Id is in a positive direction (as indicated by an arrow in fig. 4); and under the switching tube column needing to adjust the duty ratio, 0 represents that the duty ratio of the switching tube of the corresponding sub-column does not need to be adjusted, and 1 represents that the duty ratio of the switching tube of the corresponding sub-column needs to be adjusted.

Taking the case that the input voltage sampling value Vs in the first table is in the negative half cycle as an example, when the differential mode current sampling value Id is in the negative direction, the truth table output state is [1, 0, 0, 0], which indicates that the duty ratio of the upper switching tube S1 of the first switching leg 111 needs to be adjusted, the duty ratio adjustment amount Δ D1 corresponding to the upper switching tube S1 of the first switching leg 111 can be obtained by multiplying the truth table output state by the differential mode current compensation value Idcom, and then the duty ratio adjustment amount Δ D1 is superimposed on the first pulse width modulation signal D1' through the duty ratio adjustment submodule 2355; when the differential mode current sampling value Id is a positive direction, the truth table output state is [0, 1, 0, 0], which indicates that the duty ratio of the upper switching tube S3 of the second switching arm 113 needs to be adjusted, the duty ratio adjustment quantity Δ D3 corresponding to the upper switching tube S3 of the second switching arm 113 can be obtained by multiplying the truth table output state by the differential mode current compensation value Idcom, and the duty ratio adjustment quantity Δ D3 is further superimposed on the third pulse width modulation signal D3' by the duty ratio adjustment submodule 2355.

Referring to fig. 10B, in an embodiment of the invention, the magnetic balance control circuit 230 includes a magnetic balance control module 235 ', and the magnetic balance control module 235' is different from the magnetic balance control module 235 shown in fig. 10A in that: the magnetic balance control module 235 'includes a regulation amount operator module 2353' and a duty ratio regulation submodule 2355 ', the regulation amount operator module 2353' includes a multiplication operation unit 3537 ', the multiplication operation unit 3537' includes two multipliers connected in parallel, one input end of each multiplier is connected with the output end of the differential mode current compensation submodule 2351, and the other input end of each multiplier is connected with a true value output end of the truth table unit 3535.

In this embodiment, the truth table unit 3535 is configured to determine a truth table output state of a switching tube of the first switching leg 111 or the second switching leg 113, which needs to adjust a duty ratio, according to a direction of the differential mode current sampling value Id and a positive or negative of the input voltage sampling value Vs.

The duty ratio adjusting sub-module 2355 ' includes two adders connected in parallel, a first input end of each adder is connected to an output end of the wave generating module 233, a second input end of each adder is connected to an output end of one multiplier, so as to superimpose the duty ratio adjusting amounts Δ D1, Δ D2 of each switching tube in the first switching leg 111, which are calculated by the multiplication unit 3537, on the first pulse width modulation signal D1 ', the second pulse width modulation signal D2 ', respectively, or superimpose the duty ratio adjusting amounts Δ D3, Δ D4 of each switching tube in the second switching leg 113, which are calculated by the multiplication unit 3537, on the third pulse width modulation signal D3 ' and the fourth pulse width modulation signal D4 ', respectively.

Referring to fig. 11, in an embodiment of the invention, the magnetic balance control module 235 includes a differential mode current compensation submodule 2351 ', and the differential mode current compensation submodule 2351' includes a third difference operator 3511, a differential mode current controller 3515, a fourth difference operator 3513 and a gain operator K, which are connected in sequence;

the differential mode current controller 3515 is configured to perform differential mode current regulation operation on the differential mode current sampling value Id;

the fourth difference operator 3513 is configured to perform a difference operation on the output of the differential mode current controller 3515 and a differential mode current reference value Id _ ref;

the gain operator K is configured to perform a gain operation on the output of the fourth difference operator 3513 to obtain a differential mode current compensation value Idcom.

It Is understood that the sampled value Id of the differential mode current may be obtained by sampling two or three of the first current I1 in the first winding L1, the second current I2 in the second winding L2, and the total input current Is of the coupled inductor T, using (I1-I2) or (I2-I1), or using the sampled value Id of the differential mode current as the input current

Or

Or can beOr

And (4) calculating.

In the embodiment shown in fig. 9-11, by fixing the duty ratio of the switching tubes of the first switching leg 111, the duty ratio adjustment amounts Δ D3 and Δ D4 of each switching tube in the second switching leg 113 are calculated, and then the duty ratio adjustment amounts Δ D3 and Δ D4 are respectively superimposed on the third pulse width modulation signal D3 'and the fourth pulse width modulation signal D4'; or fixing the duty ratio of the switching tubes of the second switching arm 113 to be unchanged, and calculating the duty ratio adjustment amounts Δ D1 and Δ D2 of each switching tube in the first switching arm 111, so as to respectively superimpose the duty ratio adjustment amounts Δ D1 and Δ D2 on the first pulse width modulation signal D1 'and the second pulse width modulation signal D2'; or calculating the duty ratio adjustment amounts Δ D1 and Δ D2 of each switching tube in the first switching leg 111 and the duty ratio adjustment amounts Δ D3 and Δ D4 of each switching tube in the second switching leg 113, and further superimposing the duty ratio adjustment amounts D1, Δ D2, Δ D3 and Δ D4 on the first pulse width modulation signal D1 ', the second pulse width modulation signal D2', the third pulse width modulation signal D3 'and the fourth pulse width modulation signal D4', so as to effectively reduce the difference between the duty ratio of the driving signal of the upper switching tube S1 of the first switching leg 111 and the duty ratio of the driving signal of the upper switching tube S3 of the second switching leg 113, and reduce the difference between the duty ratio of the driving signal of the lower switching tube S2 of the first switching leg 111 and the duty ratio of the driving signal of the lower switching tube S4 of the second switching leg 113, and further effectively reduce the difference between the magnitude of the winding L1 of the coupled inductor T and the magnitude of the differential mode current 2 of the second switching leg 113, the coupling inductor T is guaranteed to have good flux linkage balance, the magnetic core loss of the coupling inductor is reduced, and the efficiency of the multi-state totem PFC circuit is improved.

Referring to fig. 12, in an embodiment of the invention, a method for controlling the magnetic balance of the coupling inductor of the multi-state totem PFC circuit is provided, and is applied to the multi-state totem PFC circuit 200 shown in fig. 9-11 to implement the magnetic balance control of the coupling inductor T of the multi-state totem PFC circuit 200. The method comprises the following steps:

step S201: acquiring an input voltage sampling value, an input current sampling value and an output voltage sampling value of the multi-state totem PFC circuit, and calculating an input current compensation value by combining an output voltage reference value;

step S202: generating a first pulse width modulation signal, a second pulse width modulation signal, a third pulse width modulation signal and a fourth pulse width modulation signal by using the input current compensation value as a modulation wave, wherein the first pulse width modulation signal and the second pulse width modulation signal are used for driving a switching tube of the first switching bridge arm to be alternately conducted, and the third pulse width modulation signal and the fourth pulse width modulation signal are used for driving a switching tube of the second switching bridge arm to be alternately conducted;

step S203: acquiring differential mode current sampling values of the first winding and the second winding, and calculating a differential mode current compensation value by combining a differential mode current reference value;

step S204: calculating the duty ratio regulating quantity of each switching tube in the first switching bridge arm or/and the second switching bridge arm according to the direction of the differential mode current sampling value, the positive and negative of the input voltage sampling value and the differential mode current compensation value;

step S205: and respectively superposing the duty ratio regulating quantity of each switching tube of the first switching bridge arm on the first pulse width modulation signal and the second pulse width modulation signal, or/and respectively superposing the duty ratio regulating quantity of each switching tube of the second switching bridge arm on the third pulse width modulation signal and the fourth pulse width modulation signal.

In one embodiment of the present invention, the calculating the differential mode current compensation value includes:

In an embodiment of the present invention, the calculating a duty ratio adjustment amount of each switching tube in the first switching leg or/and the second switching leg includes:

It can be understood that, in the embodiment, each step and specific implementation of the method for controlling the coupling inductance magnetic balance of the multi-state totem PFC circuit may also refer to the related descriptions in the embodiments shown in fig. 9 to fig. 11, and are not described herein again.

Referring to fig. 13 and 14 together, in an embodiment of the present invention, a multi-state totem PFC circuit 300 is provided, which is opposite to the multi-state totem PFC circuit 10 shown in fig. 1, and further includes a magnetic balance control circuit 330, where the magnetic balance control circuit 330 includes a feedback control module 331, a modulated wave generation module 332, a wave generation module 333, and a magnetic balance control module 335, and the feedback control module 331 and the magnetic balance control module 335 are connected to the wave generation module 333 through the modulated wave generation module 332;

the feedback control module 331 Is further connected to two ends of the input power supply Vss, and Is configured to obtain an input voltage sampling value Vs and an input current sampling value Is of the multi-state totem PFC circuit 300; the feedback control module 331 is further connected to two ends of the first switch leg 111 and the second switch leg 113, and is configured to obtain a sampling value Vo of the output voltage of the multi-state totem PFC circuit 300; the feedback control module 331 Is further configured to calculate an input current compensation value Iscom according to the input voltage sampling value Vs, the input current sampling value Is, and the output voltage sampling value Vo, and in combination with the output voltage reference value Vo _ ref;

the magnetic balance control module 335 is further connected to the first winding L1 and the second winding L2, and is configured to obtain a differential mode current sample value Id of the first winding L1 and the second winding L2, and calculate a differential mode current compensation value Idcom in combination with the differential mode current reference value Id _ ref;

the modulation wave generating module 332 is configured to superimpose the differential-mode current compensation value Idcom onto the input current compensation value Iscom to generate a modulation wave m;

the wave generating module 333 is further connected to the first switching leg 111 and the second switching leg 113, and configured to generate a first pulse width modulation signal D1 ', a second pulse width modulation signal D2', a third pulse width modulation signal D3 ', and a fourth pulse width modulation signal D4' according to the modulation wave m, where the first pulse width modulation signal D1 'and the second pulse width modulation signal D2' are configured to drive an upper switching tube S1 and a lower switching tube S2 of the first switching leg 111 to be alternately turned on, and the third pulse width modulation signal D3 'and the fourth pulse width modulation signal D4' are configured to drive an upper switching tube S3 and a lower switching tube S4 of the second switching leg 113 to be alternately turned on.

The feedback control module 331 includes a first difference calculator 3311, an output voltage compensator 3313, a reference current calculator 3315, a second difference calculator 3317, and an input current compensator 3319, which are connected in sequence;

the first difference operator 3311 is configured to perform a difference operation on the output voltage sampling value Vo and the output voltage reference value Vo _ ref;

the output voltage compensator 3313 is configured to perform an output voltage compensation operation on the output of the first difference calculator 3311 to obtain an amplitude B of the input current reference value;

the reference current calculator 3315 is configured to multiply the amplitude B of the input current reference value by the input voltage sampling value Vs, and divide by the square C of the input voltage sampling value Vs to obtain an input current reference value Isref;

the second difference operator 3317 Is configured to perform a difference operation on the input current reference value Isref and the input current sampling value Is;

the input current compensator 3319 is configured to perform an input current compensation operation on the output of the second difference operator 1317 to obtain an input current compensation value Iscom.

The structure of the reference current calculator 3315 is the same as that of the reference current calculator 1315 shown in fig. 7, and reference may be specifically made to the description related to the embodiment shown in fig. 7, which is not repeated herein.

The magnetic balance control module 335 may be the differential mode current compensation sub-module 2351 shown in fig. 10A and 10B, and the specific structure thereof may refer to the description in the embodiment shown in fig. 10A and 10B, which is not described herein again; alternatively, the magnetic balance control module 335 may also be a differential mode current compensation sub-module 2351' shown in fig. 11, and the specific structure thereof may refer to the description in the embodiment shown in fig. 11, which is not described herein again.

In this embodiment, a differential mode current compensation value Idcom is obtained by obtaining a differential mode current sampling value Id of the first winding L1 and the second winding L2, and calculating a differential mode current compensation value Idcom by combining with a differential mode current reference value Id _ ref, and further superimposing the differential mode current compensation value Idcom on the input current compensation value Iscom as a modulation wave m, so as to change the modulation wave m according to a change of the differential mode current sampling value Id, thereby adjusting a duty ratio of each of the first switching leg 111 and the second switching leg 113 by a change of the modulation wave m, so as to reduce a difference between a duty ratio of a driving signal of the upper switching tube S1 of the first switching leg 111 and a duty ratio of a driving signal of the upper switching tube S3 of the second switching leg 113, and reduce a difference between a duty ratio of a driving signal of the lower switching tube S2 of the first switching leg 111 and a duty ratio of a driving signal of the lower switching tube S4 of the second switching leg 113, and then effectively reducing the magnitude of differential mode current in the first winding L1 and the second winding L2 of the coupling inductor T, ensuring that the coupling inductor T has better flux linkage balance, reducing the magnetic core loss of the coupling inductor, and improving the efficiency of the multi-state totem PFC circuit.

Referring to fig. 15, in an embodiment of the invention, a method for controlling the magnetic balance of the coupling inductor of the multi-state totem PFC circuit is provided, and is applied to the multi-state totem PFC circuit 300 shown in fig. 13-14 to implement the magnetic balance control of the coupling inductor T of the multi-state totem PFC circuit 300. The method comprises the following steps:

step S301: acquiring an input voltage sampling value, an input current sampling value and an output voltage sampling value of the multi-state totem PFC circuit, and calculating an input current compensation value by combining an output voltage reference value;

step S302: acquiring differential mode current sampling values of the first winding and the second winding, and calculating a differential mode current compensation value by combining a differential mode current reference value;

step S303: superposing the differential mode current compensation value on the input current compensation value to generate a modulation wave;

step S304: and generating a first pulse width modulation signal, a second pulse width modulation signal, a third pulse width modulation signal and a fourth pulse width modulation signal according to the modulation wave, wherein the first pulse width modulation signal and the second pulse width modulation signal are used for driving the switching tube of the first switching bridge arm to be alternately conducted, and the third pulse width modulation signal and the fourth pulse width modulation signal are used for driving the switching tube of the second switching bridge arm to be alternately conducted.

It can be understood that, in the embodiment, each step and specific implementation of the method for controlling the coupling inductance magnetic balance of the multi-state totem PFC circuit may also refer to the related description in the embodiments shown in fig. 13 to fig. 14, and are not described herein again.

Referring to fig. 16A to 16E, fig. 16A to 16E are schematic structural diagrams of a PFC circuit applying the coupled inductor magnetic balance control method according to an embodiment of the present invention. Fig. 16A is a four-state totem PFC circuit; fig. 16B is a three-state single-phase three-level PFC circuit; fig. 16C is a tri-state boost PFC circuit; fig. 16D is a tri-state midpoint clamp PFC circuit; fig. 16E is a tri-state dual boost PFC circuit. The PFC circuits shown in fig. 16A to 16E may all use the coupling inductor magnetic balance control method provided in the embodiment of the present invention to perform magnetic balance control on the coupling inductor, so as to reduce the dc offset in the coupling inductor, improve the magnetic balance of the coupling inductor, and avoid saturation of the magnetic core as much as possible, thereby improving the efficiency and power density of the PFC circuit.

It can be understood that the coupling inductance magnetic balance control method is not limited to be applied to the PFC circuit structure disclosed in the embodiment of the present invention, and as long as the circuit structure includes a multi-state switch, the multi-state switch includes N switch legs and a coupling inductance, the coupling inductance includes N windings coupled to each other, and the N windings are respectively connected to the N switch legs in a one-to-one correspondence manner, the circuit structure may apply the coupling inductance magnetic balance control method described in the embodiment of the present invention to perform magnetic balance control on the coupling inductance in the multi-state switch. Wherein N is an integer greater than or equal to 2.

Referring to fig. 17A and 17B, fig. 17A-17B are schematic waveforms of simulation waveforms of the coupled inductor magnetic balance control method of the multi-state totem PFC circuit according to the embodiment of the present invention.

In an embodiment of the present invention, simulation operating conditions are set as an input voltage 220V, an output voltage 400V, and an output power 1000W, and three simulation conditions, including equal dead time, equal duty ratio, unequal dead time, unequal duty ratio, unequal dead time and unequal duty ratio of switching tube driving signals of front and rear arms (i.e., the first switching arm 111 and the second switching arm 113) of the multi-state totem PFC circuit 100 shown in fig. 1, and performing simulation comparative analysis on the three simulation conditions of magnetic balance control by using the coupling inductance magnetic balance control method of the embodiment shown in fig. 8, 12, or 15.

Fig. 17A is a schematic diagram showing waveforms of the output voltage Vo and the input current Iin of the multi-state totem PFC circuit 100 under three simulation conditions. Wherein, Vo1 and Iin1 are respectively an output voltage waveform and an input current waveform with equal dead time and equal duty ratio of front and rear bridge arms; vo2 and Iin2 are output voltage waveforms and input current waveforms with unequal dead time and unequal duty ratio of front and rear bridge arms respectively; vo3 and Iin3 are output voltage waveforms and input current waveforms which are respectively different in dead time and duty ratio of front and rear bridge arms and are subjected to magnetic balance control by adopting the coupling inductor magnetic balance control method of the embodiment shown in FIG. 8, FIG. 12 or FIG. 15. Iin1(Iin2) and Vo1(Vo2) in the figure indicate that the two waveforms overlap each other. Since the differential mode current Id only flows between the two windings L1 and L2 of the coupling inductor T and in the switching tubes of the first switching leg 111 and the second switching leg 113, and does not flow to the input inductor Lin, the control of the output voltage and the input current of the multi-state totem PFC circuit 100 is not influenced by the presence or absence of coupled inductor magnetic balance control, and it can be seen from fig. 17A that the deviation between the output voltage Vo and the input current Iin is small under three simulation conditions, and is consistent with the theoretical analysis result.

Fig. 17B is a graph showing the magnetic induction of the coupling inductor core and the waveform of the coupling inductor winding current under three simulation conditions. B1 is to keep the dead time of the front and rear arm driving signals equal (30 ns in this embodiment), the magnetic induction intensity waveforms (about-0.1T) when the driving signals of the front and rear arm are phase-shifted by half a switching period, I11 and I21 are the current waveforms in the first winding L1 and the second winding L2 corresponding to B1, respectively; b2 is a magnetic induction intensity waveform (about-1.5T) when the dead time of the front and rear bridge arm driving signals is not equal (the difference is 40ns in the embodiment), I21 and I22 are current waveforms in the first winding L1 and the second winding L2 corresponding to B2, respectively; b3 is a magnetic induction intensity waveform (about 0.5T) obtained by performing magnetic balance control by using the coupling inductor magnetic balance control method according to the embodiment shown in fig. 12 or 15, where I31 and I32 are current waveforms in the first winding L1 and the second winding L2 corresponding to B3, respectively.

As can be seen from fig. 17B, when the dead time of the front and rear bridge arm driving signals is unequal, a certain dc offset exists in the currents in the first winding L1 and the second winding L2, and the magnetic induction intensity-1.5T of the magnetic core of the coupling inductor at this time is far beyond the maximum magnetic induction intensity of the magnetic core made of soft magnetic material.

When the dead time of the driving signals of the front and rear bridge arms is unequal, the magnetic balance control method of the coupling inductor in the embodiment shown in fig. 8 is adopted to perform magnetic balance control on the coupling inductor, so that the same magnetic induction intensity waveform and winding current waveform can be obtained when the dead time for keeping the driving signals of the front and rear bridge arms equal to that shown in fig. 17B and the driving signals of the front and rear bridge arms are phase-shifted by half a switching period.

When the dead time of the front and rear bridge arm driving signals is unequal, the coupling inductance magnetic balance control method of the embodiment shown in fig. 12 or fig. 15 can adjust the magnetic induction intensity of the front and rear bridge arm driving signals with unequal dead time from-1.5T to about 0.5T, that is, the direct current bias in the coupling inductance winding can be effectively controlled, the magnetic bias of the coupling inductance core is reduced, and the magnetic saturation of the coupling inductance core is prevented. The positive and negative of the magnetic induction are related to the definition of the positive direction, and are not limited herein.

While the invention has been described with reference to a preferred embodiment, it will be understood by those skilled in the art that various changes in form and detail may be made therein without departing from the spirit and scope of the invention.

Claims

1. A multi-state totem Power Factor Correction (PFC) circuit is characterized by comprising an input power supply, a rectifier inductor, a multi-state switch, a first rectifier diode and a second rectifier diode;

one end of the rectifier inductor is connected with one end of the input power supply;

the multi-state switch comprises a coupling inductor and at least a first switch bridge arm and a second switch bridge arm which are connected in parallel; the coupling inductor comprises at least a first winding and a second winding which are coupled with each other; the first switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a first node is arranged between the upper switch tube and the lower switch tube of the first switch bridge arm; the second switch bridge arm comprises an upper switch tube and a lower switch tube which are connected in series, wherein a second node is arranged between the upper switch tube and the lower switch tube of the second switch bridge arm;

the other end of the rectifying inductor is connected with one ends of the first winding and the second winding; the other end of the first winding is connected with the first node, and the other end of the second winding is connected with the second node;

the anode of the first rectifier diode is connected with the other end of the input power supply, and the cathode of the first rectifier diode is connected with one ends of the first switch bridge arm and the second switch bridge arm;

the anode of the second rectifier diode is connected with the other ends of the first switch bridge arm and the second switch bridge arm, and the cathode of the second rectifier diode is connected with the other end of the input power supply;

the multi-state totem PFC circuit further comprises a magnetic balance control circuit, wherein the magnetic balance control circuit comprises a feedback control module, a wave-generating module and a magnetic balance control module which are sequentially connected;

the feedback control module is also connected with two ends of the input power supply and is used for acquiring an input voltage sampling value and an input current sampling value of the multi-state totem PFC circuit;

the feedback control module is also connected with two ends of the first switch bridge arm and the second switch bridge arm and is used for acquiring an output voltage sampling value of the multi-state totem PFC circuit;

the feedback control module is also used for calculating an input current compensation value according to the input voltage sampling value, the input current sampling value and the output voltage sampling value and by combining with an output voltage reference value;

the wave generation module is further connected with the first switch bridge arm and is used for generating a first pulse width modulation signal and a second pulse width modulation signal by taking the input current compensation value as a modulation wave, wherein the first pulse width modulation signal and the second pulse width modulation signal are used for driving an upper switch tube and a lower switch tube of the first switch bridge arm to be alternately conducted;

the magnetic balance control module is also connected with the second switch bridge arm and is used for phase-shifting the first pulse width modulation signal by a preset angle to obtain a third pulse width modulation signal with the same duty ratio and phase-shifting the second pulse width modulation signal by a preset angle to obtain a fourth pulse width modulation signal with the same duty ratio, and the third pulse width modulation signal and the fourth pulse width modulation signal are used for driving an upper switch tube and a lower switch tube of the second switch bridge arm to be alternately conducted;

the feedback control module comprises a first difference value arithmetic unit, an output voltage compensator, a reference current calculator, a second difference value arithmetic unit and an input current compensator which are connected in sequence;

2. A multi-state totem PFC circuit of claim 1,

the wave-sending module comprises a first output end and a second output end, wherein the first output end is used for outputting the first pulse width modulation signal, and the second output end is used for outputting the second pulse width modulation signal;

the magnetic balance control module comprises a first delayer and a second delayer; the first delayer is connected with the first output end and is used for phase shifting the first pulse width modulation signal by a preset angle to obtain a third pulse width modulation signal with the same duty ratio; and the second delayer is connected with the second output end and used for phase shifting the second pulse width modulation signal by a preset angle to obtain a fourth pulse width modulation signal with the same duty ratio.

3. The multi-state totem PFC circuit of claim 1, wherein the multi-state switch comprises N switching legs connected in parallel with each other, the coupling inductance comprises N windings coupled with each other, the N windings are respectively connected with the N switching legs in a one-to-one correspondence, and a phase shift between driving signals of two adjacent switching legs is 360/N degrees, where N is an integer greater than or equal to 2.

4. A multi-state totem PFC circuit of claim 2, wherein the multi-state switch comprises N switching legs connected in parallel with each other, the coupling inductance comprises N windings coupled with each other, the N windings are respectively connected with the N switching legs in a one-to-one correspondence, and a phase shift between driving signals of two adjacent switching legs is 360/N degrees, where N is an integer greater than or equal to 2.

5. A multi-state totem PFC circuit is characterized by comprising an input power supply, a rectifier inductor, a multi-state switch, a first rectifier diode and a second rectifier diode;

the wave sending module is used for generating a first pulse width modulation signal, a second pulse width modulation signal, a third pulse width modulation signal and a fourth pulse width modulation signal by taking the input current compensation value as a modulation wave;

the magnetic balance control module comprises a differential mode current compensation submodule, an adjustment meter operator module and a duty ratio adjustment submodule which are sequentially connected;

the differential mode current compensation submodule is also connected with the first winding and the second winding and is used for acquiring differential mode current sampling values of the first winding and the second winding and calculating a differential mode current compensation value by combining a differential mode current reference value;

6. The multi-state totem PFC circuit of claim 5, wherein the feedback control module comprises a first difference operator, an output voltage compensator, a reference current calculator, a second difference operator, and an input current compensator connected in sequence;

7. The multi-state totem PFC circuit of claim 5 or 6, wherein the differential mode current compensation submodule comprises a third difference operator, a fourth difference operator, and a differential mode current controller connected in sequence;

8. The multi-state totem PFC circuit of claim 5 or 6, wherein the differential mode current compensation submodule comprises a third difference operator, a differential mode current controller, a fourth difference operator and a gain operator connected in sequence;

9. The multi-state totem PFC circuit of any one of claims 5 to 6, wherein the adjustment quantity operator module comprises a sign judgment unit, an input voltage state judgment unit, a truth table unit and a multiplication unit;

10. The multi-state totem PFC circuit of claim 7, wherein the regulation amount operator module comprises a sign determination unit, an input voltage state determination unit, a truth table unit, and a multiplication unit;

11. The multi-state totem PFC circuit of claim 9, wherein the regulation amount operator module comprises a sign determination unit, an input voltage state determination unit, a truth table unit, and a multiplication unit;

12. A multi-state totem PFC circuit is characterized by comprising an input power supply, a rectifier inductor, a multi-state switch, a first rectifier diode and a second rectifier diode;

the anode of the first rectifier diode is connected with the other end of the input power supply, and the cathode of the first rectifier diode is connected with one ends of the first switch bridge arm and the second switch bridge arm; the anode of the second rectifier diode is connected with the other ends of the first switch bridge arm and the second switch bridge arm, and the cathode of the second rectifier diode is connected with the other end of the input power supply;

the multi-state totem PFC circuit further comprises a magnetic balance control circuit, the magnetic balance control circuit comprises a feedback control module, a magnetic balance control module, a modulating wave generation module and a wave sending module, and the feedback control module and the magnetic balance control module are connected with the wave sending module through the modulating wave generation module;

the feedback control module is also connected with two ends of the input power supply and is used for acquiring an input voltage sampling value and an input current sampling value of the multi-state totem PFC circuit; the feedback control module is also connected with two ends of the first switch bridge arm and the second switch bridge arm and is used for acquiring an output voltage sampling value of the multi-state totem PFC circuit; the feedback control module is also used for calculating an input current compensation value according to the input voltage sampling value, the input current sampling value and the output voltage sampling value and by combining with an output voltage reference value;

the magnetic balance control module is also connected with the first winding and the second winding and is used for acquiring differential mode current sampling values of the first winding and the second winding and calculating a differential mode current compensation value by combining a differential mode current reference value;

the wave generating module is further connected with the first switch bridge arm and the second switch bridge arm and used for generating a first pulse width modulation signal, a second pulse width modulation signal, a third pulse width modulation signal and a fourth pulse width modulation signal according to the modulation wave, the first pulse width modulation signal and the second pulse width modulation signal are used for driving an upper switch tube and a lower switch tube of the first switch bridge arm to be alternately conducted, and the third pulse width modulation signal and the fourth pulse width modulation signal are used for driving an upper switch tube and a lower switch tube of the second switch bridge arm to be alternately conducted.

13. The multi-state totem PFC circuit of claim 12, wherein the feedback control module comprises a first difference operator, an output voltage compensator, a reference current calculator, a second difference operator, and an input current compensator connected in sequence;

14. The multi-state totem PFC circuit of claim 12 or 13, wherein the magnetic balance control module comprises a third difference operator, a fourth difference operator, and a differential mode current controller connected in sequence;

15. The multi-state totem PFC circuit of claim 12 or 13, wherein the magnetic balance control module comprises a third difference operator, a differential mode current controller, a fourth difference operator, and a gain operator connected in sequence;