CN106506038B - A kind of telemetry communication implementation method under the unified signal model based on UQPSK - Google Patents
A kind of telemetry communication implementation method under the unified signal model based on UQPSK Download PDFInfo
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- H—ELECTRICITY
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- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
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- G—PHYSICS
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- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S19/00—Satellite radio beacon positioning systems; Determining position, velocity or attitude using signals transmitted by such systems
- G01S19/01—Satellite radio beacon positioning systems transmitting time-stamped messages, e.g. GPS [Global Positioning System], GLONASS [Global Orbiting Navigation Satellite System] or GALILEO
- G01S19/13—Receivers
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- G01S19/29—Acquisition or tracking or demodulation of signals transmitted by the system carrier including Doppler, related
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- H04B1/707—Spread spectrum techniques using direct sequence modulation
- H04B1/7073—Synchronisation aspects
- H04B1/7087—Carrier synchronisation aspects
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
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Abstract
The invention discloses the telemetry communication implementation methods under a kind of unified signal model based on UQPSK, break conventional telemetry, remote control, the discrete progress of communication function work(operating mode, the acquisition of target velocity, distance, angle information is completed in the transmission that unit discharging and remote control/communication data are completed using the non-equilibrium of UQPSK using the pseudorandom and correlation properties of spreading code；The various information carried in signal transmission are greatly utilized in the framework, under same signal model framework, can obtain telemetering, remote control, signal of communication simultaneously, and no interactions are interfered between each road signal；In addition, uplink downlink is all made of unification, the modular architecture of standard ensure that the effective operation of TTC ＆ DT Systems while hardware resource and load space maximumlly is utilized；Thus, there is extraordinary autgmentability and flexibility, it is growing with space, resource-constrained contradiction to efficiently solve current telemetry communication data capacity.
Description
Technical Field
The invention belongs to the technical field of comprehensive information processing, and particularly relates to a measurement and control communication implementation method based on a UQPSK unified signal model.
Background
Aircraft integrated information processing is an organic component and an important node of an information network. With the larger amount of information to be processed and the larger amount of information to be transmitted in emergency communication, the traditional radio communication mode is obviously not suitable for the requirement of emergency handling under modern high-tech conditions. Therefore, a set of efficient and applicable measurement and control communication implementation method under a unified signal model must be built to solve the contradiction between the increasing functional task types and the performance requirements. Integrated information processing must simultaneously provide integrated task processing capabilities including communication, navigation, measurement and control flight control, and information support in a limited physical channel.
The traditional aircraft is limited by the single function of information load, and a plurality of load devices with different functions are required to be carried to simultaneously realize the required comprehensive tasks. Meanwhile, the load redundancy and reliability of the aircraft are considered, so that the aircraft is required to have stronger effective load bearing capacity; on the other hand, with the continuous improvement of the flying speed, the altitude, the maneuvering performance and the like of the aircraft, the airframe design generally adopts an integrated design, so that the loading capacity of the effective load of the aircraft including the loading space, the loading weight, the power supply capacity and the like is strictly limited. Therefore, the measurement and control communication implementation method under the unified signal model is developed from 'function synthesis' to 'structure synthesis', and is evolving to an integrated flexible reconfigurable architecture.
The invention provides a signal model which is based on UQPSK and can simultaneously realize the functions of remote measurement, remote control and communication in the same signal model. The invention is based on a software radio architecture, greatly utilizes various information carried in signal transmission, can simultaneously obtain telemetering, remote control and communication signals under the same signal model architecture, and has no mutual interference among all paths of signals. After the distance, the speed and the angle are measured in real time, relative positioning can be completed according to the external measurement information, and the navigation assistance function of the aircraft is completed. The limitation that a single sensor can only obtain single information under the traditional signal model is changed. The framework adopts a unified and standard modular system structure, realizes the multi-task measurement and control communication requirements in limited resources and limited space, can dynamically adjust resource division according to the actual task requirements and the resource use condition, and realizes comprehensive task processing such as communication, navigation, measurement and control, flight control, information support and the like.
Disclosure of Invention
The invention aims to overcome the defects of the prior art and provides a measurement and control communication implementation method based on a UQPSK unified signal model, which can simultaneously implement measurement and control communication functions of remote measurement, remote control, communication and the like on an aircraft in the same signal model.
In order to achieve the above object, the invention provides a method for implementing measurement and control communication based on a unified signal model of UQPSK, which is characterized by comprising the following steps:
(1) a UQPSK generator generates up/down link signals;
the uplink signal includes: original UQPSK modulated uplink signal sUQPSK_UP(t) original I-path PN code signal PN1(t) original Q path PN code signal PN2(t) and the original remote control data signal Sdata(t)；
The downlink signal includes: original UQPSK modulated downlink signal sUQPSK_DOWN(t), original PN code signal PN (t) and original communication data signal Sdata(t)；
(2) Realizing measurement and control communication on uplink/downlink signals under a UQPSK unified signal model;
(2.1) realizing measurement and control communication on the uplink signal under a UQPSK unified signal model;
(2.1.1) mixing sUQPSK_UP(t) input to a channel fading submodule, which simulates a radio communication channel pair sUQPSK_UP(t) increasing the delay τ and Doppler frequency offset fdThe output end of the Gaussian white noise simulates the UQPSK signal received by the receiver, and then the UQPSK signal is respectively input into the capture submodule and the relevant interference submodule;
(2.1.2) after receiving the UQPSK signal, the capture submodule sequentially performs primary coarse capture and secondary fine capture on the UQPSK signal;
1) first-stage coarse capture: multiplying UQPSK signal by local parallel local oscillation sequence cos2 pi fLOt+j sin2πfLOAfter t, comparing the product of each path of signal, finding out the signal corresponding to the point with the maximum amplitude, marking as a capture signal, and capturingObtaining the frequency f of the signal0+fdThen frequency f of the corresponding local oscillator sequenceLO＝f0+ i Δ f, from which an approximate Doppler shift f is derivedd'＝fLO-f0(ii) a Wherein f isLOIs the frequency of the local oscillator sequence, f0Is s isUQPSK_UP(t) frequency, Δ f local oscillator frequency interval, i ith local oscillator;
capturing local PN codes PN of which signals are respectively orthogonal with two paths of signals1(t)、PN2(t) autocorrelation to obtain PN code bias PPN1、PPN2In which PN1(t)、PN2The order of (t) is N and the length is 2N-1；
Using PN code bias PPN1、PPN2Correcting the local linear shift register to obtain a corrected I path of spread spectrum codes and a corrected Q path of spread spectrum codes;
and (3) obtaining a target distance D by utilizing the relation between the PN code offset and the distance:
wherein c represents the speed of light;
2) and secondary fine capture: shortening the local oscillator frequency interval delta f', repeating the primary coarse capture process to obtain the Doppler coarse frequency offset fd”；
Finally, the Doppler carrier wave is subjected to coarse frequency deviation fd' the distance D between the Doppler carrier and the target is sent to an output display module to carry out coarse frequency offset f of the Doppler carrierd' sum PN code offset PPN1、PPN2Sending the data to a tracking submodule;
(2.1.3) after receiving the UQPSK signal, the tracking submodule acquires an error frequency component delta f by using a double-path carrier tracking loopdFinishing accurate tracking of carrier frequency; meanwhile, a code tracking ring is used for acquiring a phase error signal of the PN code, so that the accurate tracking of the PN code is completed, and a further corrected demodulation I path spread spectrum code and demodulation Q path spread spectrum code are obtained;
when the double-path carrier tracking loop and the code tracking loop in the tracking sub-module are stable, the demodulated remote control data information S is obtaineddata(t+τ)；
Using a Doppler coarse frequency offset fd"sum error frequency component Δ fdCalculating Doppler fine frequency offset fd＝fd”+Δfd；
Calculating the target speed by using the relation between the Doppler fine frequency offset and the speed
Finally, the Doppler carrier fine frequency offset signal fdAnd demodulating the remote control data signal Sdata(t + tau) is output to the display module for display, and I path of spread spectrum code is demodulated, Q path of spread spectrum code is demodulated, and remote control data signal S is demodulateddata(t + tau) is fed back to the data result comparison submodule;
(2.1.4) the related interference sub-module adopts a multi-element antenna array to receive UQPSK signals, then the received signals are multiplied by the further modified demodulation I path spread spectrum codes, and the product signal is marked as sUQPSK_PN_UP(t) then for sUQPSK_PN_UP(t) Hilbert transformation and as imaginary and original sUQPSK_PN_UP(t) addition, i.e. scomplex(t)＝sUQPSK_PN_UP(t)+jH[sUQPSK_PN_UP(t)]Sequentially carrying out A/D conversion and DDC conversion on the obtained signals, and finally selecting two paths of non-adjacent signals to carry out relevant interference operation, further calculating a pitch angle and an azimuth angle, and outputting the pitch angle and the azimuth angle to a display module for display;
(2.1.5) comparing the original data with the processed data by the data result comparison sub-module, calculating the error rate of various signals, and outputting the error rate to the display module for display;
(2.2) realizing measurement and control communication on downlink signals under a UQPSK unified signal model;
(2.2.1) mixing sUQPSK_DOWN(t) input to a channel fading submodule, which simulates a radio communication channel pair sUQPSK_DOWN(t) increasing the delay τ and Doppler frequency offset fdThe output end of the Gaussian white noise simulates the UQPSK signal received by the receiver, and then the UQPSK signal is respectively input into the capture submodule and the relevant interference submodule;
(2.2.2) after receiving the UQPSK signal, the capture submodule performs primary coarse capture and secondary fine capture on the UQPSK signal;
1) first-stage coarse capture: multiplying UQPSK signal by local parallel local oscillation sequence cos2 pi fLOAfter t, comparing the product of each path of signal, finding out the signal corresponding to the point with the maximum amplitude, marking as the capture signal, and capturing the frequency f of the signal0+fdThen frequency f of the corresponding local oscillator sequenceLO＝f0+ i Δ f, from which an approximate Doppler shift f is derivedd'＝fLO-f0(ii) a Wherein f isLOIs the frequency of the local oscillator sequence, f0Is s isUQPSK_DOWN(t) frequency, Δ f local oscillator frequency interval, i ith local oscillator;
self-correlation between the captured signal and the local PN code PN (t) is obtained to obtain PN code bias P, the order number of the PN (t) is N, and the length is 2N-1；
Correcting the local linear shift register by utilizing the PN code offset P to obtain a corrected I path spread spectrum code;
and (3) obtaining a target distance D by utilizing the relation between the PN code offset P and the distance:
wherein c represents the speed of light;
2) and secondary fine capture: shortening the local oscillator frequency interval delta f', repeating the primary coarse capture process to obtain the Doppler coarse frequency offset fd”；
Finally, the DuoduoCoarse frequency deviation f of the le-carrierd"and the target distance D are sent to the output display module; coarse frequency deviation f of Doppler carrierd' sum PN code bias P is sent to tracking submodule
(2.2.3) after receiving the UQPSK signal, the tracking submodule acquires an error frequency component delta f by using a double-path carrier tracking loopdFinishing accurate tracking of carrier frequency; meanwhile, a code tracking ring is used for acquiring a phase error signal of the PN code, so that the accurate tracking of the PN code is completed, and a further corrected demodulation I path spread spectrum code is obtained;
when the two-way carrier tracking loop and the code tracking loop in the tracking sub-module are stable, the demodulated communication data information S is obtaineddata(t+τ)；
Using a Doppler coarse frequency offset fd"sum error frequency component Δ fdCalculating Doppler fine frequency offset fd＝fd”+Δfd；
Calculating the target speed by using the relation between the Doppler fine frequency offset and the speed
Finally, the Doppler carrier is finely shifted fdAnd demodulating the communication data signal Sdata(t + tau) is output to the display module for display, and the demodulated I-path spread spectrum code and demodulated communication data signal Sdata(t + tau) is fed back to the data result comparison submodule;
(2.2.4) the related interference sub-module adopts a multi-element antenna array to receive UQPSK signals, then the received signals are multiplied by the further modified demodulation I path spread spectrum codes, and the product signal is marked as sUQPSK_PN_DOWN(t) and then subjecting sUQPSK_PN_DOWN(t) as an imaginary number subtracted from its Hilbert change, i.e. scomplex(t)＝-H[sUQPSK_PN_DOWN(t)]+jsUQPSK_PN_DOWN(t), sequentially carrying out A/D conversion and DDC conversion on the obtained signals, and finally selecting two paths of non-adjacent signals to carry out correlation interference operation so as to calculate the pitch angle and the azimuth angleAnd output to the display module for display;
and (2.2.5) comparing the original data with the processed data by the data result comparison submodule, calculating the error rate of various signals, and outputting the error rate to the display module for display.
The invention aims to realize the following steps:
the invention discloses a measurement and control communication implementation method based on a UQPSK unified signal model, which breaks through the working mode that the functions of traditional remote measurement, remote control and communication are carried out separately, utilizes the non-equilibrium of the UQPSK to complete the transmission of external measurement data and remote control/communication data, and utilizes the pseudo-random and relevant characteristics of a spread spectrum code to complete the acquisition of target speed, distance and angle information. The framework greatly utilizes various information carried in signal transmission, can simultaneously obtain telemetering, remote control and communication signals under the same signal model framework, and has no mutual interference among all paths of signals. The uplink and the downlink adopt a unified and standard modular system structure, so that the effective operation of the measurement and control communication system is ensured while the hardware resources and the load space are utilized to the maximum extent. Therefore, the method has very good expansibility and flexibility, and effectively solves the contradiction between the increasing capacity of the current measurement and control communication data and the limitation of space and resources.
Meanwhile, the measurement and control communication implementation method based on the UQPSK unified signal model also has the following beneficial effects:
(1) the original multi-source information processing system is changed, and the traditional information fusion mode is improved into signal fusion. The processing flow of information fusion, namely decoding and fusion is simplified into direct processing, so that the consumption of hardware resources is reduced; meanwhile, the processing time is greatly shortened, and the consumption of time resources is reduced.
(2) And by adopting a top-down modular design, each functional module has the characteristics of relative independence, interchangeability and universality. The reuse, upgrade, maintenance and recovery of the module are facilitated, and the change of the functional requirements of the measurement and control communication system is quickly responded.
(3) Dynamic resource division can be completed according to actual task requirements and resource use conditions, and comprehensive task processing such as communication, navigation, measurement and control, flight control, information support and the like is realized;
drawings
Fig. 1 is a block diagram of the communication principle for implementing measurement and control on uplink signals based on a UQPSK unified signal model;
FIG. 2 is a block diagram of the measurement and control communication of downlink signals based on a UQPSK unified signal model according to the present invention;
FIG. 3 is a block diagram of one embodiment of a capture submodule;
FIG. 4 is a block diagram of one embodiment of a tracking submodule;
fig. 5 is a 7-element uniform circular array reception model.
Detailed Description
The following description of the embodiments of the present invention is provided in order to better understand the present invention for those skilled in the art with reference to the accompanying drawings. It is to be expressly noted that in the following description, a detailed description of known functions and designs will be omitted when it may obscure the subject matter of the present invention.
Examples
For convenience of description, the related terms appearing in the detailed description are explained:
UQPSK (Unbasic Quadrature Phase Shift Keying): non-uniform quadrature phase shift keying
PN Code (Pseudo-Noise Code): pseudo-random code sequence
I/I channel (In-Phase Components): equidirectional component path/equidirectional component channel
Q lane/Q channel (quadratures Components): quadrature component path/quadrature component channel
A/D (Analog to Digital): analog to digital conversion
DDC (Digital Down Converter): digital down converter
Fig. 1 is a block diagram of the communication principle for implementing measurement and control on uplink signals based on a UQPSK unified signal model.
Fig. 2 is a block diagram of the principle of implementing measurement and control communication on downlink signals based on a UQPSK unified signal model.
In this embodiment, in the present invention, based on the UQPSK signal model, the I channel is used to transmit narrowband information data, and the Q channel is used to transmit wideband data signal. Because the requirements of the telemetering, remote control and communication functions on the signal power are different, the power ratio of the I/Q two channels isWherein A isI、AQThe amplitudes of the two paths of I/Q channels respectivelyAndin an uplink channel, the path I transmission spread spectrum code is used for speed measurement, distance measurement and angle measurement; and Q paths of transmission spread spectrum remote control signals. In a downlink channel, I path transmission spread spectrum codes are used for speed measurement, distance measurement and angle measurement; the Q path transmits communication signals.
The invention is explained in detail by combining the division of the work of the channel in the upper channel and the downlink channel, and specifically comprises the following steps:
(1) a UQPSK generator generates up/down link signals;
the uplink signal includes: original UQPSK modulated uplink signal sUQPSK_UP(t) original I-path PN code signal PN1(t) original Q path PN code signal PN2(t) and the original remote control data signal Sdata(t)；
Wherein, the signal form of the uplink is represented as:
sUQPSK_UP(t)＝AIPN1(t)cos(2πf0t)+AQPN2(t)Sdata(t)sin(2πf0t)
wherein f is0Is s isUQPSK_UP(t) frequency;
the downlink signal includes: original UQPSK modulated downlink signal sUQPSK_DOWN(t), original PN code signal PN (t) and original communication data signal Sdata(t)；
The downlink signal form is represented as:
sUQPSK_DOWN(t)＝AIPN(t)cos(2πf0t)+AQSdata(t)sin(2πf0t)；
(2) realizing measurement and control communication on uplink/downlink signals under a UQPSK unified signal model;
(2.1) with reference to fig. 1, the specific process of implementing measurement and control communication on the uplink signal under the UQPSK unified signal model is as follows:
(2.1.1) mixing sUQPSK_UP(t) input to a channel fading submodule, which simulates a radio communication channel pair sUQPSK_UP(t) increasing the delay τ and Doppler frequency offset fdThe output end of the Gaussian white noise simulates the UQPSK signal received by the receiver, and then the UQPSK signal is respectively input into the capture submodule and the relevant interference submodule;
the output end simulates the UQPSK signal received by the receiver as follows:
sUQPSK(t)＝AIPN1'(t+τ)cos[2π(f0+fd)(t+τ)]+AQPN2'(t+τ)Sdata(t+τ)sin[2π(f0+fd)(t+τ)]+n(t)
where n (t) is additive white gaussian noise, which can be expressed as:
n(t)＝nI(t)cos2πf0t+nQ(t)sin2πf0t；
(2.1.2) as shown in fig. 3, after receiving the UQPSK signal, the capturing submodule sequentially performs primary coarse capturing and secondary fine capturing on the UQPSK signal;
1) first-stage coarse capture: multiplying UQPSK signal by local parallel local oscillation sequence cos2 pi fLOt+j sin2πfLOAfter t, comparing the product of each path of signal, finding out the signal corresponding to the point with the maximum amplitude, marking as the capture signal, and capturing the frequency f of the signal0+fdThen frequency f of the corresponding local oscillator sequenceLO＝f0+ i Δ f, from which an approximate Doppler shift f is derivedd'＝fLO-f0(ii) a Wherein f isLOIs the frequency of the local oscillator sequence, f0Is s isUQPSK_UP(t) frequency, Δ f local oscillator frequency interval, i ith local oscillator;
in this embodiment, 21 parallel local oscillation sequences are taken, that is:
fLO＝{f0-10Δf,f0-9Δf,f0-8Δf,f0-7Δf,f0-6Δf,f0-5Δf,f0-4Δf,f0-3Δf,f0-2Δf,f0-Δf,0,
f0+Δf,f0+2Δf,f0+3Δf,f0+4Δf,f0+5Δf,f0+6Δf,f0+7Δf,f0+8Δf,f0+9Δf,f0+10Δf}
then the product of 21 signals needs to be compared, and the signal obtained by the first-stage coarse acquisition is:
Scapture(t)＝SUQPSK'(t)(cos2πfLOt+j sin2πfLOt)
after low-pass filtering, the signal can be obtained:
from this, an approximate Doppler shift f can be determinedd'＝fLO-f0。
Capturing local PN codes PN of which signals are respectively orthogonal with two paths of signals1(t)、PN2(t) autocorrelation to obtain PN code bias PPN1、PPN2In which PN1(t)、PN2The order of (t) is N and the length is 2N-1, for performing speed, distance and angle measurement functions;
using PN code bias PPN1、PPN2Correcting the local linear shift register to obtain a corrected I path of spread spectrum codes and a corrected Q path of spread spectrum codes;
and (3) obtaining a target distance D by utilizing the relation between the PN code offset and the distance:
wherein c represents the speed of light;
2) and secondary fine capture: shortening the local oscillator frequency interval delta f', repeating the primary coarse capture process to obtain the Doppler coarse frequency offset fd”；
Finally, the Doppler carrier wave is subjected to coarse frequency deviation fd"and target distance D are sent to the output display module and tracking submodule respectively;
(2.1.3) after receiving the UQPSK signal, the tracking submodule acquires an error frequency component delta f by using a double-path carrier tracking loopdFinishing accurate tracking of carrier frequency; while also acquiring P with a code tracking loopThe phase error signal of the N code completes the accurate tracking of the PN code, and obtains the further corrected demodulation I path spread spectrum code and demodulation Q path spread spectrum code;
when the double-path carrier tracking loop and the code tracking loop in the tracking sub-module are stable, the demodulated remote control data information S is obtaineddata(t+τ)；
Using a Doppler coarse frequency offset fd"sum error frequency component Δ fdCalculating Doppler fine frequency offset fd＝fd”+Δfd；
Calculating the target speed by using the relation between the Doppler fine frequency offset and the speed
Finally, the Doppler carrier fine frequency offset signal fdAnd demodulating the remote control data signal Sdata(t + tau) is output to the display module for display, and I path of spread spectrum code is demodulated, Q path of spread spectrum code is demodulated, and remote control data signal S is demodulateddata(t + tau) is fed back to the data result comparison submodule;
in this embodiment, as shown in fig. 4, the received UQPSK signal passes through the carrier synchronous digital phase demodulation module to generate a carrier phase error signal ∈eError value epsiloneSending into loop filter, filtering out high frequency component and noise, tuning the obtained result to an integer controlled oscillator (NCO), and finally outputting an accurate PN code clock fcode. Carrier tracking relies on the acquisition and tracking of spreading codes, while code tracking loops employ integration and zeroing processes for baseband signal processing and carrier demodulation of carrier signals, so that code tracking loops and carrier tracking loops of a receiving baseband are interrelated.
Receiving signal SUQPSK't' are multiplied by the in-phase component and quadrature component of the local oscillator signal, respectivelyAndwherein,the change value of the local oscillation phase in the tracking process of the loop is obtained. Then two paths of local spread spectrum codes PN which are respectively orthogonal with each other1(t)、PN2And (t) multiplying, and performing low-pass filtering to obtain four paths of signals. When the loop is stabilized hasThe four signals are approximated as follows:
wherein S isIC1' (t) is SUQPSK' (t) multiplied by the in-phase component of the local oscillator signal and PN1(t)，SIC2'(t)SIC1' (t) is SUQPSK' (t) multiplied by the in-phase component of the local oscillator signal and PN2(t)，SQC1'(t)SIC1' (t) is SUQPSK' (t) multiplied by the quadrature component of the local oscillator signal and PN1(t)，SQC2'(t)SIC1' (t) is SUQPSK' (t) multiplied by the quadrature component of the local oscillator signal and PN2(t) for SQC2' (t) making 01 decision to obtain remote control data information Sdata(t+τ)。
(2.1.4) relevant interference submoduleReceiving UQPSK signal by using multi-element antenna array, multiplying the received signal by the further modified demodulation I path spread spectrum code, and marking the product signal as sUQPSK_PN_UP(t) then for sUQPSK_PN_UP(t) Hilbert transformation and as imaginary and original sUQPSK_PN_UP(t) addition, i.e. scomplex(t)＝sUQPSK_PN_UP(t)+jH[sUQPSK_PN_UP(t)]Sequentially carrying out A/D conversion and DDC conversion on the obtained signals, and finally selecting two paths of non-adjacent signals to carry out relevant interference operation, further calculating a pitch angle and an azimuth angle, and outputting the pitch angle and the azimuth angle to a display module for display;
in this embodiment, a 7-ary uniform circular array receiving model with an array radius R as shown in fig. 5 is constructed by using a correlation interference algorithm in which a cosine function is used as a cost function.
And taking the array element 0 as a reference array element, forming six array element pairs by other array elements and the array element 0, and solving the phase difference of the six array elements. The range of the pitch angle theta is 0-90 DEG, and the azimuth angle thetaThe range is 0-360 degrees, the azimuth angle takes 5 degrees as a unit, and the pitch angle takes 2 degrees as a unit to establish a phase difference sample library. In the above seven array elements, six different sets of phase difference vectors (0, 1), (0, 2), (0, 3), (0, 4), (0, 5), (0, 6) can be obtained to form a sample matrix.
To the received signal sUQPSK(t) multiplying the local corrected demodulated I-path spreading code to obtain:
sUQPSK'(t)＝sUQPSK'(t)PN1'(t+τ)＝AIcos[2π(f0+fd)(t+τ)]+n'(t)
wherein PN1'(t + tau) is the corrected I path spread code, n' (t) is the noise signal multiplied by the corrected demodulation I path spread code;
without considering additive white gaussian noise, it can be abstracted as a signal:
sUQPSK_PN_UP(t)＝a(t)cos(2πfct+φ)
among them are:
fc＝f0+fd
wherein f iscPhi is the random initial phase for the received signal center frequency.
The Hilbert change of the received signal can be obtained
H[sUQPSK_PN_UP(t)]＝-a(t)cos(2πfct+φ)
Defining:
if the circle center is taken as a reference point, the signal received by the antenna element m can be expressed as:
wherein n ism(t) is white Gaussian noise received by array element m, and E (n)m(t))＝0，D(nm(t))＝σ2。τmRepresenting the time delay of the array element m relative to a reference point.
xm(t) becomes after A/D, DDC:
wherein Δ fDDCIs the residual carrier frequency difference after DDC, TsIs the sampling interval.
For xm(n)、xn(N) performing an N-point FFT operation:
wherein a (ω) is xm(ω)、xnAmplitude information of (omega), phim(ω)、φn(ω) is each xm(ω)、xnPhase information of (ω), nm(ω)、nn(ω) is each xm(ω)、xn(ω) noise information.
xm(omega) and xn(ω) the cross-correlation results:
here, assuming that signals received by different array elements are not correlated with each other, there are:
to rm,nThe phase difference phi can be obtained by taking the phase of (omega)m,nAnd different phase differences can be obtained by processing different array elements.
Using array element 0 as reference array element, phase difference vector φ composed of six different data sets of (0, 1), (0, 2), (0, 3), (0, 4), (0, 5) and (0, 6) can be measured and compared with ψijAnd (i 2,4,6, 90; j 5,10,15, 360) respectively. Wherein psiijFor the phase difference data stored in the sample library, dividing the pitch angle range by taking 2 degrees as scales to obtain samplesThe sample point is i, and the sample point obtained by dividing the azimuth angle range by taking 5 degrees as scales is j.
Expression of the relevant comparison operations with the data of the sample library:
ρ＝(∑cos(ψij-φ))/(M-1)
the maximum value of ρ corresponds to the azimuth angle of the incoming wave, and the maximum value of each azimuth angle corresponds to the pitch angle of the incoming wave. From this, the pitch angle theta and azimuth angle can be measuredAngle information of (2).
(2.1.5) comparing the original data with the processed data by the data result comparison sub-module, calculating the error rate of various signals, and outputting the error rate to the display module for display;
(2.2) with reference to fig. 2, the specific process of implementing measurement and control communication on the downlink signal under the UQPSK unified signal model is as follows;
(2.2.1) mixing sUQPSK_DOWN(t) input to a channel fading submodule, which simulates a radio communication channel pair sUQPSK_DOWN(t) increasing the delay τ and Doppler frequency offset fdThe output end of the Gaussian white noise simulates the UQPSK signal received by the receiver, and then the UQPSK signal is respectively input into the capture submodule and the relevant interference submodule;
the output end simulates the UQPSK signal received by the receiver as follows:
sUQPSK(t)＝AIPN'(t+τ)cos[2π(f0+fd)(t+τ)]+AQSdata(t+τ)sin[2π(f0+fd)(t+τ)]+n(t)
where n (t) is additive white gaussian noise, which can also be expressed as:
n(t)＝nI(t)cos2πf0t+nQ(t)sin2πf0t；
(2.2.2) after receiving the UQPSK signal, the capture submodule performs primary coarse capture and secondary fine capture on the UQPSK signal;
1) first-stage coarse capture: multiplying UQPSK signal by local parallel local oscillation sequence cos2 pi fLOAfter t, comparing the product of each path of signal, finding out the signal corresponding to the point with the maximum amplitude, marking as the capture signal, and capturing the frequency f of the signal0+fdThen frequency f of the corresponding local oscillator sequenceLO＝f0+ i Δ f, from which an approximate Doppler shift f is derivedd'＝fLO-f0(ii) a Wherein f isLOIs the frequency of the local oscillator sequence, f0Is s isUQPSK_DOWN(t) frequency, Δ f local oscillator frequency interval, i ith local oscillator;
in this embodiment, also, 21 parallel local oscillation sequences are taken, that is:
fLO＝{f0-10Δf,f0-9Δf,f0-8Δf,f0-7Δf,f0-6Δf,f0-5Δf,f0-4Δf,f0-3Δf,f0-2Δf,f0-Δf,0,
f0+Δf,f0+2Δf,f0+3Δf,f0+4Δf,f0+5Δf,f0+6Δf,f0+7Δf,f0+8Δf,f0+9Δf,f0the +10 Δ f also needs to be multiplied by the 21 signals, so the signal obtained by the first stage of coarse acquisition is:
Scapture(t)＝SUQPSK'(t)cos2πfLOt
after low-pass filtering, the signal can be obtained:
from this, an approximate Doppler shift f can be determinedd'＝fLO-f0
Self-correlation between the captured signal and the local PN code PN (t) is obtained to obtain PN code bias P, the order number of the PN (t) is N, and the length is 2N-1, also used for completing the functions of speed measurement, distance measurement and angle measurement;
correcting the local linear shift register by utilizing the PN code offset P to obtain a corrected I path spread spectrum code;
and (3) obtaining a target distance D by utilizing the relation between the PN code offset P and the distance:
wherein c represents the speed of light;
2) and secondary fine capture: shortening the local oscillator frequency interval delta f', repeating the primary coarse capture process to obtain the Doppler coarse frequency offset fd”；
Finally, the Doppler carrier wave is subjected to coarse frequency deviation fd"and target distance D are sent to the output display module and tracking submodule respectively;
(2.2.3) after receiving the UQPSK signal, the tracking submodule acquires an error frequency component delta f by using a double-path carrier tracking loopdFinishing accurate tracking of carrier frequency; meanwhile, a code tracking ring is used for acquiring a phase error signal of the PN code, so that the accurate tracking of the PN code is completed, and a further corrected demodulation I path spread spectrum code is obtained;
when the two-way carrier tracking loop and the code tracking loop in the tracking sub-module are stable, the demodulated communication data information S is obtaineddata(t+τ)；
Using a Doppler coarse frequency offset fd"sum error frequency component Δ fdCalculating Doppler fine frequency offset fd＝fd”+Δfd；
Calculating the target speed by using the relation between the Doppler fine frequency offset and the speed
Finally, the Doppler carrier is finely shifted fdAnd demodulating the communication data signal Sdata(t + tau) is output to the display module for display, and the demodulated I-path spread spectrum code and demodulated communication data signal Sdata(t + tau) is fed back to the data result comparison submodule;
in the present embodiment, a signal S is receivedUQPSK't' are multiplied by the in-phase component and quadrature component of the local oscillator signal, respectivelyAndand then low-pass filtering to obtain two paths of signals. When the loop is stabilized hasThe two signals are approximated as follows:
wherein S isI' (t) is SUQPSK' t is multiplied by the in-phase component of the local oscillator signal, SQ' t is multiplied by the quadrature component of the local oscillator signal, for SQ' (t) making a 01 decision obtains demodulated communication data information Sdata(t+τ)。
(2.2.4) the related interference sub-module adopts a multi-element antenna array to receive UQPSK signals, then the received signals are multiplied by the further modified demodulation I path spread spectrum codes, and the product signal is marked as sUQPSK_PN_DOWN(t) and then subjecting sUQPSK_PN_DOWN(t) as an imaginary number subtracted from its Hilbert change, i.e. scomplex(t)＝-H[sUQPSK_PN_DOWN(t)]+jsUQPSK_PN_DOWN(t), sequentially carrying out A/D conversion and DDC conversion on the obtained signals, and finally selecting two paths of non-adjacent signals to carry out relevant interference operation, further calculating a pitch angle and an azimuth angle, and outputting the pitch angle and the azimuth angle to a display module for display;
the working principle of the relevant interference sub-modules in the downlink and uplink is the same, and the description is omitted here.
And (2.2.5) comparing the original data with the processed data by the data result comparison submodule, calculating the error rate of various signals, and outputting the error rate to the display module for display.
Although illustrative embodiments of the present invention have been described above to facilitate the understanding of the present invention by those skilled in the art, it should be understood that the present invention is not limited to the scope of the embodiments, and various changes may be made apparent to those skilled in the art as long as they are within the spirit and scope of the present invention as defined and defined by the appended claims, and all matters of the invention which utilize the inventive concepts are protected.
Claims (2)
1. A measurement and control communication implementation method based on a UQPSK unified signal model is characterized by comprising the following steps:
(1) a UQPSK generator generates up/down link signals;
the uplink signal includes: original UQPSK modulated uplink signal sUQPSK_UP(t) original I-path PN code signal PN1(t) original Q path PN code signal PN2(t) and the original remote control data signal Sdata1(t)；
The downlink signal includes: original UQPSK modulated downlink signal sUQPSK_DOWN(t), original PN code signal PN (t) and original communication data signal Sdata2(t)；
(2) Realizing measurement and control communication on uplink/downlink signals under a UQPSK unified signal model;
(2.1) realizing measurement and control communication on the uplink signal under a UQPSK unified signal model;
(2.1.1) mixing sUQPSK_UP(t) input to a channel fading submodule, which simulates a radio communication channel pair sUQPSK_UP(t) increasing the delay τ and Doppler frequency offset fdThe output end of the Gaussian white noise simulates the UQPSK signal received by the receiver, and then the UQPSK signal is respectively input into the capture sub-module and the relevant interference sub-module;
(2.1.2) after receiving the UQPSK signal, the capture submodule sequentially performs primary coarse capture and secondary fine capture on the UQPSK signal;
1) first-stage coarse capture: multiplying UQPSK signal by local parallel local oscillation sequence cos2 pi fLOt+jsin2πfLOAfter t, comparing the product of each path of signal, finding out the signal corresponding to the point with the maximum amplitude, marking as the capture signal, and capturing the frequency f of the signal0+fdThen frequency f of the corresponding local oscillator sequenceLO＝f0+ i Δ f, from which an approximate Doppler shift f is derivedd'＝fLO-f0(ii) a Wherein f isLOIs the frequency of the local oscillator sequence, f0Is s isUQPSK_UP(t) frequency, Δ f local oscillator frequency interval, i ith local oscillator;
capturing local PN codes PN of which signals are respectively orthogonal with two paths of signals1(t)、PN2(t) autocorrelation to obtain PN code bias PPN1、PPN2In which PN1(t)、PN2The order of (t) is N and the length is 2N-1；
Using PN code bias PPN1、PPN2Correcting the local linear shift register to obtain a corrected I path of spread spectrum codes and a corrected Q path of spread spectrum codes;
and (3) obtaining a target distance D by utilizing the relation between the PN code offset and the distance:
wherein c represents the speed of light;
2) and secondary fine capture: shortening the local oscillator frequency interval delta f', repeating the primary coarse capture process to obtain the Doppler coarse frequency offset fd”；
Finally, the Doppler carrier wave is subjected to coarse frequency deviation fd' the distance D between the Doppler carrier and the target is sent to an output display module to carry out coarse frequency offset f of the Doppler carrierd' sum PN code offset PPN1、PPN2Sending the data to a tracking submodule;
(2.1.3) after receiving the UQPSK signal, the tracking submodule acquires an error frequency component delta f by using a double-path carrier tracking loopdFinishing accurate tracking of carrier frequency; meanwhile, a code tracking ring is used for acquiring a phase error signal of the PN code, so that the accurate tracking of the PN code is completed, and a further corrected demodulation I path spread spectrum code and demodulation Q path spread spectrum code are obtained;
when the double-path carrier tracking loop and the code tracking loop in the tracking sub-module are stable, the demodulated remote control data signal S is obtaineddata1(t+τ)；
Using a Doppler coarse frequency offset fd"sum error frequency component Δ fdCalculating Doppler fine frequency offset fd＝fd”+Δfd；
Calculating the target speed by using the relation between the Doppler fine frequency offset and the speed
Finally, the Doppler carrier fine frequency offset signal fdAnd demodulating the remote control data signal Sdata1(t + tau) is output to the display module for display, and I path of spread spectrum code is demodulated, Q path of spread spectrum code is demodulated, and remote control data signal S is demodulateddata1(t + tau) is fed back to the data result comparison submodule;
(2.1.4) the related interference sub-module adopts a multi-element antenna array to receive UQPSK signals, then the received signals are multiplied by the further modified demodulation I path spread spectrum codes, and the product signal is marked as sUQPSK_PN_UP(t) then for sUQPSK_PN_UP(t) Hilbert transformation and as imaginary and original sUQPSK_PN_UP(t) addition, i.e. scomplex(t)＝sUQPSK_PN_UP(t)+jH[sUQPSK_PN_UP(t)]Sequentially carrying out A/D conversion and digital down-conversion DDC conversion on the obtained signals, and finally selecting two paths of non-adjacent signals to carry out relevant interference operation, so as to calculate a pitch angle and an azimuth angle and output the pitch angle and the azimuth angle to a display module for display;
(2.1.5) comparing the original data with the processed data by the data result comparison sub-module, calculating the error rate of various signals, and outputting the error rate to the display module for display;
(2.2) realizing measurement and control communication on downlink signals under a UQPSK unified signal model;
(2.2.1) mixing sUQPSK_DOWN(t) input to a channel fading submodule, which simulates a radio communication channel pair sUQPSK_DOWN(t) increasing the delay τ and Doppler frequency offset fdThe output end of the Gaussian white noise simulates the UQPSK signal received by the receiver, and then the UQPSK signal is respectively input into the capture submodule and the relevant interference submodule;
(2.2.2) after receiving the UQPSK signal, the capture submodule performs primary coarse capture and secondary fine capture on the UQPSK signal;
1) first-stage coarse capture: multiplying UQPSK signal by local parallel local oscillation sequence cos2 pi fLOAfter t, comparing the product of each path of signal, finding out the signal corresponding to the point with the maximum amplitude, marking as the capture signal, and capturing the frequency f of the signal0+fdThen frequency f of the corresponding local oscillator sequenceLO＝f0+ i Δ f, from which an approximate Doppler shift f is derivedd'＝fLO-f0(ii) a Wherein f isLOIs the frequency of the local oscillator sequence, f0Is s isUQPSK_DOWN(t) frequency, Δ f local oscillator frequency interval, i ith local oscillator;
self-correlation between the captured signal and the local PN code PN (t) is obtained to obtain PN code bias P, the order number of the PN (t) is N, and the length is 2N-1；
Correcting the local linear shift register by utilizing the PN code offset P to obtain a corrected I path spread spectrum code;
and (3) obtaining a target distance D by utilizing the relation between the PN code offset P and the distance:
wherein c represents the speed of light;
2) and secondary fine capture: shortening the local oscillator frequency interval delta f', repeating the primary coarse capture process to obtain the Doppler coarse frequency offset fd”；
Finally, the Doppler carrier wave is subjected to coarse frequency deviation fd"and the target distance D are sent to the output display module; coarse frequency deviation f of Doppler carrierd"and PN code bias P are sent to the tracking submodule;
(2.2.3) after receiving the UQPSK signal, the tracking submodule acquires an error frequency component delta f by using a double-path carrier tracking loopdFinishing accurate tracking of carrier frequency; meanwhile, a code tracking ring is used for acquiring a phase error signal of the PN code, so that the accurate tracking of the PN code is completed, and a further corrected demodulation I path spread spectrum code is obtained;
when the double-path carrier tracking loop and the code tracking loop in the tracking sub-module are stable, the demodulated communication data signal S is obtaineddata2(t+τ)；
Using a Doppler coarse frequency offset fd"sum error frequency component Δ fdCalculating Doppler fine frequency offset fd＝fd”+Δfd；
Calculating the target speed by using the relation between the Doppler fine frequency offset and the speed
Finally, the Doppler carrier is finely shifted fdAnd demodulating the communication data signal Sdata2(t + tau) is output to the display module for display, and the demodulated I-path spread spectrum code and demodulated communication data signal Sdata2(t + tau) is fed back to the data result comparison submodule;
(2.2.4) the related interference sub-module adopts a multi-element antenna array to receive UQPSK signals, and then the received signals are multiplied by the further modified demodulation I path spread spectrum codesThe product signal being denoted sUQPSK_PN_DOWN(t) and then subjecting sUQPSK_PN_DOWN(t) as an imaginary number subtracted from its Hilbert change, i.e. scomplex(t)＝-H[sUQPSK_PN_DOWN(t)]+jsUQPSK_PN_DOWN(t), sequentially carrying out A/D conversion and DDC conversion on the obtained signals, and finally selecting two paths of non-adjacent signals to carry out relevant interference operation, further calculating a pitch angle and an azimuth angle, and outputting the pitch angle and the azimuth angle to a display module for display;
and (2.2.5) comparing the original data with the processed data by the data result comparison submodule, calculating the error rate of various signals, and outputting the error rate to the display module for display.
2. The method for implementing measurement and control communication based on the UQPSK unified signal model according to claim 1, wherein the tracking sub-module adopts a dual-loop structure in which a dual-path carrier tracking loop and a code tracking loop are synchronized.
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