CN105187059B - A kind of broadband Low phase noise local frequency combiner circuit and method - Google Patents
A kind of broadband Low phase noise local frequency combiner circuit and method Download PDFInfo
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- CN105187059B CN105187059B CN201510429848.0A CN201510429848A CN105187059B CN 105187059 B CN105187059 B CN 105187059B CN 201510429848 A CN201510429848 A CN 201510429848A CN 105187059 B CN105187059 B CN 105187059B
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Abstract
The present invention proposes a kind of broadband Low phase noise local frequency combiner circuit, including：Direct Digital Frequency Synthesizers, frequency multiplier, low-pass filter, high-pass filter, bandpass filter, orthogonal mixer, frequency mixer, amplifier, integer frequency divider, phase discriminator, loop filter, voltage controlled oscillator, coupler.The present invention uses high phase comparison frequency phase demodulation first, reduces the deterioration of mutually making an uproar of loop；Secondly loop uses integer frequency divider, eliminates influence of the mantissa of fractional frequency division to mutually making an uproar；Quadrature up-conversion is carried out using the baseband signal that Direct Digital Frequency Synthesizers generate, the high-frequency signal of high-resolution Low phase noise is generated, carries out being mixed down coversion with the output of voltage controlled oscillator, the signal after down coversion is made to become the signal of one big stepping；Voltage controlled oscillator exports and high-resolution Low phase noise signal down coversion, reduces the input frequency of integer frequency divider, reduces the frequency dividing ratio of integral frequency divisioil.
Description
Technical field
The present invention relates to radio frequency and microwave regime, more particularly to a kind of broadband Low phase noise local frequency combiner circuit also relates to
And a kind of broadband Low phase noise local frequency synthetic method.
Background technology
Spectrum analysis technique is radio frequency and the very important analysis method of microwave regime, in the design of modern spectrum analyzer
In, super-heterodyne technique is mostly used, therefore, local oscillation signal, especially the first local oscillation signal directly determine spectrum analyzer
Performance.The noiseproof feature that local oscillation signal can greatly be improved using PHASE-LOCKED LOOP PLL TECHNIQUE, to improve the survey of spectrum analyzer
Try performance.
The development of frequency synthesis technique mainly by traditional analog direct synthesizer, the indirect frequency synthesizer of phaselocked loop,
Direct Digital Frequency Synthesizers three phases are constituted, and the index of output signal is higher and higher, and the technical sophistication degree of realization is also got over
Come higher.Existing frequency synthesis mode mainly has direct mode, indirect mode, digital form and combines these three modes
The hybrid mode got up.
Traditional Direct frequency synthesizer, exactly using circuit devcie to the adding of signal frequency, subtract, multiplication and division arithmetic function
Generate the mode of new signal frequency.
Phase-locked loop frequency synthesis mode, the phase noise by synthesizing phase discrimination signal and voltage controlled oscillator improve output signal
Phase noise inhibits phase demodulation spuious using loop filter.
Current frequency synthesis technique has bicyclic or polycyclic frequency synthesizer of phase locking, phaselocked loop to add direct digital synthesis technique
Hybrid frequency synthesizer of device etc..
In prior art, the influence that loop divider is brought is reduced using a harmonic wave Sampling frequency mixer；As
The local oscillator excitation signal of harmonic wave Sampling frequency mixer, since highest needs frequency multiplication to tens times, fundamental wave needs fabulous phase to make an uproar
Sound index.Direct digital synthesis technique (DDS) is due to possessing fabulous index of mutually making an uproar (depend on input reference signal) and very
High frequency resolution, can be as the variable reference signal of phase-locked loop circuit, to obtain the voltage controlled oscillator of optional frequency
(VCO) output signal.
As shown in Figure 1, entire circuit can be divided into sampling loop, DDS, preset adjustment loop, several parts such as main phase-locked loop.
Sampling loop is several by sampling voltage controlled oscillator, the first amplifier, frequency mixer, sampling ring phase discriminator, sampling circle filtering
A major part composition, function are to provide the input local oscillator of the sampling mixing with cline frequency range, good phases noise
Signal is sent into the sampling frequency mixer of main ring after the second amplifier.
The reference signal of the part Direct Digital Frequency Synthesizers (DDS), input passes through integer frequency device, the first band logical successively
Filter, the second amplifier, Direct Digital Frequency Synthesizers, third amplifier, the second bandpass filter generate main phase-locked loop
With the phase discriminator input signal of preset adjustment loop.
Preset adjustment loop segments, including the second coupler, the second integer frequency divider, the 4th integer frequency divider, preset ring mirror
Phase device, preset circle filtering, preset ring switch, by the switching of main ring switch and preset ring switch, by the frequency of main voltage controlled oscillator
Rate is tuned in advance near required frequency, in order to avoid losing lock and wrong lock occur when main ring works.
The main voltage controlled oscillator output frequency of main phase-locked loop is coupled out Partial Power by the first coupler and passes through first
Integer frequency divider exists using sampling frequency mixer is entered after low-pass filter, the 6th amplifier with the signal from sampling loop
It is mixed together in sampling frequency mixer, the signal of generation is defeated by third bandpass filter, the 5th amplifier and the phase demodulation from DDS
Enter signal in main ring phase discriminator phase demodulation, phase demodulation output is using main voltage controlled oscillators of control such as main ring filtering, main ring switches.
The prior art realizes that the synthesis of broadband Low phase noise local frequency, circuit are divided into sampling using polycyclic frequency synthesizer of phase locking
Loop, Direct Digital Frequency Synthesizers (DDS), preset adjustment loop, main phase-locked loop etc., circuit complexity is very high, it is of high cost,
Debugging difficulty is big, and the locking of each Frequency point is required for controlling each section circuit, and switches preset adjustment loop and master
Phase-locked loop, control are excessively complicated.
Invention content
To solve the deficiencies in the prior art, a kind of broadband Low phase noise local frequency combiner circuit of present invention proposition and method,
Direct Digital Frequency Synthesizers are added using monocycle Phase locking frequency synthesis loop, it is no longer necessary to sample local oscillation frequency synthesizer loop,
Preset adjustment secondary ring, simple, at low cost, the easy debugging of circuit.
The technical proposal of the invention is realized in this way：
A kind of broadband Low phase noise local frequency combiner circuit, is divided into three tunnels by input signal, is respectively transmitted to the first frequency multiplication
Device, the second frequency multiplier and Direct Digital Frequency Synthesizers；
The signal all the way of the first frequency multiplier is transmitted to by the first frequency multiplier, the first amplifier, the first high-pass filter, the
Local oscillation signal after two amplifiers as orthogonal mixer；
It is transmitted to the signal all the way of the second frequency multiplier, by generating phaselocked loop using the second high-pass filter after frequency multiplication
Phase demodulation reference frequency signal；
The reference frequency signal of Direct Digital Frequency Synthesizers is transmitted to after frequency multiplication inside Direct Digital Frequency Synthesizers
As the reference clock of Direct Digital Frequency Synthesizers, the digital orthogonal baseband signal that two-way frequency same phase difference is 90 degree is generated,
Two-way baseband signal after the first low-pass filter and the second low-pass filter filter out reference clock signal, is input to just respectively
The roads I and the input of the roads Q, the output signal of orthogonal mixer for handing over frequency mixer are input to frequency mixer after bandpass filter；
The output signal of voltage controlled oscillator is coupled out Partial Power by coupler, as mixing after third amplifier
The local oscillation signal of device is put with the intermediate-freuqncy signal of the radiofrequency signal down coversion from bandpass filter, frequency mixer output by the 4th
Enter phase discriminator after big device, third low-pass filter, integer frequency divider, with the phase demodulation reference frequency from the second high-pass filter
Voltage controlled oscillator is tuned by loop filter after signal phase demodulation, makes the Frequency Locking of voltage controlled oscillator in the frequency of setting
On.
Optionally, it is transmitted to the signal all the way of the first frequency multiplier, after frequency multiplication, filtering, amplification, with Direct Digital frequency
The baseband signal that the two-way of rate synthesizer generation is mutually orthogonal is mixed in orthogonal mixer, by orthogonal mixer local oscillator frequency
After rate quadrature up-conversion, the frequency range of output signal is that frequency, bandwidth are 2 times centered on orthogonal mixer local frequency
Maximum base-band signal frequency.
Optionally, the frequency resolution of the orthogonal mixer output signal is exported depending on Direct Digital Frequency Synthesizers
Base-band signal frequency resolution ratio.
Optionally, the output signal of voltage controlled oscillator is first with the output signal down coversion of orthogonal mixer, frequency after frequency conversion
Rate stepping is 2 times of maximum base-band signal frequency, and the signal after frequency mixer down coversion after integer frequency divider by being consolidated
2 times fixed of maximum base-band signal frequency, the maximum base-band signal frequency that the reference frequency of phase discriminator is 2 times, by phase discriminator
Reference frequency obtains the frequency multiplication multiple of the second frequency multiplier.
Optionally, if reference frequency is FR, the frequency multiplication multiple of the first frequency multiplier is integer D1, the frequency multiplication times of the second frequency multiplier
Number is integer D2, and the output frequency of Direct Digital Frequency Synthesizers is FBB, and the frequency dividing ratio of integer frequency divider is Integer N, voltage-controlled to shake
The locking output frequency for swinging device is F, then：
F=FR*D1+FR*D2*N ± FBB
In order to realize that the locking output frequency of voltage controlled oscillator is differentiated in voltage controlled oscillator hunting range with minimum frequency
Rate continuously covers, and the frequency range of FBB is 0~(FR*D2)/2.
The present invention also provides a kind of broadband Low phase noise local frequency synthetic methods, and input signal is divided into three tunnels, respectively
It is transmitted to the first frequency multiplier, the second frequency multiplier and Direct Digital Frequency Synthesizers；
It is transmitted to the signal all the way of the first frequency multiplier, after frequency multiplication, filtering, amplification, with direct digital synthesis technique
The baseband signal that the two-way of device generation is mutually orthogonal is mixed in orthogonal mixer, orthogonal by orthogonal mixer local frequency
It is input to bandpass filter after up-conversion；
It is transmitted to the signal all the way of the second frequency multiplier, by generating phaselocked loop using the second high-pass filter after frequency multiplication
Phase demodulation reference frequency signal；
The reference frequency signal of Direct Digital Frequency Synthesizers is transmitted to after frequency multiplication inside Direct Digital Frequency Synthesizers
As the reference clock of Direct Digital Frequency Synthesizers, the digital orthogonal baseband signal that production two-way frequency same phase difference is 90 degree,
Two-way baseband signal after the first low-pass filter and the second low-pass filter filter out reference clock signal, is input to just respectively
The roads I and the input of the roads Q, the output signal of orthogonal mixer for handing over frequency mixer are input to frequency mixer after bandpass filter；
The output signal of voltage controlled oscillator is coupled out Partial Power by coupler, as mixing after third amplifier
The local oscillation signal of device is put with the intermediate-freuqncy signal of the radiofrequency signal down coversion from bandpass filter, frequency mixer output by the 4th
Enter phase discriminator after big device, third low-pass filter, integer frequency divider, with the phase demodulation reference frequency from the second high-pass filter
Voltage controlled oscillator is tuned by loop filter after signal phase demodulation, makes the Frequency Locking of voltage controlled oscillator in the frequency of setting
On.
Optionally, the frequency range of the orthogonal mixer output signal is the frequency centered on orthogonal mixer local frequency
Rate, bandwidth are 2 times of maximum base-band signal frequencies.
Optionally, the frequency resolution of the orthogonal mixer output signal is exported depending on Direct Digital Frequency Synthesizers
Base-band signal frequency resolution ratio.
Optionally, the output signal of voltage controlled oscillator is first with the output signal down coversion of orthogonal mixer, frequency after frequency conversion
Rate stepping is 2 times of maximum base-band signal frequency, and the signal after frequency mixer down coversion after integer frequency divider by being consolidated
2 times fixed of maximum base-band signal frequency, the maximum base-band signal frequency that the reference frequency of phase discriminator is 2 times, by phase discriminator
Reference frequency obtains the frequency multiplication multiple of the second frequency multiplier.
Optionally, if reference frequency is FR, the frequency multiplication multiple of the first frequency multiplier is integer D1, the frequency multiplication times of the second frequency multiplier
Number is integer D2, and the output frequency of Direct Digital Frequency Synthesizers is FBB, and the frequency dividing ratio of integer frequency divider is Integer N, voltage-controlled to shake
The locking output frequency for swinging device is F, then：
F=FR*D1+FR*D2*N ± FBB
In order to realize that the locking output frequency of voltage controlled oscillator is differentiated in voltage controlled oscillator hunting range with minimum frequency
Rate continuously covers, and the frequency range of FBB is 0~(FR*D2)/2.
The beneficial effects of the invention are as follows：
(1) circuit design is simplified, it is no longer necessary to sample local oscillation frequency synthesizer loop, preset adjustment secondary ring, circuit
Simply, the software control of at low cost, easy debugging, circuit is simple；
(2) frequency mixer is used to reduce the input frequency of integer frequency divider, to reduce the frequency dividing ratio of integral frequency divisioil, and not
Need preset adjustment secondary ring；
(3) method for not using sampling to be mixed eliminates sampling local oscillation frequency synthesizer loop；
(4) realization of low phase noise, other than lowering integer frequency divider input frequency using frequency mixer down coversion, also
It uses high phase comparison frequency and carries out phase demodulation, reduce frequency dividing ratio；
(5) in order to realize integral frequency divisioil, the frequency mixer before frequency dividing, voltage controlled oscillator exports and one high-resolution low
High-frequency signal of mutually making an uproar is mixed；
(6) high-frequency signal of high-resolution Low phase noise is realized by way of quadrature up-conversion.
Description of the drawings
In order to more clearly explain the embodiment of the invention or the technical proposal in the existing technology, to embodiment or will show below
There is attached drawing needed in technology description to be briefly described, it should be apparent that, the accompanying drawings in the following description is only this
Some embodiments of invention for those of ordinary skill in the art without creative efforts, can be with
Obtain other attached drawings according to these attached drawings.
Fig. 1 is polycyclic locking phase local frequency combiner circuit schematic diagram in the prior art；
The broadband Low phase noise local frequency combiner circuit schematic diagram of Fig. 2 present invention.
Specific implementation mode
Following will be combined with the drawings in the embodiments of the present invention, and technical solution in the embodiment of the present invention carries out clear, complete
Site preparation describes, it is clear that described embodiments are only a part of the embodiments of the present invention, instead of all the embodiments.It is based on
Embodiment in the present invention, it is obtained by those of ordinary skill in the art without making creative efforts every other
Embodiment shall fall within the protection scope of the present invention.
As shown in Fig. 2, the broadband Low phase noise local frequency combiner circuit of the present invention includes：Direct Digital Frequency Synthesizers,
Frequency multiplier, low-pass filter, high-pass filter, bandpass filter, orthogonal mixer, frequency mixer, amplifier, integer frequency divider,
Phase discriminator, loop filter, voltage controlled oscillator, coupler.
As shown in Fig. 2, input signal is divided into three tunnels by the broadband Low phase noise local frequency combiner circuit of the present invention, pass respectively
It is sent to the first frequency multiplier, the second frequency multiplier and Direct Digital Frequency Synthesizers.
The signal all the way of the first frequency multiplier is transmitted to by the first frequency multiplier, the first amplifier, the first high-pass filter, the
Local oscillation signal after two amplifiers as orthogonal mixer.
It is transmitted to the signal all the way of the second frequency multiplier, by generating phaselocked loop using the second high-pass filter after frequency multiplication
Phase demodulation reference frequency signal.
It is transmitted to reference frequency conduct after frequency multiplication inside Direct Digital Frequency Synthesizers of Direct Digital Frequency Synthesizers
The reference clock of Direct Digital Frequency Synthesizers generates the digital orthogonal baseband signal that two-way frequency same phase difference is 90 degree, two-way
Baseband signal after the first low-pass filter and the second low-pass filter filter out reference clock signal, is input to orthogonal mixed respectively
The roads I of frequency device and the input of the roads Q.
The output signal of orthogonal mixer is input to frequency mixer after bandpass filter.
The output signal of voltage controlled oscillator by coupler be coupled out fraction power be used as after third amplifier it is mixed
The local oscillation signal of frequency device, with the radiofrequency signal down coversion from bandpass filter, the intermediate frequency of frequency mixer output is by the 4th amplification
Enter phase discriminator after device, third low-pass filter, integer frequency divider, believes with the phase demodulation reference frequency from the second high-pass filter
Voltage controlled oscillator is tuned by loop filter after number phase demodulation, makes the Frequency Locking of voltage controlled oscillator in the frequency of setting.
The present invention broadband Low phase noise local frequency combiner circuit operation principle be：
It is transmitted to the signal all the way of the first frequency multiplier, after frequency multiplication, filtering, amplification, with direct digital synthesis technique
The baseband signal that the two-way of device generation is mutually orthogonal is mixed in orthogonal mixer, orthogonal by orthogonal mixer local frequency
After up-conversion, the frequency range of output signal is that frequency, bandwidth are 2 times of maximum bases centered on orthogonal mixer local frequency
The frequency resolution of band signal frequency, output signal depends on the base-band signal frequency resolution of Direct Digital Frequency Synthesizers output
Rate.
The output of voltage controlled oscillator is first with the output signal down coversion of orthogonal mixer, and frequency stepping is 2 times after frequency conversion
Maximum base-band signal frequency, the signal after frequency mixer down coversion after integer frequency divider by obtaining fixed 2 times most
Big base-band signal frequency, the reference frequency of phase discriminator are 2 times of maximum base-band signal frequency, can by the reference frequency of phase discriminator
To obtain the frequency multiplication multiple of the second frequency multiplier.
If reference frequency is FR, the frequency multiplication multiple of the first frequency multiplier is integer D1, and the frequency multiplication multiple of the second frequency multiplier is whole
The output frequency of number D2, Direct Digital Frequency Synthesizers are FBB, and the frequency dividing ratio of integer frequency divider is Integer N, voltage controlled oscillator
Locking output frequency is F, then：
F=FR*D1+FR*D2*N ± FBB
In order to realize that the locking output frequency of voltage controlled oscillator is differentiated in voltage controlled oscillator hunting range with minimum frequency
Rate continuously covers, and the frequency range of FBB is 0~(FR*D2)/2.
The local frequency synthetic method phase demodulation frequency of the present invention is higher, and performance of mutually making an uproar is better, i.e., FR*D2 is higher, integer point
The frequency dividing ratio of frequency device is smaller, and the phase noise of output frequency is lower, but with the increase of FR*D2, the frequency range of FBB also can
It broadens, it is also higher to the performance requirement of Direct Digital Frequency Synthesizers.
The present invention adds Direct Digital Frequency Synthesizers (DDS) to realize broadband Low phase noise sheet by monocycle frequency synthesizer of phase locking
Vibration frequency synthesizes, and high resolution frequency signal exports the radiofrequency signal of down coversion as voltage controlled oscillator (VCO), solves by more
Ring frequency synthesizer of phase locking realizes the circuit of broadband Low phase noise local frequency synthesis and the problem of control excessively complexity.
The present invention uses monocycle frequency synthesizer of phase locking, it is no longer necessary to sample local oscillation frequency synthesizer loop, preset adjustment is auxiliary
Loop is helped, circuit structure is simplified, the software control of at low cost, easy debugging, circuit is simple.
The prior art uses sampling mixing, and losing lock is locked in order not to which mistake occurs, and increases preset adjustment secondary ring, and originally
Invention uses frequency mixer for fundamental mixer, reduces the input frequency of integer frequency divider, to reduce the frequency dividing ratio of integral frequency divisioil,
And preset adjustment secondary ring is not needed.Method due to not using sampling to be mixed, also eliminates sampling local oscillation frequency synthesizer
Loop.
The realization of low phase noise of the present invention, in addition to using frequency mixer down coversion lower integer frequency divider input frequency it
Outside, it additionally uses high phase comparison frequency and carries out phase demodulation, reduce frequency dividing ratio.
The present invention is in order to realize integral frequency divisioil, the frequency mixer before frequency dividing, voltage controlled oscillator output and a high-resolution
Low phase noise high-frequency signal be mixed, obtain the larger variable frequency signal of frequency interval.The present invention passes through between frequency
With phase demodulation reference frequency phase demodulation after larger variable frequency signal integral frequency divisioil, control by loop filter after phase demodulation voltage-controlled
Oscillator (VCO) realizes Frequency Locking.The high-frequency signal of high-resolution Low phase noise is realized by way of quadrature up-conversion.
The present invention need not calculate the parameters such as sampling local frequency, sampling number, preset voltage according to local frequency, simplify
FREQUENCY CONTROL flow.
The foregoing is merely illustrative of the preferred embodiments of the present invention, is not intended to limit the invention, all essences in the present invention
With within principle, any modification, equivalent replacement, improvement and so on should all be included in the protection scope of the present invention god.
Claims (10)
1. a kind of broadband Low phase noise local frequency combiner circuit, which is characterized in that input signal is divided into three tunnels, is respectively transmitted to
First frequency multiplier, the second frequency multiplier and Direct Digital Frequency Synthesizers；
The signal all the way for being transmitted to the first frequency multiplier is put by the first frequency multiplier, the first amplifier, the first high-pass filter, second
Local oscillation signal after big device as orthogonal mixer；
It is transmitted to the signal all the way of the second frequency multiplier, by the mirror for generating phaselocked loop after frequency multiplication using the second high-pass filter
Phase reference frequency signal；
The input signal for being transmitted to Direct Digital Frequency Synthesizers is used as directly after frequency multiplication inside Direct Digital Frequency Synthesizers
The reference clock of digital frequency synthesizer generates the digital orthogonal baseband signal that two-way frequency same phase difference is 90 degree, two-way base band
Signal after the first low-pass filter and the second low-pass filter filter out reference clock signal, is input to orthogonal mixer respectively
The roads I and the input of the roads Q, the output signal of orthogonal mixer is input to frequency mixer after bandpass filter；
The output signal of voltage controlled oscillator is coupled out Partial Power by coupler, as frequency mixer after third amplifier
Local oscillation signal, and the radiofrequency signal down coversion from bandpass filter, the intermediate-freuqncy signal of frequency mixer output by the 4th amplifier,
Enter phase discriminator after third low-pass filter, integer frequency divider, with the phase demodulation reference frequency signal from the second high-pass filter
Voltage controlled oscillator is tuned by loop filter after phase demodulation, makes the Frequency Locking of voltage controlled oscillator in the frequency of setting.
2. a kind of broadband Low phase noise local frequency combiner circuit as described in claim 1, which is characterized in that be transmitted to first times
The signal all the way of frequency device, after frequency multiplication, filtering, amplification, the two-way generated with Direct Digital Frequency Synthesizers is mutually orthogonal
Baseband signal be mixed in orthogonal mixer, after orthogonal mixer local frequency quadrature up-conversion, output signal
Frequency range be that frequency, bandwidth are 2 times of maximum base-band signal frequencies centered on orthogonal mixer local frequency.
3. a kind of broadband Low phase noise local frequency combiner circuit as claimed in claim 2, which is characterized in that the orthogonal mixing
The frequency resolution of device output signal depends on the base-band signal frequency resolution ratio of Direct Digital Frequency Synthesizers output.
4. a kind of broadband Low phase noise local frequency combiner circuit as described in claim 1, which is characterized in that voltage controlled oscillator
Output signal is first with the output signal down coversion of orthogonal mixer, the maximum baseband signal frequency that frequency stepping is 2 times after frequency conversion
Rate, the signal after frequency mixer down coversion reflect by obtaining fixed 2 times of maximum base-band signal frequency after integer frequency divider
The maximum base-band signal frequency that the reference frequency of phase device is 2 times, the frequency multiplication of the second frequency multiplier is obtained by the reference frequency of phase discriminator
Multiple.
5. a kind of broadband Low phase noise local frequency combiner circuit as described in claim 1, which is characterized in that
If reference frequency is FR, the frequency multiplication multiple of the first frequency multiplier is integer D1, and the frequency multiplication multiple of the second frequency multiplier is integer D2,
The output frequency of Direct Digital Frequency Synthesizers is FBB, and the frequency dividing ratio of integer frequency divider is Integer N, the locking of voltage controlled oscillator
Output frequency is F, then：
F=FR*D1+FR*D2*N ± FBB
In order to realize that the locking output frequency of voltage controlled oscillator is connected in voltage controlled oscillator hunting range with minimum frequency resolution ratio
The frequency range of continuous covering, FBB is 0~(FR*D2)/2.
6. a kind of broadband Low phase noise local frequency synthetic method, which is characterized in that input signal is divided into three tunnels, is respectively transmitted to
First frequency multiplier, the second frequency multiplier and Direct Digital Frequency Synthesizers；
It is transmitted to the signal all the way of the first frequency multiplier, after frequency multiplication, filtering, amplification, is given birth to Direct Digital Frequency Synthesizers
At the mutually orthogonal baseband signal of two-way be mixed in orthogonal mixer, just handing in change by orthogonal mixer local frequency
It is input to bandpass filter after frequency；
It is transmitted to the signal all the way of the second frequency multiplier, by the mirror for generating phaselocked loop after frequency multiplication using the second high-pass filter
Phase reference frequency signal；
The input signal for being transmitted to Direct Digital Frequency Synthesizers is used as directly after frequency multiplication inside Direct Digital Frequency Synthesizers
The reference clock of digital frequency synthesizer, the digital orthogonal baseband signal that production two-way frequency same phase difference is 90 degree, two-way base band
Signal after the first low-pass filter and the second low-pass filter filter out reference clock signal, is input to orthogonal mixer respectively
The roads I and the input of the roads Q, the output signal of orthogonal mixer is input to frequency mixer after bandpass filter；
The output signal of voltage controlled oscillator is coupled out Partial Power by coupler, as frequency mixer after third amplifier
Local oscillation signal, and the radiofrequency signal down coversion from bandpass filter, the intermediate-freuqncy signal of frequency mixer output by the 4th amplifier,
Enter phase discriminator after third low-pass filter, integer frequency divider, with the phase demodulation reference frequency signal from the second high-pass filter
Voltage controlled oscillator is tuned by loop filter after phase demodulation, makes the Frequency Locking of voltage controlled oscillator in the frequency of setting.
7. a kind of broadband Low phase noise local frequency synthetic method as claimed in claim 6, which is characterized in that
The frequency range of the orthogonal mixer output signal is frequency, bandwidth 2 centered on orthogonal mixer local frequency
Maximum base-band signal frequency again.
8. a kind of broadband Low phase noise local frequency synthetic method as claimed in claim 7, which is characterized in that the orthogonal mixing
The frequency resolution of device output signal depends on the base-band signal frequency resolution ratio of Direct Digital Frequency Synthesizers output.
9. a kind of broadband Low phase noise local frequency synthetic method as claimed in claim 6, which is characterized in that voltage controlled oscillator
Output signal is first with the output signal down coversion of orthogonal mixer, the maximum baseband signal frequency that frequency stepping is 2 times after frequency conversion
Rate, the signal after frequency mixer down coversion reflect by obtaining fixed 2 times of maximum base-band signal frequency after integer frequency divider
The maximum base-band signal frequency that the reference frequency of phase device is 2 times, the frequency multiplication of the second frequency multiplier is obtained by the reference frequency of phase discriminator
Multiple.
10. a kind of broadband Low phase noise local frequency synthetic method as claimed in claim 6, which is characterized in that
If reference frequency is FR, the frequency multiplication multiple of the first frequency multiplier is integer D1, and the frequency multiplication multiple of the second frequency multiplier is integer D2,
The output frequency of Direct Digital Frequency Synthesizers is FBB, and the frequency dividing ratio of integer frequency divider is Integer N, the locking of voltage controlled oscillator
Output frequency is F, then：
F=FR*D1+FR*D2*N ± FBB
In order to realize that the locking output frequency of voltage controlled oscillator is connected in voltage controlled oscillator hunting range with minimum frequency resolution ratio
The frequency range of continuous covering, FBB is 0~(FR*D2)/2.
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Families Citing this family (21)
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| CN115395950B (en) * | 2022-08-01 | 2023-08-15 | 北京华力睿源电子有限公司 | Frequency synthesizer |
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| CN116470909A (en) * | 2023-06-14 | 2023-07-21 | 成都世源频控技术股份有限公司 | Low-phase noise fine stepping frequency synthesis circuit and synthesis method thereof |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101242181A (en) * | 2008-03-20 | 2008-08-13 | 北京创毅视讯科技有限公司 | A frequency mixer and frequency mixing method |
| CN101834604A (en) * | 2009-03-13 | 2010-09-15 | 北京北广科技股份有限公司 | High-resolution and low-spurious-frequency synthesizer of UHF (Ultrahigh Frequency) frequency band |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2010237172A (en) * | 2009-03-31 | 2010-10-21 | Toshiba Corp | Fmcw signal generation circuit |
-
2015
- 2015-07-16 CN CN201510429848.0A patent/CN105187059B/en not_active Expired - Fee Related
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101242181A (en) * | 2008-03-20 | 2008-08-13 | 北京创毅视讯科技有限公司 | A frequency mixer and frequency mixing method |
| CN101834604A (en) * | 2009-03-13 | 2010-09-15 | 北京北广科技股份有限公司 | High-resolution and low-spurious-frequency synthesizer of UHF (Ultrahigh Frequency) frequency band |
Non-Patent Citations (1)
| Title |
|---|
| Ka波段高性能频率合成器的设计;任威;《中国优秀硕士学位论文全文数据库信息科技辑》;20070915(第3期);第18页 * |
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