CN104779806B - Asymmetrical half-bridge anti exciting converter and its control method - Google Patents
Asymmetrical half-bridge anti exciting converter and its control method Download PDFInfo
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- CN104779806B CN104779806B CN201510218441.3A CN201510218441A CN104779806B CN 104779806 B CN104779806 B CN 104779806B CN 201510218441 A CN201510218441 A CN 201510218441A CN 104779806 B CN104779806 B CN 104779806B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
- Inverter Devices (AREA)
Abstract
The present invention relates to switch converters field, its object is to provide it is a kind of can take into account the efficiency of underloading and heavy duty, dutycycle can be reduced under underloading, reduce primary side peak point current, circulating energy is reduced, VFC can also be realized, effectively reduction no-load power consumption and underloading loss；Complementation can be realized under heavy loads, part energy is transmitted by capacitance to greatest extent, the energy of transformer storage is reduced, and two switching tubes is realized that no-voltage is open-minded, improve the control method of the asymmetrical half-bridge anti exciting converter of the efficiency of converter.
Description
Technical field
The present invention relates to the control in switch converters field, more particularly to asymmetrical half-bridge flyback class switch converters.
Background technology
As the development of field of power electronics rapidly causes the more and more extensive of switch converters application, particularly people couple
The switch converters of high power density, high reliability and small size propose more requirements.General traditional small-power AC/DC
Conversion realizes that it has the advantages that simple in construction, with low cost using flyback topologies；
But common flyback topologies are hard switchings, and leakage inductance energy can not be reclaimed, therefore limit the effect of middle low power
Rate and volume, in order to meet the miniaturization, lightweight, modular development trend of power inverter, soft switch technique has turned into
One of focus of Power Electronic Technique." Sofe Switch " refers to zero voltage switching or zero current switching, and it is to utilize resonance principle, is made
The switch tube voltage (or electric current) of switch converters presses sinusoidal (or quasi sine) rule change, when voltage zero-cross, opens device
Logical (or during electric current natural zero-crossing, turning off device), it is zero to realize switching loss, so that switching frequency is improved, reduction transformer,
The volume of inductance.Although soft switch technique can realize the miniaturization of power inverter, modularization etc., many circuit examples
Such as LLC, circuit becomes extremely complex so that the cost increase of the converter of middle low power, is often unfavorable for commercial competition, without
Symmetrical half bridge circuit with the number of devices and complexity of common circuit of reversed excitation relatively under conditions of can realize two pipes
The no-voltage of son is open-minded, reclaims leakage inductance energy and easily realizes self-device synchronous rectification, effectively while raising efficiency
Reduce volume of transformer, as a relatively good application scheme.
Conventional asymmetry half-bridge circuit circuit diagram is as shown in Fig. 1-1 and 1-2 at present, in wherein Fig. 1-1 based on upper pipe QH
Switching tube, down tube QL is clamping switch tube, and upper pipe QH is clamping switch tube in Fig. 1-2, and down tube QL is main switch, two kinds of circuits
Effect is the same, and simply winding position is different.
Now by taking Fig. 1-1 as an example, the work wave of its stable state is as shown in Fig. 2 VGSH and VGSL are respectively top tube and down tube
Drive signal waveform；Ic is the current waveform above capacitance, while being also the current waveform above primary side winding, Ilm is
Excitation current waveform above magnetizing inductance, in addition to dotted portion, excitation current waveform and capacitance current waveform are
Unanimously overlap；VdsH and VdsL are respectively the waveform voltage signal of the drain-to-source of top tube and down tube.If the driving of supervisor
Signal VGSH dutycycle is D, then the dutycycle of clamper tube is (1-D), to avoid supervisor and clamper tube is common needs to leave one
Fixed dead time, the work period is T.Analyze, now will for convenience of the course of work to transformer primary side winding in circuit
The primary side winding of transformer, is equivalent to leakage inductance LK and magnetizing inductance two parts to illustrate.At the T0 moment, upper pipe drives VGSH
For high level, upper pipe is open-minded, and the energy of input passes through QH, capacitance Cb, leakage inductance Lk and magnetizing inductance in the T0-T1 periods
This primary Ioops to transformer excitation, exciting curent first from negative sense be linearly reduced to zero after linearly increasing, now primary side electric capacity
On electric current and exciting current overlap, capacitance, leakage inductance, transformer storage energy, secondary commutation diode D negative senses cut-off,
To T1 moment, upper pipe shut-off；In the T1-T2 times, upper pipe is off state, and down tube is not opened yet, and time period is dead band
Time, because leakage inductance and transformer magnetizing inductance want afterflow, the junction capacity of upper down tube, blocking electricity in this section of dead time
Resonance occurs for appearance, leakage inductance, magnetizing inductance, extracts the energy of QL junction capacity, VdsL voltages decline, while the junction capacity to QH is filled
Electricity, the rising of VdsH voltages, exciting current is reduced because of the voltage for so organizing two ends so while, T2 very small in the still amplitude that increases
Moment QH junction capacity voltage reaches highest, and QL junction capacity voltage is pumped to no-voltage, and now down tube is open-minded, then thus real
The no-voltage for having showed down tube is open-minded, and English is abbreviated as ZVS；In the T2-T3 times, commutation diode D forward conductions, transformer primary side
The energy of storage discharges to secondary, exciting current linearly decrease to zero then negative sense it is linearly increasing, meanwhile, leakage inductance Lk, blocking electricity
Hold Cb and occur resonance, primary current presses the track resonance of sine wave, and the energy that now capacitance is stored above passes through normal shock
Process also discharges to secondary, and primary current enters negative sense；T3 moment down tube is turned off, because leakage inductance electric current and exciting current afterflow,
So resonance occurs for the junction capacity of upper down tube, capacitance, leakage inductance, magnetizing inductance, the energy of QH junction capacity, VdsH voltages are extracted
Decline, while the junction capacity charging to QL, the rising of VdsL voltages, exciting current are because the voltage reduction at winding two ends, though
So in negative sense increase, but amplitude is very small, and T4 moment QL junction capacity voltage reaches highest, and QH junction capacity voltage is pumped to
No-voltage, now upper pipe is open-minded, then is so achieved that the no-voltage of pipe is open-minded, thus completes a cycle, then after
Continue according to same work process repeated work.
But this control mode is because be complementary, exciting current is a continuous waveform, dutycycle not with
The change of load and change, therefore peak point current can be very big when unloaded and underloading, the circulation in resonant tank
Energy is big, increases loss, substantially reduces light-load efficiency, while this control mode is unable to frequency conversion, has the risk of saturation, institute
This complementary control mode can be changed to incomplementarity control mode, but the control mode of this incomplementarity can be reduced again
The efficiency of full load.
The content of the invention
To solve the above problems, present invention offer is a kind of can to take into account the efficiency of underloading and heavy duty, it can be dropped under underloading
Low duty ratio, reduce primary side peak point current, reduce circulating energy, VFC can also be realized, effectively reduction no-load power consumption and
Underloading is lost；Complementation can be realized under heavy loads, part energy is transmitted by capacitance to greatest extent, reduce transformer
The energy of storage, and two switching tubes is realized that no-voltage is open-minded, improve the asymmetrical half-bridge inverse-excitation converting of the efficiency of converter
The control method of device.
Corresponding with this, the present invention also provides a kind of asymmetrical half-bridge flyback that can take into account underloading and the efficiency of heavy duty and become
Parallel operation.
For method theme, the present invention provides a kind of control method of asymmetrical half-bridge anti exciting converter, including as follows
Step,
Whether the load signal of asymmetrical half-bridge anti exciting converter is judged higher than the load point set,
If so, then control asymmetrical half-bridge anti exciting converter enters complementary working mode, the complementary working mode be by
The mode of operation of two the first complementary drive signals and the second drive signal control main switch and clamping switch tube, i.e., first
The dutycycle of drive signal driving main switch is value D, then the dutycycle of the second drive signal driving clamping switch tube is value (1-
D)；
If it is not, then control asymmetrical half-bridge anti exciting converter enters incomplementarity mode of operation, the incomplementarity Working mould
Formula is the 3rd drive signal and fourth drive signal the control main switch and the Working mould of clamping switch tube by two incomplementarities
Formula, i.e. the 3rd drive signal drive the shut-off of clamping switch tube with a fixed pulse width signal, and fourth drive signal is to be delayed one
The fixed pulse width signal driving main switch produced after the fixed pulse width of 3rd drive signal and the duration of a dead time
Shut-off, before main switch shut-off and clamping switch tube are not opened, the leakage inductance of transformer and the energy of magnetizing inductance are through clamper
Body diode or junction capacity the formation leakage inductance resonant tank of switching tube and main switch and transformer resonance loop, until clamper is opened
Close pipe to be again turned on, resonance terminates, then restarts the new cycle.
It is preferred that, the leakage inductance resonant tank, during leakage inductance current stream, body two of the leakage inductance energy through clamping switch tube
Pole pipe flow to capacitance Cb with the loop that capacitance Cb is formed；Terminate in leakage inductance current stream, primary current vanishing
When, in the loop that the junction capacity of clamping switch tube is formed with capacitance Cb resonance occurs for leakage inductance energy.
It is preferred that, the transformer resonance loop, when exciting current is discharged into zero, i.e., transformer magnetizing inductance is not clamped
During position, the energy in transformer leakage inductance and magnetizing inductance, respectively in electric capacity Cin, the junction capacity of main switch and capacitance Cb
Occurs resonance in the loop that the loop formed and the junction capacity of clamping switch tube are formed with capacitance Cb.
For product theme, the present invention provides a kind of asymmetrical half-bridge anti exciting converter, including circuit of reversed excitation and driving
Control module, the circuit of reversed excitation includes primary circuit and secondary output rectifier and filter, and the primary circuit is by blocking electricity
Appearance, main switch, the primary side winding of clamping switch tube and transformer are formed by connecting, and the drive control module is used to drive clamper
Switching tube and main switch, it is characterised in that：
The drive control module include Master control chip, feedback voltage module, signal selecting circuit, isolation drive and
Pwm pulse time-sharing circuit,
The Master control chip, for producing two complementary the first drive signals and the second drive signal, and by first
Drive signal and the second driving are directly output to signal selecting circuit, while the first drive signal is also outputted to pwm pulse timesharing
Circuit；
The pwm pulse time-sharing circuit, for receiving the first drive signal, and it is non-according to the first drive signal generation two
The 3rd complementary drive signal and fourth drive signal, and the 3rd drive signal and fourth drive signal are output to signal behavior
Circuit, wherein, the 3rd drive signal is the signal of a fixed pulse width, and fourth drive signal is one the 3rd drive signal of delay
Fixed pulse width and a dead time duration after the fixed pulse width signal that produces；
The feedback voltage module, signal selecting circuit is fed back to for gathering load signal, and by load signal；
The signal selecting circuit, for receiving the first drive signal, the second drive signal, the 3rd drive signal, the 4th
Drive signal and load signal, and the first control signal of output and the second control signal are judged according to load signal,
When load point of the load signal higher than setting, signal selecting circuit is by the first drive signal and the second drive signal
Output is operated in complement mode as the first control signal and the second control signal, control asymmetrical half-bridge anti exciting converter；
When load point of the load signal less than setting, signal selecting circuit is by the 3rd drive signal and fourth drive signal
Output is operated in incomplementarity pattern as the first control signal and the second control signal, control asymmetrical half-bridge anti exciting converter.
It is preferred that, the pwm pulse time-sharing circuit, including resistance R1, R2, electric capacity C1, C2, trigger a and trigger b,
Wherein, a resistance R1 termination Master control chip end, the resistance R1 other end is grounded through electric capacity C1, forms integrating circuit；Resistance
Input of the R1 other end also with trigger a is connected；An electric capacity C2 termination Master control chip end, electric capacity C2 other end warp
Resistance R2 is grounded, and forms differential circuit；Input of the electric capacity C2 other end also with trigger b is connected.
Compared with prior art, the present invention has the advantages that：
(1) no-load power consumption is reduced, light-load efficiency is improved；
(2) underloading can realize VFC, eliminate the risk of magnetic core saturation；
(3) energy can be transmitted using capacitance to greatest extent when heavily loaded, reduces transformer storage energy then
Reduce volume of transformer, while improving the efficiency of complete machine.
(4) the complementary advantage with incomplementarity is combined, the shortcoming of complementary and incomplementarity is eliminated.
Brief description of the drawings
Fig. 1-1 is asymmetrical half-bridge circuit of reversed excitation schematic diagram (upper pipe is main switch)；
Fig. 1-2 is asymmetrical half-bridge circuit of reversed excitation schematic diagram (down tube is main switch)；
Fig. 2 is the asymmetrical half-bridge circuit of reversed excitation working waveform figure under complementary duty state (upper pipe is supervisor)；
Fig. 3 is the asymmetrical half-bridge circuit of reversed excitation working waveform figure under incomplementarity working condition (upper pipe is supervisor)；
Fig. 4 is mixed mode asymmetrical half-bridge circuit of reversed excitation theory diagram of the present invention (upper pipe is main switch)；
Fig. 5 is mixed mode asymmetrical half-bridge circuit of reversed excitation theory diagram of the present invention (down tube is main switch)；
Fig. 6 is the theory diagram of the pwm pulse time-sharing circuit of asymmetrical half-bridge circuit of reversed excitation of the present invention；
Fig. 7 is the signal selecting circuit theory diagram of asymmetrical half-bridge circuit of reversed excitation of the present invention；
Fig. 8 selects oscillogram for the drive signal of asymmetrical half-bridge circuit of reversed excitation of the present invention.
Embodiment
Embodiment one
Referring to Fig. 4, being the theory diagram of embodiment of the present invention asymmetrical half-bridge circuit of reversed excitation, the present invention is existing
The once improvement carried out in technical foundation to control strategy, hereon referred to as mixing control asymmetrical half-bridge flyback scheme, mixing control
The asymmetrical half-bridge anti exciting converter list of molding formula includes：Primary circuit, resonance circuit, output rectifier and filter, main control
IC, signal selecting circuit, isolation drive, pwm pulse time-sharing circuit.For the circuit that upper pipe is main switch, described primary side
Primary side winding, capacitance and the main switch of electric routing transformer are formed by connecting, and described resonance circuit is by clamping switch tube
There is transformer to be formed by connecting with capacitance, described pwm pulse time-sharing circuit is connected to master control IC, signal selecting circuit,
Signal selecting circuit is connected to master control IC, pwm pulse time-sharing circuit, clamper metal-oxide-semiconductor and isolation drive.
The operation principle of the present invention：
Larger when loading, converter is operated in complementary working mode when being operated under non-light condition, its operating wave
The course of work introduced in shape such as Fig. 2, with background technology is the same, and when workload is underloading, converter is operated in non-
Complementary working mode, its course of work are as shown in figure 3, at the T0 moment, upper pipe driving VGSH is high level, and upper pipe is open-minded, T0-T1
In period the energy of input by electric capacity Cin just, upper switching tube QH, capacitance Cb, leakage inductance Lk and magnetizing inductance arrive again
Electric capacity Cin bears this primary Ioops to transformer excitation, exciting curent first from negative sense be linearly reduced to zero after it is linearly increasing, now
Electric current and exciting current on primary side electric capacity are overlapped, capacitance Cb, leakage inductance Lk, transformer storage energy, the pole of secondary rectification two
Pipe D negative senses end, to T1 moment, upper pipe QH shut-offs；In the T1-T2 times, upper pipe QH is off state, and down tube QL is not opened yet
Open, during this period of time because leakage inductance and transformer magnetizing inductance want afterflow, the junction capacity of upper, lower tube, capacitance, leakage
Resonance occurs for sense, magnetizing inductance, extracts the energy of down tube QL junction capacity, and resonant tank has two, one be electric capacity Cin just, arrive
Upper pipe QH junction capacity, it is negative to electric capacity Cin to magnetizing inductance to leakage inductance Lk to capacitance Cb.Another is capacitance
Cb, to leakage inductance Lk, to magnetizing inductance, to down tube QL junction capacity, to capacitance Cb.VdsL (drain source voltage of down tube) declines,
The junction capacity to upper pipe QH charges simultaneously, and VdsH (drain source voltage of upper pipe) rises, and exciting current is because the voltage at winding two ends
Reduction, so while VdsH is in increase, but amplitude is very small, and T2 moment QH junction capacity voltage reaches highest, QL knot electricity
Hold voltage and be pumped to no-voltage；In the T2-T3 times, commutation diode D forward conductions, the energy of transformer primary side storage is to secondary
With capacitance resonance occurs for release, exciting current Ilm linear declines, primary side leakage inductance electric current Ic afterflows, under the loop of resonance is
Pipe QL body diode is then return to down tube QL body diodes to capacitance Cb and then to leakage inductance Lk, when arrival T3 moment
Leakage inductance electric current Ic afterflows terminate, and leakage inductance energy is zero, primary current vanishing；It is different from complementary control in the T3-T4 periods,
Although the path of resonance is equally capacitance Cb to leakage inductance Lk magnetizing inductance arrived again arrive down tube QL again and return capacitance Cb,
But the down tube QL in the stage of this in complement mode is in opening state, so the part for participating in resonance is down tube QL, capacitance
Cb, leakage inductance LK, harmonic period are very long.And down tube QL is off state in the incomplementarity control of the present invention, so participating in humorous
The part shaken is capacitance Cb, leakage inductance LK, down tube QL junction capacity, and the very short voltage of harmonic period is very low, so being neglected in waveform
The slightly fluctuation of voltage.The stage transformer continues to provide energy to secondary, and exciting current Ilm continues linear decline, two pipes
The voltage of drain-to-source be basically unchanged, secondary commutation diode D continues to turn on, and T4 moment exciting currents Ilm is discharged into zero,
Commutation diode D electric current is also to zero；In the T4-T5 periods, static exciter inductance is not clamped, so leakage inductance Lk, transformation
Resonance, upper pipe QH and down tube QL knot electricity occur for device magnetizing inductance, two switching tubes QH, QL junction capacity and capacitance Cb
Appearance is to be together in series and then in parallel with input, so two pipes QH, QL junction capacity voltage sum are equal to when resonance
Input voltage, this period is the difference maximum with the control mode of existing complementary duty, and T5 moment down tubes QL is opened, and this section humorous
Shake end；In the T5-T6 times, commutation diode D forward conductions, the energy above leakage inductance Lk energy and capacitance Cb passes through
The process of normal shock is delivered to secondary, exciting current negative sense linear rise, meanwhile, resonance, resonance occur for leakage inductance Lk, capacitance Cb
Loop is leakage inductance Lk, to magnetizing inductance (resonance being not involved in, equivalent to wire), to down tube QL (equivalent to wire), to blocking electricity
Hold Cb, to leakage inductance Lk.Primary current presses the track resonance of sine wave, and the energy that now capacitance Cb is stored above passes through normal shock
Process also discharged to secondary, primary current enters negative sense；T6 moment down tubes QL is turned off, because leakage inductance electric current and exciting current are continuous
Stream is so resonance occurs for upper, lower tube QH, QL junction capacity, capacitance Cb, leakage inductance Lk, magnetizing inductance, and the upper pipe QH of extractions ties electric
The energy of appearance, resonant tank is with being consistent in the T1-T2 periods, and simply the sense of current is opposite.VdsH voltages decline, and give simultaneously
Down tube QL junction capacity charging, VdsL voltages rise, and exciting current Ilm is reduced because of the voltage at winding two ends, so while
Negative sense increase, but amplitude is very small, T7 moment down tubes QL junction capacity voltage reaches highest, upper pipe QH junction capacity voltage quilt
No-voltage is extracted into, now upper pipe QH is open-minded, then is so achieved that pipe QH no-voltage is open-minded, this completes a week
Phase, then continue to according to same work period repeated work.
Examples detailed above provides one kind and can be detected and be operated in corresponding suitable non-according to output loading size
The control mode of the asymmetrical half-bridge anti exciting converter of complementary or complementary state, by such control mode, has taken into account light
Carry and heavily loaded efficiency, dutycycle can be reduced under underloading, reduce primary side peak point current, reduce circulating energy, can also be real
Existing VFC, effectively reduction no-load power consumption and underloading loss；Complementation can be realized under heavy loads, pass through blocking to greatest extent
Electric capacity transmits part energy, reduces the energy of transformer storage, and two switching tubes is realized that no-voltage is open-minded, improves conversion
The efficiency of device.
Wherein, main control IC is common asymmetrical half-bridge driving chip, and itself can export two complementary drivings
Signal GSL1 and GSH1, drive signal GSH1 are directly inputted in signal selecting circuit, GSL1 points of two-way of drive signal, all the way directly
Tap into signal selecting circuit, enter pwm pulse time-sharing circuit all the way in addition, pwm pulse time-sharing circuit by differential circuit and
Integrating circuit produce respectively fixed pulse width drive signal GSL2 and one by delay, delay width is fixed pulse width drive
Dynamic signal GSL2 time, and have with GSL2 the drive signal GSH2 of certain dead time, two signals are input to signal behavior
In circuit, while there is the signal of a reflection load output size, i.e. feedback voltage is also entered among signal selecting circuit, root
According to different loads, signal selector exports two suitable drive signal GSH3 and GSL3, realizes the complementary switching with incomplementarity,
Signal GSH3 exports signal isolation to form GSH4 by isolated drive circuit.Finally, GSH4 is input in pipe QH, and GSL3 is defeated
Enter into down tube QL.
As shown in figure 5, being the theory diagram for the asymmetrical half-bridge circuit of reversed excitation that upper pipe is clamping switch tube, it is for upper pipe
The circuit of clamping switch tube is equally applicable, and the control effect of two kinds of circuits is similar, and simply the link position of each module is right accordingly
Adjust.
Pwm pulse time-sharing circuit is as shown in fig. 6, the drive signal GSL1 of half-bridge main control IC outputs passes through all the way after coming out
Electric capacity C2 then connect a resistance R2 to form a differential circuit, this one end that electric capacity C2 is connected with resistance R2 is while be connected to
Above trigger b, differential voltage waveform shaping is exported for regular square wave；Pwm signal meets a resistance R1 all the way in addition, electricity
Resistance R1 out be followed by an electric capacity C1 to form an integrating circuit, this one end that resistance R1 is connected with electric capacity C1 is while connect
Integral voltage waveform shaping is exported for regular square wave above to trigger a.
Signal selecting circuit block diagram as shown in fig. 7, drive signal GSH1, GSH2, GSL1, GSL2 be separately input to b, c, d,
In tetra- signal transmission gates of e, feedback signal and reference voltage connect comparator a positive input and inverting input respectively, instead
Feedback signal represent it is any can reflect the signal of output loading size, such as chip FB pin voltage or directly from output end resistance
Sampling comes by opto-coupled feedback again, and when feedback signal voltage increase represents the increase of output load current size, reference voltage is
Corresponding feedback signal voltage value under one load point of corresponding design, comparator is exported when load is worth higher than this
High level, ENA signals are changed into high level, and ENB signals are anti-phase for ENA signals, when signal ENA is high level, transmission
Door b, c input signal GSH1 and GSL1 are transmitted over, formation control signal GSH3 and GSL3, two other transmission gate d and e
Signal is not transmitted, now, two signals of GSH3 and GSL3 are complementary drive, realize the complementary duty under heavy duty；On the contrary, when load
ENB is high level when small, and transmission gate b and c do not transmit signal, and input signal GSH2 and GSL2 passes through transmission gate d and e, shape
Into control signal GSH3 and GSL3, now, two signals of GSH3 and GSL3 drive for incomplementarity, realize that underloading incomplementarity works.
Drive signal GSH1, GSL1, GSH2, GSL2, GSH3, GSL3 and GSH4 that the signal selecting circuit is generated drive waveforms are shown
It is intended to as shown in Figure 8.
Waveform under complementary state and under incomplementarity state respectively as shown in Figures 2 and 3, above saying by detailed process
State clear, will not be repeated here.It is worth noting that being equally applicable for upper pipe for the circuit form of clamping switch tube.
It the above is only the preferred embodiment of the present invention, it is noted that above-mentioned preferred embodiment is not construed as pair
The limitation of the present invention, for those skilled in the art, without departing from the spirit and scope of the present invention, also
Some improvements and modifications can be made, circuit is improved and retouched also should be regarded as protection scope of the present invention, here no longer
Repeated with embodiment, protection scope of the present invention should be defined by claim limited range.
Claims (6)
1. a kind of control method of asymmetrical half-bridge anti exciting converter, comprises the following steps,
Whether the load signal of asymmetrical half-bridge anti exciting converter is judged higher than the load point set,
If so, then control asymmetrical half-bridge anti exciting converter enters complementary working mode, the complementary working mode is by two
The mode of operation of the first complementary drive signal and the second drive signal control main switch and clamping switch tube, i.e., the first driving
The dutycycle of signal driving main switch is value D, then the dutycycle of the second drive signal driving clamping switch tube is value (1-D)；
If it is not, then control asymmetrical half-bridge anti exciting converter enters incomplementarity mode of operation, the incomplementarity mode of operation is
By the 3rd drive signal and fourth drive signal the control main switch and the mode of operation of clamping switch tube of two incomplementarities, i.e.,
3rd drive signal drives the shut-off of clamping switch tube with a fixed pulse width signal, and fourth drive signal is with the 3rd drive that is delayed
The fixed pulse width signal produced after the fixed pulse width of dynamic signal and the duration of a dead time drives the shut-off of main switch,
Before main switch is turned off and clamping switch tube do not open, the leakage inductance of transformer and the energy of magnetizing inductance through clamping switch tube and
Body diode or junction capacity the formation leakage inductance resonant tank of main switch and transformer resonance loop, until clamping switch tube is again
Open, resonance terminates, then restarts the new cycle.
2. the control method of asymmetrical half-bridge anti exciting converter according to claim 1, it is characterised in that：The leakage inductance is humorous
Shake loop, during leakage inductance current stream, what body diode of the leakage inductance energy through clamping switch tube was formed with capacitance Cb
Loop flow to capacitance Cb；Terminate in leakage inductance current stream, during primary current vanishing, leakage inductance energy is in clamping switch tube
Occurs resonance in the loop that junction capacity is formed with capacitance Cb.
3. the control method of asymmetrical half-bridge anti exciting converter according to claim 1, it is characterised in that：The transformer
Resonant tank, when exciting current is discharged into zero, i.e., when transformer magnetizing inductance is not clamped, transformer leakage inductance and magnetizing inductance
In energy, respectively in electric capacity Cin, the junction capacity of main switch and capacitance the Cb loop formed and clamping switch tube
Occurs resonance in the loop that junction capacity is formed with capacitance Cb.
4. a kind of asymmetrical half-bridge anti exciting converter, including circuit of reversed excitation and drive control module, the circuit of reversed excitation include original
Side circuit and secondary output rectifier and filter, the primary circuit is by capacitance, main switch, clamping switch tube and transformation
The primary side winding of device is formed by connecting, and the drive control module is used to drive clamping switch tube and main switch, it is characterised in that：
The drive control module, for judging the load signal of asymmetrical half-bridge anti exciting converter whether higher than the load set
Point,
If so, then control asymmetrical half-bridge anti exciting converter enters complementary working mode, the complementary working mode is by two
The mode of operation of the first complementary drive signal and the second drive signal control main switch and clamping switch tube, i.e., the first driving
The dutycycle of signal driving main switch is value D, then the dutycycle of the second drive signal driving clamping switch tube is value (1-D)；
If it is not, then control asymmetrical half-bridge anti exciting converter enters incomplementarity mode of operation, the incomplementarity mode of operation is
By the 3rd drive signal and fourth drive signal the control main switch and the mode of operation of clamping switch tube of two incomplementarities, i.e.,
3rd drive signal drives the shut-off of clamping switch tube with a fixed pulse width signal, and fourth drive signal is with the 3rd drive that is delayed
The fixed pulse width signal produced after the fixed pulse width of dynamic signal and the duration of a dead time drives the shut-off of main switch,
Before main switch is turned off and clamping switch tube do not open, the leakage inductance of transformer and the energy of magnetizing inductance through clamping switch tube and
Body diode or junction capacity the formation leakage inductance resonant tank of main switch and transformer resonance loop, until clamping switch tube is again
Open, resonance terminates, then restarts the new cycle.
5. asymmetrical half-bridge anti exciting converter according to claim 4, it is characterised in that：The drive control module includes
Master control chip, feedback voltage module, signal selecting circuit, isolation drive and pwm pulse time-sharing circuit,
The Master control chip, drives for producing two complementary the first drive signals and the second drive signal, and by first
Signal and the second driving are directly output to signal selecting circuit, while the first drive signal is also outputted to pwm pulse time-sharing circuit；
The pwm pulse time-sharing circuit, two incomplementarities are produced for receiving the first drive signal, and according to the first drive signal
The 3rd drive signal and fourth drive signal, and by the 3rd drive signal and fourth drive signal be output to signal behavior electricity
Road, wherein, the 3rd drive signal is the signal of a fixed pulse width, and fourth drive signal is one the 3rd drive signal of delay
The fixed pulse width signal produced after the duration of fixed pulse width and a dead time；
The feedback voltage module, signal selecting circuit is fed back to for gathering load signal, and by load signal；
The signal selecting circuit, for receiving the first drive signal, the second drive signal, the 3rd drive signal, the 4th driving
Signal and load signal, and the first control signal of output and the second control signal are judged according to load signal,
When load point of the load signal higher than setting, signal selecting circuit exports the first drive signal and the second drive signal
As the first control signal and the second control signal, control asymmetrical half-bridge anti exciting converter is operated in complement mode；
When load point of the load signal less than setting, signal selecting circuit exports the 3rd drive signal and fourth drive signal
As the first control signal and the second control signal, control asymmetrical half-bridge anti exciting converter is operated in incomplementarity pattern.
6. asymmetrical half-bridge anti exciting converter according to claim 5, it is characterised in that：The pwm pulse time-sharing circuit,
Including resistance R1, resistance R2, electric capacity C1, electric capacity C2, the first trigger a and the second trigger b, wherein, a resistance R1 termination
Master control chip end, the resistance R1 other end is grounded through electric capacity C1, forms integrating circuit；The resistance R1 other end is also touched with first
Send out device a input connection；An electric capacity C2 termination Master control chip end, the electric capacity C2 other end is grounded through resistance R2, formed
Differential circuit；Input of the electric capacity C2 other end also with the second trigger b is connected.
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| CN106100352B (en) * | 2016-08-05 | 2019-02-05 | 广州金升阳科技有限公司 | Flyback control circuit and control method |
| US9998021B2 (en) * | 2016-10-25 | 2018-06-12 | Alpha And Omega Semiconductor Incorporated | Forced zero voltage switching flyback converter |
| CN106505865B (en) * | 2016-11-21 | 2019-05-21 | 广州金升阳科技有限公司 | A kind of asymmetrical half-bridge flyback converter and its drive control method |
| CN107276374B (en) * | 2017-06-26 | 2023-10-20 | 广州金升阳科技有限公司 | Asymmetric half-bridge flyback driving circuit |
| CN107769569A (en) * | 2017-10-13 | 2018-03-06 | 深圳市盛弘电气股份有限公司 | A kind of half bridge flyback resonance circuit |
| CN108471238A (en) * | 2018-03-21 | 2018-08-31 | 上海钧功电子科技有限公司 | A kind of converter |
| CN109861542A (en) * | 2018-12-29 | 2019-06-07 | 浙江机电职业技术学院 | A kind of D.C. regulated power supply of programmable wide range output asymmetrical half-bridge structure |
| CN110572037B (en) * | 2019-09-05 | 2020-12-18 | 深圳南云微电子有限公司 | Control method and circuit of active clamp flyback converter |
| CN111130353B (en) * | 2019-12-25 | 2021-05-18 | 广州金升阳科技有限公司 | Switching power supply device |
| CN112564489B (en) * | 2020-11-03 | 2022-05-20 | 广州金升阳科技有限公司 | Mode control method of switch converter and switch converter |
| KR20220151671A (en) * | 2021-02-10 | 2022-11-15 | 후아웨이 디지털 파워 테크놀러지스 컴퍼니 리미티드 | DC-to-DC converters, electronics and chargers |
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