CN100511942C - Method for controlling positive and negative excitation bidirectional DC-DC converter - Google Patents
Method for controlling positive and negative excitation bidirectional DC-DC converter Download PDFInfo
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- CN100511942C CN100511942C CNB2003101063495A CN200310106349A CN100511942C CN 100511942 C CN100511942 C CN 100511942C CN B2003101063495 A CNB2003101063495 A CN B2003101063495A CN 200310106349 A CN200310106349 A CN 200310106349A CN 100511942 C CN100511942 C CN 100511942C
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- 238000000034 method Methods 0.000 title claims abstract description 16
- 230000002457 bidirectional effect Effects 0.000 title claims description 24
- 230000005284 excitation Effects 0.000 title 1
- 238000004804 winding Methods 0.000 claims abstract description 53
- 230000008859 change Effects 0.000 claims description 31
- 230000035939 shock Effects 0.000 claims description 30
- 238000005070 sampling Methods 0.000 claims description 8
- 238000007493 shaping process Methods 0.000 claims description 6
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
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- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention relates to a forward-flyback two-way DC-DC converter, composing a forward transformer by coupling secondary and primary windings; composing a flyback transformer by coupling another secondary and primary windings, where the two secondary windings are connected in series with the two switches tubes, respectively, and then connected in parallel with a DC power supply. The two primary windings are connected in series and then connected in parallel with a DC power supply through rectifier/inverter. It uses active clamping, RCD clamping, LCD clamping, ZVT and other techniques to compose a family of two-way converter topologies. It uses the forward transformer and a coupling inductance together to transmit energy, solving the defect in using transformer leakage inductance or coupling inductance to transmission energy; avoids the peak problem in current topologies in existing techniques; has the advantages of small current ripple, implementing soft switch for each switch tube, etc.
Description
Technical field
The present invention relates to a kind of control method of positive and negative sharp bidirectional DC-DC converter, belong to converters.
Background technology
The traditional scheme of isolation type bidirectional DC-DC converter has following three kinds:
1. phase shift two-way changing technology
This technology is to utilize transformer leakage inductance (or external inductance), finishes the bidirectional energy transmission by the brachium pontis phase shift.It utilizes leakage inductance to come transmission of power, has limited the application of this technology in powerful application scenario.
2. voltage-type-current mode combined bidirectional converter technique
This technology is voltage-type-current mode composite type topology, and its major defect is that the due to voltage spikes that is caused by transformer leakage inductance that bears on the switching device is very big.These two defectives are because the current mode topology that contains in this technology causes, and have limited this The Application of Technology.
3. inverse-excitation type two-way changing technology
This technology utilizes single end flyback converter to be main topology, and its major defect is: utilize coupling inductance (anti-violent change depressor) to come transmission of power, limited its application in large-power occasions.
Summary of the invention
The objective of the invention is on the basis of the defective that the above-mentioned prior art of research exists, a kind of normal shock transformer and coupling inductance transmission of power of utilizing simultaneously proposed, due to voltage spikes is little, the I/O current ripples is little, can realize the positive and negative sharp bidirectional DC-DC converter of the soft switch of whole switching tubes, and provide the control method that it realizes the bidirectional energy transmission.Utilize the control method of positive and negative sharp bidirectional DC-DC converter of the present invention, can realize the two-way controlled transmission of energy.
Realize the control method of a kind of positive and negative sharp bidirectional DC-DC converter of above-mentioned purpose, with transformer secondary output winding and elementary winding with the end mode of the same name formation normal shock transformer that intercouples; Another transformer secondary output winding and elementary winding intercoupled in different name end mode constitute anti-violent change depressor; With the normal shock transformer be connected in first dc power anode simultaneously after two secondary winding different name ends of anti-violent change depressor link to each other, with the normal shock Secondary winding of transformer other end be connected in first dc power cathode after the 3rd switching tube is connected, be connected in first dc power cathode after will instead swashing the Secondary winding of transformer other end and the 4th switching tube be connected, will be just, the cascaded structure of forming with second switch pipe and electric capacity after anti-two elementary winding forwards that swash two transformers are connected is in parallel, normal shock primary winding end of the same name is connected in second dc power anode, the different name end of the elementary winding of anti-violent change depressor by be connected in second dc power cathode after first switching tube is connected; It is characterized in that, utilize the annexation of above-mentioned each parts, under backup mode, the second switch pipe, the 3rd switching tube and the 4th switching tube all are operated on off state, the inverse parallel diode of first switching tube serves as rectifier diode to be used, the switching sequence of switching tube is: the control signal complementation of the control signal of second switch pipe and the 3rd switching tube, the control signal complementation of the control signal of the 4th switching tube and the 3rd switching tube, and the control signal of the control signal of the 4th switching tube and the 3rd switching tube has conducting reclosing time, and realizes FEEDBACK CONTROL by the duty ratio of regulating the 3rd switching tube; Under charge mode, the control signal of the control signal of first switching tube and second switch pipe has Dead Time, and by following a) or b) described method, realize conducting reclosing time under the backup mode and the Dead Time under the charge mode:
A) be implemented in conducting reclosing time and the Dead Time under charge mode under the backup mode by the gate driving resistance that disposes each switching tube;
B) first, second being set earlier closes with the 3rd simulation Ji, under charge mode, the first simulation Ji is closed and is linked to each other with the sampling resistor of first DC power supply, the second simulation Ji pass links to each other with the current sampling signal of first Ji pass pipe and constitutes current feedback, control signal links to each other with shaping circuit by the 3rd analog switch, after isolating, amplify, distributing, obtain the Dead Time under the charge mode, and drive signal is provided for the first and second two switching tubes, form under the charge mode voltage, current double closed-loop control to first DC power supply; Under backup mode, first analog switch links to each other with the sampling resistor of second DC power supply, the anti-phase back of the current sampling signal of first switching tube links to each other with second analog switch and constitutes current feedback, the anti-phase back of control signal links to each other with shaping circuit by the 3rd analog switch, after isolating, amplify, distributing, obtain the conducting reclosing time under the backup mode, and drive signal is provided for second, third and the four or three switching tube, voltage, current double closed-loop to second DC power supply under the formation charge mode are controlled.
Positive and negative sharp bidirectional DC-DC converter of the present invention has following advantage: 1) utilize the common transmission of power of normal shock transformer and coupling inductance, solved the defective of using the defective of transformer leakage inductance transmission of power or using the coupling inductance transmission of power merely; 2) avoid the current mode topology, thereby avoided the due to voltage spikes problem; 3) positive and negative violent change depressor winding side electric current in parallel is continuous, and current ripples is little; 4) control rationally can realize the soft Ji pass of whole switching tubes.
Description of drawings
The positive and negative sharp bidirectional DC-DC converter main circuit schematic diagram of Fig. 1.
Gang's main circuit topology schematic diagram of the positive and negative sharp bidirectional DC-DC converter of Fig. 2.
The positive and negative sharp bidirectional DC-DC converter main circuit schematic diagram of Fig. 3 active-clamp.
Positive and negative sharp bidirectional DC-DC converter charge mode equivalent electric circuit of Fig. 4 active-clamp and principle waveform.Among the figure, last figure is an equivalent electric circuit, and figure below is the principle waveform.
Positive and negative sharp bidirectional DC-DC converter backup mode equivalent electric circuit of Fig. 5 active-clamp and operation principle waveform.Among the figure, last figure is an equivalent electric circuit, and figure below is the principle waveform.
The control logic block diagram of the positive and negative sharp bidirectional DC-DC converter of Fig. 6.
The driving sequential schematic diagram of the positive and negative sharp bidirectional DC-DC converter of Fig. 7 active-clamp.
The positive and negative sharp bidirectional DC-DC converter drive circuit block diagram of Fig. 8 active-clamp.
The positive and negative sharp composite type boost DC-DC converter circuit diagram of Fig. 9.
Designation among the above-mentioned figure:
N
S1---normal shock transformer secondary output winding, N
P1---normal shock primary winding, N
S2---anti-violent change depressor secondary winding, N
P2---the elementary winding of anti-violent change depressor, S
1, S
2, S
3, S
4, S
5, S
6, S
7---bidirectional switch pipe, S
A1, S
A2, S
A3---analog switch, T
1---E violent change depressor, T
2---anti-violent change depressor, V
Bus---DC power supply, V
Bat---DC power supply, other are general ordinary symbol such as C, and---------diode, L---inductance, k---contactor etc. no longer repeat for resistance, D for electric capacity, R.
Embodiment
Fig. 1 is positive and negative sharp bidirectional DC-DC converter main circuit schematic diagram.As shown in Figure 1, the composition of positive and negative sharp bidirectional DC-DC converter of the present invention is, by a transformer secondary output winding N
S1With elementary winding N
P1End of the same name intercouples and constitutes normal shock transformer T
1By another transformer secondary output winding N
S2With elementary winding N
P2The different name end intercouples and constitutes anti-violent change depressor T
2, positive and negative two secondary winding N that swash two transformers
S1With N
S2The different name end is connected in DC power supply V after linking to each other simultaneously
1Positive pole, two secondary winding N
S1With N
S2The other end respectively with switching tube S
1With S
2Be connected in DC power supply V after the series connection simultaneously
1Negative pole, positive and negative two elementary winding N that swash two transformers
P1With N
P2The forward series connection is by rectification/inverter circuit and DC power supply V
2Parallel connection, wherein V
1, V
2Also can be the direct current active load.
The present invention can utilize active-clamp, clamp and resetting technique composition gang's normal shock and anti-sharp knockdown reversible transducer topologys as shown in Figure 2 such as resistance capacitance diode (RCD) clamp, inductance capacitance diode (LCD) clamp and Zero voltage transition (ZVT) reset.Usually, consider to reduce the voltage stress of semiconductor device, the high voltage-small current side adopts the form of windings in series, as Fig. 2 (a)～(g); The low-voltage, high-current side adopts the form of winding parallel connection, as Fig. 2 (h)～(o).Selecting arbitrary topology among Fig. 2 (a)～(g) as the high-pressure side topology, is the positive and negative sharp composite type topology of characteristic with the active-clamp technology and select proper topologies among Fig. 2 (h)～(o) can form gang as the low-pressure side topology.Except that the active-clamp technology, multiple magnetic core of transformer resets and switching tube clamp technology to also have that auxiliary winding resets, resistance capacitance diode (RCD) clamp, inductance capacitance diode (LCD) clamp, Zero voltage transition (ZVT) reset etc., and these can constitute based on normal shock and instead swash combined bidirectional DC-DC transformation topology.
Fig. 3 has provided a kind of main circuit structure of positive and negative sharp bidirectional DC-DC converter: the positive and negative sharp two-way DC of active-clamp-DC converter.In line map shown in Figure 1, winding N
P1With winding N
S1Constitute normal shock transformer T
1, transformer turn ratio n
1=N
P1/ N
S1, winding N
P2With winding N
S2Constitute anti-violent change depressor T
2, transformer turn ratio n
2=N
P2/ N
S2C
1～C
4Be switching tube S
1～S
4Equivalence output junction capacitance and shunt capacitance thereof, L
LkBe transformer equivalence leakage inductance, C
C1Be active-clamp electric capacity.V
Bus, V
BatBe DC power supply.Positive and negative sharp two-way DC-DC converter has two kinds of main mode of operations: charge mode and backup mode.Be that example illustrates its operation principle with topology shown in Figure 3 below.
The charge mode operation principle
DC power supply V
BusJust often, the relay k among Fig. 3
1And k
2All closed, DC power supply V
BusLoad R is provided
L1Energy is given load R by converter simultaneously
L2Energy and accumulators V are provided
BatCharging is called charge mode.Under charge mode, switching tube S
1And S
2Be operated on off state, and switching tube S
3And S
4Do not work its anti-and diode D
S3, diode D
S4Use as rectifier diode.Active-clamp is positive and negative to swash by the reasonable parameter design and can realize S
1And S
2Zero voltage switch, Fig. 4 is positive and negative sharp charge mode equivalent electric circuit of active-clamp and principle waveform, and 8 operation modes are arranged under this state.
Supposition below before analyzing, doing:
1) resonance frequency of former limit inductance and clamping capacitance is much smaller than switching frequency, so clamping capacitance voltage is the constant relevant with input voltage and duty ratio during steady operation, and value is
2) transformer equivalence leakage inductance is converted the high-pressure side, is designated as L
Lk, its value is much smaller than the high-pressure side magnetizing inductance.
(1) [t
0-t
1] main switch S
1Be in conducting state, energy is by normal shock transformer T
1Be sent to load, normal shock transformer T
1Original edge voltage be output voltage clamp, elementary winding N
P1And N
P2In linear increase of electric current.Normal shock transformer T
1Exciting curent i
M1Rise, the magnetic core operating state carries out the transition to first quartile from third quadrant; Anti-violent change depressor T of while
2Exciting curent i
M2Also rise anti-violent change depressor T
2Store electromagnetic energy, anti-violent change depressor T
2The magnetic core operating state changes at first quartile all the time.
(2) [t
1-t
2] switching tube S
1Turn-off primary current i
P1Give capacitor C
1Linear-charging, switching tube S simultaneously
2Junction capacitance C
2To the transformer magnetic field discharge, diode D
S3Continue conducting, diode D
S4Still blocking-up.Switching tube S
2Drain-source voltage V
Ds2Drop to V
Cc1, switching tube S
1Drain-source voltage V
Ds1Rise to V
BusThe time, diode D
S4With conducting, diode D after this
S3And D
S4The beginning change of current.Because C
1Limited switching tube S
1Voltage build-up rate, therefore be to have the no-voltage of junction capacitance buffering to turn-off.
(3) [t
2-t
3] transformer leakage inductance L
LkWith switching tube output junction capacitance resonance.Harmonic period
Equivalence resonant capacitance C
Eq=C
1+ C
2Capacitor C
1Resonant charging, switching tube S
1Drain-source voltage V
Ds1By V
BusRise to V
Bus+ V
Cc1, and by clamp; Capacitor C
2Discharge, switching tube S
2Drain-source voltage V
Ds2From V
Cc1Drop to 0, after this diode D
S2With conducting, created S
2The condition that no-voltage is opened.Simultaneously, leakage inductance L
LkIn current resonance reduce.Switching tube S
2Can realize that the condition that no-voltage is opened is: the transformer leakage inductance energy storage must be greater than switching tube S
1, S
2The energy storage of output junction capacitance.
(4) [t
3-t
4] diode D
S2Conduction period, but no-voltage is opened switching tube S
2Diode D
S4With diode D
S3Still the change of current of conducting simultaneously, when mode 4 finishes, electric current I
Ds3Be reduced to zero, diode D
S4And D
S3The change of current finishes.
(5) [t
4-t
5] switching tube S
2Conduction period, switching tube S
1Drain-source voltage V
Ds1Be clamped at V
Bus+ V
Cc1, while diode D
S4Middle carrying load current, anti-violent change depressor T
2Exciting curent i
M2Reduce, load energy is by anti-violent change depressor T
2Energy storage provide.Anti-violent change depressor T
2Elementary winding voltage is n by clamp
2V
Bat, normal shock transformer T like this
1The voltage on former limit is: V
Cc1-n
2V
Bat, T
1Magnetic core resets under this voltage effect, exciting curent i
M1Descend, third quadrant is transferred to by first quartile in the magnetic core working point.
(6) [t
5-t
6] switching tube S
2Turn-off capacitor C
2And C
1Discharged and recharged diode D by the exciting current linearity
S4Still conducting, load energy is provided by anti-violent change depressor.Switching tube S
1Drain-source voltage V
Ds1By V
Bus+ V
Cc1Drop to V
Bus, V
Ds2Rise to V by 0
Cc1
(7) [t
6-t
7] transformer leakage inductance and switching tube output junction capacitance resonance.Switching tube S
2Drain-source voltage V
Ds2By V
Cc1Rise to V
Bus+ V
Cc1Switching tube S
1Drain-source voltage V
Ds1Then drop to zero, diode D
S1Switching tube S has been created in the beginning conducting
1The condition that no-voltage is opened.Simultaneously, transformer leakage inductance L
LkIn current resonance increase.
(8) [t
7-t
8] at diode D
S1Conduction period, switching tube S
1Can the no-voltage conducting, the leakage inductance electric current is with V
Bus/ L
LkLinear increase of slope.Up to diode D
S4End diode D
S3Whole load currents circulate.
Backup (meeting an urgent need) pattern operation principle
As DC power supply V
BusDuring fault, relay k
1Disconnect V
BatProvide load R as emergency power supply
L1And R
L2Energy is called backup (meeting an urgent need) pattern.Under backup mode, switching tube S
2, S
3And S
4Be operated on off state, switching tube S
1Anti-and diode D
S1Serving as rectifying tube uses.
During backup mode, the switching tube switching sequence is: switching tube S
2And S
3Complementary work, switching tube S
3And S
4Complementary work also has one period conducting reclosing time.Backup mode equivalent electric circuit and operation principle waveform are as shown in Figure 5.A switch periods, 6 switch mode are arranged.
(1) [t
0-t
1] t
0Constantly, switching tube S
3Oneself is in conducting state, switching tube S
4Be in off state, switching tube S
4Conduction period is stored in anti-violent change depressor T
2In electromagnetic energy and by normal shock transformer T
1Directly Chuan Shu energy is discharged into load together.Exciting curent i
M1Rise exciting curent i
M2Reduce normal shock transformer T
1The magnetic core operating state carries out the transition to first quartile from third quadrant, anti-violent change depressor T
2The magnetic core operating state changes at first quartile.
(2) [t
1-t
2] t
1Constantly, switching tube S
4Open-minded, anti-violent change depressor T
2Exciting current i
M2Increase anti-violent change depressor T
2Store electromagnetic energy; Normal shock transformer T
1Exciting current i
M1Still rise, but switching tube S
3In no longer include load current and flow through, be added in leakage inductance L
LkOn voltage be
Diode D
S1In electric current at t
2Can be reduced to 0, diode D constantly
S1End diode D
S1Voltage be V
Ds1 (t2)=V
Bus-(n
1-n
2) V
Batt
2Constantly, can zero-current switching switching tube S
3
(3) [t
2-t
3] switching tube S
3Behind the zero-current switching, normal shock transformer T
1Exciting current transfer in the winding of high-pressure side, this exciting current will extract capacitor C
2Electric charge, t
3Constantly, capacitor C
2Last voltage drop to 0, diode D
S2Switching tube S has been created in the beginning conducting
2After this condition that ZVS opens can open switching tube S by ZVS
2
(4) [t
4-t
5] switching tube S
2Conduction period, normal shock transformer T
1Exciting current at (V
Cc1-n
2V
Bat) effect under, carry out the transition to third quadrant by first quartile, realized normal shock transformer T
1The two-way magnetization of magnetic core.Here utilize voltage (V
Cc1-n
2V
Bat) be the degaussing of normal shock transformer.During this period, anti-violent change depressor T
2Exciting current continue to increase T
2Store electromagnetic energy.
(5) [t
5-t
6] t
5Constantly, switching tube S
2No-voltage is turn-offed under the buffering of junction capacitance, and exciting current is given capacitor C
2Charging, meanwhile, winding N
P1(winding N
S1) on voltage also raise t
6Constantly, winding N
S1On voltage be elevated to V
Bat, after this by diode D
S3Clamp, normal shock transformer T
1Exciting current is transferred to low-pressure side, and magnetization energy is via diode D
S3Feed back to power supply V
BatThis moment diode D
S1On voltage be V
Ds1 (t6)=V
Bus-(n
1-n
2) V
Batt
6Can no-voltage open switching tube S constantly
3In fact switching tube S
3Diode D when opening
S1Still being in the disconnected state in anti-Pianguan County, not bearing load current, also is zero current turning-on therefore.
(6) [t
6-t
8] t
7Constantly, switching tube S
3No-voltage is open-minded.t
8Constantly, switching tube S
4At junction capacitance C
4Buffering under no-voltage turn-off winding N
P1And N
P2Release energy to load together, begin next switch periods.
Control logic, driving sequential and realization circuit
Here provide control control logic, the driving sequential of two ends voltage stabilizing and realize circuit, if product has different control to need (as single-ended voltage stabilizing, single-ended current limliting, not voltage stabilizing etc.) to provide corresponding control circuit with reference to the present invention.
(1) control method of backup mode.
Realize that energy is conventional PWM control by Vbus to the control method of Vbat transmission, does not give unnecessary details herein.
Realize that energy by Vbat to the control method of Vbus transmission is:
With reference to figure 5, under backup mode, switching tube S
2, S
3And S
4Be operated on off state, switching tube S
1Anti-and diode D
S1Serving as rectifying tube uses.Normal shock Transformer Winding and anti-violent change depressor winding are connected with switching tube S3 and S4 respectively, and S3 and S4 realize that output voltage or output current etc. reach the main switch of controlled target, and S2 is a magnetic core reset switch pipe.The basic controlling logic of S2, S3, three switching tubes of S4 is: S3 is a master switch, by its duty ratio decision controlled target; The control signal complementation of the control signal of S2 and S3; The control signal complementation of the control signal of S4 and S3.As the controlled target end, on the basis of voltage that detects Vbus or electric current,, regulate the duty ratio of S3 by FEEDBACK CONTROL, can finish the control of backward energy transmission.
Because the factors such as distributivity of device parameters can't guarantee the drive condition of " strictly complementary " in the above-mentioned hypothesis in the side circuit, so must provide the zone of reasonableness of drive signal.At first, S
3With active-clamp pipe S
2Drive signal should be complementary, and leave suitable dead band in order to avoid C
C1Straight-through discharge.And S
4And S
3Drive signal should be complementary, and leave suitable conducting and overlap (as t1-t2 corresponding among Vgs3, the Vgs4 among Fig. 5, and two time periods of t6-t7), only in this way just can avoid occurring the situation of two equivalent current sources series connection, realize the reverse transfer of energy.The working control signal sequence as shown in Figure 7.
(2) realization of mode switch and Comprehensive Control logic.
Provide control logic, the driving sequential of two ends voltage stabilizing below and realize circuit, different control needs (as single-ended voltage stabilizing, single-ended current limliting, not voltage stabilizing etc.) to provide corresponding control circuit with reference to the present invention.
Control logic block diagram such as Fig. 6.Control logic adopts analog switch respectively two energy Flow directions to be formed closed loop.S among Fig. 6
As1, S
As2, S
As3Be analog switch, its Enable Pin is under certain signal (as charge mode time high level) effect, and " a " passage of gating analog switch has just constituted V like this under charge mode
BatThe dicyclo control system of voltage stabilizing.Equally, " b " passage of gating analog switch under the backup mode constitutes V
BusThe dicyclo voltage-regulating system of voltage stabilizing has realized bi-directional voltage stabilizing.
Fig. 7 is a switching tube driving pulse sequential chart.In Fig. 7, Δ is represented " dead band " or " conducting coincidence " time of certain-length, and each Δ among the figure all can be regulated, and does not require that time span equates.From Fig. 7 as seen, do not have simple homophase or anti-phase relation in sequential under charge mode and the backup mode: requiring under backup mode has certain conducting reclosing time, and charge mode requires to have certain Dead Time down.Realize above-mentioned drive controlling sequential, following two kinds of schemes can be arranged:
1) reasonable disposition driving resistor
Gate driving resistance by each switching tube of reasonable disposition (as Power MOSFET) obtains " dead band " shown in Figure 7 or " conducting coincidence " time.Advantage in this driven strategy works is succinct, and shortcoming is to have prolonged opening or turn-off speed of some switching tube, has increased the switching loss of circuit.
2) separate " cross-drive signal " with analog switch
So-called " cross-drive signal " is meant the gate signal that all needs the switch driven pipe under charge mode and two kinds of mode of operations of backup mode, the switching tube S in the topology for example shown in Figure 3
2Drive signal.Adopt analog switch to separate this kind signal and just can realize independent closed loop and drive under the different mode.Fig. 8 has provided the physical circuit that this kind scheme realizes.Fig. 8 dotted line left side is for realizing circuit block diagram, and the dotted line right side is the specific implementation circuit of each unit.Delay circuit realizes that with the RC circuit forward position time-delay and back only need along delaying time and adjustable resistance diode in parallel gets final product, and the delay time constant all is adjustable.Shaping circuit can constitute with homophase or inverter buffer, plays shaping and signal amplification.Signal amplifies the totem structure that can adopt NPN triode and PNP triode to constitute.Because the duty ratio here changes between 0～1, the isolation drive unit adopts structure as shown in Figure 8.
Positive and negative sharp composite type boosting inverter main circuit topology
Fig. 9 is positive and negative sharp composite type boosting inverter main circuit topology, and its line map is characterized as: Transformer Winding N
S1, N
P1Intercouple and constitute normal shock transformer T
1, Transformer Winding N
S2, N
P2Intercouple and constitute anti-violent change depressor T
2Winding N
S1With switching tube S
1Be in series winding N
S2With switching tube S
2Be in series two cascaded structures and input DC power parallel connection; Winding N
P1, N
P2Be in series, and and be in parallel by the DC power supply that rectification/inversion unit is converted to, wherein rectification unit can be figure (p) halfwave rectifier shown in Figure 9, figure (q) full-wave rectification, figure (r) full-bridge rectification etc." " indication transformer end of the same name among the figure.S among the figure
1, S
2For having the active controllable switch of bi-directional current flow ability, comprise power metal-oxide field effect transistor (Power MOSFET), igbt (IGBT), MOS control thyristor (MCT) or the similar switch of inventing in the future also can be the composite constructions with same purpose.
Claims (1)
1. the control method of a positive and negative sharp bidirectional DC-DC converter is with transformer secondary output winding (N
S1) and elementary winding (N
P1) intercoupling in end mode of the same name constitutes normal shock transformer (T
1); With another transformer secondary output winding (N
S2) and elementary winding (N
P2) intercoupling in different name end mode constitutes anti-violent change depressor (T
2); Two secondary winding (N with normal shock transformer and anti-violent change depressor
S1, N
S2) the different name end is connected in the first DC power supply (V after linking to each other simultaneously
Bat) positive pole, with normal shock Secondary winding of transformer (N
S1) other end and the 3rd switching tube (S
3) be connected in the first DC power supply (V after the series connection
Bat) negative pole, will instead swash Secondary winding of transformer (N
S2) other end and the 4th switching tube (S
4) be connected in the first DC power supply (V after the series connection
Bat) negative pole, with positive and negative two elementary winding (N that swash two transformers
P1, N
P2) forward series connection back and second switch pipe (S
2) and electric capacity (C
C1) cascaded structure formed is in parallel normal shock primary winding (N
P1) end of the same name is connected in the second DC power supply (V
Bus) positive pole, the elementary winding (N of anti-violent change depressor
P2) the different name end by with the first switching tube (S
1) be connected in the second DC power supply (V after the series connection
Bus) negative pole; It is characterized in that, utilize the annexation of above-mentioned each parts, under backup mode, second switch pipe (S
2), the 3rd switching tube (S
3) and the 4th switching tube (S
4) all be operated on off state, the first switching tube (S
1) inverse parallel diode (Ds
1) serving as the rectifier diode use, the switching sequence of switching tube is: second switch pipe (S
2) control signal and the 3rd switching tube (S
3) the control signal complementation, the 4th switching tube (S
4) control signal and the 3rd switching tube (S
3) the control signal complementation, and the 4th switching tube (S
4) control signal and the 3rd switching tube (S
3) control signal have conducting reclosing time, and by regulating the 3rd switching tube (S
3) duty ratio realize FEEDBACK CONTROL; Under charge mode, the first switching tube (S
1) control signal and second switch pipe (S
2) control signal have Dead Time, and by following a) or b) two kinds of methods, realize conducting reclosing time under the backup mode and the Dead Time under the charge mode:
A) be implemented in conducting reclosing time and the Dead Time under charge mode under the backup mode by the gate driving resistance that disposes each switching tube;
B) first, second and the three or three analog switch (S are set earlier
As1, S
As2, S
As3), under charge mode, the first analog switch (S
As1) and the first DC power supply (V
Bat) sampling resistor link to each other the second analog switch (S
As2) and the first switching tube (S
1) current sampling signal link to each other to constitute current feedback, control signal is by the 3rd analog switch (S
As3) link to each other with shaping circuit, after isolating, amplify, distributing, obtain charge mode Dead Time down, and to the first and second two switching tube (S
1, S
2) drive signal is provided, form under the charge mode the first DC power supply (V
Bat) the control of voltage, current double closed-loop; Under backup mode, the first analog switch (S
As1) and the second DC power supply (V
Bus) sampling resistor link to each other the first switching tube (S
1) the anti-phase back of current sampling signal and the second analog switch (S
As2) linking to each other constitutes current feedback, the anti-phase back of control signal is by the 3rd analog switch (S
As3) link to each other with shaping circuit, after isolation, amplification, distributing, obtain the conducting reclosing time under the backup mode, and give second, third and the four or three switching tube (S
2, S
3, S
4) drive signal is provided, form under the charge mode the second DC power supply (V
Bus) the control of voltage, current double closed-loop.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB2003101063495A CN100511942C (en) | 2003-11-19 | 2003-11-19 | Method for controlling positive and negative excitation bidirectional DC-DC converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB2003101063495A CN100511942C (en) | 2003-11-19 | 2003-11-19 | Method for controlling positive and negative excitation bidirectional DC-DC converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN1545195A CN1545195A (en) | 2004-11-10 |
| CN100511942C true CN100511942C (en) | 2009-07-08 |
Family
ID=34334117
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CNB2003101063495A Expired - Fee Related CN100511942C (en) | 2003-11-19 | 2003-11-19 | Method for controlling positive and negative excitation bidirectional DC-DC converter |
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| Country | Link |
|---|---|
| CN (1) | CN100511942C (en) |
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- 2003-11-19 CN CNB2003101063495A patent/CN100511942C/en not_active Expired - Fee Related
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|---|---|
| CN1545195A (en) | 2004-11-10 |
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Assignee: UTOP Electronic (Guangzhou) Co., Ltd. Assignor: Nanjing University of Aeronautics and Astronautics Contract record no.: 2010440000455 Denomination of invention: Method for controlling positive and negative excitation bidirectional DC-DC converter Granted publication date: 20090708 License type: Exclusive License Open date: 20041110 Record date: 20100505 |
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