CN103959637A - Power converter, electric motor drive device, and air conditioner - Google Patents

Power converter, electric motor drive device, and air conditioner Download PDF

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Publication number
CN103959637A
CN103959637A CN201280058552.7A CN201280058552A CN103959637A CN 103959637 A CN103959637 A CN 103959637A CN 201280058552 A CN201280058552 A CN 201280058552A CN 103959637 A CN103959637 A CN 103959637A
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China
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pulse
phase
power
signal
current
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CN201280058552.7A
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CN103959637B (en
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右之子知惠
田村建司
田村正博
初濑涉
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Hitachi Johnson Controls Air Conditioning Inc
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Hitachi Appliances Inc
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/24—Vector control not involving the use of rotor position or rotor speed sensors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/14—Electronic commutators
    • H02P6/16—Circuit arrangements for detecting position
    • H02P6/18—Circuit arrangements for detecting position without separate position detecting elements
    • H02P6/182—Circuit arrangements for detecting position without separate position detecting elements using back-emf in windings

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

Provided are a high-efficiency power converter, electric motor drive device, and air conditioner with which switching loss in PWM control is minimized. A vector control unit (8) outputs current phase information (8A), which is computed on the basis of phase current information (6A) from a phase current detector unit (6), to a pulse suspension control unit (9). The pulse suspension control unit (9) outputs a phase pulse suspension control signal (9A), which is generated on the basis of the current phase information (8A), to a pulse width determination unit (12). The pulse width determination unit (12) outputs a pulse start/suspension instruction (12A), for the pulse width to remain above a given value, to a pulse control unit (7). Thus, the pulse control unit (7) suspends a pulse signal (7A) of a prescribed interval with the zero-cross of the current phase of a prescribed phase of a power converter circuit (4) as a reference.

Description

Power-converting device, motor drive and air conditioner
Technical field
The present invention relates to use the control technology of the power-converting device of PWM (Pulse Width Modulation, pulse width modulation) control mode.
Background technology
The miniaturization that the motor drive strong request of using in air conditioner etc. is cut down based on part number of packages and high efficiency, high output, developed for realizing the various technology of these requirements.The gimmick that drives the motor that becomes its load in such motor drive as the power-converting device using and high efficiency, for example, disclose technology as follows.; the technology of 180 degree/120 degree energising switching modes is disclosed; the electric current PWM that flows to motor from power-converting device is controlled and be: sinuous 180 degree step modes and the phase place of induced voltage of take are benchmark, and every 120 degree carry out the 120 degree step modes that PWM controls to carry out switch motion.Recorded by using which, can carry out high efficiency driving corresponding to loading condition and the drive condition of motor, and can, under the rotary speed of wide region, make the driving stabilisation (referring to Patent Document 1) of motor.
In addition, while switching on as 120 degree that carry out the power-converting device of PWM control, reduce the gimmick of the loss of motor, the technology of 120 degree/150 degree energising switching modes is disclosed, energising angle when 120 degree are switched on torque instruction expands to 150 degree energisings, make the electric current flowing through at motor approach sine wave, thereby reduce the pulsation of torque.Recorded by using which, when the starting of motor, and from heavy duty until underload can, with the few revolving force of noise and vibration, be carried out to high-performance the driving (referring to Patent Document 2) of motor.
In addition, the technology of 2 phase modulation systems is also disclosed, in the situation that use carries out when the power-converting device of the three-phase of PWM control carrys out run motor power-converting device to carry out vector control, only in approaching zero the phase of current value, do not carry out switch and carry out 2 arm modulation (2 modulation mutually).According to this technology, position-sensor-free carry out vector control in the situation that, by the timing of the electric degree every certain, carry out 2 modulation mutually, can avoid the zero clamper phenomenon of stator current zero clamper of motor.Its result, can be in the vector control of full-load range the stability (referring to Patent Document 3) of Lifting Control System.
Look-ahead technique document
Patent documentation
Patent documentation 1:JP JP 2008-172948 communique
Patent documentation 2:JP JP 2003-169491 communique
Patent documentation 3:JP Unexamined Patent 11-164597 communique
The summary of invention
The problem that invention will solve
The 120 degree step modes that described patent documentation 1 and patent documentation 2 recorded and 150 degree step modes, due to the switch motion region in 1 cycle of having compared constriction with 180 degree step modes, therefore can reduce the switching loss of power-converting device.But, for the magnet positions of not using magnet positions transducer and detect motor (, position probing), and induced voltage testing circuit need to be set, at the stopping period of switch motion, obtain the phase information of induced voltage, based on these phase informations, switch the phase of carrying out switch motion.
In other words, 120 of non-magnet position transducer mode degree step modes and 150 degree step modes must near the zero cross point of the induced voltage of motor, arrange shutdown switch action during.Thereby, be difficult to more than expanding to electric degree 150 degree during switch motion.In addition, the stopping period of switch motion must carry out with induced voltage Phase synchronization.Yet, owing to can departing from the current phase of induced voltage phase place and motor because loading condition is different with drive condition, even if therefore use 150 degree step modes also to differ, obtain surely the minimizing effect of torque pulsation.And then if will prevent departing from of the phase place of above-mentioned induced voltage and the current phase of motor, the action self of 150 degree energisings will become impossible.
; because 120 degree step modes or 150 degree step modes be take the phase place of induced voltage and are decided the interval and open phase interval of energising (interval that the switch element of upper underarm of the homophase of inverter is both stopped) as benchmark; therefore in order to obtain position signalling under non-magnet position transducer mode, need to make open phase interval comprise the zero cross point of induced voltage.Yet, owing to can departing from the phase place of induced voltage and the current phase of motor because loading condition is different with drive condition, therefore also have open phase interval not comprise the situation of the zero cross point of induced voltage.Its result, in the situation that non-magnet position transducer and phase place based on induced voltage are carried out vector control and sometimes can not correctly be carried out position probing.What in other words, enable switch motion by regulation interval stops reducing the vector control that switching loss can not be carried out the position probing based on correct.
So, in the mode of patent documentation 1 and patent documentation 2, by when 120 degree step modes and 150 are spent the driving of step modes, the interval that switch is stopped being set, can reduce the on-off times of power transformation circuit.But, due to use sense, to answer voltage detecting circuit etc. and obtain the phase information of induced voltage, the phase information based on this induced voltage is switched the phase of carrying out switch, therefore in the situation that the phase place of voltage and current is different, can not carry out correct position probing.Its result, has current distortion to become greatly and the possibility of the torque pulsation increase of motor.In addition, at 180 of patent documentation 1, spend in the driving of step modes, although use sense is not answered voltage detecting circuit etc. and is sinusoidal wave shape by the Current Control that flows through motor, but owing to must always carry out switch motion between 1 cycle of voltage, electric current, thereby so Efficiency Decreasing of switching loss increase power transformation circuit.
In addition, disclosed technology in patent documentation 3 in the situation that with the power-converting device of three-phase that carries out PWM control carry out vector control only at current value close to zero phase, make switch stop to carry out 2 modulation mutually.But, owing to not occurring between the stand-down of electric current, therefore can there is the copper loss of motor.
That is, even can not reduce by the 2 phase modulation systems that patent documentation 3 is recorded the efficiency that switching loss that PWM controls promotes power-converting device.
Summary of the invention
The present invention proposes in view of such situation, the high efficiency power-converting device of switching loss when object is to provide PWM to control.
For solving the means of problem
In order to solve described problem, power-converting device of the present invention is use vector control mode, by PWM, controls the power-converting device that carries out power converter, possesses: pulse control part, the pulse signal of its output for carrying out described PWM control; Power transformation circuit, it is used from the pulse signal of described pulse control part output direct current is transformed to alternating current; Current detecting part, it detects the electric current of described power transformation circuit; Vector control portion, it generates the command voltage to described pulse control part based on carrying out vector control by the detected electric current of described current detecting part; Stop control part with pulse, it generates the pulse stop control signal that described pulse signal is stopped between the pulse stop zone that the current phase of described power transformation circuit is benchmark take, and described pulse stop control signal is exported to described pulse control part, described pulse control part is exported the pulse signal of the time width of the action that can ensure gate drivers.
The effect of invention
According to the present invention, provide the high efficiency power-converting device of the switching loss when having met the specification of gate drivers and having reduced PWM control etc.
Accompanying drawing explanation
Fig. 1 means the block diagram that the circuit of the power-converting device of the PWM control mode that the 1st execution mode is related forms.
Fig. 2 means the oscillogram of the relation of the alternating voltage that flows through motor, alternating current and pulse signal in comparative example, (a) characterize PWM carrier signal and apply voltage instruction, (b) characterize U cross streams electric current, (c) characterize pulse signal.
Fig. 3 means the oscillogram of the alternating voltage that flows through motor, alternating current and pulse signal in the 1st execution mode and the relation of phase pulse stop control signal, (a) characterize PWM carrier signal and apply voltage instruction, (b) characterize U cross streams electric current, (c) characterize pulse signal, (d) characterize open phase control signal (phase pulse stop control signal).
Fig. 4 is the oscillogram that obtains the relation of U phase voltage, U phase current and pulse signal in the situation of physical device of the power-converting device that possesses the 1st execution mode, (a) characterize U phase terminal voltage, (b) characterize U phase current, (c) characterize pulse signal.
Fig. 5 means the power transformation circuit loss with respect to (open phase interval) between phase pulse stop zone, the generator loss of the power-converting device of the 1st execution mode and the performance plot of the relation of composite loss that their are added.
Fig. 6 means the block diagram that the circuit of power-converting device of the PWM control mode of comparative example forms.
Fig. 7 means the oscillogram of the alternating voltage that flows through motor, alternating current and pulse signal in the variation of the power-converting device that the 1st execution mode is related and the relation of phase pulse stop control signal, (a) characterize PWM carrier signal and apply voltage instruction, (b) characterize U cross streams electric current, (c) characterize pulse signal, (d) characterize open phase control signal (phase pulse stop control signal).
Fig. 8 means the block diagram that the circuit of the power-converting device of the PWM control mode that the 2nd execution mode is related forms.
Fig. 9 means the performance plot of the setting example of (open phase is interval) between the phase pulse stop zone in the power-converting device of the 2nd execution mode, (a) characterize the situation that is set as ideally rotary speed N1, (b) characterize the situation of rotary speed N3 that changes to from rotary speed N2 with certain rate of change, the curve (c) characterizing with regulation changes to the situation of rotary speed N3 from rotary speed N2.
The whole pie graph of the air conditioner of Figure 10 is the related use of the 3rd execution mode power-converting device.
Figure 11 means the performance plot of relation of the efficiency of the rotary speed with respect to compressor driving motor in the air conditioner shown in Figure 10.
Figure 12 means the oscillogram of the relation of the alternating voltage that flows through alternating current motor, alternating current and pulse signal in the 1st execution mode, phase pulse stop control signal.(a) characterize PWM carrier signal and apply voltage instruction, (b) characterizing U cross streams electric current, (c) characterizing pulse signal, (d) characterizing phase pulse stop control signal.
Figure 13 indicates for Figure 12 that phase pulse stop control signal becomes in 0 interval situation to flow through alternating voltage, alternating current and the pulse signal of alternating current motor, the figure of the relation of phase pulse stop control signal.(a) characterize PWM carrier signal and apply voltage instruction, (b) characterizing U cross streams electric current, (c) characterizing pulse signal, (d) characterizing phase pulse stop control signal.
Figure 14 indicates for Figure 12 that phase pulse stop control signal becomes in 0 interval situation to flow through alternating voltage, alternating current and the pulse signal of alternating current motor, the figure of the relation of phase pulse stop control signal.(a) characterize PWM carrier signal and apply voltage instruction, (b) characterizing U cross streams electric current, (c) characterizing pulse signal, (d) characterizing phase pulse stop control signal.
Figure 15 means the block diagram that the circuit of the power-converting device of the PWM control mode that the 4th execution mode is related forms.
Figure 16 is for the figure flowing through between the alternating voltage of alternating current motor and switching exclusion area that pulse signal represents phase pulse stop control signal (open phase phase control signal), (a) characterize PWM carrier signal and apply voltage instruction, (b) characterizing pulse signal.
Figure 17 is the figure of the processing order that undertaken by the related pulse duration detection unit of the 4th execution mode with flowcharting.
Figure 18 means the figure of the timing of pulse duration detection unit output impulse starting/halt instruction that the 5th execution mode is related, (a) characterizes PWM carrier signal and applies voltage instruction, (b) characterizes pulse signal.
Embodiment
Next, with reference to suitable accompanying drawing, describe the form (being later called " execution mode ") for carrying out an invention in detail.
< < summary > >
The related power-converting device of present embodiment possesses: the pulse signal that uses PWM to control is transformed to direct current the power transformation circuit (inverter) of alternating current; The electric current that flows through power transformation circuit with detection carries out the vector control portion of vector control to this power transformation circuit.And the zero cross point that the current phase make to flow through power transformation circuit is set is that the open phase of switch element of benchmark and the definite interval pulse signal upper underarm that stops homophase is interval.Thus, the on-off times in the time of reducing PWM and control reduces switching loss, and can use by open phase interval is set the zero cross point of current phase to obtain the correct positional information of the magnet positions of motor.Its result, can carry out the efficiency that stable vector control promotes power transformation circuit (inverter) and motor.
Below with reference to accompanying drawing, describe the execution mode of power-converting device involved in the present invention 1 (1a of Fig. 1, the 1b of Fig. 6, Fig. 8 11, the 11a of Figure 15) in detail.In addition, for whole figure of each execution mode are described, same inscape is given same label in principle, omits its explanation repeatedly.In addition, in the execution mode of the following stated, Yi Bian contrast with the comparative example that has used existing mode the content that present embodiment is described on one side for ease of understanding.
< < the 1st execution mode > >
Fig. 1 represents that the circuit of the power-converting device 1a of the PWM control mode that the 1st execution mode is related forms.In the power-converting device 1a of the 1st execution mode, as shown in Figure 1, explanation is in the situation that drive the alternating current motor 3 of permanent magnet synchronous motor by control the power transformation circuit that three-phase inverter was formed 4 drive with PWM with vector control, the control method when pulse signal of power transformation circuit 4 is arranged to (being that open phase is interval) between phase pulse stop zone.
The circuit of < power-converting device forms >
As shown in Figure 1, power-converting device 1a possesses: the power transformation circuit 4 consisting of the 3 phase inverters that direct current are transformed to alternating current; The phase current test section 6 of the motor current of the alternating current motor (motor) 3 being connected with power transformation circuit 4 is flow through in detection; With based on phase current information (electric current) 6A detected by phase current test section 6, with pulse signal, carry out the control device 5a of vector control while controlling carrying out PWM.In addition, power transformation circuit 4 possesses following key element and forms: the power converter main circuit 41 that thyristor Sup, the Sun consisting of the three-phase of anti-parallel connection IGBT (Insulated Gate Bipolar Transistor, insulated gate bipolar transistor) and diode, Svp, Svn, Swp, Swn form; Produce the gate drivers 42 of the signal of the IGBT that offers power converter main circuit 41 with the pulse signal 7A based on from pulse control part 7.
In addition, control device 5a consists of following key element: will be based on applying voltage instruction (command voltage) V *and the pulse signal 7A controlling offers the pulse control part 7 of gate drivers 42; Use by the detected phase current information of phase current test section 6 6A and carry out vector control and calculate the vector control portion 8 that applies voltage instruction V*; Near the pulse that the phase information of the electric current based on calculating by vector control (current phase) 8A is made current zero intersects phase pulse stop control signal (pulse stop control signal) 9A that the pulse signal 7A of (open phase is interval) δ between phase pulse stop zone stops export to pulse control part 7 stops control part 9.
At this, vector control portion 8 is such as recorded in non-patent literature 1 (this grade of slope " the simple and easy vector control of the position-sensor-free permanent magnet synchronous motor of object appliance equipment " electricity opinion D, Vol.124 roll up No. 11 (2004) pp.1133-1140) and non-patent literature 2 (family the research of the new vector control mode of permanent magnet synchronous motor " at a high speed with " electricity opinion D, the Vol.129 such as is opened and rolled up No. 1 (2009) pp.36-45), can use general vector control to realize, for example, detect inverter output current and carry out (the dq conversion of 3 phase-2 phase inversion; Direct-quadrature conversion), and feed back to control system, carry out once again 2 phase-3 phase transformations and bring driving inverter, about control mode, do not have specific.Therefore, the action of vector control portion 8, owing to being known technology, is therefore omitted detailed explanation.
< comparative example >
At this, the switch motion while controlling in order to make PWM in the power-converting device 1a of the 1st execution mode clear, illustrates the PWM control in the power-converting device 1b (with reference to figure 6) of the comparative example that has used existing mode with Fig. 2 and Fig. 6.Fig. 2 means the oscillogram of the relation of the alternating voltage that flows through alternating current motor 3, alternating current and pulse signal in comparative example.In addition, the transverse axis of Fig. 2 illustrates voltage-phase, and each level of voltage (Fig. 2 (a)), electric current (Fig. 2 (b)) and pulse signal (Fig. 2 (c)) is shown at the longitudinal axis.In addition, the circuit of power-converting device 1b that Fig. 6 represents to have the PWM control mode of comparative example forms.In addition, in Fig. 6, there is identical function with the key element of Fig. 1 same numeral.In addition, the vector control that vector control portion 8 carries out is the control method identical with the situation of Fig. 1.
Control device 5b shown in Fig. 6, compares PWM carrier signal and applies voltage instruction Vu at pulse control part 7 as shown in Fig. 2 (a) *generate pwm pulse signal.In addition, this applies voltage instruction V *command value be to take the detected phase current information of phase current test section 6 6A as basis, by vector control portion 8, carry out computing and the value that obtains.At this, the phase current information 6A that phase current test section 6 carries out obtain can be both for example as disclosed in Fig. 1 of JP 2004-48886 communique with CT (Current Transformer, current transformer) mode of direct-detection ac output current, obtains the current information of DC bus and based on this current information, reproduces the mode of phase current with shunt resistance also can be as disclosed in Figure 12 of this communique.
Next, with Fig. 2, describe the relation that offers the alternating voltage of alternating current motor 3 and alternating current, pulse signal from power-converting device 1b (with reference to figure 6) in detail.Fig. 2 (a) represents PWM carrier signal and applies voltage instruction V *, as representative, U is shown and applies mutually voltage instruction Vu *.At this, the θ of the transverse axis shown in Fig. 2 vit is the voltage-phase of benchmark mutually that U is take in expression.
Under PWM control mode, as Fig. 2 (a), by comparing U at pulse control part 7, apply mutually voltage instruction Vu *generate the pulse signal shown in Fig. 2 (c) " pulse signal of GPU+:U phase upside element (Sup) ", " pulse signal of GPU-:U phase downside element (Sun) " with triangular wave carrier signal (PWM carrier signal), in order to drive power converter main circuit 41 by this output of pulse signal to gate drivers 42.That is, the pulse signal of GPU+ and the pulse signal of GPU-become positive and negative (1,0) contrary signal.
By carrying out PWM control by this pulse signal of power converter main circuit 41 use (pulse signal of GPU+/GPU-), at alternating current motor 3, flow through U cross streams electric current I u such shown in Fig. 2 (b).At this, the phase difference that represents voltage and electric current.
In addition, in vector control portion 8, by take, comprise that the phase current information 6A of U cross streams electric current I u carries out vector control as basis, carry out the amplitude of voltage and the phase difference of voltage and electric current control.
As shown in Figure 2, in the PWM of comparative example controls, always carry out switch motion and carry out 180 degree energisings between 1 cycle of voltage, electric current, on-off times is more than 120 degree step modes and 150 degree step modes during having that switch motion stops.Therefore,, in 180 degree energisings, it is many that the switching loss causing thus becomes.
Pulse in < the 1st execution mode stops the action > of control part
In the following description, with Fig. 1 and Fig. 3, illustrate that pulse that the switch motion of the pulse signal that makes to carry out PWM control temporarily stops stops the action of control part 9 (with reference to figure 1).Therefore, the basic action that the PWM that narrated in comparative example is controlled, for fear of repetition and description thereof is omitted.
Fig. 3 means the oscillogram of the relation of the alternating voltage that flows through alternating current motor 3, alternating current and pulse signal in the 1st execution mode, phase pulse stop control signal.In addition, transverse axis at Fig. 3 illustrates voltage-phase, and each level of voltage (Fig. 3 (a)), electric current (Fig. 3 (b)), pulse signal (Fig. 3 (c)) and open phase control signal (phase pulse stop control signal: Fig. 3 (d)) is shown at the longitudinal axis.That is, Fig. 3 is oscillogram with Fig. 2 of the comparative example oscillogram to the present embodiment recently representing.
As shown in Fig. 3 (d), pulse stops control part 9 (with reference to figure 1) with by vector control and the zero cross point of controlled current phase for benchmark, in phase place and phase place shown in formula described as follows (1), between phase pulse stop zone between (open phase interval) δ by pulse signal GPU+, GPU-all phase pulse stop control signal (open phase control signal) 9A of shutdown switch export to pulse control part 7.This phase pulse stop control signal 9A is in shutdown switch in the situation that output " 0 " of pulse signal GPU+, GPU-, in the situation that shutdown switch and compare switch output " 1 " (with reference to figure 3 (d)) of routine PWM control mode not.
[several 1]
That is,, known to from formula (1), inciting somebody to action being made as the phase difference of voltage and electric current, while δ being made as between phase pulse stop zone to (open phase is interval), is the voltage-phase θ of benchmark take U mutually vfor time and + π+δ/2 o'clock, pulse control part 7 (with reference to figure 1) stops the switch based on pulse signal GPU+ and GPU-.Then, in addition time, carry out the switch based on pulse signal GPU+ and GPU-.
For this reason, from output state δ between the phase pulse stop zone of phase pulse stop control signal 9A of pulse control part 7, pulse signal GPU+, GPU-become cut-off.Therefore, as shown in Fig. 3 (c), from the train of signal of the pulse control part 7 output pulse signals that δ stops between phase pulse stop zone.In other words, between 1 cycle of voltage and electric current, set (open phase is interval) δ between the phase pulse stop zone of 2 times.In addition, in the situation that the formation of the 1st execution mode, the modulation system that becomes the PWM control of object is not only sinusoidal wave PWM control mode, even in bi-phase modulated type PWM control mode or three order harmonics add operation type PWM control modes, δ between same phase pulse stop zone also can be set.
So, in pulse signal GPU+, GPU-during being provided with that pulse by the 1st execution mode stops that control part 9 makes that switch motion stops, become between switch stop zone and switch motion interval be not the induced voltage phase place that applies voltage-phase (with reference to figure 3 (a)) and alternating current motor 3 be the shape that benchmark is established.That is, take the zero cross point of current phase and set (with reference to figure 3 (b), Fig. 3 (d)) as benchmark between the switch stop zone of pulse signal GPU+, GPU-and switch motion interval.
In other words, in comparative example, because being take the pulse signal that the voltage-phase of induced voltage is benchmark, therefore as shown in Fig. 2 (c), pulse signal conspires to create the front and back into the zero cross point at voltage, and effectively/cut-off (ON/OFF) duty becomes symmetrical shape.Yet, in the 1st execution mode, owing to take current phase, δ is set between phase pulse stop zone (as benchmark, not to take the pulse signal that voltage-phase is benchmark), therefore as shown in Fig. 3 (c), in the front and back of the zero cross point of voltage, pulse signal string effectively/cut-off duty do not become symmetry.That is, in the 1st execution mode, in the front and back of the zero cross point of electric current, pulse signal string effectively/cut-off duty becomes asymmetric.
So, in the 1st execution mode, because the interval comprising the zero cross point of electric current arranges δ between phase pulse stop zone, therefore, as shown in Fig. 3 (c), pulse signal string A and the B of the front and back centered by δ between phase pulse stop zone become asymmetrical shape.Accordingly, as the 1st execution mode, in the situation that comprise that the interval of the zero cross point of electric current arranges δ between phase pulse stop zone, whether pulse signal that can be by the front and back of δ between observation phase pulse stop zone is asymmetricly easily to differentiate whether applied the 1st execution mode.
Waveform > during the driving of < physical device
Fig. 4 means the oscillogram of the relation of U phase voltage, U phase current and pulse signal in the situation of the physical device that drives the power-converting device 1a possess the 1st execution mode.In addition, at the transverse axis of Fig. 4, voltage-phase is shown, each level of voltage (Fig. 4 (a)), electric current (Fig. 4 (b)) and pulse signal (Fig. 4 (c)) is shown at the longitudinal axis.; Fig. 4 represent with the 1st execution mode comprise electric current zero cross point be nearby provided with the gimmick between phase pulse stop zone, in bi-phase modulated type PWM control mode, establish voltage, electric current and pulse signal in the situation that of driving physical device between phasing pulse stop zone.
Fig. 4 (a) represents the U phase terminal voltage Vun of power converter main circuit 41 (with reference to figure 1), and Fig. 4 (b) represents to flow through the U phase current Iu of alternating current motor 3, and Fig. 4 (c) illustrates pulse signal GPU+, GPU-.
As shown in Fig. 4 (c), in by the folded interval of a chain-dotted line (showing with δ), the switching signal of pulse signal GPU+, GPU-all becomes cut-off, can confirm to have set δ between phase pulse stop zone.In addition, owing to having set δ between phase pulse stop zone, therefore in the interval folded by a chain-dotted line, can also confirm together U phase current Iu becomes zero this situation (with reference to figure 4 (b)).
The effect > of < the 1st execution mode
Fig. 5 means the power transformation circuit loss with respect to (open phase interval) δ between phase pulse stop zone, the generator loss of the power-converting device 1a of the 1st execution mode and the performance plot of the relation of composite loss that their are added, the length that characterizes (open phase is interval) δ between phase pulse stop zone at transverse axis, characterizes loss at the longitudinal axis.That is, Fig. 5 represents to be stopped by pulse loss, the loss of alternating current motor 3 and the characteristic that these 2 losses is added to the composite loss obtaining of δ and power transformation circuit 4 between phase pulse stop zone that control part 9 sets.
As shown in Figure 5, owing to becoming large along with δ between phase pulse stop zone, on-off times reduces, and therefore the loss (power transformation circuit loss) of the power transformation circuit 4 of the 1st execution mode reduces the switching loss causing thus.In addition, because by δ between phase pulse stop zone, the higher harmonic components of electric current increases, so the loss of alternating current motor 3 (generator loss) therefore becomes large.And then because the increase of the higher harmonic components of electric current by making δ between phase pulse stop zone becomes significantly, the increase of the loss (generator loss) of the alternating current motor 3 therefore causing thus also becomes remarkable.For this reason, as shown in Figure 5, existence is added by these 2 losses (power transformation circuit loss and generator loss) composite loss obtaining becomes δ opt between minimum phase pulse stop zone, by δ between phase pulse stop zone is set as to δ opt between this phase pulse stop zone, can reduce the loss of power-converting device 1a integral body.
Above, as described, by using pulse to stop control part 9, can use the formation of the power transformation circuit 4 identical with the PWM control mode of comparative example, reduce the on-off times of the pulse signal that carries out PWM control.In other words, in the situation that form with software the pulse carry out with the control of microcomputer, stop control part 9, can not change the power transformation circuit 4 of comparative example formation, do not append new hardware ground, reach the high efficiency of power-converting device 1a.In addition, due near the shutdown switch action zero crossing of the electric current at alternating current motor 3, therefore can be to the torque pulsation inhibited increase of 150 degree step mode.
The variation > of < the 1st execution mode
At this, as the variation of the 1st execution mode, the situation that δ between phase pulse stop zone is only made as to the folk prescription of 1 intercycle is described, and the phase place between phase pulse stop zone is made as to the situation of stationary state.Fig. 7 means the oscillogram of the alternating voltage that flows through motor, alternating current and pulse signal in the related power-converting device of the variation of the 1st execution mode and the relation of phase pulse stop control signal.In addition, the transverse axis at Fig. 7 characterizes voltage-phase θ v, at each level of longitudinal axis sign voltage (Fig. 7 (a)), electric current (Fig. 7 (b)), pulse signal (Fig. 7 (c)) and open phase control signal (Fig. 7 (d)).
In this variation, narration pulse stops control part 9 and sets the only mode of δ between the phase pulse stop zone shown in 1 Fig. 1 with respect to 1 cycle of electric current (1 circulation).In addition, for the common content of the power-converting device 1a with above-mentioned the 1st execution mode, description thereof is omitted.
In the situation that realize the control device 5a shown in Fig. 1 with integrated circuits such as microcomputers, be suitable for reducing the computing load of this microcomputer.For this reason, if as shown in Fig. 7 (d), pulse stops only δ between 1 phase pulse stop zone of 9 pairs of electric currents of control part, 1 cycle setting, can reduce the computing load of microcomputer.
That is,, in this variation, the pulse of carrying out with the control of microcomputer stops control part 9 with by vector control and the zero cross point of controlled current phase for benchmark, in phase place (with reference to figure 7 (d)), as shown in following formula (2), the phase pulse stop control signal 9A that the switching signal making pulse signal GPU+ and GPU-between phase pulse stop zone between δ is all stopped exports to pulse control part 7.
[several 2]
That is,, known to from formula (2), inciting somebody to action be made as the phase difference of voltage and electric current, when δ is made as between phase pulse stop zone to (open phase is interval), take U, be only the voltage-phase θ of benchmark mutually vfor time, pulse control part 7 stops based on only the pulse signal GPU+ of 1 time and the switch of GPU-.Then, in addition time, pulse control part 7 all carries out the switch based on pulse signal GPU+ and GPU-.In addition, also can be configured to the phase difference at voltage and electric current in 1 cycle of electric current is only set to δ between the phase pulse stop zone of 1 time.
So, by being configured to, 1 cycle of electric current is only set to δ between the phase pulse stop zone of 1 time, the computing load that the pulse that can make microcomputer bear stops control part 9 reduces by half.In addition, by the voltage under the loading condition that mensuration drives in advance and the phase difference of electric current pulse is stopped to voltage in the phase pulse stop control signal 9A of control part 9 and the phase difference of electric current be made as fixed value, can further reduce the computing load of microcomputer.
As described above, the switch motion that the power transformation circuit 4 of the 1st execution mode is undertaken by the pulse signal 7A based on from 7 outputs of pulse control part, carries out PWM control thus, to alternating current motor 3 output AC electricity.The phase information 8A of the electric current that now, the phase current information 6A based on from phase current test section 6 calculates in vector control portion 8 exports to pulse and stops control part 9.Thus, pulse stops the phase pulse stop control signal 9A that control part 9 generates the phase information 8A based on electric current and exports to pulse control part 7.Therefore, pulse control part 7 take power transformation circuit 4 regulation phase (for example U phase) current phase zero crossing as benchmark stop regulation interval pulse signal 7A.Thus, power transformation circuit 4, due near the shutdown switch zero crossing of electric current, has therefore reduced switching loss.Its result, can promote the improved efficiency of power-converting device 1a, and can reduce the distortion of output current.
< < the 2nd execution mode > >
In the 2nd execution mode, illustrate and switch the common PWM control mode that is provided with the PWM control mode of δ between phase pulse stop zone and δ between phase pulse stop zone is not set as the 1st execution mode.
That is,, in the 2nd execution mode, the power-converting device 11 of δ between commutator pulse stop zone can for example, be cut in explanation according to operating condition (rotary speed of alternating current motor 3).
The circuit that Fig. 8 characterizes the power-converting device 11 of the related PWM control mode of the 2nd execution mode forms.As shown in Figure 8, power-converting device 11 has been deleted the phase current test section 6 of the power-converting device 1a of the 1st execution mode shown in Fig. 1, is changed to and detects DC bus current I dCdC bus current test section (current detecting part) 10.That is, the power-converting device 11 of the 2nd execution mode is configured to DC bus current test section 10 to 8 output DC bus current information (electric current) 10A of vector control portion.
In Fig. 8, it is that rotating speed data 8B exports to pulse and stops control part 91 that vector control portion 8 is configured to the rotary speed of the phase information 8A of the electric current of calculating by vector control and alternating current motor 3.Thus, the pulse of the 2nd execution mode stops control part 91 and can cut δ between commutator pulse stop zone according to operating condition (being the rotary speed of alternating current motor 3).Because other constitution content is all identical with the power-converting device 1a of the 1st execution mode shown in Fig. 1, therefore description thereof is omitted.
Fig. 9 means the performance plot of the setting example of (open phase is interval) between the phase pulse stop zone in the power-converting device 11 of the 2nd execution mode, at transverse axis, characterizes rotary speed N, characterizes the length of the interval δ of open phase at the longitudinal axis.; in the power-converting device 11 of the 2nd execution mode; pulse stops control part 91 as shown in Fig. 9 (a); judge the current rotary speed N of alternating current motor 3 and the magnitude relationship of predefined rotary speed N1; in the situation that the not enough rotary speed N1 of current rotary speed N exports to pulse control part 7 by the phase pulse stop control signal 91A that has set δ between phase pulse stop zone.In addition, in the situation that current rotary speed N is more than rotary speed N1, pulse stops control part 91 δ between phase pulse stop zone is made as to 0, and the phase pulse stop control signal 91A that does not establish δ between phasing pulse stop zone is exported to pulse control part 7.
In other words, in the situation that the not enough rotary speed N1 of the current rotary speed N of alternating current motor 3, pulse control part 7 output has the pulse signal of δ between phase pulse stop zone, be rotary speed N1 above in the situation that, and pulse control part 7 is exported the pulse signal that there is no δ between phase pulse stop zone.
In addition, the rotary speed of alternating current motor 3 in order to suppress to cut δ between commutator pulse stop zone according to operating condition is, the excessive change of torque, also can, as shown in Fig. 9 (b), adopt and make the length of δ between phase pulse stop zone from rotary speed N2, change to the mode of rotary speed N3 with certain rate of change.In addition, in order to make the switching of δ between phase pulse stop zone further smooth and easy, also can, as shown in Fig. 9 (c), adopt from rotary speed N2 until rotary speed N3 changes the length of δ between phase pulse stop zone along the curve of regulation with nonlinear rate of change.
In addition, can not also that the rotary speed based on alternating current motor 3 is cut δ between commutator pulse stop zone, but be configured to the DC bus current I that the DC bus current test section 10 based on by Fig. 8 detects dCmean value I dCavecut δ between commutator pulse stop zone.In this case, the transverse axis in the performance plot of Fig. 9 (a), (b), (c) is not rotary speed N but regards DC bus current mean value I as dCave.
In addition, also can form the rotary speed not being based on alternating current motor 3 and cut δ between commutator pulse stop zone, but the torque tau of exporting based on alternating current motor 3 is cut δ between commutator pulse stop zone.In this case, the transverse axis in the performance plot of Fig. 9 (a), (b), (c) is not rotary speed N but regards output torque tau as.
Above, as described, by according to the operating condition of alternating current motor 3 (the rotary speed N of alternating current motor 3, output torque tau or DC bus current mean value I dCavedeng) cut δ between commutator pulse stop zone, at alternating current motor 3, in low speed rotation territory in the situation that, by establishing δ between phasing pulse stop zone, can compare and drive more expeditiously power-converting device 11 with the PWM control mode of comparative example.In addition, at alternating current motor 3, in High Rotation Speed territory in the situation that, δ between phase pulse stop zone can be made as to 0, be passed to swimmingly and do not establish the degree energising of 180 between phasing pulse stop zone.
In addition, in the situation that make δ between phase pulse stop zone to the direction change of constriction according to the operating condition of alternating current motor 3, can be by being switched to immediately between stop zone zero state between the stop zone from regulation, with certain rate of change from changing between stop zone zero state between the stop zone of regulation or carrying out from any one that changes between stop zone zero state between the stop zone of regulation with nonlinear rate of change.
In addition, in the situation that make δ between phase pulse stop zone to the direction change of expansion according to the operating condition of alternating current motor 3, can be by being switched to immediately from zero state between stop zone between the stop zone of regulation, with certain rate of change from zero state variation between stop zone to the stop zone of regulation, carry out from zero state variation between stop zone to any one stop zone of regulation with nonlinear rate of change.
< < the 3rd execution mode > >
In the 3rd execution mode, illustrate the power-converting device 11 of the power-converting device 1a of the 1st execution mode and the 2nd execution mode is applied in to the situation in the driven compressor of air conditioner.
Figure 10 characterizes the whole pie graph of the related air conditioner 100 of the 3rd execution mode.
As shown in figure 10, the air conditioner 100 of the 3rd execution mode by with extraneous air carry out heat exchange off-premises station 101, carry out the indoor set 102 of heat exchange with room air, the pipe arrangement 103 that links off-premises station 101 and indoor set 102 forms.
Off-premises station 101 by the compressor 104 of compression refrigerant, the compressor driving motor 105 of drive compression machine 104, drive the motor drive 106 of controlling and the heat exchanger 107 that uses compression refrigerant and extraneous air to carry out heat exchange to form to compressor driving motor 105.At this, motor drive 106 is used the power-converting device 1a of the 1st execution mode or the power-converting device 11 of the 2nd execution mode.In addition, indoor set 102 is by carrying out the heat exchanger 108 of heat exchange and form to the forced draft fan 109 of indoor air-supply with room air.
At this, the efficiency of compressor driving motor 105 is described with Figure 11.Figure 11 is that efficiency in the air conditioner 100 shown in Figure 10 is with respect to the performance plot of the relation of the rotary speed of compressor driving motor 105, transverse axis characterizes the rotary speed of compressor driving motor 105, and the longitudinal axis characterizes the efficiency of compressor driving motor 105.
When carrying out PWM control, motor drive 106, in the situation that the rotary speed of compressor driving motor 105 is more than N4 (with reference to Figure 11), is carried out as following and is controlled.That is, in the voltage saturation region of motor drive 106 exportable voltage under the sine wave modulation mode exceeding at power transformation circuit 4, carry out and control, make to control to flow through idle current by weak excitation, thus the electric current of minimizing magnet exciting coil.Can realize thus the stabilized driving in the High Rotation Speed territory of compressor driving motor 105.Yet, owing to carrying out so weak excitation, control, therefore as shown in the solid line of Figure 11, in the reduction of the High Rotation Speed territory of compressor driving motor 105 (more than rotary speed N4) luminous efficiency.
For this reason, in the 3rd execution mode, for example the power-converting device 1a of the 1st execution mode is applied to air conditioner 100, by stopping by pulse the pulse signal 7A that control part 9 is provided with δ between phase pulse stop zone from 7 outputs of pulse control part, controls power transformation circuit 4.In other words, can reduce by δ between phase pulse stop zone is set the on-off times of power transformation circuit 4.Thus, in result, reduced the loss of motor drive 106.
So, by reducing the switching loss of power transformation circuit 4, as shown in one of Figure 11 dashdotted characteristic, the lifting of efficiency is sought in the region of low speed rotation that can become in the efficiency of the motor drive 106 lower than drive compression machine drive motor 105 the rotary speed N4 of peak value.In addition, the output of voltage saturation region more than rotary speed N4 stops control part 9 by the pulse of Fig. 1 and δ between phase pulse stop zone is made as to 0 pulse signal is switched to the PWM control mode of 180 degree energisings, thereby can carry out the driving of weak excitation control area.
As described above, by the 3rd execution mode, because the formation of power transformation circuit 4 that can be identical by the PWM control mode with comparative example reduces the on-off times of power transformation circuit 4, therefore in the situation that form by software the pulse of carrying out with the control of microcomputer, stop control part 9, can not carry out the on-off times that reduces power transformation circuit 4 of hardware with appending.Therefore, the loss of power transformation circuit 4 and motor drive 106 can be reduced, and the high efficiency of air conditioner 100 can be realized.
According to above-mentioned the 1st execution mode to the 3 execution modes, can provide high efficiency power-converting device and the air conditioner of the switching loss while reducing PWM control.
But in the various embodiments described above, the timing of switching at phase pulse stop control signal, produces minimal width pulse signal sometimes.In the more situation of width of this pulse signal, by the specification of gate drivers 42, stipulated minimum value, the pulse signal of not enough this minimum value thinks that have can not be by the possibility of gate drivers 42 correct identification signals.In the situation that can not correctly identifying, action that can not be to the pulse signal offset gate driver 42 of not enough minimum value.That is, also have gate drivers 42 to occur the non-possibility of wanting the action carried out.Accordingly, must be made as pulse signal more than minimal width.For this reason known, as the 4th execution mode or the 5th execution mode below.In the 4th execution mode of the following stated, for ease of understanding, with 1st to 3rd execution mode contrast on one side, the content of present embodiment is described on one side.
< < the 4th execution mode > >
Figure 12 amplify illustrate the alternating voltage that flows through alternating current motor 3 (Figure 12 (a)), alternating current (Figure 12 (b)) and the pulse signal (Figure 12 (c)) that represent in the 1st execution mode, with the oscillogram of the relation of phase pulse stop control signal (Figure 12 (d)).As shown in Figure 12 (d), phase pulse stop control signal (open phase control signal) always becomes 1.In addition, owing to generating the vector control portion 8 production burst width of command voltage, can not become minimum instruction, therefore in Figure 12 (c), the pulse duration of pulse signal GPU+, GPU-can not become minimum.
Figure 13 and Figure 14 represent to have phase pulse stop control signal for Figure 12 to become in 0 interval situation and flow through alternating voltage, alternating current and the pulse signal of alternating current motor 3 and the figure of the relation of phase pulse stop control signal.At the phase pulse stop control signal 9A that stops control part 9 output from pulse, change at 0 o'clock (with reference to Figure 13 (d)) from 1, GPU+ and GPU-become pulse cut-off state (switch stops) (with reference to Figure 13 (c)).On the other hand, at phase pulse stop control signal 9A, change at 1 o'clock (with reference to Figure 13 (d)) from 0, GPU+ and GPU-carry out the switch (with reference to Figure 13 (c)) of PWM control mode.At Figure 13, at the pulse signal that carries out PWM control, become effectively, through the timing of regular hour, phase pulse stop control signal 9A changes to 0 from 1.For this reason, can output stage small-pulse effect signal (the label P1 shown in Figure 13 (c)).In addition, until the pulse signal that carries out PWM control is from effectively becoming cut-off, having the timing of regular hour, phase pulse stop control signal 9A just changes to 1 from 0.For this reason, output stage small-pulse effect signal (the label P2 shown in Figure 13 (c)) not.But, in Figure 14, at the pulse signal that carries out PWM control, becoming effectively, only through the timing of very short time, phase pulse stop control signal (open phase control signal) 9A changes to 0 from 1.Will export thus minimum width-pulse signal (the label P3 shown in Figure 14 (c)).In addition, until the pulse signal that carries out PWM control is from effectively becoming cut-off, having the timing of regular hour, phase pulse stop control signal 9A changes to 1 from 0.For this reason, can output stage small-pulse effect signal (the label P4 shown in Figure 14 (c)).So, according to the switching timing of carrying out pulse signal and the pulse stop control signal 9A of PWM control, can export minimum width-pulse signal.
The circuit that Figure 15 characterizes the power-converting device 11a of the related PWM control mode of the 4th execution mode forms.During the circuit of Figure 15 forms, the pulse of the Fig. 8 forming at the circuit that represents the power-converting device 11 of the PWM control mode that the 2nd execution mode is related stops 7 of control part 9 and pulse control parts, appends pulse duration detection unit 12.The command voltage V of pulse duration detection unit 12 to be generated by vector control portion 8 *and between phase pulse stop control signal 9A and phase pulse stop zone, δ is input, production burst starting/stopping executive signal.More specifically explanation, pulse duration detection unit 12 monitors phase pulse stop control signal 9A, and phase pulse stop control signal 9A is switched to 1 timing or is switched to 0 timing and pulse decision instruction voltage V from 1 from 0 *compare.Then, pulse duration detection unit 12 has the function of the timing that postpones actual starting/stopping pulse signal in the situation that pulse signal becomes minimal width.Because other constitution content is all identical with the power-converting device 11 of the 2nd execution mode shown in Fig. 8, therefore description thereof is omitted.
Figure 16 is for the figure between the switching exclusion area of the alternating voltage that flows through alternating current motor 3 (Figure 16 (a)) and pulse signal (Figure 16 (b)) expression phase pulse stop control signal (an open circuit layer phase control signal) 9A.While switching pulse signal within the time of the interval C shown in oblique line (0 → 1 switches between exclusion area) or interval D (1 → 0 switches between exclusion area), can export minimum width-pulse.For its solution is arranged to pulse duration detection unit 12, to 7 outputs of pulse control part, there is not the phase impulse starting/halt instruction of minimal width pulse.
Figure 17 is the figure by pulse duration detection unit 12 along orders with flowcharting.At step S200, pulse duration detection unit 12 is sentenced the magnitude relationship of δ and minimal width between phasing pulse stop zone.Conventionally, in order to reduce switching loss, consider δ between phase pulse stop zone to set widelyr than fully with minimal width pulsion phase.But, in the situation that the 2nd execution mode makes between phase pulse stop zone that δ slowly changes like that, owing to also having the situation of the not enough minimal width pulse of δ between phase pulse stop zone, therefore need the determination processing of step S200.
The in the situation that of the not enough minimal width pulse of δ between phase pulse stop zone (step S200 → "No"), pulse duration detection unit 12 is no matter how phase pulse stop control signal 9A makes phase impulse starting/halt instruction be output as 1 (S212).On the other hand, at δ between phase pulse stop zone, be minimal width pulse above in the situation that (step S200 → "Yes"), at step S201, pulse duration detection unit 12 determines whether to erect and switches extension mark.In the situation that erectting switching extension mark (S201 → "Yes"), the processing of pulse duration detection unit 12 advances to step S203.On the other hand, in the situation that not erectting switching extension mark (S201 → "No"), the processing of pulse duration detection unit 12 advances to step S202.
At step S202, whether pulse duration detection unit 12 is judged last time different with this phase pulse stop control signal 9A.In the situation that last time with this phase pulse stop control signal 9A not different (S202 → "No"), do not need the switching of pulse stop signal.Therefore, the processing of pulse duration detection unit 12 advances to step S206, directly using phase pulse stop control signal 9A as phase impulse starting/and halt instruction output.On the other hand, in the situation that last time with this phase pulse stop control signal 9A different (S202 → "Yes"), the processing of pulse duration detection unit 12 advances to step S203.At step S203, pulse duration detection unit 12 judges whether this phase pulse stop control signal is 1.In the situation that this phase pulse stop control signal is 1 (S203 → "Yes"), the processing of pulse duration detection unit 12 advances to step S204.On the other hand, in the situation that this phase pulse stop control signal is 0 (S203 → "No"), the processing of pulse duration detection unit 12 advances to step S205.
At step S204, pulse duration detection unit 12 in the situation that this returns to PWM on off state from pulse halted state, judge in PWM output until the time that becomes pulse cut-off whether as Minimum-time below (in the interval D of Figure 16).In the situation that till the time of pulse cut-off is not (S204 → "No") below Minimum-time, the processing of pulse duration detection unit 12 advances to step S207.At step S207,12 outputs 1 of pulse duration detection unit are as phase impulse starting/halt instruction 12A.
On the other hand, in the situation that step S204 is judged to be, the time of pulse cut-off is (S204 → "Yes") below Minimum-time, and the processing of pulse duration detection unit 12 advances to step S209.At step S209, pulse duration detection unit 12 is erect and is switched extension mark, and at step S211, output 0 is as phase impulse starting/halt instruction 12A.Thus, after pulse duration detection unit 12 puts off until next time by the switching of pulse stop signal.
In addition, at step S205, pulse duration detection unit 12 in the situation that this is switched to pulse halted state from PWM on off state, judge in PWM output from make pulse as the time effectively whether as Minimum-time below (in the interval C of Figure 16).In the situation that the elapsed time from pulse effectively starts is not (S205 → "No") below Minimum-time, the processing of pulse duration detection unit 12 advances to step S208.At step S208,12 outputs 0 of pulse duration detection unit are as phase impulse starting/halt instruction 12A.
On the other hand, in the situation that the elapsed time from pulse effectively starts is (S205 → "Yes") below Minimum-time, the processing of pulse duration detection unit 12 advances to step S210.At step S210, pulse duration detection unit 12 is erect and is switched extension mark, and at step S212, output 1 is as phase impulse starting/halt instruction 12A.Thus, after pulse duration detection unit 12 puts off until next time by the switching of phase impulse starting/halt instruction 12A.
So, take from pulse, stop control part 9 phase pulse stop control signal 9A as basis, by pulse duration detection unit 12, will not make phase impulse starting/halt instruction 12A of minimal width pulse generation export to pulse control part 7.In pulse control part 7, based on phase impulse starting/halt instruction, 12A exports the pulse signal with δ between phase pulse stop zone.That is, not the phase pulse stop control signal 9A according to the 1st to the 3rd execution mode, but the phase of exporting according to pulse duration detection unit 12 impulse starting/halt instruction 12A, pulse control part 7 output pulse signals.
As described above, by the 4th execution mode, can provide the high efficiency power-converting device 11a that meets the specification of gate drivers 42 and reduced switching loss when PWM controls.
< < the 5th execution mode > >
In the 5th execution mode, pulse duration detection unit 12 use in the 4th execution mode generate phase impulse starting/halt instruction 12A with the 4th execution mode diverse ways.Figure 18 (a) represents PWM carrier signal and applies voltage instruction V *, as representative, U is shown and applies mutually voltage instruction Vu *.Idle time shown in Figure 18 (b), interval E was the interval of establishing in order to make pulse signal GPU+ and GPU-become effectively (upper underarm short circuit) interval disappearance simultaneously.In the 5th execution mode, pulse duration detection unit 12 plays and pulse is stopped to the phase pulse stop control signal 9A that control part 9 exports in idle time, in interval E, passes to the effect of pulse control part 7.Pulse control part 7 is followed phase impulse starting/halt instruction 12A and is carried out the switching of PWM on off state and pulse halted state.Now, owing to being the timing that pulse signal GPU+ and GPU-become cut-off, therefore, even if carry out the switching of phase pulse, can not send minimal width pulse yet.
As described above, by the 5th execution mode, can provide the high efficiency power-converting device that meets the specification of gate drivers 42 and reduced switching loss when PWM controls.
In addition, understand specifically power-converting device 1a involved in the present invention, 11 and used this power-converting device 1a, 11 motor drive 106, used in addition the execution mode of the air conditioner 100 of this motor drive 106, but the present invention is not limited to the content of each described execution mode, can in the scope that does not depart from its main idea, carry out various changes, this is self-evident.
That is, the present invention is not limited to the content of the 1st execution mode to the 5 execution modes, can carry out various distortion.In other words, each described execution mode is to describe and detailed illustrative formation for ease of understanding content of the present invention, might not leave no choice but limit the whole formations that possess described explanation.In addition, a part for the formation of certain execution mode can also be replaced into the formation of other execution mode, can also further the formation of other execution mode be added in the formation of certain execution mode.
In addition, for a part for the formation of each execution mode, the formation that can also append, delete, replace other execution mode.And then each described formation, function, handling part, processing unit etc. also can be realized by designing with integrated circuit etc. they part or all with hardware.In addition, the program that each above-mentioned formation, function etc. also can realize each function by processor by explanation is carried out, and realizes thus with software.In addition, the information such as program, table, file that realizes each function can be placed in memory, hard disk, SSD (Solid State Drive, solid-state drive) tape deck or IC (the integrated circuit such as, integrated circuit) card, in the recording mediums such as SD card, DVD (Digital Versatile Disc, digital multimedia dish).In addition, control line and information wire illustrate for the needs on illustrating, but on product, whole control lines and information wire might not be shown.Reality also can be thought and almost all form and all interconnect.
In industry, utilize possibility
According to the present invention, the power-converting device of the drive motor that is not limited to use in air conditioner, also can effectively utilize in the power-converting device of the drive motor using in the home appliances such as freezer, washing machine, electric vacuum cleaner etc.
The explanation of label
1,1a, 1b, 11 power-converting devices
2 DC power supply
3 alternating current motors (motor)
4 power transformation circuits
5,5a, 5b control device
6 phase current test sections (current detecting part)
6A phase current information (electric current)
7 pulse control parts
7A pulse signal
8 vector control portions
8A phase information (current phase)
8B rotating speed data
9,91 pulses stop control part
9A, 91A phase pulse stop control signal (pulse stop control signal)
10 DC bus current test sections (current detecting part)
10A DC bus current information (electric current)
12 pulse duration detection units
12A impulse starting/halt instruction
41 power converter main circuits
42 gate drivers
100 air conditioners
101 off-premises stations
102 indoor sets
103 pipe arrangements
104 compressors
105 compressor driving motors
106 motor drives
107,108 heat exchangers
109 forced draft fans
V *apply voltage instruction (command voltage)
Between δ phase pulse stop zone
Pulse when P1, P2, P3, P4 open phase control signal are switched
C, D phase pulse stop control signal switch between exclusion area
E is interval idle time

Claims (5)

1. a power-converting device, it uses vector control mode, by PWM, controls to carry out power converter, and described power-converting device is characterised in that to possess:
Pulse control part, the pulse signal of its output for carrying out described PWM control;
Power transformation circuit, it is used from the pulse signal of described pulse control part output direct current is transformed to alternating current;
Current detecting part, it detects the electric current of described power transformation circuit;
Vector control portion, it,, based on the detected electric current of described current detecting part, carries out vector control, generates the command voltage that offers described pulse control part; With
Pulse stops control part, and it is created on take the pulse stop control signal that pulse signal stops described in the pulse stop zone chien shih that the current phase of described power transformation circuit is benchmark, and described pulse stop control signal is exported to described pulse control part,
Described pulse control part is exported the pulse signal of the time width of the action that can ensure gate drivers.
2. power-converting device according to claim 1, is characterized in that,
Described power-converting device also possesses pulse duration detection unit, and this pulse duration detection unit is in the situation that the pulse generation below described pulse enable signal setting-up time width postpones to carry out the interval of described PWM control and the switching between described pulse stop zone.
3. power-converting device according to claim 2, is characterized in that,
The idle time that described pulse duration detection unit all stops at the switch element of the upper underarm of homophase is interval, switches between the interval and described pulse stop zone of carrying out described PWM control.
4. a motor drive, it possesses:
Power-converting device in claim 1～3 described in any one; With
The motor that the alternating current of being exported by described power transformation circuit drives,
Described motor drive is characterised in that,
In the situation that the rotary speed of described motor is more than set point, described pulse control part does not arrange between described pulse stop zone.
5. an air conditioner, possesses:
Power-converting device in claim 1～3 described in any one; With
The compressor that the alternating current of being exported by described power transformation circuit drives,
Described air conditioner is characterised in that,
In the situation that the rotary speed of described compressor is more than setting, described pulse control part does not arrange between described pulse stop zone.
CN201280058552.7A 2011-11-30 2012-08-08 Power-converting device, motor drive and air conditioner Active CN103959637B (en)

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JP2011261179A JP5675567B2 (en) 2011-11-30 2011-11-30 Power conversion device, electric motor drive device, and air conditioner
JP2011-261179 2011-11-30
PCT/JP2012/070182 WO2013080610A1 (en) 2011-11-30 2012-08-08 Power converter, electric motor drive device, and air conditioner

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