CN103312648B - The synchronization offset estimation method of communication system and device, mobile terminal and base station - Google Patents

Abstract

The synchronization offset estimation method of communication system and device, mobile terminal and base station, the synchronization offset estimation method of described communication system comprises: carry out R times of over-sampling to the channel estimation results of signal; Based on the channel estimation results after R times of over-sampling, obtain estimated position and the power in the estimated position in the strongest path of signal and time strong path of power and signal; According to the relation between the power in the strongest path and the power in secondary strong path, at least based on the simultaneous bias of the estimated position in the strongest described path and the target location certainty annuity of synchronous point.Technical solution of the present invention can well adapt to, at mobile channel and the raw wireless channel environments such as channel that go out, obtain good systematic function, and do not affect the performance under conventional channel.

Description

The synchronization offset estimation method of communication system and device, mobile terminal and base station

Technical field

The present invention relates to the communications field, particularly a kind of synchronization offset estimation method of communication system and device, mobile terminal and base station.

Background technology

In mobile communication system, the synchronous of the sampling clock of guarantee transmitting terminal and receiving terminal is needed.Due to the operation of subscriber equipment (UE, UserEquipment) and the deviation of crystal oscillator, sending and receiving end clock may be caused to occur deviation, UE needs to remain synchronous by timing.Therefore, sampling clock synchronously to have become in associated communication system an important component, and in clock synchronous, an important part is exactly accurately estimate the sampling clock offset existed in communication system.

The synchronization offset estimation of communication system is usually based on the interpolation method of channel estimating; its general principle is that the channel estimation results of signal is carried out R times of over-sampling; R depends on the demand to estimated accuracy, then chooses moment corresponding to the strongest path of signal as the optimum sampling moment.The estimated accuracy of this method depends on the multiple of over-sampling, and such as, if carried out 8 times of over-samplings, the synchronism deviation estimated accuracy so obtained is 1/8 chip (chip).

For the channel estimation results of each subframe, said method all can be adopted to obtain the estimated position in the strongest path of a signal under certain estimated accuracy requires, this estimated position just can as synchronous point position, and the difference between itself and synchronous point target location is the simultaneous bias of system.

Although the synchronization offset estimation method of this routine; good systematic function can be had under common channel circumstance; but under the raw wireless channel environment such as channel and mobile channel that goes out, often systematic function can be caused poor because of the inaccurate of synchronization offset estimation result.In order to keep the transmission performance under conventional channel and can be good at supporting raw go out channel and mobile channel, need to be optimized and improvement the method for synchronization offset estimation.

Correlation technique can be also the U.S. Patent application of US2011122979 (A1) with reference to publication number, the patent application discloses a kind of sampling clock offset and estimates and compensation method and device.

Summary of the invention

The problem to be solved in the present invention is the synchronization offset estimation that prior art is difficult to adapt to communication system under the raw wireless channel environment such as channel and mobile channel that goes out, to obtain good systematic function.

For solving the problem, technical solution of the present invention provides a kind of synchronization offset estimation method of communication system, comprising:

R times of over-sampling is carried out to the channel estimation results of signal;

Based on the channel estimation results after R times of over-sampling, obtain estimated position and the power in the estimated position in the strongest path of signal and time strong path of power and signal;

According to the relation between the power in the strongest path and the power in secondary strong path, at least based on the simultaneous bias of the estimated position in the strongest described path and the target location certainty annuity of synchronous point.

Optionally, the described channel estimation results to signal carries out a R times over-sampling and comprises:

R is carried out to the channel estimation results of signal ₁times interpolation;

With described R ₁the strongest path of the channel estimation results determination signal after times interpolation and the interval that time strong path occurs;

Respectively in the strongest described path and interval that time strong path occurs to described R ₁channel estimation results after times interpolation carries out R ₂times interpolation; Wherein, R ₁* R ₂=R.

Optionally, described based on the channel estimation results after R times of over-sampling, the estimated position and the power that obtain the estimated position in the strongest path of signal and time strong path of power and signal comprise:

From described to R ₁first estimated value L ' of the estimated position in the strongest path described in obtaining in channel estimation results after times interpolation _maxwith the first estimated value V ' of the estimated position in described strong path _max;

From described to R ₁channel estimation results after times interpolation carries out R ₂second estimated value L of the estimated position in the strongest path described in obtaining in result after times interpolation " _maxwith the second estimated value V of the estimated position in power and described time strong path " _maxand power;

With R ₂* L ' _maxwith L " _maxsum as the estimated position in the strongest described path, with R ₂* V ' _maxwith V " _maxsum is as the estimated position in described strong path.

Optionally, described with described R ₁the interval that time strong path occurs of the channel estimation results determination signal after times interpolation comprises:

At described R ₁in channel estimation results after times interpolation, data corresponding to the adjacent N number of position in the left end point position in the interval occurred in the strongest described path and left and right thereof empty; Wherein N sets based on channel circumstance;

Based on the channel estimation results emptied after described data, determine the interval of time strong path appearance of signal.

Optionally, R=16, R ₁=2, R ₂=8.

Optionally, the relation between the power in the described the strongest path of basis and the power in secondary strong path, the simultaneous bias at least based on the estimated position in the strongest described path and the target location certainty annuity of synchronous point comprises:

Judge whether the power in described strong path is greater than threshold value, be then with the estimated position in the strongest described path and and the estimated position in described time strong path between centre position and the simultaneous bias of target location computing system of synchronous point, otherwise using the difference of the target location of the estimated position in the strongest described path and described synchronous point as the simultaneous bias of system; Described threshold value for described in the power in the strongest path and the product of threshold parameter.

Optionally, the span of described threshold parameter be [1/2,1).

Optionally, described with the estimated position in the strongest described path and and the estimated position in described time strong path between centre position and the simultaneous bias of target location computing system of synchronous point comprise:

With the estimated position L in the strongest described path _peakwith the estimated position V in described strong path _peakbetween centre position T ₀determine the shifted by delta L of integral multiple chip _int;

With the estimated position L in the strongest described path _peakwith the target location L of described synchronous point _trgtcalculate little several times chip offset Δ L _frac;

By described integral multiple chip offset Δ L _intwith little several times chip offset Δ L _fracsum is as the simultaneous bias of system.

Optionally, described integral multiple chip offset Δ L _int=T _{0, int}-L _trgt, wherein: t ₀=round ((L _peak+ V _peak)/2), round is round function; Described little several times chip offset Δ L _frac=mod (L _peak-L _trgt, R), wherein mod is MOD function.

Optionally, described over-sampling is realized by raised cosine FIR filter or low pass filter.

Optionally, described communication system is TD-SCDMA communication system.

For solving the problem, technical solution of the present invention also provides a kind of synchronization offset estimation device of communication system, comprising:

Over-sampling unit, is suitable for carrying out R times of over-sampling to the channel estimation results of signal;

Acquiring unit, is suitable for the channel estimation results after based on R times of over-sampling, obtains estimated position and the power in the estimated position in the strongest path of signal and time strong path of power and signal;

Simultaneous bias determining unit, is suitable for according to the relation between the power in the strongest path and the power in secondary strong path, at least based on the simultaneous bias of the estimated position in the strongest described path and the target location certainty annuity of synchronous point.

For solving the problem, technical solution of the present invention also provides a kind of and comprises the mobile terminal of the synchronization offset estimation device of above-mentioned communication system and a kind of base station comprising the synchronization offset estimation device of above-mentioned communication system.

Compared with prior art, technical solution of the present invention has the following advantages:

Over-sampling is carried out to the channel estimation results of signal, the strongest path of signal and the estimated position in secondary strong path and power is obtained from the result after over-sampling, again according to the relation between the power in the strongest described path and the power in described strong path, at least based on the simultaneous bias of the estimated position in the strongest described path and the target location certainty annuity of synchronous point, so, determine that synchronous point position can estimate the simultaneous bias of system exactly by estimating two the strongest paths of signal, thus well can adapt to mobile channel and the raw wireless channel environments such as channel that go out, obtain good systematic function, and the performance do not affected under conventional channel.

Accompanying drawing explanation

Fig. 1 is the schematic flow sheet of the synchronization offset estimation method of the communication system that embodiment of the present invention provides;

Fig. 2 is the clock skew schematic diagram of communication system under mobile propagation conditions;

Fig. 3 is the clock skew schematic diagram of communication system under the raw propagation conditions that goes out;

Fig. 4 is the structural representation of the synchronization offset estimation device of the communication system that the embodiment of the present invention provides.

Embodiment

For enabling above-mentioned purpose of the present invention, feature and advantage more become apparent, and are described in detail the specific embodiment of the present invention below in conjunction with accompanying drawing.Set forth detail in the following description so that fully understand the present invention.But the present invention can be different from alternate manner described here to implement with multiple, those skilled in the art can when without prejudice to doing similar popularization when intension of the present invention.Therefore the present invention is not by the restriction of following public embodiment.

Fig. 1 is the schematic flow sheet of the synchronization offset estimation method of the communication system that embodiment of the present invention provides.As shown in Figure 1, the synchronization offset estimation method of described communication system comprises:

Step S101, carries out R times of over-sampling to the channel estimation results of signal;

Step S102, based on the channel estimation results after R times of over-sampling, obtains estimated position and the power in the estimated position in the strongest path of signal and time strong path of power and signal;

Step S103, according to the relation between the power in the strongest path and the power in secondary strong path, at least based on the simultaneous bias of the estimated position in the strongest described path and the target location certainty annuity of synchronous point.

Elaborate with the synchronization offset estimation method of specific embodiment to above-mentioned communication system below.

In the present embodiment, described communication system is TD-SCDMA communication system.In other embodiments, described communication system also can have employed the communication system of spread spectrum, the communication systems such as such as WCDMA, CDMA2000 for other.Therefore, the synchronization offset estimation method described in the embodiment of the present invention can be applicable to plurality of communication systems, and is not limited only to TD-SCDMA system.

As described in the background art; synchronization offset estimation method of the prior art; good systematic function can be had under common channel circumstance; but under mobile channel and the raw wireless channel environments such as channel that go out, often systematic function can be caused poor because of the inaccurate of synchronization offset estimation result.First mobile propagation conditions and the raw propagation conditions that goes out are briefly described below.

Mobile propagation conditions is the channel model without decline having two footpaths.Fig. 2 is the clock skew schematic diagram of communication system under mobile propagation conditions, as shown in Figure 2, two paths in mobile propagation conditions, one is static---be assumed to be at t ₀the path P in moment ₀, one for movement---be assumed to be at t ₀the path P in ' moment ₀', the amplitude in two paths is identical with phase place, and the time difference between two paths is as shown in formula (1).

$\mathrm{\Δ\τ}=B+\frac{A}{2}(1+\sin (\mathrm{\Δ\ω}\·t))---\left(1\right)$

Parameter usually can according to following table (mobile propagation conditions multipath parameter table) value in formula (1):

A	5μs
		B	1μs
Δω	40*10 -3s -1

The raw propagation conditions that goes out is the non-fading propagation environment with two signal paths.Two signal paths of the raw propagation conditions that goes out, replace between " life " and " going out " state, signal path appearance position is on a timeline equiprobable at random.Fig. 3 is the clock skew schematic diagram of communication system under the raw propagation conditions that goes out, and as shown in Figure 3, supposes that two signal paths that certain moment time shaft occurs are respectively at P ₁the path 1 of position and at P ₂the path 2 of position, Stochastic choice from one group of relative time delay [-3 ,-2 ,-1,0,1,2,3] chip (781.25ns), and there is identical amplitude and phase place.After 191ms, at P ₁the path 1 of position disappears (being represented by dotted lines in figure), and occurs a new delay positions immediately, position Stochastic choice from [-3 ,-2 ,-1,0,1,2,3] this group of chip of appearance, but does not comprise the position P at original place, path 2 ₂, as the position P in Fig. 3 ₁', amplitude, the phase place in two paths remain unchanged; After 191ms, be positioned at P ₂the path 2 of position disappears, and occurs a new delay positions immediately, position Stochastic choice from [-3 ,-2 ,-1,0,1,2,3] this group of chip of appearance, but does not comprise the position P at original place, path 1 ₁'.Amplitude, the phase place in two paths still remain unchanged; Two paths so repeatedly appearing and subsiding on a timeline of signal.

Mobile propagation conditions and the raw propagation conditions that goes out are conventionally known to one of skill in the art, are not described in detail at this.Inventor finds, due to the particularity of wireless channel environment under mobile propagation conditions and the raw propagation conditions that goes out, the generation of the exit window problem of channel estimation results may be caused, thus to make in prior art only with the strongest path of signal to determine that simultaneous bias is difficult to obtain estimated result accurately, and then make systematic function poor.Therefore, inventor considers, simultaneous bias can be determined by the position and power estimating two the strongest paths of signal, can effectively avoid making the inaccurate of synchronization offset estimation result because of the exit window problem of channel estimation results, thus well can adapt to mobile channel and the raw wireless channel environments such as channel that go out, obtain good systematic function, and do not affect the performance under conventional channel.

Next the synchronization offset estimation method of the communication system in the present embodiment is described.

First perform step S101, R times of over-sampling is carried out to the channel estimation results of signal.In the present embodiment, carrying out R times of over-sampling to the channel estimation results of signal described in step S101 can comprise:

Step S101a, carries out R to the channel estimation results of signal ₁times interpolation;

Step S101b, with described R ₁the strongest path of the channel estimation results determination signal after times interpolation and the interval that time strong path occurs;

Step S101c, respectively in the strongest described path and interval that time strong path occurs to described R ₁channel estimation results after times interpolation carries out R ₂times interpolation; Wherein, R ₁* R ₂=R.

In specific implementation process, in order to reduce operand, R times of over-sampling interpolation can be carried out in two steps, first the channel estimation results of signal is carried out to the interpolation of less multiple, object first determines the strongest path of signal and the interval of time strong path appearance, then in the interpolation of in the interval determined, the result after a step interpolation above being carried out again to larger multiple, just the estimated position in the strongest path and the estimated position in power and secondary strong path and power can be obtained from the result after twice interpolation by subsequent step, and carry out the estimation of simultaneous bias accordingly.Owing to only needing to carry out for the channel estimation results in certain two interval in second time Interpolation Process, and do not need to carry out interpolation to all channel estimation results in activation detection window, therefore amount of calculation can greatly reduce, and improves the efficiency of synchronization offset estimation.

It should be noted that, although R, R ₁, R ₂between a relation demand fulfillment R ₁* R ₂=R, but as a rule, R, R ₁, R ₂be positive integer, and 1 < R ₁< R ₂.In the present embodiment, in order to estimated accuracy can be made to reach 1/16chip, get R=16, R ₁=2, R ₂=8.In other embodiments, also can to R, R ₁, R ₂get other value, such as: estimated accuracy when 1/8chip, R=8, R ₁=2, R ₂=4; Certainly, estimated accuracy when 1/16chip, also desirable R=16, R ₁=4, R ₂=4.

When reality is implemented, for the consideration of cost, more use digit compensated crystal oscillator (DCXO) as crystal oscillator at present in communication system, but, because the deviation ratio Temp .-compensation type crystal oscillator (TCXO) of DCXO is large, and can not automatically adjust, in this case, clock skew is larger, the estimated accuracy of common 1/8chip can not meet the requirement of performance, the clock skew of 1/16chip precision must be estimated, when there is 1/16chip skew in clock, the receiving terminal of communication system can estimate clock jitter accurately, thus adjust, clock jitter is controlled all the time within 1/16chip.Because estimated accuracy depends on the multiple of over-sampling, therefore, in order to the estimated accuracy of 1/16chip can be reached, need with 16 times of over-samplings.

In the present embodiment, first of the targeted customer channel estimation results activating detection window can be used to carry out synchronism deviation estimation.In other embodiments, other channel estimation results activating arbitrarily detection window of targeted customer also can be used to carry out synchronism deviation estimation, the channel estimation results of multiple activation detection windows of targeted customer can also be used to carry out synchronism deviation estimation.If set first to activate the channel estimation results of detection window as h (k), k=0,1,2 ..., W-1, wherein W is length of window.

Work as R ₁=2, R ₂when=8, then step S101a is specially: carry out 2 times of interpolation to h (k), obtain h ' (k).

h′(2k)＝h(k)，k＝0，1，2，...，W-1，

$h^{\&prime;}(2k+1)={\mathrm{\&Sigma;}}_{n=-\frac{M}{2}+1}^{\frac{M}{2}}h(k+n)\&CenterDot;f_2(2n-1),$ k＝0，1，2，...，W-1，

F ₂x () is raised cosine pulse, $f_2\left(x\right)=\left(\frac{\cos \left(\frac{\mathrm{\&pi;\&alpha;}\left(x\right)}{2}\right)}{1-{\mathrm{\&alpha;}}^2{\left(x\right)}^2}\right)\&CenterDot;\left(\frac{\sin \left(\frac{\mathrm{\&pi;}\left(x\right)}{2}\right)}{\frac{\mathrm{\&pi;}\left(x\right)}{2}}\right),$

$x=-\frac{2M}{2},...,\frac{2M}{2}.$ Wherein, M participates in counting of interpolation, and α is rolloff-factor.In the present embodiment, specifically get M=6, α=0.1.

It should be noted that, in the present embodiment, described over-sampling is realized by raised cosine FIR filter, in other embodiments, also can carry out over-sampling by low pass filter to the channel estimation results of signal.

Work as R ₁=2, R ₂when=8, step S101b is specially: determine the strongest path of signal and the interval of time strong path appearance with channel estimation results h ' (k) after described 2 times of interpolation.

L ' _max=max _0≤i≤2W-2| h ' (i)+h ' (i+1) | ²; L ' _maxit is the estimated position in the strongest path of the signal obtained in the channel estimation results after 2 times of interpolation, this estimated position is the position comparatively "ball-park" estimate value to the strongest path, the left end point in the interval that the strongest path of signal can be it can be used as to occur, the interval that the strongest described path occurs be then [L ' _max, L ' _max+ 1].It should be noted that, in other embodiments, also can pass through L ' _max=max _0≤i≤2W-2| h ' (i) | ²calculate this estimated position in the strongest path of signal.

With described R in step S101b ₁the interval that time strong path occurs of the channel estimation results determination signal after times interpolation comprises: at described R ₁in channel estimation results after times interpolation, data corresponding to the adjacent N number of position in the left end point position in the interval occurred in the strongest described path and left and right thereof empty; Wherein N sets based on channel circumstance; Based on the channel estimation results emptied after described data, determine the interval of time strong path appearance of signal.

Wherein, the object that the data corresponding to the adjacent N number of position in the left end point position in the interval that the strongest described path occurs and left and right thereof empty is made a concerted effort in order to avoid two or more very not strong signal is formed, thus to cause being mistaken as be signal on time strong path.Owing to generally depositing at certain time intervals between the strongest path and secondary strong path, by the data in the N number of path near the strongest path being emptied, time estimated position in strong path more adequately can be searched out.It should be noted that, the value of N sets based on the channel circumstance of reality, and the setting range of General N can be 1 ~ 3, but the value of N can not be excessive, otherwise the data in secondary strong path may be caused to be deleted by mistake.

In the present embodiment, get N=2.When specific implementation, can by sequence { h ' (i) } assignment to sequence { b (i) }, and by sequence { b (i) } at position L ' _maxand two zeros data that left and right is adjacent, that is:

b(L′ _max-2)＝0；b(L′ _max-1)＝0；b(L′ _max)＝0；b(L′ _max+1)＝0；b(L′ _max+2)＝0；

Then, in the interval that the secondary strong path resetting the middle searching of the sequence { b (i) } after described data signal occurs:

V′ _max＝max _0≤i≤2W-2|b(i)+b(i+1)| ²。

Similarly, V ' _maxbe through 2 times of interpolation and empty the strongest path and near path corresponding data after letter lead to the estimated position in time strong path of the signal obtained in estimated result, this estimated position is the position comparatively "ball-park" estimate value to secondary strong path, the left end point in the interval that time strong path occurs of signal can be it can be used as, the interval that described strong path occurs be then [V ' _max, V ' _max+ 1].

Work as R ₁=2, R ₂when=8, step S101c is specially: the interval that occurs in the strongest described path [L ' _max, L ' _max+ 1] in, 8 times of interpolation are carried out to channel estimation results h ' (k) after described 2 times of interpolation, and the interval occurred in secondary strong path [V ' _max, V ' _max+ 1] in, 8 times of interpolation are carried out to channel estimation results h ' (k) after described 2 times of interpolation.

Wherein, interval [L ' _max, L ' _max+ 1], after 8 times of interpolation being carried out to h ' (k) in, h " (k) is obtained.

If (L ' _max) mod (2)=0, then:

$h^{\&prime;\&prime;}\left(j\right)={\mathrm{\&Sigma;}}_{m=-\frac{M}{2}+1}^{\frac{M}{2}}h(\frac{{L^{\&prime;}}_{\max }}{2}+m)\&CenterDot;f_{16}(16m-j),$ j＝1，2，3，...，7；

If (L ' _max) mod (2)=1, then:

$h^{\&prime;\&prime;}\left(j\right)={\mathrm{\&Sigma;}}_{m=-\frac{M}{2}+1}^{\frac{M}{2}}h(\frac{{L^{\&prime;}}_{\max }-1}{2}+m)\&CenterDot;f_{16}(16m-8-j),$ j＝1，2，3，...，7；

$f_{16}\left(x\right)=\left(\frac{\cos \left(\frac{\mathrm{\&pi;\&alpha;}\left(x\right)}{16}\right)}{1-\frac{{\mathrm{\&alpha;}}^2{\left(x\right)}^2}{64}}\right)\&CenterDot;\left(\frac{\sin \left(\frac{\mathrm{\&pi;}\left(x\right)}{16}\right)}{\frac{\mathrm{\&pi;}\left(x\right)}{16}}\right),$ $x=-\frac{16M}{2},...,\frac{16M}{2}.$

Similarly, interval [V ' _max, V ' _max+ 1], after 8 times of interpolation being carried out to h ' (k) in, u " (k) is obtained.

If (V ' _max) mod (2)=0, then:

$u^{\&prime;\&prime;}\left(j\right)={\mathrm{\&Sigma;}}_{m=-\frac{M}{2}+1}^{\frac{M}{2}}h(\frac{{V^{\&prime;}}_{\max }}{2}+m)\&CenterDot;f_{16}(16m-j),$ j＝1，2，3，...，7；

If (V ' _max) mod (2)=1, then:

$u^{\&prime;\&prime;}\left(j\right)={\mathrm{\&Sigma;}}_{m=-\frac{M}{2}+1}^{\frac{M}{2}}h(\frac{{V^{\&prime;}}_{\max }-1}{2}+m)\&CenterDot;f_{16}(16m-8-j),$ j＝1，2，3，...，7；

$f_{16}\left(x\right)=\left(\frac{\cos \left(\frac{\mathrm{\&pi;\&alpha;}\left(x\right)}{16}\right)}{1-\frac{{\mathrm{\&alpha;}}^2{\left(x\right)}^2}{64}}\right)\&CenterDot;\left(\frac{\sin \left(\frac{\mathrm{\&pi;}\left(x\right)}{16}\right)}{\frac{\mathrm{\&pi;}\left(x\right)}{16}}\right),$ $x=-\frac{16M}{2},...,\frac{16M}{2}.$

It should be noted that, in step S101c, based on (L ' _max) result of mod (2) take different calculating formulas respectively to h " (j) calculates, based on (V ' _max) result of mod (2) takes different calculating formulas respectively to u " (j) calculates, and with h " (j) calculates the second estimated value L of the estimated position in the strongest path " in subsequent step S102 _max, with u " (j) calculates time the second estimated value V of the estimated position in strong path " _max, so can reduce amount of calculation, raise the efficiency.In other embodiments, also L can not be calculated by this kind of mode " _maxwith V " _max, but can calculate as follows:

Step S1, carries out down-sampling to channel estimation results h (k):

H ₁₆" (16k)=h (k), k=0,1,2 ..., W-1, wherein W is length of window;

h ₁₆″(16k+j)＝0，j＝1，2，3，...，15，k＝0，1，2，...，W-1。

Step S2, carries out 16 times of filtering to the result after down-sampling:

H " _conv(k)=conv (h ₁₆", f ₁₆), k=0,1,2 ..., 16W+16M; Wherein, h ₁₆" represent h ₁₆" sequence of (k), f ₁₆represent f ₁₆x the sequence of (), conv is convolution algorithm function, and M participates in counting of interpolation.

It should be noted that, in the embodiment of the present invention, based on (L ' _max) mod (2) result calculate h " (j) and based on (V ' _max) mod (2) result calculate u " process of (j) is namely to h " _conv(k)=conv (h ₁₆", f ₁₆) simplification.

Step S3, owing to can obtain the numerical value more than 16W through above-mentioned convolution algorithm, therefore, filtered value must start value after 8M number, obtains 16 times of filtered values:

h″(k)＝h″ _conv(k+8M)，k＝0，1，2，...，16W-1；

Step S4, from h " at L ' (k) _maxthe position L of maximum is found out " near × 8 positions _max, from h " at V ' (k) _maxthe position V of second largest value is found out " near × 8 positions _max.Or also directly " the position L of maximum (k), can be found out " from h _maxand the position V of second largest value " _max.

After R times of over-sampling is carried out to the channel estimation results of signal, perform step S102, based on the channel estimation results after R times of over-sampling, obtain estimated position and the power in the estimated position in the strongest path of signal and time strong path of power and signal.

In the present embodiment, step S102 can comprise:

Step S102a, from described to R ₁first estimated value L ' of the estimated position in the strongest path described in obtaining in channel estimation results after times interpolation _maxwith the first estimated value V ' of the estimated position in described strong path _max;

Step S102b, from described to R ₁channel estimation results after times interpolation carries out R ₂second estimated value L of the estimated position in the strongest path described in obtaining in result after times interpolation " _maxwith the second estimated value V of the estimated position in power and described time strong path " _maxand power;

Step S102c, with R ₂* L ' _maxwith L " _maxsum as the estimated position in the strongest described path, with R ₂* V ' _maxwith V " _maxsum is as the estimated position in described strong path.

Wherein, the first estimated value L ' of the estimated position in the strongest path in step S102a _max, secondary strong path the first estimated value V ' of estimated position _max, can occur in the strongest path, secondary strong path described in performing step S101b and estimating interval time can obtain.

Work as R ₁=2, R ₂when=8, the concrete implementation of step S102b is as follows:

From described, result h after 8 times of interpolation " the second estimated value L of the estimated position in the strongest path described in obtaining (k) " is carried out to channel estimation results h ' (k) after 2 times of interpolation _maxand power.

Note P " (j)=| h " (j) | ², j=1,2,3 ..., 7; P " (0)=| h ' (L ' _max) | ², P " and (8)=| h ' (L ' _max+ 1) | ², then interval [L ' _max, L ' _max+ 1] the channel estimation results h after 8 times of interpolation being carried out to h ' (k) in " estimated position in the strongest path obtained in (k) is:

${L^{\&prime;\&prime;}}_{\max }=\underset{j\&Element;\left\{\mathrm{0,1,2,3,4,5,6,7,8}\right\}}{\arg \max }\left\{P^{\&prime;\&prime;}\left(j\right)\right\},$ Wherein, argmax represents the value of the parameter asking one group of sequence, reaches maximum, then L when using the value in this parameters time-sequence row " _max" the value of j corresponding when (j) reaches maximum that is make function P.Due to L " _maxthat the channel estimation results h after 8 times of interpolation is carried out to h ' (k) " estimated position in the strongest path obtained in (k), this estimated position is to the comparatively accurate estimated value in the position in the strongest path of signal, by L in the present embodiment " _maxbe called the second estimated value of the estimated position in the strongest path.

The power in the strongest path is P " _max=P " (L " _max), P " _maxnamely be power corresponding to the estimated position in the strongest described path.

Similarly, the result u after 8 times of interpolation is carried out to channel estimation results h ' (k) after 2 times of interpolation " (k), obtain the second estimated value V of the estimated position in described time strong path " from described _maxand power.

Note Q " (j)=| u " (j) | ², j=1,2,3 ..., 7; Q " (0)=| u ' (V ' _max) | ², Q " and (8)=| u ' (V ' _max+ 1) | ², then interval [V ' _max, V ' _max+ 1] in, the channel estimation results u after 8 times of interpolation is carried out to h ' (k) " estimated position in time strong path obtained in (k) is:

${V^{\&prime;\&prime;}}_{\max }=\underset{j\&Element;\left\{\mathrm{0,1,2,3,4,5,6,7,8}\right\}}{\arg \max }\left\{Q^{\&prime;\&prime;}\left(j\right)\right\},$ V " _max" the value of j corresponding when (j) reaches maximum that is make function Q.Due to V " _maxthat the channel estimation results u after 8 times of interpolation is carried out to h ' (k) " estimated position in time strong path obtained in (k), this estimated position is the comparatively accurate estimated value in position in time strong path to signal, by V in the present embodiment " _maxbe called time the second estimated value of the estimated position in strong path.

The power in secondary strong path is Q " _max=Q " (V " _max), Q " _maxnamely be power corresponding to the estimated position in described time strong path.

In the present embodiment, due to the first estimated value L ' of the estimated position in the strongest path of signal _maxobtain in the result after channel estimation results 2 times of interpolation, and the second estimated value L of the estimated position in the strongest path " _maxthen obtain in the result after channel estimation results 16 times of interpolation, L ' _maxcomparatively rough to the positional representation in the strongest path, L " _maxmore accurate to the positional representation in the strongest path.In like manner, due to the first estimated value V ' of the estimated position in time strong path of signal _maxobtain in the result after channel estimation results 2 times of interpolation, and the second estimated value V of the estimated position in secondary strong path " _maxthen obtain in the result after channel estimation results 16 times of interpolation, V ' _maxcomparatively rough to the positional representation in secondary strong path, V " _maxmore accurate to the positional representation in secondary strong path.Under 1/16chip precision, the estimated position L in the strongest path described in calculating _peakand the estimated position V in secondary strong path _peak, namely specifically perform step S102c:

L _peak＝8L′ _max+L″ _max，L _peak∈{0，1，2，...，16W-1}；

V _peak＝8V′ _max+V″ _max，V _peak∈{0，1，2，...，16W-1}。

In TD-SCDMA communication system, for the channel estimation results of a subframe or multiple subframe, said process all can be adopted to obtain the estimated position in the strongest path of a signal and the estimated position in time strong path, and corresponding power.In subsequent step, can, based on the relation between the power in the strongest path and the power in secondary strong path, the target location of these two estimated positions above-mentioned and synchronous point be utilized to calculate position corresponding to synchronous point.The target location of described synchronous point is the desired location of communication system for synchronous point, and this position can be obtained through precalculating by the path of initial determined peak signal.

Behind the estimated position and power of the estimated position in the strongest path and time strong path of power and signal that get signal, perform step S103, according to the relation between the power in the strongest path and the power in secondary strong path, at least based on the simultaneous bias of the estimated position in the strongest described path and the target location certainty annuity of synchronous point.

In the present embodiment, step S103 comprises: judge whether the power in described strong path is greater than threshold value, be then with the estimated position in the strongest described path and and the estimated position in described time strong path between centre position and the simultaneous bias of target location computing system of synchronous point, otherwise using the difference of the target location of the estimated position in the strongest described path and described synchronous point as the simultaneous bias of system; Described threshold value for described in the power in the strongest path and the product of threshold parameter.

Due to described threshold value for described in the power in the strongest path and the product of threshold parameter, then judge the relation between the power in described strong path and threshold value, be the relation between power and the power in the strongest described path judging described strong path, if judge, the power in time strong path of signal is comparatively close to the power in the strongest path, such as exceed the half of the power in the strongest path, then show the result of synchronization offset estimation to be caused inaccurate because of channel estimation results exit window, so just the estimated position combining the strongest path is needed to carry out synchronization offset estimation with time estimated position in strong path in the present embodiment, can be specifically with the estimated position in the strongest described path and and the estimated position in described time strong path between centre position and the simultaneous bias of target location computing system of synchronous point, otherwise show the non-exit window of channel estimation results, synchronization offset estimation can be carried out by means of only the estimated position in the strongest path, can be specifically with the simultaneous bias of the difference computing system of the target location of the estimated position in the strongest described path and described synchronous point.

Wherein, described with the estimated position in the strongest described path and and the estimated position in described time strong path between centre position and the simultaneous bias of target location computing system of synchronous point comprise: determine integral multiple chip offset with the centre position between the estimated position in the strongest described path and the estimated position in described strong path; Little several times chip offset is calculated with the target location of the estimated position in the strongest described path and described synchronous point; Using described integral multiple chip offset and the little several times chip offset sum simultaneous bias as system.

During concrete enforcement, if the estimated position in the strongest current path and time strong path is respectively L _peak, V _peak, the target location of synchronous point is L _trgt, then the estimation for simultaneous bias can calculate in accordance with the following steps:

First the power Q in time strong path of the signal after R times of interpolation is judged " _maxwhether be greater than certain threshold T hrd, wherein Thrd=ε P " _max, P " _maxnamely the power in the strongest path of the signal of acquisition is calculated before being; ε is a threshold parameter, its span be [1/2,1).In the present embodiment, get ε=1/2, then the value of Thrd is P " _maxhalf.

If Q " _max≤ Thrd, then only need use the estimated position L in the strongest path _peakwith the target location L of synchronous point _trgtcalculate synchronism deviation Δ L, computational process is as follows:

ΔL＝L _peak-L _trgt；

If Q " _max> Thrd, then need the estimated position L simultaneously using the strongest path _peakand with the estimated position V in secondary strong path _peakbetween centre position T ₀, synchronous point target location L _trgtcalculate synchronism deviation Δ L, computational process is as follows:

1) the estimated position L in the strongest path is calculated _peakwith the estimated position V in secondary strong path _peakbetween centre position T ₀:

T ₀=round ((L _peak+ V _peak)/2), round is round function;

2) to centre position T ₀integer chip approximate (by T ₀value be transformed into integer chip level):

$T_{0,\mathrm{int}}=\mathrm{round}\left(\frac{T_0}{R}\right)*R;$

In specific embodiment, as R=16, that is: $T_{0,\mathrm{int}}=\mathrm{round}\left(\frac{T_0}{16}\right)*16;$

3) for integral multiple chip shifted by delta L _intcalculating:

ΔL _int＝T _0，int-L _trgt；

4) little several times chip shifted by delta L _fracaccording to the estimated position L in the strongest path of signal _peakcalculate:

Δ L _frac=mod (L _peak-L _trgt, R), wherein mod is MOD function;

In specific embodiment, as R=16, that is: Δ L _frac=mod (L _peak-L _trgt, 16);

5) total deviation calculates:

ΔL＝ΔL _int+ΔL _frac

Synchronism deviation is Δ L, if in units of 1/16chip, be then that unit adjusts according to 1/8chip when carrying out synchronous point adjustment, the synchronism deviation of system will be made like this to fluctuate between-1/16chip1/16chip, in general, there is the clock jitter of-1/16chip in system, very little on systematic function impact.

To sum up, in the present embodiment, synchronous point position is determined by two paths estimating signal the strongest, can effectively avoid making the inaccurate of synchronization offset estimation result because of the exit window problem of channel estimation results, thus well can adapt to the raw wireless channel environment such as channel and mobile channel that goes out, obtain good systematic function, and do not affect the performance under conventional channel.

The synchronization offset estimation method of corresponding above-mentioned communication system, the present embodiment also provides a kind of synchronization offset estimation device of communication system.Fig. 4 is the structural representation of the synchronization offset estimation device of the communication system that the embodiment of the present invention provides, as shown in Figure 4, the synchronization offset estimation device of described communication system comprises: over-sampling unit 10, is suitable for carrying out R times of over-sampling to the channel estimation results of signal; Acquiring unit 20, is connected with described over-sampling unit 10, is suitable for the channel estimation results after based on R times of over-sampling, obtains estimated position and the power in the estimated position in the strongest path of signal and time strong path of power and signal; Simultaneous bias determining unit 30, is connected with described acquiring unit 20, is suitable for according to the relation between the power in the strongest path and the power in secondary strong path, at least based on the simultaneous bias of the estimated position in the strongest described path and the target location certainty annuity of synchronous point.In the present embodiment, described communication system is TD-SCDMA communication system.

During concrete enforcement, described over-sampling unit 10 comprises: the first interpolating unit 101, is suitable for carrying out R to the channel estimation results of signal ₁times interpolation; Interval determination unit 102, is connected with described first interpolating unit 101, is suitable for described R ₁the strongest path of the channel estimation results determination signal after times interpolation and the interval that time strong path occurs; Second interpolating unit 103, is connected with described first interpolating unit 101, interval determination unit 102, be suitable for respectively in the strongest described path and interval that time strong path occurs to described R ₁channel estimation results after times interpolation carries out R ₂times interpolation; Wherein, R ₁* R ₂=R.In the present embodiment, get R=16, R ₁=2, R ₂=8.During actual enforcement, described over-sampling unit 10 comprises raised cosine FIR filter or low pass filter.

Described acquiring unit 20 comprises: the first acquiring unit 201, is suitable for from described R ₁first estimated value L ' of the estimated position in the strongest path described in obtaining in channel estimation results after times interpolation _maxwith the first estimated value V ' of the estimated position in described strong path _max; Second acquisition unit 202, is suitable for from described R ₁channel estimation results after times interpolation carries out R ₂second estimated value L of the estimated position in the strongest path described in obtaining in result after times interpolation " _maxwith the second estimated value V of the estimated position in power and described time strong path " _maxand power; 3rd acquiring unit 203, is connected with described first acquiring unit 201, second acquisition unit 202, is suitable for R ₂* L ' _maxwith L " _maxsum as the estimated position in the strongest described path, with R ₂* V ' _maxwith V " _maxsum is as the estimated position in described strong path.

Described interval determination unit 102 can comprise: pretreatment unit (not shown), at described R ₁in channel estimation results after times interpolation, data corresponding to the adjacent N number of position in the left end point position in the interval occurred in the strongest described path and left and right thereof empty; Wherein N sets based on channel circumstance; First interval determination unit (not shown), is connected with described pretreatment unit, is suitable for the channel estimation results based on emptying after described data, determines the interval of time strong path appearance of signal.

Described simultaneous bias determining unit 30 comprises: judging unit 301, is suitable for judging whether the power in described strong path is greater than threshold value; Described threshold value for described in the power in the strongest path and the product of threshold parameter; First simultaneous bias determining unit 302, be connected with described judging unit 301, be suitable for when the power in described time strong path is greater than threshold value, with the estimated position in the strongest described path and and the estimated position in described strong path between centre position and the simultaneous bias of target location computing system of synchronous point; Second simultaneous bias determining unit 303, is connected with described judging unit 301, is suitable for when the power in described time strong path is less than or equal to threshold value, using the difference of the target location of the estimated position in the strongest described path and described synchronous point as the simultaneous bias of system.Actual when implementing, the span of described threshold parameter can be [1/2,1).

Described first simultaneous bias determining unit 302 comprises: integral multiple offset-determining unit (not shown), is suitable for the estimated position L in the strongest described path _peakwith the estimated position V in described strong path _peakbetween centre position T ₀determine integral multiple chip offset Δ L _int; Little several times offset-determining unit (not shown), is suitable for the estimated position L in the strongest described path _peakwith the target location L of described synchronous point _trgtcalculate little several times chip offset Δ L _frac; Total drift determining unit (not shown), is suitable for described integral multiple chip offset Δ L _intwith little several times chip offset Δ L _fracsum is as the simultaneous bias of system.When specific implementation process, described integral multiple chip offset Δ L _int=T _{0, int}-L _trgt, wherein: t ₀=round ((L _peak+ V _peak)/2), round is round function; Described little several times chip offset Δ L _frac=mod (L _peak-L _trgt, R), wherein mod is MOD function.

In addition, the present embodiment additionally provides a kind of mobile terminal comprising the synchronization offset estimation device of above-mentioned communication system.During concrete enforcement, described mobile terminal can also comprise the first adjustment unit, is connected with described synchronization offset estimation device, is suitable for the synchronization offset estimation device determined simultaneous bias result adjustment synchronous point based on described communication system.

The present embodiment additionally provides a kind of base station comprising the synchronization offset estimation device of above-mentioned communication system.During concrete enforcement, described base station can also comprise the second adjustment unit, is connected with described synchronization offset estimation device, is suitable for the synchronization offset estimation device determined simultaneous bias result adjustment synchronous point based on described communication system.

The concrete enforcement of the synchronization offset estimation device of described communication system, the mobile terminal comprising described synchronization offset estimation device and the base station that comprises described synchronization offset estimation device with reference to the enforcement of the synchronization offset estimation method of communication system described in the present embodiment, can not repeat them here.

To sum up, the synchronization offset estimation method of the communication system that embodiment of the present invention provides and device, mobile terminal and base station, at least have following beneficial effect:

Over-sampling is carried out to the channel estimation results of signal, the strongest path of signal and the estimated position in secondary strong path and power is obtained from the result after over-sampling, again according to the relation between the power in the strongest described path and the power in described strong path, at least based on the simultaneous bias of the estimated position in the strongest described path and the target location certainty annuity of synchronous point, so, determine that synchronous point position can estimate the simultaneous bias of system exactly by estimating two the strongest paths of signal, thus well can adapt to mobile channel and the raw wireless channel environments such as channel that go out, obtain good systematic function, and the performance do not affected under conventional channel.

The process of the channel estimation results of signal being carried out to R times of over-sampling is divided into two steps, first carries out R ₁times interpolation, with R ₁channel estimation results after times interpolation determines the strongest path of signal and interval that time strong path occurs respectively, then carries out R in the strongest path and interval that time strong path occurs respectively ₂times interpolation to estimate position and the power in the strongest path and time strong path, wherein, R ₁* R ₂=R, owing to not needing to carry out interpolation to all channel estimation results in activation detection window, therefore greatly reduces amount of calculation, improves the efficiency of synchronization offset estimation.

For the communication system adopting DCXO as clock, estimated accuracy is brought up to 1/16chip, make just effectively to estimate clock jitter when 1/16chip skew appears in system, thus adjust, and do not need can adjust when there is 1/8chip skew, further increase systematic function.

Although adopt TCXO can realize the estimated accuracy of 1/16chip as the crystal oscillator of communication system, it has higher cost, and can replace TCXO with DCXO in the technical program, can obtain identical performance, effectively provide cost savings.

Although the present invention with preferred embodiment openly as above; but it is not for limiting the present invention; any those skilled in the art without departing from the spirit and scope of the present invention; the Method and Technology content of above-mentioned announcement can be utilized to make possible variation and amendment to technical solution of the present invention; therefore; every content not departing from technical solution of the present invention; the any simple modification done above embodiment according to technical spirit of the present invention, equivalent variations and modification, all belong to the protection range of technical solution of the present invention.

Claims (20)

1. a synchronization offset estimation method for communication system, is characterized in that, comprising:

R times of over-sampling is carried out to the channel estimation results of signal;

Based on the channel estimation results after R times of over-sampling, obtain estimated position and the power in the estimated position in the strongest path of signal and time strong path of power and signal;

According to the relation between the power in the strongest path and the power in secondary strong path, at least based on the simultaneous bias of the estimated position in the strongest described path and the target location certainty annuity of synchronous point, comprise: judge whether the power in described strong path is greater than threshold value, be then with the estimated position in the strongest described path and and the estimated position in described time strong path between centre position and the simultaneous bias of target location computing system of synchronous point, wherein, with the estimated position L in the strongest described path _peakwith the estimated position V in described strong path _peakbetween centre position T ₀determine integral multiple chip offset Δ L _int, with the estimated position L in the strongest described path _peakwith the target location L of described synchronous point _trgtcalculate little several times chip offset Δ L _frac, by described integral multiple chip offset Δ L _intwith little several times chip offset Δ L _fracsum is as the simultaneous bias of system; Otherwise using the difference of the target location of the estimated position in the strongest described path and described synchronous point as the simultaneous bias of system; Described threshold value for described in the power in the strongest path and the product of threshold parameter, the span of described threshold parameter be [1/2,1).

2. the synchronization offset estimation method of communication system according to claim 1, is characterized in that, the described channel estimation results to signal carries out a R times over-sampling and comprises:

R is carried out to the channel estimation results of signal ₁times interpolation;

With described R ₁the strongest path of the channel estimation results determination signal after times interpolation and the interval that time strong path occurs;

Respectively in the strongest described path and interval that time strong path occurs to described R ₁channel estimation results after times interpolation carries out R ₂times interpolation; Wherein, R ₁* R ₂=R.

3. the synchronization offset estimation method of communication system according to claim 2, it is characterized in that, described based on the channel estimation results after R times of over-sampling, the estimated position and the power that obtain the estimated position in the strongest path of signal and time strong path of power and signal comprise:

From described to R ₁first estimated value L' of the estimated position in the strongest path described in obtaining in channel estimation results after times interpolation _maxwith the first estimated value V' of the estimated position in described strong path _max;

From described to R ₁channel estimation results after times interpolation carries out R ₂second estimated value L of the estimated position in the strongest path described in obtaining in result after times interpolation " _maxwith the second estimated value V of the estimated position in power and described time strong path " _maxand power;

With R ₂* L' _maxwith L " _maxsum as the estimated position in the strongest described path, with R ₂* V' _maxwith V " _maxsum is as the estimated position in described strong path.

4. the synchronization offset estimation method of communication system according to claim 2, is characterized in that, described with described R ₁the interval that time strong path occurs of the channel estimation results determination signal after times interpolation comprises:

At described R ₁in channel estimation results after times interpolation, data corresponding to the adjacent N number of position in the left end point position in the interval occurred in the strongest described path and left and right thereof empty; Wherein N sets based on channel circumstance;

Based on the channel estimation results emptied after described data, determine the interval of time strong path appearance of signal.

5. the synchronization offset estimation method of communication system according to claim 2, is characterized in that, R=16, R ₁=2, R ₂=8.

6. the synchronization offset estimation method of communication system according to claim 1, is characterized in that,

Described integral multiple chip offset Δ L _int=T _{0, int}-L _trgt, wherein: t ₀=round ((L _peak+ V _peak)/2), round is round function;

Described little several times chip offset Δ L _frac=mod (L _peak-L _trgt, R), wherein mod is MOD function.

7. the synchronization offset estimation method of communication system according to claim 1, is characterized in that, described over-sampling is realized by raised cosine FIR filter or low pass filter.

8. the synchronization offset estimation method of communication system according to claim 1, is characterized in that, described communication system is TD-SCDMA communication system.

9. a synchronization offset estimation device for communication system, is characterized in that, comprising:

Over-sampling unit, is suitable for carrying out R times of over-sampling to the channel estimation results of signal;

Acquiring unit, is suitable for the channel estimation results after based on R times of over-sampling, obtains estimated position and the power in the estimated position in the strongest path of signal and time strong path of power and signal;

Simultaneous bias determining unit, is suitable for according to the relation between the power in the strongest path and the power in secondary strong path, at least based on the simultaneous bias of the estimated position in the strongest described path and the target location certainty annuity of synchronous point;

Described simultaneous bias determining unit comprises:

Judging unit, is suitable for judging whether the power in described strong path is greater than threshold value; Described threshold value for described in the power in the strongest path and the product of threshold parameter, the span of described threshold parameter be [1/2,1);

First simultaneous bias determining unit, be suitable for when the power in described time strong path is greater than threshold value, with the estimated position in the strongest described path and and the estimated position in described strong path between centre position and the simultaneous bias of target location computing system of synchronous point;

Second simultaneous bias determining unit, is suitable for when the power in described time strong path is less than or equal to threshold value, using the difference of the target location of the estimated position in the strongest described path and described synchronous point as the simultaneous bias of system;

Described first simultaneous bias determining unit comprises:

Integral multiple offset-determining unit, is suitable for the estimated position L in the strongest described path _peakwith the estimated position V in described strong path _peakbetween centre position T ₀determine integral multiple chip offset Δ L _int;

Little several times offset-determining unit, is suitable for the estimated position L in the strongest described path _peakwith the target location L of described synchronous point _trgtcalculate little several times chip offset Δ L _frac;

Total drift determining unit, is suitable for described integral multiple chip offset Δ L _intwith little several times chip offset Δ L _fracsum is as the simultaneous bias of system.

10. the synchronization offset estimation device of communication system according to claim 9, is characterized in that, described over-sampling unit comprises:

First interpolating unit, is suitable for carrying out R to the channel estimation results of signal ₁times interpolation;

Interval determination unit, is suitable for described R ₁the strongest path of the channel estimation results determination signal after times interpolation and the interval that time strong path occurs;

Second interpolating unit, be suitable for respectively in the strongest described path and interval that time strong path occurs to described R ₁channel estimation results after times interpolation carries out R ₂times interpolation; Wherein, R ₁* R ₂=R.

The synchronization offset estimation device of 11. communication systems according to claim 10, is characterized in that, described acquiring unit comprises:

First acquiring unit, is suitable for from described R ₁first estimated value L' of the estimated position in the strongest path described in obtaining in channel estimation results after times interpolation _maxwith the first estimated value V' of the estimated position in described strong path _max;

Second acquisition unit, is suitable for from described R ₁channel estimation results after times interpolation carries out R ₂second estimated value L of the estimated position in the strongest path described in obtaining in result after times interpolation " _maxwith the second estimated value V of the estimated position in power and described time strong path " _maxand power;

3rd acquiring unit, is suitable for R ₂* L' _maxwith L " _maxsum as the estimated position in the strongest described path, with R ₂* V' _maxwith V " _maxsum is as the estimated position in described strong path.

The synchronization offset estimation device of 12. communication systems according to claim 10, is characterized in that, described interval determination unit comprises:

Pretreatment unit, is suitable at described R ₁in channel estimation results after times interpolation, data corresponding to the adjacent N number of position in the left end point position in the interval occurred in the strongest described path and left and right thereof empty; Wherein N sets based on channel circumstance;

First interval determination unit, is suitable for the channel estimation results based on emptying after described data, determines the interval of time strong path appearance of signal.

The synchronization offset estimation device of 13. communication systems according to claim 10, is characterized in that, R=16, R ₁=2, R ₂=8.

The synchronization offset estimation device of 14. communication systems according to claim 13, is characterized in that,

Described integral multiple chip offset Δ L _int=T _{0, int}-L _trgt, wherein: t ₀=round ((L _peak+ V _peak)/2), round is round function;

Described little several times chip offset Δ L _frac=mod (L _peak-L _trgt, R), wherein mod is MOD function.

The synchronization offset estimation device of 15. communication systems according to claim 9, is characterized in that, described over-sampling unit comprises raised cosine FIR filter or low pass filter.

The synchronization offset estimation device of 16. communication systems according to claim 9, is characterized in that, described communication system is TD-SCDMA communication system.

17. 1 kinds of mobile terminals, is characterized in that, comprise the synchronization offset estimation device of the communication system described in any one of claim 9 to 16.

18. mobile terminals according to claim 17, is characterized in that, also comprise the first adjustment unit, are suitable for the synchronization offset estimation device determined simultaneous bias result adjustment synchronous point based on described communication system.

19. 1 kinds of base stations, is characterized in that, comprise the synchronization offset estimation device of the communication system described in any one of claim 9 to 16.

20. base stations according to claim 19, is characterized in that, also comprise the second adjustment unit, are suitable for the synchronization offset estimation device determined simultaneous bias result adjustment synchronous point based on described communication system.