CN102946200A - Wide-load-range low-voltage flyback power factor correction converter control method and device for realizing method - Google Patents
Wide-load-range low-voltage flyback power factor correction converter control method and device for realizing method Download PDFInfo
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- CN102946200A CN102946200A CN2012104471762A CN201210447176A CN102946200A CN 102946200 A CN102946200 A CN 102946200A CN 2012104471762 A CN2012104471762 A CN 2012104471762A CN 201210447176 A CN201210447176 A CN 201210447176A CN 102946200 A CN102946200 A CN 102946200A
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- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention discloses a wide-load-range low-voltage flyback power factor correction converter control method and a device for realizing the method. A switching tube Q2 is serially connected between the switching tube Q1 of the traditional flyback power factor correction converter and the primary winding end 2 of a flyback transformer T. The anode of a power diode D6 is connected between the switching tube Q1 and the switching tube Q2. The cathode of the power diode D6 is connected with the primary winding end 1 of the flyback transformer T. By adopting the design, the loading capacity of the traditional flyback power factor correction converter is widened. On the premise of the same main circuit parameters, the loading range of the traditional flyback power factor correction converter can be improved and the voltage stress born by the switching tube which is connected with the primary winding of the transformer is reduced. The wide-load-range low-voltage flyback power factor correction converter has the advantages that the efficiency is high and unit power factors can be obtained within the entire input voltage range.
Description
Technical field
The present invention relates to electric control appliance, especially a kind of anti-excited power factor correction converter control method and device thereof of low voltage stress.
Background technology
In recent years, power electronic technology develops rapidly, becomes gradually the focus of application and research as the power technology of field of power electronics important component part.Switching Power Supply has been established its dominant position in field of power supplies so that its efficient is high, power density is high, but can there be a fatal weakness in it during by rectifier access electrical network: power factor lower (generally only being 0.45～0.75), and in electrical network, can produce a large amount of current harmonicss and reactive power and pollute electrical network.The method that suppresses Switching Power Supply generation harmonic wave mainly contains two kinds: the one, and passive means namely adopts passive filtering or active filter circuit to come bypass or harmonic carcellation; The 2nd, active method namely designs high-performance rectifier of new generation, and it has input current for sine wave, harmonic content is low and the power factor high, namely has power factor emendation function.Switch power supply power factor is proofreaied and correct the emphasis of research, mainly is the research of circuit of power factor correction topology and the exploitation of Power Factor Correction Control integrated circuit.Traditional APFC generally adopts the Boost-Boost topology, this be because Boost have control easily, drive simple and power factor can be close to 1, but the Boost power factor correction has the high shortcoming of output voltage.In low power application scenario, Buck-buck topology and anti exciting converter often use, but when the Buck circuit is realized PFC, because when input voltage is lower than output voltage, transferring energy not, input current is 0, intermodulation distortion is serious.And anti exciting converter can transferring energy in whole power frequency period, and power factor and total harmonic distortion all are better than the Buck converter.Anti-excited power factor corrector has discontinuous mode and two kinds of mode of operations of critical continuous conduction mode usually.The anti-excited power factor corrector of discontinuous mode can obtain unity power factor, but its peak current is very large, makes the conduction loss increase of switching tube and affects transducer effciency; The anti-excited power factor corrector of critical continuous conduction mode, its ON time is fixed in a power frequency period, although efficient is higher than the anti-excited power factor corrector of discontinuous mode, but can not obtain unity power factor, power factor and total harmonic distortion are all poor than the anti-excited power factor corrector of discontinuous mode.
Summary of the invention
The anti-excited power factor correction converter of the low voltage stress with wide loading range and the control method thereof that the purpose of this invention is to provide a kind of novelty, adopt the method can make anti-excited power factor corrector obtain unity power factor, reduce the voltage stress that switching tube bears, and improved the load capacity of converter.
The present invention realizes its goal of the invention, and the technical scheme that adopts is a kind of anti-excited power factor correction converter of low voltage stress control method with wide loading range, and its concrete practice is:
Switching tube Q at classical inverse excited power factor correction converter
1With the switching tube Q that connects between former limit winding 2 ends of flyback transformer T
2, switching tube Q
1With switching tube Q
2Between connect power diode D
6Anode, power diode D
6Negative electrode connect 1 end of the former limit of flyback transformer T winding.
After classical inverse excited power factor correction converter is as above arranged, by R
1And R
2The output voltage sampling that forms is to converter output voltage v
o(t) negative terminal of input operational amplifier after the sampling, the anode input reference voltage signal V of operational amplifier
Ref, through operational amplifier output compensating control signal V after the compensating network
CompSawtooth waveforms and the compensating control signal V of saw-toothed wave generator output
CompAnode and the negative terminal of difference input comparator 1.Be input to half-bridge drive circuit behind the output signal process RS-trigger 1 of comparator 1, after drive circuit amplifies, export to switching tube Q
1When the sawtooth voltage of saw-toothed wave generator output greater than compensating control signal V
CompThe time switching tube Q
1Turn-off, when the sawtooth voltage of saw-toothed wave generator output less than compensating control signal V
CompThe time switching tube Q
1Conducting; And the setting compensation network makes the cut-off frequency of whole voltage control loop much smaller than power frequency, then the compensating control signal V of operational amplifier output
CompIn half power frequency period, remain unchanged.Input voltage v
In(t) with load current i
o(t) signal difference input sine wave circuit for generating, the sine wave signal of generation is input to the negative terminal of comparator 2, and the anode input signal of comparator 2 is flyback transformer secondary output current signal i
L2(t).RS-trigger 2 is passed through or inputted behind the door to the output signal of the output signal of comparator 2 and comparator 1, and its output is exported to switching tube Q after amplifying through half-bridge drive circuit again
2
Compared with prior art, the invention has the beneficial effects as follows:
1, with respect to traditional anti-excited power factor corrector, adopt the anti-excited power factor correction converter of low voltage stress and the control thereof of wide loading range of the present invention, can obtain unity power factor and less total harmonic distortion; 2, with respect to traditional anti-excited power factor correction converter, adopt the anti-excited power factor correction converter of low voltage stress and the control thereof of wide loading range of the present invention, under same main circuit parameter condition, go for more powerful power factor correcting converter, in the situation that obtains same high power factor, can obtain higher efficient.3, with respect to traditional anti-excited power factor correction converter, adopt the anti-excited power factor correction converter of low voltage stress and the control thereof of wide loading range of the present invention, can reduce the voltage stress that switching tube bears, reduced the selection difficulty of switching tube, reduced simultaneously the converter cost and improved efficient.
Another object of the present invention provides a kind of device of realizing above power factor correcting method.Its concrete structure adopts:
Switching tube Q at classical inverse excited power factor correction converter
1With the switching tube Q that connects between former limit winding 2 ends of flyback transformer T
2, switching tube Q
1With switching tube Q
2Between connect power diode D
6Anode, power diode D
6Negative electrode connect 1 end of the former limit of flyback transformer T winding.By R
1And R
2The output voltage sampling that forms is to converter output voltage v
o(t) negative terminal of input operational amplifier after the sampling, the anode input reference voltage signal V of operational amplifier
Ref, through operational amplifier output compensating control signal V after the compensating network
CompSawtooth waveforms and the compensating control signal V of saw-toothed wave generator output
CompAnode and the negative terminal of difference input comparator 1.Be input to half-bridge drive circuit behind the output signal process RS-trigger 1 of comparator 1, after drive circuit amplifies, export to switching tube Q
1When the sawtooth voltage of saw-toothed wave generator output greater than compensating control signal V
CompThe time switching tube Q
1Turn-off, when the sawtooth voltage of saw-toothed wave generator output less than compensating control signal V
CompThe time switching tube Q
1Conducting; And the setting compensation network makes the cut-off frequency of whole voltage control loop much smaller than power frequency, then the compensating control signal V of operational amplifier output
CompIn half power frequency period, remain unchanged.Input voltage v
In(t) with load current i
o(t) the anti-other input sine wave circuit for generating of signal, the sine wave signal of generation is input to the negative terminal of comparator 2, and the anode input signal of comparator 2 is flyback transformer secondary output current signal i
L2(t).RS-trigger 2 is passed through or inputted behind the door to the output signal of the output signal of comparator 2 and comparator 1, and its output is exported to switching tube Q after amplifying through half-bridge drive circuit again
2As seen, adopt above device can realize easily and reliably the above method of the present invention.
Description of drawings
Fig. 1 is the anti-excited power factor correction converter of the low voltage stress of wide loading range system architecture diagram.
Fig. 2 is the main oscillogram of classical inverse excited power factor correction converter under the 100W bearing power.
Fig. 3 is the main oscillogram of classical inverse excited power factor correction converter under the 200W bearing power.
Fig. 4 is the main oscillogram of the embodiment of the invention one under the 100W bearing power.
Fig. 5 is the main oscillogram of the embodiment of the invention one under the 200W bearing power.
Fig. 6 is the electrical block diagram of the embodiment of the invention two.
Embodiment
Also by reference to the accompanying drawings the present invention is done further detailed description below by concrete example.
Embodiment one
Fig. 1 is the structured flowchart of the embodiment of the invention one.
A kind of embodiment of the present invention is, topological structure and the control method of the anti-excited power factor correction converter of a kind of low voltage stress of wide loading range, and its concrete practice is:
Switching tube Q at classical inverse excited power factor correction converter
1With the switching tube Q that connects between former limit winding 2 ends of flyback transformer T
2, switching tube Q
1With switching tube Q
2Between connect power diode D
6Anode, power diode D
6Negative electrode connect 1 end of the former limit of flyback transformer T winding.
By R
1And R
2The output voltage sampling that forms is to converter output voltage v
o(t) negative terminal of input operational amplifier after the sampling, the anode input reference voltage signal V of operational amplifier
Ref, through operational amplifier output compensating control signal V after the compensating network
CompSawtooth waveforms and the compensating control signal V of saw-toothed wave generator output
CompAnode and the negative terminal of difference input comparator 1.Be input to half-bridge drive circuit behind the output signal process RS-trigger 1 of comparator 1, after drive circuit amplifies, export to switching tube Q
1When the sawtooth voltage of saw-toothed wave generator output greater than compensating control signal V
CompThe time switching tube Q
1Turn-off, when the sawtooth voltage of saw-toothed wave generator output less than compensating control signal V
CompThe time switching tube Q
1Conducting; And the setting compensation network makes the cut-off frequency of whole voltage control loop much smaller than power frequency, then the compensating control signal V of operational amplifier output
CompIn half power frequency period, remain unchanged.Input voltage v
In(t) with load current i
o(t) the anti-other input sine wave circuit for generating of signal, the sine wave signal of generation is input to the negative terminal of comparator 2, and the anode input signal of comparator 2 is flyback transformer secondary output current signal i
L2(t).RS-trigger 2 is passed through or inputted behind the door to the output signal of the output signal of comparator 2 and comparator 1, and its output is exported to switching tube Q after amplifying through half-bridge drive circuit again
2
Utilize the SIMetrix/SIMPLIS simulation software respectively classical inverse excited power factor correction converter and the embodiment of the invention one to be advanced the school time-domain-simulation, the simulation result waveform is as follows:
Fig. 2 is the time-domain-simulation waveform of classical inverse excited power factor correction converter under the 100W bearing power, is followed successively by from top to bottom switching tube Q
1The voltage stress waveform, output voltage waveforms, the input voltage waveform that bear close input current waveform.As can be seen from Figure 2, input current has well been followed the tracks of the waveform of input voltage, and this power supply has very high power factor.This moment anti-excited power factor correction converter output voltage stabilization at 48V, switching tube Q during stable state
1The maximum voltage stress that bears is 300V.
Fig. 3 is the time-domain-simulation waveform of classical inverse excited power factor correction converter under the 200W bearing power, is followed successively by from top to bottom switching tube Q
1The voltage stress waveform, output voltage waveforms, the input voltage waveform that bear close input current waveform.As can be seen from Figure 3, when bearing power increased, input current is distorted near peak point, can't follow the tracks of the waveform of input voltage, had reduced the power factor of power supply.This moment anti-excited power factor correction converter output voltage stabilization at 48V, switching tube Q during stable state
1The maximum voltage stress that bears is 450V.
Fig. 4 is the time-domain-simulation waveform of the embodiment of the invention one under the 100W bearing power, is followed successively by from top to bottom switching tube Q
2The voltage stress waveform that bears, switching tube Q
1The voltage stress waveform, output voltage waveforms, the input voltage waveform that bear close input current waveform.As can be seen from Figure 4, input current has well been followed the tracks of the waveform of input voltage, and this power supply has very high power factor.This moment anti-excited power factor correction converter output voltage stabilization at 48V, switching tube Q during stable state
1The maximum voltage stress that bears is 180V, switching tube Q during stable state
1The maximum voltage stress that bears is 140V.
Fig. 5 is the time-domain-simulation waveform of the embodiment of the invention one under the 200W bearing power, is followed successively by from top to bottom switching tube Q
2The voltage stress waveform that bears, switching tube Q
1The voltage stress waveform, output voltage waveforms, the input voltage waveform that bear close input current waveform.As can be seen from Figure 5, the input current of the embodiment of the invention one had still well been followed the tracks of the waveform of input voltage when load increased, and this power supply has very high power factor.This moment anti-excited power factor correction converter output voltage stabilization at 48V, switching tube Q during stable state
1The maximum voltage stress that bears is 200V, switching tube Q during stable state
1The maximum voltage stress that bears is 140V.
Can be found out that by Fig. 2～Fig. 5 classical inverse excited power factor correction converter can't work under the 200W bearing power; But under same main circuit parameter condition, the embodiment of the invention one can realize that all input current well followed the tracks of the waveform of input voltage under 100W and 200W bearing power, have very high power factor, and switching tube Q
1With Q
2The voltage stress that bears is all less than switching tube Q in the classical inverse excited power factor correction converter
1The voltage stress that bears.
Embodiment two
Fig. 6 illustrates, and this example is compared with embodiment one, and difference is: the power factor correcting converter of Switching Power Supply is forward converter.Control mode and the course of work and embodiment one are similar.Can pass through simulation results show equally, it can realize purpose of the present invention.
The Switching Power Supply that the anti-excited power factor correction converter of the inventive method in can be used for above embodiment forms, also can be used for the power factor Switching Power Supply of the isolated form power factor correction converter circuit compositions such as normal shock power factor correcting converter.
Claims (3)
1. the anti-excited power factor correction converter of the low voltage stress of wide loading range control method is characterized in that: at the switching tube Q of classical inverse excited power factor correction converter
1With the switching tube Q that connects between former limit winding 2 ends of flyback transformer T
2, switching tube Q
1With switching tube Q
2Between connect power diode D
6Anode, power diode D
6Negative electrode connect 1 end of the former limit of flyback transformer T winding; After classical inverse excited power factor correction converter is as above arranged, by R
1And R
2The output voltage sampling that forms is to converter output voltage v
o(t) negative terminal of input operational amplifier after the sampling, the anode input reference voltage signal V of operational amplifier
Ref, through operational amplifier output compensating control signal V after the compensating network
Comp, sawtooth waveforms and the compensating control signal V of saw-toothed wave generator output
CompAnode and the negative terminal of difference input comparator 1; Be input to half-bridge drive circuit behind the output signal process RS-trigger 1 of comparator 1, after drive circuit amplifies, export to switching tube Q
1When the sawtooth voltage of saw-toothed wave generator output greater than compensating control signal V
CompThe time switching tube Q
1Turn-off, when the sawtooth voltage of saw-toothed wave generator output less than compensating control signal V
CompThe time switching tube Q1 conducting; And the setting compensation network makes the cut-off frequency of whole voltage control loop much smaller than power frequency, then the compensating control signal V of operational amplifier output
CompIn half power frequency period, remain unchanged; Input voltage v
In(t) with load current i
o(t) signal difference input sine wave circuit for generating, the sine wave signal of generation is input to the negative terminal of comparator 2, and the anode input signal of comparator 2 is flyback transformer secondary output current signal i
L2(t); RS-trigger 2 is passed through or inputted behind the door to the output signal of the output signal of comparator 2 and comparator 1, and its output is exported to switching tube Q after amplifying through half-bridge drive circuit again
2
2. the anti-excited power factor correction converter of low voltage stress device of realizing the wide loading range of claim or 1 described method, formed by improved anti-excited power factor correction converter and controller, it is characterized in that, at the switching tube Q of classical inverse excited power factor correction converter
1With the switching tube Q that connects between former limit winding 2 ends of flyback transformer T
2, switching tube Q
1With switching tube Q
2Between connect power diode D
6Anode, power diode D
6Negative electrode connect 1 end of the former limit of flyback transformer T winding.
3. the anti-excited power factor correction converter of the low voltage stress of wide loading range as claimed in claim 2 control device is characterized in that, described anti exciting converter topology is also replaceable to be isolated form power factor correcting converter topology: such as the forward converter topology.
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| Application Number | Priority Date | Filing Date | Title |
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| CN2012104471762A CN102946200A (en) | 2012-11-09 | 2012-11-09 | Wide-load-range low-voltage flyback power factor correction converter control method and device for realizing method |
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| CN2012104471762A CN102946200A (en) | 2012-11-09 | 2012-11-09 | Wide-load-range low-voltage flyback power factor correction converter control method and device for realizing method |
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103997206A (en) * | 2014-05-20 | 2014-08-20 | 华为技术有限公司 | Switching power source |
| CN108880259A (en) * | 2017-05-15 | 2018-11-23 | 意法半导体股份有限公司 | Secondary side current scheme control for converter |
| CN112838757A (en) * | 2020-12-30 | 2021-05-25 | 西华大学 | Power factor correction converter of time-division multiplexing transformer |
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| US5991172A (en) * | 1996-06-21 | 1999-11-23 | Delta Electronics, Inc. | AC/DC flyback converter with improved power factor and reduced switching loss |
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| US5991172A (en) * | 1996-06-21 | 1999-11-23 | Delta Electronics, Inc. | AC/DC flyback converter with improved power factor and reduced switching loss |
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| 张斐等: "A Novel Tri-State Boost PFC Converter with Fast Dynamic Performance", 《2010 THE 5TH IEEE CONFERENCE ON DIGITAL OBJECT IDENTIFIER》, 31 December 2010 (2010-12-31), pages 2104 - 2109 * |
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Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103997206A (en) * | 2014-05-20 | 2014-08-20 | 华为技术有限公司 | Switching power source |
| US9641060B2 (en) | 2014-05-20 | 2017-05-02 | Huawei Technologies Co., Ltd. | Switching mode power supply |
| CN108880259A (en) * | 2017-05-15 | 2018-11-23 | 意法半导体股份有限公司 | Secondary side current scheme control for converter |
| US10715046B2 (en) | 2017-05-15 | 2020-07-14 | Stmicroelectronics S.R.L. | Secondary side current mode control for a converter |
| CN108880259B (en) * | 2017-05-15 | 2021-01-08 | 意法半导体股份有限公司 | Secondary side current mode control for converters |
| CN112838757A (en) * | 2020-12-30 | 2021-05-25 | 西华大学 | Power factor correction converter of time-division multiplexing transformer |
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Application publication date: 20130227 |