CN102685066A - Carrier recovery method of short-time burst high-spread-spectrum communication receiving system in large-frequency deviation condition - Google Patents

Carrier recovery method of short-time burst high-spread-spectrum communication receiving system in large-frequency deviation condition Download PDF

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CN102685066A
CN102685066A CN2012101597542A CN201210159754A CN102685066A CN 102685066 A CN102685066 A CN 102685066A CN 2012101597542 A CN2012101597542 A CN 2012101597542A CN 201210159754 A CN201210159754 A CN 201210159754A CN 102685066 A CN102685066 A CN 102685066A
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frequency
carrier
code
correlation peak
receiving system
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CN102685066B (en
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易志强
张福洪
戴绍港
李芸
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Haining Dingcheng Intelligent Equipment Co ltd
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Hangzhou Dianzi University
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Abstract

The invention relates to a carrier recovery method of short-time burst high-spread-spectrum communication receiving system in a large-frequency deviation condition. The conventional method cannot recover carriers in the large-frequency deviation condition depending on a short-time front lead code element sequence in a very low signal-to-noise ratio threshold condition. The carrier recovery method comprises the following steps of: at first, calculating a relative peak value of a spread spectrum code, and comparing and positioning the relative peak value by changing a local carrier frequency of the receiving system, so as to obtain a roughly-estimated value of carrier frequency deviation; secondly, synchronizing the spread spectrum code through a state machine and dispreading data; carrying out fast Fourier transform on the dispread data for a plurality of times, so as to further correct the local carrier frequency of the receiving system; and finally, constructing a phase locking loop by using I/Q (In-phase/Quadrature) data, so as to accurately synchronize the carrier frequency and track a phase. The method provided by the invention can accurately, rapidly and reliably complete carrier recovery, can be applicable to a large range of the carrier frequency deviation, and has a low working threshold.

Description

Burst the in short-term carrier recovering method of high spread spectrum communication receiving system of big frequency deviation condition
Technical field
The invention belongs to the spread spectrum technic field, be specifically related to a kind of carrier recovering method of high spread spectrum communication receiving system under big frequency deviation condition of bursting in short-term.
Background technology
Therefore advantages such as that spread spectrum technic has is anti-interference, work under the antinoise, anti-multipath decline, low power spectral density, good confidentiality are widely used in the military and civilian communications field, also comprise mobile communication business certainly.In mobile communication business, if emission system with (or) the receiving system carrier has higher mobility, then can cause bigger Doppler frequency shift, causes between emission system and receiving system carrier frequency offset excessive, thereby normally demodulation.Carrier recovering method commonly used has automatic frequency control loop (AFC), phase-locked loop (PLL) etc.Wherein the frequency deviation region of automatic frequency control loop correction is bigger; Suppose that systematic symbols speed is
Figure 2012101597542100002DEST_PATH_IMAGE002
baud, then the repairable maximum frequency deviation numerical value of AFC is near
Figure 2012101597542100002DEST_PATH_IMAGE004
Hz; Phase-locked loop then is used for correcting frequency deviation (handling residual frequency difference afterwards like AFC) among a small circle and follows the tracks of carrier phase difference.Yet under some high-speed mobile communications occasion, system's carrier is in high-speed motion state, and the Doppler frequency shift deviate of initiation can reach the several times of chip rate, only can't accomplish the recovery of carrier wave this moment with AFC and PLL method.
In addition,, require spread spectrum system should improve spreading factor as much as possible for further promoting antijamming capability and strengthening confidentiality, and the risk that adopts the communication mode of the system of bursting in short-term to be hunted down and to decode with reduction information.Therefore; The spreading factor of high spread spectrum system is generally more than or equal to 1023, and like global positioning system (GPS), the system works thresholding of this moment is extremely low; Signal is fallen into oblivion by noise fully; Can't directly implement carrier recovery algorithm, must carry out despreading to signal earlier and handle, obtain to implement after the spreading gain receiving signal.Recover generally to be no more than a hundreds of code element and be used to carry out carrier wave under the system of bursting in short-term in the Frame with the targeting sequencing length of regularly recovering.Under utmost point low threshold and big frequency deviation condition, conventional method can't be accomplished carrier wave at brief targeting sequencing and recover in the time period.
Summary of the invention
The object of the invention is exactly the deficiency that overcomes existing carrier recovering method; Propose a kind of novelty effectively to the high spread spectrum communication receiving system carrier recovering method of bursting in short-term under low threshold, the big frequency deviation condition, in hundreds of targeting sequencing code elements, accurately accomplish the correction of carrier wave frequency deviation and the tracking of carrier phase.The inventive method is applicable to quadrature amplitude modulation, and has the spread spectrum communication receiving system of targeting sequencing.
The carrier recovering method of the high spread spectrum communication receiving system of bursting in short-term under the big frequency deviation condition of the present invention; The Doppler frequency shift scope of setting carrier wave is
Figure 2012101597542100002DEST_PATH_IMAGE006
; Wherein
Figure 2012101597542100002DEST_PATH_IMAGE008
is the calibration value of carrier wave in this communication system;
Figure 2012101597542100002DEST_PATH_IMAGE010
is maximum doppler frequency; Its numerical value can be the several times of chip rate
Figure 2012101597542100002DEST_PATH_IMAGE012
, and concrete steps are:
Step (1) is provided with receiving system local carrier frequency , is used for the input intermediate-freuqncy signal is carried out frequency spectrum shift.
Step (2) will be passed through quadrature demodulation; Still exist the accurate baseband chip data sequence of two-way
Figure 2012101597542100002DEST_PATH_IMAGE016
of residual frequency difference and
Figure 2012101597542100002DEST_PATH_IMAGE018
to deliver to spreading code matched filter calculating correlation peak
Figure 2012101597542100002DEST_PATH_IMAGE020
successively after accomplishing frequency spectrum shift; " * " representes convolution algorithm;
Figure 2012101597542100002DEST_PATH_IMAGE022
is the matched filter tap coefficient, is the reverse sequence of spread spectrum code sequence.
In a code-element period, relatively and write down the maximum of relevant peaks in this cycle , record altogether KIndividual code-element period, thus obtain KIndividual maximal correlation peak value
Figure 2012101597542100002DEST_PATH_IMAGE026
To above-mentioned KSummation of maximal correlation peak value and record in the individual code-element period,
Figure 2012101597542100002DEST_PATH_IMAGE028
, parameter KSelection look the preamble symbol sequence length usually and decide, it is big more that numerical value is obtained, the sequence of symhols length that needs is long more, corresponding correlation peak summation is accurate more, helps frequency offset estimating more, through simulation analysis, parameter KGeneral desirable 3,4,5 or 6.
Step (3) increases local carrier frequency
Figure 2012101597542100002DEST_PATH_IMAGE030
, promptly set
Figure 2012101597542100002DEST_PATH_IMAGE032
, repeating step (2) is noted the maximal correlation peak value summation of each time S, up to local carrier frequency , promptly meet or exceed the frequency deviation region upper limit.Obtain this moment altogether JIndividual maximal correlation peak value summation is designated as
Figure 2012101597542100002DEST_PATH_IMAGE036
,
Figure 2012101597542100002DEST_PATH_IMAGE038
Step (4) relatively JIndividual maximal correlation peak value with
Figure 2012101597542100002DEST_PATH_IMAGE040
, find out maximum wherein
Figure 2012101597542100002DEST_PATH_IMAGE042
If
Figure 26582DEST_PATH_IMAGE042
is less than a certain setting threshold; Think that then this moment, receiving system was not received spread-spectrum signal, will return step (1) and carry out again; According to
Figure 2012101597542100002DEST_PATH_IMAGE044
corrected received system local carrier frequency
Figure 2012101597542100002DEST_PATH_IMAGE046
; Get into step (5), the frequency difference between local carrier and the reception signal carrier becomes
Figure 2012101597542100002DEST_PATH_IMAGE048
at this moment.
Step (5) continues the relatively correlation peak of spreading code matched filter output P, if
Figure 2012101597542100002DEST_PATH_IMAGE050
, then write down present clock
Figure 2012101597542100002DEST_PATH_IMAGE052
, and no longer right in a follow-up code-element period PCompare, set confidence level simultaneously C=1.Wherein
Figure 2012101597542100002DEST_PATH_IMAGE054
is proportionality coefficient; Through simulation analysis, its span is 0.6 ~ 0.8 o'clock best performance.
Step (6) is worked as clock
Figure 2012101597542100002DEST_PATH_IMAGE056
The time, compare correlation peak once more P, wherein
Figure 2012101597542100002DEST_PATH_IMAGE058
, be code-element period.If , confidence level then CAdd 1; Otherwise CSubtract 1.
Step (7) is with clock TIncrease
Figure 2012101597542100002DEST_PATH_IMAGE060
, repeating step (6), during if confidence level CGreater than a certain threshold value, think that then spreading code accomplishes synchronously, get into step (8) and carry out the data despreading; If confidence level C=0, then turn back to step (5) and carry out again.
Step (8) is with current time TAs the initial moment, the local spread spectrum code sequence of synchronized generation
Figure 2012101597542100002DEST_PATH_IMAGE062
, calculate respectively
Figure 2012101597542100002DEST_PATH_IMAGE064
,
Figure 2012101597542100002DEST_PATH_IMAGE066
Obtain I, Q two-way symbol data sequence.
Step (9) order
Figure 2012101597542100002DEST_PATH_IMAGE068
, structure MIndividual complex symbol
Figure 2012101597542100002DEST_PATH_IMAGE070
, this complex symbol sequence is carried out fast Fourier transform, obtain MIndividual frequency domain value.Right MTake absolute value back and obtain the subscript of maximum and correspondence position thereof of individual frequency domain value LAccording to subscript LCorrected received system local carrier frequency is to accomplish the synchronously thick of carrier frequency once more:
if , then
Figure 2012101597542100002DEST_PATH_IMAGE074
;
Otherwise, .
Step (10) is calculated phase demodulation value
Figure 2012101597542100002DEST_PATH_IMAGE078
,
Figure 2012101597542100002DEST_PATH_IMAGE080
Confirm normalization phase demodulation value
Figure 2012101597542100002DEST_PATH_IMAGE082
Calculate the filtered output of loop
Figure 2012101597542100002DEST_PATH_IMAGE084
,
Figure 2012101597542100002DEST_PATH_IMAGE086
Then carrier phase
Figure 2012101597542100002DEST_PATH_IMAGE088
is pressed the following formula renewal:
Figure 2012101597542100002DEST_PATH_IMAGE090
Thereby accomplish the accurate recovery and the Phase Tracking of carrier wave.Wherein, parameter G1, G2, G3All represent loop gain, should suitable numerical value be set according to specific requirements such as chip rate, residual frequency departure size, loop noise indexs.
The present invention accurately rapid and reliable accomplishes carrier wave recovery in the spread spectrum communication system, and the carrier wave frequency deviation scope that tackles is big, and the work thresholding is low, is suitable for the spread spectrum system of quadrature amplitude modulation.
Embodiment
Step (1) is provided with receiving system local carrier frequency
Figure 798064DEST_PATH_IMAGE014
, is used for the input intermediate-freuqncy signal is carried out frequency spectrum shift.
Step (2) will be passed through quadrature demodulation; Still exist the accurate baseband chip data sequence of two-way
Figure 911514DEST_PATH_IMAGE016
of residual frequency difference and
Figure 774427DEST_PATH_IMAGE018
to deliver to spreading code matched filter calculating correlation peak
Figure 998735DEST_PATH_IMAGE020
successively after accomplishing frequency spectrum shift; " * " representes convolution algorithm;
Figure 247183DEST_PATH_IMAGE022
is the matched filter tap coefficient, is the reverse sequence of spread spectrum code sequence.
In a code-element period, relatively and write down the maximum of relevant peaks in this cycle
Figure 531534DEST_PATH_IMAGE024
, record altogether KIndividual code-element period, thus obtain KIndividual maximal correlation peak value
Figure 881744DEST_PATH_IMAGE026
To above-mentioned KSummation of maximal correlation peak value and record in the individual code-element period,
Figure 909743DEST_PATH_IMAGE028
, parameter KSelection look the preamble symbol sequence length usually and decide, it is big more that numerical value is obtained, the sequence of symhols length that needs is long more, corresponding correlation peak summation is accurate more, helps frequency offset estimating more, through simulation analysis, parameter KGeneral desirable 3,4,5 or 6.
Step (3) increases local carrier frequency
Figure 292924DEST_PATH_IMAGE030
, promptly set
Figure 482597DEST_PATH_IMAGE032
, repeating step (2) is noted the maximal correlation peak value summation of each time S, up to local carrier frequency
Figure 382420DEST_PATH_IMAGE034
, promptly meet or exceed the frequency deviation region upper limit.Obtain this moment altogether JIndividual maximal correlation peak value summation is designated as
Figure 886214DEST_PATH_IMAGE036
,
Step (4) relatively JIndividual maximal correlation peak value with
Figure 735407DEST_PATH_IMAGE040
, find out maximum wherein
Figure 122526DEST_PATH_IMAGE042
If
Figure 430011DEST_PATH_IMAGE042
is less than a certain setting threshold; Think that then this moment, receiving system was not received spread-spectrum signal, will return step (1) and carry out again; According to
Figure 320606DEST_PATH_IMAGE044
corrected received system local carrier frequency
Figure 304612DEST_PATH_IMAGE046
; Get into step (5), the frequency difference between local carrier and the reception signal carrier becomes
Figure 913447DEST_PATH_IMAGE048
at this moment.
Step (5) continues the relatively correlation peak of spreading code matched filter output P, if
Figure 24623DEST_PATH_IMAGE050
, then write down present clock
Figure 35304DEST_PATH_IMAGE052
, and no longer right in a follow-up code-element period PCompare, set confidence level simultaneously C=1.Wherein
Figure 190211DEST_PATH_IMAGE054
is proportionality coefficient; Through simulation analysis, its span is 0.6 ~ 0.8 o'clock best performance.
Step (6) is worked as clock
Figure 286343DEST_PATH_IMAGE056
The time, compare correlation peak once more P, wherein
Figure 935630DEST_PATH_IMAGE058
, be code-element period.If
Figure 800818DEST_PATH_IMAGE050
, confidence level then CAdd 1; Otherwise CSubtract 1.
Step (7) is with clock TIncrease
Figure 129556DEST_PATH_IMAGE060
, repeating step (6), during if confidence level CGreater than a certain threshold value, think that then spreading code accomplishes synchronously, get into step (8) and carry out the data despreading; If confidence level C=0, then turn back to step (5) and carry out again.
Step (8) is with current time TAs the initial moment, the local spread spectrum code sequence of synchronized generation , calculate respectively
Figure 962699DEST_PATH_IMAGE064
,
Figure 885656DEST_PATH_IMAGE066
Obtain I, Q two-way symbol data sequence.
Step (9) order
Figure 195415DEST_PATH_IMAGE068
, structure MIndividual complex symbol
Figure 453090DEST_PATH_IMAGE070
, this complex symbol sequence is carried out fast Fourier transform, obtain MIndividual frequency domain value.Right MTake absolute value back and obtain the subscript of maximum and correspondence position thereof of individual frequency domain value LAccording to subscript LCorrected received system local carrier frequency is to accomplish the synchronously thick of carrier frequency once more:
if
Figure 506496DEST_PATH_IMAGE072
, then
Figure 283959DEST_PATH_IMAGE074
;
Otherwise,
Figure 764619DEST_PATH_IMAGE076
.
Step (10) is calculated phase demodulation value
Figure 244011DEST_PATH_IMAGE078
,
Figure 101109DEST_PATH_IMAGE080
Confirm normalization phase demodulation value
Calculate the filtered output of loop
Figure 384639DEST_PATH_IMAGE084
,
Figure 616906DEST_PATH_IMAGE086
Then carrier phase
Figure 12116DEST_PATH_IMAGE088
is pressed the following formula renewal:
Figure 498592DEST_PATH_IMAGE090
Thereby accomplish the accurate recovery and the Phase Tracking of carrier wave.Wherein, parameter G1, G2, G3All represent loop gain, should suitable numerical value be set according to specific requirements such as chip rate, residual frequency departure size, loop noise indexs.

Claims (1)

1. burst the in short-term carrier recovering method of high spread spectrum communication receiving system of big frequency deviation condition; The Doppler frequency shift scope of setting carrier wave is
Figure 2012101597542100001DEST_PATH_IMAGE002
; Wherein
Figure 2012101597542100001DEST_PATH_IMAGE004
is the calibration value of carrier wave in this communication system; is maximum doppler frequency, it is characterized in that the concrete steps of this method are:
Step (1) is provided with receiving system local carrier frequency
Figure 2012101597542100001DEST_PATH_IMAGE008
, is used for the input intermediate-freuqncy signal is carried out frequency spectrum shift;
Step (2) will be passed through quadrature demodulation; Still exist the accurate baseband chip data sequence of two-way
Figure 2012101597542100001DEST_PATH_IMAGE010
of residual frequency difference and to deliver to spreading code matched filter calculating correlation peak
Figure 2012101597542100001DEST_PATH_IMAGE014
successively after accomplishing frequency spectrum shift; " * " representes convolution algorithm;
Figure 2012101597542100001DEST_PATH_IMAGE016
is the matched filter tap coefficient, is the reverse sequence of spread spectrum code sequence;
In a code-element period, relatively and write down the maximum of relevant peaks in this cycle
Figure 2012101597542100001DEST_PATH_IMAGE018
, record altogether KIndividual code-element period, thus obtain KIndividual maximal correlation peak value
Figure 2012101597542100001DEST_PATH_IMAGE020
To above-mentioned KSummation of maximal correlation peak value and record in the individual code-element period,
Figure 2012101597542100001DEST_PATH_IMAGE022
, parameter KGet 3,4,5 or 6;
Step (3) increases local carrier frequency , promptly set
Figure 2012101597542100001DEST_PATH_IMAGE026
, repeating step (2) is noted the maximal correlation peak value summation of each time, up to local carrier frequency
Figure 2012101597542100001DEST_PATH_IMAGE028
, promptly meet or exceed the frequency deviation region upper limit; Obtain this moment altogether JIndividual maximal correlation peak value summation is designated as
Figure 2012101597542100001DEST_PATH_IMAGE030
,
Figure 2012101597542100001DEST_PATH_IMAGE032
Step (4) relatively JIndividual maximal correlation peak value with
Figure 2012101597542100001DEST_PATH_IMAGE034
, find out maximum wherein
Figure 2012101597542100001DEST_PATH_IMAGE036
If
Figure 996607DEST_PATH_IMAGE036
Less than a certain setting threshold, think that then this moment, receiving system was not received spread-spectrum signal, will return step (1) and carry out again; Otherwise, according to Corrected received system local carrier frequency
Figure 2012101597542100001DEST_PATH_IMAGE040
, getting into step (5), the frequency difference between local carrier and the reception signal carrier becomes at this moment
Figure 2012101597542100001DEST_PATH_IMAGE042
Step (5) continues the relatively correlation peak of spreading code matched filter output P, if
Figure 2012101597542100001DEST_PATH_IMAGE044
, then write down present clock
Figure 2012101597542100001DEST_PATH_IMAGE046
, and no longer right in a follow-up code-element period PCompare, set confidence level simultaneously C=1; Wherein
Figure 2012101597542100001DEST_PATH_IMAGE048
Be proportionality coefficient, its span is 0.6 ~ 0.8;
Step (6) is worked as clock
Figure 2012101597542100001DEST_PATH_IMAGE050
The time, compare correlation peak once more P, wherein
Figure 2012101597542100001DEST_PATH_IMAGE052
, be code-element period; If
Figure 640471DEST_PATH_IMAGE044
, confidence level then CAdd 1; Otherwise CSubtract 1;
Step (7) is with clock TIncrease
Figure 2012101597542100001DEST_PATH_IMAGE054
, repeating step (6), during if confidence level CGreater than a certain threshold value, think that then spreading code accomplishes synchronously, get into step (8) and carry out the data despreading; If confidence level C=0, then turn back to step (5) and carry out again;
Step (8) is with current time TAs the initial moment, the local spread spectrum code sequence of synchronized generation
Figure 2012101597542100001DEST_PATH_IMAGE056
, calculate respectively
Figure 2012101597542100001DEST_PATH_IMAGE058
,
Figure 2012101597542100001DEST_PATH_IMAGE060
Obtain I, Q two-way symbol data sequence;
Step (9) order
Figure 2012101597542100001DEST_PATH_IMAGE062
, structure MIndividual complex symbol , this complex symbol sequence is carried out fast Fourier transform, obtain MIndividual frequency domain value; Right MTake absolute value back and obtain the subscript of maximum and correspondence position thereof of individual frequency domain value LAccording to subscript LCorrected received system local carrier frequency is to accomplish the synchronously thick of carrier frequency once more:
if
Figure 2012101597542100001DEST_PATH_IMAGE066
, then
Figure 2012101597542100001DEST_PATH_IMAGE068
;
Otherwise,
Figure 2012101597542100001DEST_PATH_IMAGE070
;
Step (10) is calculated phase demodulation value
Figure 2012101597542100001DEST_PATH_IMAGE072
,
Figure 2012101597542100001DEST_PATH_IMAGE074
Confirm normalization phase demodulation value
Figure 2012101597542100001DEST_PATH_IMAGE076
Calculate the filtered output of loop
Figure 2012101597542100001DEST_PATH_IMAGE078
,
Figure 2012101597542100001DEST_PATH_IMAGE080
Then carrier phase
Figure 2012101597542100001DEST_PATH_IMAGE082
is pressed the following formula renewal:
Figure 2012101597542100001DEST_PATH_IMAGE084
Thereby accomplish the accurate recovery and the Phase Tracking of carrier wave; Parameter wherein G1, G2, G3All represent loop gain.
CN201210159754.2A 2012-05-22 2012-05-22 Carrier recovery method of short-time burst high-spread-spectrum communication receiving system in large-frequency deviation condition Expired - Fee Related CN102685066B (en)

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Cited By (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN105871765A (en) * 2016-06-22 2016-08-17 南京索拉亚科技有限公司 Wireless communication carrier wave tracking method based on FFT assistant S-PLL
CN106992950A (en) * 2016-01-20 2017-07-28 晨星半导体股份有限公司 Carrier wave frequency deviation estimation device and carrier wave frequency deviation estimation method
CN108243125A (en) * 2016-12-23 2018-07-03 三星电子株式会社 Automatic frequency controller and method and wireless communication device and method
CN108449296A (en) * 2018-02-07 2018-08-24 南京理工大学 Short-term burst communication carrier synchronization method based on the positive bit-reverse loop splicing of signal
CN110113280A (en) * 2019-04-12 2019-08-09 杭州电子科技大学 The GMSK of anti-frequency deviation demodulates synchronous method in a kind of burst communication
CN112671447A (en) * 2020-12-04 2021-04-16 中国电子科技集团公司第五十四研究所 Short burst spread spectrum satellite signal receiving device
CN115189752A (en) * 2022-07-06 2022-10-14 中国电子科技集团公司第五十四研究所 Low-frequency spectrum density low-speed short burst signal processing device
CN115242264A (en) * 2022-07-18 2022-10-25 中国电子科技集团公司第五十四研究所 Short burst spread spectrum signal capture and carrier recovery method based on non-data assistance
CN116032709A (en) * 2022-12-06 2023-04-28 中国电子科技集团公司第三十研究所 Method and device for blind demodulation and modulation feature analysis of FSK signal without priori knowledge

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20040001563A1 (en) * 2002-06-28 2004-01-01 Scarpa Carl G. Robust OFDM carrier recovery methods and apparatus
CN101977176A (en) * 2010-10-12 2011-02-16 浙江大学 Method for realizing general demodulation of different modulating signals
TW201114230A (en) * 2009-10-06 2011-04-16 Uniband Electronic Corp Multi-stage frequency offset estimation and compensation method and circuit thereof

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20040001563A1 (en) * 2002-06-28 2004-01-01 Scarpa Carl G. Robust OFDM carrier recovery methods and apparatus
TW201114230A (en) * 2009-10-06 2011-04-16 Uniband Electronic Corp Multi-stage frequency offset estimation and compensation method and circuit thereof
CN101977176A (en) * 2010-10-12 2011-02-16 浙江大学 Method for realizing general demodulation of different modulating signals

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
孟明,许家栋,韦高: "直扩***PN码捕获和跟踪的FPGA实现", 《现代电子技术 》, 1 September 2011 (2011-09-01) *
张福洪，孙宁波，戴绍港: "基于FPGA的扩频通信***的研究及仿真", 《计算机***应用》, 15 May 2011 (2011-05-15) *

Cited By (17)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106992950A (en) * 2016-01-20 2017-07-28 晨星半导体股份有限公司 Carrier wave frequency deviation estimation device and carrier wave frequency deviation estimation method
CN105871765A (en) * 2016-06-22 2016-08-17 南京索拉亚科技有限公司 Wireless communication carrier wave tracking method based on FFT assistant S-PLL
TWI731144B (en) * 2016-12-23 2021-06-21 南韓商三星電子股份有限公司 Automatic frequency controllers and methods, and wireless communication devices and methods
CN108243125A (en) * 2016-12-23 2018-07-03 三星电子株式会社 Automatic frequency controller and method and wireless communication device and method
CN108243125B (en) * 2016-12-23 2021-03-09 三星电子株式会社 Automatic frequency controller and method, and wireless communication device and method
CN108449296A (en) * 2018-02-07 2018-08-24 南京理工大学 Short-term burst communication carrier synchronization method based on the positive bit-reverse loop splicing of signal
CN108449296B (en) * 2018-02-07 2021-01-08 南京理工大学 Short-time burst communication carrier synchronization method based on signal positive and negative sequence cyclic splicing
CN110113280A (en) * 2019-04-12 2019-08-09 杭州电子科技大学 The GMSK of anti-frequency deviation demodulates synchronous method in a kind of burst communication
CN110113280B (en) * 2019-04-12 2021-11-23 杭州电子科技大学 Anti-frequency-offset GMSK demodulation synchronization method in burst communication
CN112671447A (en) * 2020-12-04 2021-04-16 中国电子科技集团公司第五十四研究所 Short burst spread spectrum satellite signal receiving device
CN112671447B (en) * 2020-12-04 2022-05-06 中国电子科技集团公司第五十四研究所 Short burst spread spectrum satellite signal receiving device
CN115189752A (en) * 2022-07-06 2022-10-14 中国电子科技集团公司第五十四研究所 Low-frequency spectrum density low-speed short burst signal processing device
CN115189752B (en) * 2022-07-06 2024-04-26 中国电子科技集团公司第五十四研究所 Low-frequency spectrum density low-speed short burst signal processing device
CN115242264A (en) * 2022-07-18 2022-10-25 中国电子科技集团公司第五十四研究所 Short burst spread spectrum signal capture and carrier recovery method based on non-data assistance
CN115242264B (en) * 2022-07-18 2024-04-26 中国电子科技集团公司第五十四研究所 Short burst spread spectrum signal capturing and carrier recovering method based on non-data assistance
CN116032709A (en) * 2022-12-06 2023-04-28 中国电子科技集团公司第三十研究所 Method and device for blind demodulation and modulation feature analysis of FSK signal without priori knowledge
CN116032709B (en) * 2022-12-06 2024-04-12 中国电子科技集团公司第三十研究所 Method and device for blind demodulation and modulation feature analysis of FSK signal without priori knowledge

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