CN101917169A - High-bandwidth low-power consumption frequency-compensation three-stage operational amplifier - Google Patents

High-bandwidth low-power consumption frequency-compensation three-stage operational amplifier Download PDF

Info

Publication number
CN101917169A
CN101917169A CN2010102458533A CN201010245853A CN101917169A CN 101917169 A CN101917169 A CN 101917169A CN 2010102458533 A CN2010102458533 A CN 2010102458533A CN 201010245853 A CN201010245853 A CN 201010245853A CN 101917169 A CN101917169 A CN 101917169A
Authority
CN
China
Prior art keywords
stage
output
circuit
level
power consumption
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
CN2010102458533A
Other languages
Chinese (zh)
Other versions
CN101917169B (en
Inventor
李冉
刘俊娟
洪志良
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Fudan University
Original Assignee
Fudan University
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Fudan University filed Critical Fudan University
Priority to CN2010102458533A priority Critical patent/CN101917169B/en
Publication of CN101917169A publication Critical patent/CN101917169A/en
Application granted granted Critical
Publication of CN101917169B publication Critical patent/CN101917169B/en
Expired - Fee Related legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • Y02B60/50—

Landscapes

  • Amplifiers (AREA)

Abstract

The invention belongs to the technical field of analog IC (Integrated Circuit) design, in particular to a high-bandwidth low-power consumption frequency-compensation three-stage operational amplifier. The amplifier comprises an input stage, a second stage, an output stage, a common mode feedback stage, a comprehension circuit, an internal feedforward circuit, wherein the second stage is connected with the input stage, the output stage is connected with the second stage and used for amplifying a signal output by the second stage and driving an external load circuit, the common mode feedback stage extracts the common mode level of the differential output stage and stabilizes the common mode level, the comprehension circuit comprises a traditional trsanscondutance comprehension circuit, a miller comprehension circuit and a resistor for separating a high-frequency zero pole, and the internal feedforward circuit is used for comprehending an internal additional pole and forming a push-pull circuit together with the output stage to reduce static power consumption. The three-stage operational amplifier realizes high gain, high bandwidth and high stability under the condition of little DC power consumption and can be used in a high-speed analog-digital conversion circuit, such as a sigma-delta modulator suitable for the bandwidth of an LTE (Line Terminator Equipment) wireless communication protocol.

Description

High-bandwidth low-power consumption frequency-compensation three-stage operational amplifier
Technical field
Technical field of analog integrated circuit design of the present invention is specifically related to a kind of high-bandwidth low-power consumption frequency-compensation three-stage operational amplifier, can be used in the high speed analog-digital conversion conversion circuit.
Background technology
Along with the continual renovation of semiconductor process techniques, supply voltage is more and more lower under the CMOS technology, and as analog integrated circuit design basic module, the design of operational amplifier has obtained increasing challenge.General structure need adopt short channel length to realize fast speeds in order to obtain high bandwidth under the situation of lower power consumption, but can cause lower DC current gain, and short channel length can produce bigger process deviation, and the method that tradition improves gain has been not suitable for being applied to the development of technology from now on as stack transistor or gain bootstrap circuit along with the reduction of supply voltage.
While is along with the development of home control network communication protocol, bandwidth requirement for analog to digital converter is increasing, with over-sampling type analog-to-digital conversion device is example, be applicable to that the requirement maximum to the analog to digital converter bandwidth can arrive 20 megahertzes in the LTE home control network communication protocol, like this will be very high even reach Gigahertz (GHz) to the requirement of the operational amplifier of the inside.So need find a kind of structure that realizes high-gain and high bandwidth operational amplifier with lower power consumption.
Casacade multi-amplifier can be relatively easy to the gain that reaches higher, but can there be the problem of stability in the progression that increases amplifier merely, because there is more zero limit in casacade multi-amplifier, need the stability problem that collocation structure preferably could guarantee multi-stage operational amplifier.The design of tradition casacade multi-amplifier is in order to drive very big capacitive load or resistive load, bandwidth generally at tens megahertzes to the hundreds of megahertz, generally ignore the influence of endophyte electric capacity during design.And the amplifier load that is applied in the communications field is generally lighter, requires very big bandwidth, need consider the influence of endophyte electric capacity like this in design.
Usually the casacade multi-amplifier frequency compensation technology that adopts has Miller (Miller) compensation technique, mutual conductance and miller-compensated (NGRNMC) technology of zero-regulator resistor and transconductance capacitor compensation (TCFC) technology or the like.With the three-stage operational amplifier is example, and miller-compensated technology is to adopt two feedback capacities, is connected across the output of output stage and first and second grade respectively.The miller-compensated technology of feedforward transconductance be on miller-compensated basis respectively from input and second level input cross-over connection feedforward transconductance to output; The transconductance capacitor compensation technique is to have added a mutual conductance in the middle of the output of the miller-compensated second level and second building-out capacitor.
Fig. 1 is the structured flowchart of three grades of miller-compensated technology in the background technology, and third stage amplifier comprises first order amplifier A1, second level amplifier A2, third level amplifier A3.The mutual conductance of this third stage amplifier is respectively g M1, g M2And g M3, output resistance is respectively R 1, R 2And R 3, the lump output capacitance is C 1, C 2And C LMiller-compensated capacitor C M1Be connected across the output of A1 and the output of A3.Miller-compensated capacitor C M2Be connected across the output of A2 and the output of A3.Suppose miller-compensated capacitor C M1, C M2With load capacitance C L＞＞inner lump output capacitance C 1And C 2, can obtain the open loop frequency response formula of this structure:
A v ( s ) = A dc ( 1 + s ω 3 + s 2 ω 3 ω 4 ) ( 1 + s ω d ) ( 1 + s ω 1 + s 2 ω 1 ω 2 ) - - - ( 1 )
A DcBe DC current gain A Dc=g M1g M2g M3R 1R 2R 3, ω dBe dominant pole ω d=1/C M1g M2g M3R 1R 2R 3, unity gain bandwidth is ω UG=g M1/ C M1, two limit ω 1=g M2/ C M2, ω 2=g M3/ C L, two zero point ω 3=-g M3/ C M2, ω 4=g M2/ C M1For the third stage amplifier that makes this structure keeps stable, need make ω 2=2 ω 1=4 ω UG, in order to obtain big unity gain bandwidth g M1/ C M1Bigger, and C M1Can not get very little to prevent the influence of endophyte electric capacity, in like manner C M2And C LThe mutual conductance that also can not this shows last two sets very for a short time needs could to guarantee that amplifier keeps stablizing very greatly, and this structure can not obtain lower power consumption, the design of inapplicable and low-power consumption.
Fig. 2 is the structured flowchart of three grades of mutual conductances and the miller-compensated technology of zero-regulator resistor in the background technology, and third stage amplifier comprises first order amplifier B1, second level amplifier B2, third level amplifier B3.The mutual conductance of this third stage amplifier is respectively g M1, g M2And g M3, output resistance is respectively R 1, R 2And R 3, the lump output capacitance is C 1, C 2And C LAlso have first order feed-forward amplifier B4, second level feed-forward amplifier B5, their mutual conductance is respectively g Mf1And g Mf0Miller-compensated capacitor C M1Be connected across the output of B1 and the output of B3.Miller-compensated capacitor C M2Be connected across output and the zero-regulator resistor R of B3 mTwo ends, zero-regulator resistor R mBe connected across output and the C of B2 M2Two ends.The miller-compensated capacitor C of same hypothesis M1, C M2With load capacitance C L＞＞inner lump output capacitance C 1And C 2, the dominant pole that can obtain it is
ω d=1/C M1g M2g M3R 1R 2R 3, other limits ω 1=g M2g M3/ [(g M2g M3R m+ g M3-g M2) C M2],
ω 2=(R M2R M3R m+ g M3-R M2)/C L, zero point
ω 3＝g m1g m2g m3/(g m3g mf0C m1+g m1g m2g m3R mC m2-g m1g m2C m2)
ω 4=(g M3g Mf0C M1+ g M1g M2g M3R mC M2-g M1g M2C M2)/(g M3g Mf0R m+ g Mf1-g Mf0-g M1) C M1C M2, the time this structure amplifier keep stable in, can be by adjusting C LAnd C M1, C LAnd C M2Ratio and resistance R mReduce the mutual conductance of last two-stage, can be reduced to about 1/5th of NMC structure at most, but the zero-regulator resistor that this structure is used must could guarantee the condition of zero limit separation very for a short time, and in high frequency C M1And C M2Feedforward action can make the amplitude-frequency characteristic variation, so this structure can not satisfy the requirement of very big bandwidth.
Fig. 3 is the structured flowchart of three grades of transconductance capacitor compensation techniques in the background technology, and third stage amplifier comprises first order amplifier D1, second level amplifier D2, third level amplifier D3.The mutual conductance of this third stage amplifier is respectively g M1, g M2And g M3, output resistance is respectively R 1, R 2And R 3, the lump output capacitance is C 1, C 2And C LMiller-compensated capacitor C M1Be connected across the output of D1 and the output of D3.Miller-compensated capacitor C M2Be connected across output and the D4 two ends of D3, transconductance stage D4, its mutual conductance is g MtBe connected across output and the C of D2 M2Two ends.The third stage amplifier of this structure has adopted a mutual conductance g MtIntercepted C M2Short-circuiting effect when high frequency, gain when having improved high frequency and PSRR.But this structure generally is to be applied under the situation that drives big capacitive load and resistive load, and bandwidth has bigger advantage in the time of not high, when driving smaller capacitive but when requiring very high bandwidth and low-power consumption, and first miller-compensated resistance C M1Short-circuiting effect when high frequency will display, and the parasitic poles of second level mutual conductance collocation structure also can influence the stability of amplifier, has hindered the requirement that realizes the low-power consumption high bandwidth.
Summary of the invention
The purpose of this invention is to provide a kind ofly the time, have the three-stage frequency-compensated operational amplifier of high bandwidth, high-gain, low-power consumption than low supply voltage (1.2V and following).
High-bandwidth low-power consumption three-stage frequency-compensated operational amplifier provided by the invention comprises: input stage, and the second level, current source, output stage, the common-mode feedback level, compensating circuit and inner feed forward circuit, wherein:
Input stage is used for receiving inputted signal and amplification;
The second level is connected in input stage, amplifies the signal of input stage output;
Current source is used for providing current source load to the first order and the second level;
The difference output stage is connected in the second level, amplifies the signal of second level output and drives external load circuit;
The common-mode feedback level is taken out the common mode electrical level of difference output stage and common mode electrical level is stablized;
Compensating circuit comprises: first building-out capacitor, and second building-out capacitor, the mutual conductance compensating circuit, high frequency zero limit discrete resistor, wherein:
Second building-out capacitor is connected between output stage output and the mutual conductance compensating circuit;
The mutual conductance compensating circuit is connected between the second level output and second building-out capacitor, the short circuit of building-out capacitor and feedforward effect when eliminating high frequency;
High frequency zero limit discrete resistor is connected among first building-out capacitor and the output stage output, and the feedforward effect that reduces first building-out capacitor when frequency is very high produces zero limit and separates;
Inner feed forward circuit, be used for the inner extra limit of compensation and and output stage formation push-pull circuit, to reduce quiescent dissipation.
Among the present invention, the amplifier second level comprises current mirroring circuit and mutual conductance transistor.Current mirroring circuit provides current source load; The mutual conductance transistor is connected to the output and the current mirroring circuit of the first order, increases mutual conductance by the current mirror mirror image, and second level gain is provided.
Among the present invention, the mutual conductance compensating circuit of compensating circuit be connected the output that building-out capacitor is connected to the second level and the 3rd utmost point.
Among the present invention, in traditional mutual conductance compensating circuit and miller-compensated circuit increased by zero limit discrete resistor, it is connected in the middle of the input stage output and first building-out capacitor, has improved in the time of high frequency the compensation to parasitic zero limit.
Among the present invention, the common-mode feedback level comprises sampling resistor, and sampling common mode electrical level input transistors is with reference to common mode electrical level input transistors and load current mirror transistor.Wherein: sampling resistor is connected in the output stage difference output end; Sampling common mode electrical level input transistors is connected between sampling resistor mid point and the load current mirror transistor; Be connected in input stage current mirror load and reference voltage input terminal with reference to the common mode electrical level input transistors.The part of input stage that whole common mode feedback loop is multiplexing, the second level and output stage have whole realized under the condition that consumes very little dc power and difference is imported similar DC current gain and AC characteristic.
Among the present invention, inner feed forward circuit transistor is connected between the output and output stage transistor of the first order, further compensated inner zero limit, improved phase margin, and and multiplexing one road direct current of output stage transistor, constitute push-pull circuit, increased the slew rate of operational amplifier, further reduced the needed dc power of output stage.
Three-stage operational amplifier provided by the invention can obtain the very high gain and the bandwidth of last Gigahertz in the less load of lower power consumption (pF level).
Description of drawings
Fig. 1 is the structured flowchart of three grades of miller-compensated technology in the background technology.
Fig. 2 is the structured flowchart of three grades of mutual conductances and the miller-compensated technology of zero-regulator resistor in the background technology.
Fig. 3 is the structured flowchart of three grades of transconductance capacitor compensation techniques in the background technology.
Fig. 4 is the structured flowchart of three-stage frequency-compensated operational amplifier of the present invention.
Fig. 5 is the circuit diagram of three grades of fully differential frequency-compensated operational amplifiers of example according to the present invention.
Embodiment
The present invention is described in detail below in conjunction with accompanying drawing and example.
Fig. 4 is the structured flowchart of three-stage frequency-compensated operational amplifier of the present invention, and third stage amplifier comprises first order amplifier N1, second level amplifier N2, third level amplifier N3.The mutual conductance of this third stage amplifier is respectively g M1, g M2And g M3, output resistance is respectively R 1, R 2And R 3, the lump output capacitance is C 1, C 2And C 3, load capacitance is C LTransconductance stage N4 and feedforward transconductance level N5, their mutual conductance is respectively g MtAnd g MfMiller-compensated capacitor C M1Be connected across output and the high frequency zero limit discrete resistor R of N3 sBetween.High frequency zero limit discrete resistor R sBe connected across N1 output and miller-compensated capacitor C M1Between.Miller-compensated capacitor C M2Be connected across output and the N4 two ends of N3, N4 is connected across output and the C of N2 M2Two ends.Feedforward transconductance level N5 is connected across N1 output and N3 output two ends.Mutual conductance g MtIntercepted C M2Short-circuiting effect when high frequency, be eliminated g the zero point that the feedforward effect produces M3Can obtain smaller.But when frequency is very high, C M1Short-circuiting effect when high frequency has manifested to come out, and at this moment requires g again M3Bigger could the assurance stablized, so need be at building-out capacitor C M1Branch road on increase by one zero limit discrete resistor R s, we can be referred to as high frequency zero limit discrete resistor.The zero point that endoparasitic electric capacity can produce RHP when very high frequency, can be by adjusting the zero point of feedforward transconductance cancellation RHP, guaranteed the stability of system, and this one-level can constitute push-pull configuration with afterbody and increased slew rate, reduce dc power.
Because parasitic capacitance C in the third stage amplifier 1, C 2And C 3Be generally tens flying methods (fF), still can satisfy miller-compensated capacitor C M1, C M2With load capacitance C L＞＞C 1, C 2, C 3So the open loop Frequency Response of the frequency-compensation three-stage amplifier that provides in the invention is as follows:
A v ( s ) = A dc ( 1 + s ω 4 + s 2 ω 4 ω 5 + s 3 ω 4 ω 5 ω 6 ) ( 1 + s ω d ) ( 1 + s ω 1 + s 2 ω 1 ω 2 + s 3 ω 1 ω 2 ω 3 ) - - - ( 2 )
DC current gain A Dc=g M1g M2g M3R 1R 2R 3, dominant pole ω d=1/C M1g M2g M3R 1R 2R 3, non-dominant pole ω 1=g M2/ [(1+a) C M2], ω 2=(1+a) C M2g M3/ C 2C L, ω 3=g M2/ aC M2Zero point ω 4=g M2/ aC M2, ω 5=-C M2/ [C 2C M1(g Mt/ g M2g M3-R s)], ω 6=g M2/ aC M2, a=g wherein M2/ g Mt, unity gain bandwidth is g M1/ C M1The a value is generally between 1-3.Can obtain non-dominant pole ω by top zero limit observation 3With left half-plane ω at zero point 4Just in time offset non-dominant pole ω 2Very high can ignoring, non-dominant pole ω 1With left half-plane ω at zero point 6More approaching, the phase margin loss that they cause is less.By C M1The RHP limit that feedforward produces when high frequency can be by regulating R sEliminate.Mutual conductance compensated stage g when high frequency in the compensating circuit MtGrid leak parasitic capacitance and Cm2 zero point that can produce RHP together again, so add one-level feed forward circuit g MfAdjust the RHP zero point that endophyte produces, it does not influence the distribution of original limit, structurally can also constitute push-pull circuit with output stage, reduces power consumption.Amplifier is similar to one-pole system substantially in the time of design, mutual conductance for the second level and output stage does not require, can reduce demand so greatly to dc power, be applicable to the design of low-power consumption, effect when in design, not only having considered low frequency simultaneously, the feedforward effect of master's building-out capacitor and all careful consideration of ghost effect can realize the design of high bandwidth during to high frequency.
Fig. 5 is the circuit diagram of three grades of fully differential frequency-compensated operational amplifiers of example according to the present invention.Amplifier is divided into several parts of input stage, the second level, output stage, common-mode feedback and compensating network and constitutes, and design (calculated) load is 1.5pF, and bandwidth is 1.2GHz.With reference to figure 5, input stage comprises MP0a, MP2a-MN4a, MP2b-MP4b and MN1a, MN1b.The second level comprises MN2a-MN5a, MN2b-MN5b and MP5a, MP5b, and MN2a-MN5a, MN2b-MN5b have constituted current mirror, can provide current mirror load for the second level.Output stage comprises MP8a and MP8b, and the feedforward transconductance level comprises MN7a and MN7b, and these two modules have constituted push-pull circuit together.Compensated stage comprises the first building-out capacitor C M1With high frequency zero limit discrete resistor R s, the second building-out capacitor C M2With MP6a, MP6b, MP7a and MP7b, MP6a and MP6b are mutual conductance g Mt, MP7a and MP7b are that constant-current source provides bias current.The common-mode feedback level is made of MP0b, MP1a, MP1b, MP1c and MN1c.
In input stage, 9 transistors have constituted collapsible cascodes, and input is g to the mutual conductance of pipe MP2a and MP2b in this structure M1, the difference between difference input voltage vinp and the vinn can be input to partial input through amplifying from the drain terminal of MP3a and MP3b.
The mutual conductance of MP5a and MP5b is g in the second level M2/ n, n are the ratio of load current mirror, can produce g by this way M2Electric current be reduced into original 1/n, by 1: the mirror image of n can obtain g M2, saved dc power.The direct current of mirror image also provides current circuit for transconductance stage in the collocation structure, does not need other DC channel, and it is multiplexing to make electric current obtain.
Second building-out capacitor, one end is connected to the drain terminal of output stage MP8a or MP8b in the compensating circuit, and the other end is connected to MP6a or MP6b, and the mutual conductance of MP6a and MP6b is g Mt, these two transistorized drain terminals are connected to partial output, can avoid C when higher-frequency like this M2The feedforward effect.First building-out capacitor, one end also is linked to the drain terminal of output stage MP8a or MP8b, and the other end is connected to high frequency zero limit discrete resistor R s, R sReceive the drain terminal of input stage MP3a and MP3b.The RHP of Chan Shenging is zero point like this: ω 5=-C M2/ [C 2C M1(g Mt/ g M2g M3-R s)], work as R as can be seen s＞g Mt/ g M2g M3In time, can eliminate this RHP zero point.
The common mode electrical level that samples in the common mode feedback circuit is connected to the grid end of MP1a, carries out FEEDBACK CONTROL by the grid end that relatively control signal is fed back to input stage MN1a and MN1b with desirable common-mode signal.Can under the situation that consumes very little electric current, make common mode feedback bandwidth reach more than 2/3 of difference mode signal bandwidth by this feedback system.
Compare with traditional three-stage frequency-compensated amplifier, the three-stage frequency-compensated amplifier shown in the present invention has been realized very big bandwidth under the lower power consumption condition, and third stage amplifier also can provide very high gain simultaneously.This operational amplifier is applicable in the analog to digital converter at a high speed, has satisfied its requirement to high-gain high-bandwidth low-power consumption operational amplifier under the more and more lower situation of supply voltage.

Claims (6)

1. high-bandwidth low-power consumption frequency-compensation three-stage operational amplifier is characterized in that comprising: input stage, and the second level, current source, output stage, the common-mode feedback level, compensating circuit and inner feed forward circuit, wherein:
Input stage is used for receiving inputted signal and amplification;
The second level is connected in input stage, amplifies the signal of input stage output;
Current source is used for providing current source load to the first order and the second level;
Output stage is connected in the second level, amplifies the signal of second level output and drives external load circuit;
The common-mode feedback level is taken out the common mode electrical level of difference output stage and common mode electrical level is stablized;
Compensating circuit comprises: first building-out capacitor, and second building-out capacitor, the mutual conductance compensating circuit, high frequency zero limit discrete resistor, wherein:
Second building-out capacitor is connected between output stage output and the mutual conductance compensating circuit;
The mutual conductance compensating circuit is connected between the second level output and second building-out capacitor, the short circuit of building-out capacitor and feedforward effect when eliminating high frequency;
First building-out capacitor is connected between high frequency zero limit discrete resistor and the output stage;
High frequency zero limit discrete resistor is connected among first building-out capacitor and the output stage output, and the feedforward effect that reduces first building-out capacitor when frequency is very high produces zero limit and separates;
Inner feed forward circuit, be used for inner extra zero point of compensation and and output stage formation push-pull circuit reduce quiescent dissipation.
2. high broadband according to claim 1 low-power consumption frequency-compensation three-stage operational amplifier is characterized in that this amplifier second level comprises current mirroring circuit, and current source load is provided; The mutual conductance transistor is connected to the output and the current mirroring circuit of the first order, increases mutual conductance by the current mirror mirror image, and second level gain is provided.
3. high broadband according to claim 1 low-power consumption frequency-compensation three-stage operational amplifier is characterized in that, the mutual conductance compensating circuit in the compensating circuit be connected the output that building-out capacitor is connected to the second level and the 3rd utmost point.
4. high broadband according to claim 1 low-power consumption frequency-compensation three-stage operational amplifier, it is characterized in that, in traditional mutual conductance compensating circuit, increased by zero limit discrete resistor with miller-compensated circuit, it is connected in the middle of the input stage output and first building-out capacitor, has improved in the time of high frequency the compensation to parasitic zero limit.
5. high broadband according to claim 1 low-power consumption frequency-compensation three-stage operational amplifier, it is characterized in that, inner feed forward circuit transistor is connected between the output and output stage transistor of the first order, and and multiplexing one road direct current of output stage transistor, constitute push-pull circuit.
6. high broadband according to claim 1 low-power consumption frequency-compensation three-stage operational amplifier is characterized in that, the common-mode feedback level comprises sampling resistor, sampling common mode electrical level input transistors, with reference to common mode electrical level input transistors and load current mirror transistor; Wherein: sampling resistor is connected in the output stage difference output end; Sampling common mode electrical level input transistors is connected between sampling resistor mid point and the load current mirror transistor; Be connected in input stage current mirror load and reference voltage input terminal with reference to the common mode electrical level input transistors; The part of the multiplexing input stage of whole common mode feedback loop, the second level and output stage whole.
CN2010102458533A 2010-08-05 2010-08-05 High-bandwidth low-power consumption frequency-compensation three-stage operational amplifier Expired - Fee Related CN101917169B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN2010102458533A CN101917169B (en) 2010-08-05 2010-08-05 High-bandwidth low-power consumption frequency-compensation three-stage operational amplifier

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN2010102458533A CN101917169B (en) 2010-08-05 2010-08-05 High-bandwidth low-power consumption frequency-compensation three-stage operational amplifier

Publications (2)

Publication Number Publication Date
CN101917169A true CN101917169A (en) 2010-12-15
CN101917169B CN101917169B (en) 2013-02-27

Family

ID=43324586

Family Applications (1)

Application Number Title Priority Date Filing Date
CN2010102458533A Expired - Fee Related CN101917169B (en) 2010-08-05 2010-08-05 High-bandwidth low-power consumption frequency-compensation three-stage operational amplifier

Country Status (1)

Country Link
CN (1) CN101917169B (en)

Cited By (24)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102427339A (en) * 2011-11-27 2012-04-25 中国科学技术大学 Power amplifier with adjustable output power
CN102882476A (en) * 2012-10-24 2013-01-16 四川和芯微电子股份有限公司 High-bandwidth amplifying circuit
CN104270107A (en) * 2014-10-28 2015-01-07 李梦雄 Differential operational amplifier by using active feed-forward circuit for frequency compensation
CN104601123A (en) * 2014-12-24 2015-05-06 天津大学 Low-power consumption three-level operational amplifier for driving large-load capacitor
CN104779930A (en) * 2015-04-03 2015-07-15 成都振芯科技股份有限公司 High gain common mode feedback loop applied to high impedance current source load differential mode amplification circuit
CN104796092A (en) * 2014-01-22 2015-07-22 上海华虹集成电路有限责任公司 An equalization circuit
CN104935266A (en) * 2015-06-19 2015-09-23 华东师范大学 CMOS fully-integrated pseudo-differential low noise amplifier working at 71 to 76 GHz
CN105811889A (en) * 2016-04-20 2016-07-27 佛山臻智微芯科技有限公司 Feedforward compensation type transconductance operational amplifier
CN105978496A (en) * 2015-10-28 2016-09-28 温州墨熵微电子有限公司 Frequency compensation technology for optimizing conversion speeds of operational amplifiers
CN106385239A (en) * 2016-09-09 2017-02-08 中国计量大学 Gain-adjustable CMOS (Complementary Metal-Oxide-Semiconductor Transistor) broadband low-noise amplifier
WO2017124575A1 (en) * 2016-01-21 2017-07-27 中国电子科技集团公司第二十四研究所 Frequency compensation transconductance amplifier
CN107666288A (en) * 2017-09-20 2018-02-06 西安电子科技大学 A kind of big bandwidth three-stage operational amplifier of high-gain suitable for production line analog-digital converter
CN107819446A (en) * 2016-09-14 2018-03-20 成都锐成芯微科技股份有限公司 High PSRR operational amplification circuit
CN108259007A (en) * 2017-12-29 2018-07-06 思瑞浦微电子科技（苏州）股份有限公司 Enhancing circuit applied to amplifier conversion rate
CN110233600A (en) * 2018-03-05 2019-09-13 联发科技股份有限公司 Amplifier circuit and compensation circuit
CN110377089A (en) * 2019-07-19 2019-10-25 杭州恒芯微电子科技有限公司 A kind of multi-level differential amplifier output common mode voltage stable circuit simplified
WO2020019184A1 (en) * 2018-07-23 2020-01-30 中国电子科技集团公司第二十四研究所 Clock driver circuit
CN110943697A (en) * 2019-12-23 2020-03-31 西安航天民芯科技有限公司 Double-channel operational amplifier structure with high bandwidth and high gain
CN111124026A (en) * 2019-12-31 2020-05-08 龙迅半导体（合肥）股份有限公司 Data switch and data transmission system
CN111900938A (en) * 2020-06-22 2020-11-06 东南大学 Nonlinear analysis method applied to multistage operational amplifier
CN112511113A (en) * 2021-02-04 2021-03-16 上海南麟集成电路有限公司 Transconductance amplifier with zero point compensation
CN112558678A (en) * 2020-12-08 2021-03-26 电子科技大学 Buffer circuit with high bandwidth and low power consumption
CN113395048A (en) * 2020-03-11 2021-09-14 中国电子科技集团公司第二十四研究所 Mixed compensation three-stage operational amplifier
CN115149910A (en) * 2022-09-06 2022-10-04 中国电子科技集团公司第五十八研究所 Three-stage operational amplifier capacitor multiplication frequency compensation circuit

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101388650A (en) * 2008-10-14 2009-03-18 复旦大学 Nested type Miller active capacitor frequency compensation circuit
CN101425785A (en) * 2008-12-09 2009-05-06 中国科学院微电子研究所 Transconductance-capacitor compensation circuit for rolling over network
US20100066449A1 (en) * 2008-09-15 2010-03-18 Uday Dasgupta Three-stage frequency-compensated operational amplifier for driving large capacitive loads

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20100066449A1 (en) * 2008-09-15 2010-03-18 Uday Dasgupta Three-stage frequency-compensated operational amplifier for driving large capacitive loads
CN101388650A (en) * 2008-10-14 2009-03-18 复旦大学 Nested type Miller active capacitor frequency compensation circuit
CN101425785A (en) * 2008-12-09 2009-05-06 中国科学院微电子研究所 Transconductance-capacitor compensation circuit for rolling over network

Cited By (38)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102427339B (en) * 2011-11-27 2014-05-28 中国科学技术大学 Power amplifier with adjustable output power
CN102427339A (en) * 2011-11-27 2012-04-25 中国科学技术大学 Power amplifier with adjustable output power
CN102882476A (en) * 2012-10-24 2013-01-16 四川和芯微电子股份有限公司 High-bandwidth amplifying circuit
CN102882476B (en) * 2012-10-24 2015-07-08 四川和芯微电子股份有限公司 High-bandwidth amplifying circuit
CN104796092A (en) * 2014-01-22 2015-07-22 上海华虹集成电路有限责任公司 An equalization circuit
CN104796092B (en) * 2014-01-22 2018-02-13 上海华虹集成电路有限责任公司 Equalizing circuit
CN104270107B (en) * 2014-10-28 2017-02-22 李梦雄 Differential operational amplifier by using active feed-forward circuit for frequency compensation
CN104270107A (en) * 2014-10-28 2015-01-07 李梦雄 Differential operational amplifier by using active feed-forward circuit for frequency compensation
CN104601123A (en) * 2014-12-24 2015-05-06 天津大学 Low-power consumption three-level operational amplifier for driving large-load capacitor
CN104779930A (en) * 2015-04-03 2015-07-15 成都振芯科技股份有限公司 High gain common mode feedback loop applied to high impedance current source load differential mode amplification circuit
CN104935266A (en) * 2015-06-19 2015-09-23 华东师范大学 CMOS fully-integrated pseudo-differential low noise amplifier working at 71 to 76 GHz
CN104935266B (en) * 2015-06-19 2018-01-16 华东师范大学 A kind of fully integrated pseudo-differential low-noise amplifiers of CMOS for working in 71~76GHz
CN105978496A (en) * 2015-10-28 2016-09-28 温州墨熵微电子有限公司 Frequency compensation technology for optimizing conversion speeds of operational amplifiers
WO2017124575A1 (en) * 2016-01-21 2017-07-27 中国电子科技集团公司第二十四研究所 Frequency compensation transconductance amplifier
US10181821B2 (en) 2016-01-21 2019-01-15 China Electronic Technology Corporation 24Th Research Institute Frequency-compensated transconductance amplifier
CN105811889A (en) * 2016-04-20 2016-07-27 佛山臻智微芯科技有限公司 Feedforward compensation type transconductance operational amplifier
CN105811889B (en) * 2016-04-20 2019-03-05 佛山臻智微芯科技有限公司 A kind of feedforward compensation formula operational transconductance amplifier
CN106385239A (en) * 2016-09-09 2017-02-08 中国计量大学 Gain-adjustable CMOS (Complementary Metal-Oxide-Semiconductor Transistor) broadband low-noise amplifier
CN106385239B (en) * 2016-09-09 2019-04-16 中国计量大学 A kind of CMOS wideband low noise amplifier of adjustable gain
CN107819446A (en) * 2016-09-14 2018-03-20 成都锐成芯微科技股份有限公司 High PSRR operational amplification circuit
CN107666288A (en) * 2017-09-20 2018-02-06 西安电子科技大学 A kind of big bandwidth three-stage operational amplifier of high-gain suitable for production line analog-digital converter
CN108259007A (en) * 2017-12-29 2018-07-06 思瑞浦微电子科技（苏州）股份有限公司 Enhancing circuit applied to amplifier conversion rate
CN108259007B (en) * 2017-12-29 2021-06-04 思瑞浦微电子科技（苏州）股份有限公司 Enhancement circuit applied to operational amplifier conversion rate
CN110233600A (en) * 2018-03-05 2019-09-13 联发科技股份有限公司 Amplifier circuit and compensation circuit
CN110233600B (en) * 2018-03-05 2024-02-20 联发科技股份有限公司 Amplifier circuit and compensation circuit
WO2020019184A1 (en) * 2018-07-23 2020-01-30 中国电子科技集团公司第二十四研究所 Clock driver circuit
CN110377089A (en) * 2019-07-19 2019-10-25 杭州恒芯微电子科技有限公司 A kind of multi-level differential amplifier output common mode voltage stable circuit simplified
CN110943697A (en) * 2019-12-23 2020-03-31 西安航天民芯科技有限公司 Double-channel operational amplifier structure with high bandwidth and high gain
CN111124026A (en) * 2019-12-31 2020-05-08 龙迅半导体（合肥）股份有限公司 Data switch and data transmission system
CN111124026B (en) * 2019-12-31 2021-09-03 龙迅半导体（合肥）股份有限公司 Data switch and data transmission system
CN113395048A (en) * 2020-03-11 2021-09-14 中国电子科技集团公司第二十四研究所 Mixed compensation three-stage operational amplifier
CN113395048B (en) * 2020-03-11 2023-03-14 中国电子科技集团公司第二十四研究所 Hybrid compensation three-stage operational amplifier
CN111900938B (en) * 2020-06-22 2023-10-03 东南大学 Nonlinear analysis method applied to multistage operational amplifier
CN111900938A (en) * 2020-06-22 2020-11-06 东南大学 Nonlinear analysis method applied to multistage operational amplifier
CN112558678A (en) * 2020-12-08 2021-03-26 电子科技大学 Buffer circuit with high bandwidth and low power consumption
CN112558678B (en) * 2020-12-08 2022-01-25 电子科技大学 Buffer circuit with high bandwidth and low power consumption
CN112511113A (en) * 2021-02-04 2021-03-16 上海南麟集成电路有限公司 Transconductance amplifier with zero point compensation
CN115149910A (en) * 2022-09-06 2022-10-04 中国电子科技集团公司第五十八研究所 Three-stage operational amplifier capacitor multiplication frequency compensation circuit

Also Published As

Publication number Publication date
CN101917169B (en) 2013-02-27

Similar Documents

Publication Publication Date Title
CN101917169B (en) High-bandwidth low-power consumption frequency-compensation three-stage operational amplifier
CN101373956B (en) Method for compensating common mode feedback circuit frequency of two-stage amplifier
CN101826844B (en) Power amplifier and signal amplifying method based on power amplifier
CN101853040A (en) High mains rejection ratio low dropout voltage linear voltage regulator with feedforward transconductance
CN100549898C (en) Utilize two-way asymmetric buffer structure to improve the LDO circuit of performance
CN204103873U (en) A kind of active feed forward circuit forms frequency compensated differential operational amplifier
CN104270107A (en) Differential operational amplifier by using active feed-forward circuit for frequency compensation
CN107852137A (en) Amplifier circuit and method for adaptive amplifier biasing
CN103107790A (en) Programmable gain amplifier
CN111464139A (en) Common-mode feedback circuit suitable for wide-swing fully-differential operational amplifier
CN101841309B (en) Rail-to-rail operational amplifier
CN103595360A (en) Operational amplifier with Miller compensation structure
JP2012114914A5 (en)
CN102215028A (en) Amplifier
CN103259492A (en) Video driver output amplifier circuit
TWI568171B (en) Low-stress cascode structure
CN103138691B (en) A kind of feedback operational amplifier
US7986185B2 (en) Rail-to-rail Miller compensation method without feed forward path
CN201204568Y (en) Audio power amplification circuit
US20130293304A1 (en) Compensation technique for feedback amplifiers
CN202257350U (en) DC voltage deviation canceling circuit
CN113489465A (en) Amplifier circuit
CN111865243A (en) Variable gain amplifier suitable for biomedical signal acquisition analog front end
CN201742374U (en) Track-to-track operational amplifier
CN110768636A (en) Stability compensation method and circuit structure for multistage operational amplifier

Legal Events

Date Code Title Description
C06 Publication
PB01 Publication
C10 Entry into substantive examination
SE01 Entry into force of request for substantive examination
C14 Grant of patent or utility model
GR01 Patent grant
CF01 Termination of patent right due to non-payment of annual fee

Granted publication date: 20130227

Termination date: 20150805

EXPY Termination of patent right or utility model