WO2022233200A1 - 开关控制电路、电子设备及开关控制方法 - Google Patents
开关控制电路、电子设备及开关控制方法 Download PDFInfo
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- WO2022233200A1 WO2022233200A1 PCT/CN2022/083653 CN2022083653W WO2022233200A1 WO 2022233200 A1 WO2022233200 A1 WO 2022233200A1 CN 2022083653 W CN2022083653 W CN 2022083653W WO 2022233200 A1 WO2022233200 A1 WO 2022233200A1
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- 238000004590 computer program Methods 0.000 claims description 17
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0095—Hybrid converter topologies, e.g. NPC mixed with flying capacitor, thyristor converter mixed with MMC or charge pump mixed with buck
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
- H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1582—Buck-boost converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/08—Arrangements for controlling the speed or torque of a single motor
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/08—Arrangements for controlling the speed or torque of a single motor
- H02P6/085—Arrangements for controlling the speed or torque of a single motor in a bridge configuration
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
- H02P7/03—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
- H02P7/03—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors
- H02P7/04—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors by means of a H-bridge circuit
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0006—Arrangements for supplying an adequate voltage to the control circuit of converters
Definitions
- the present application relates to the technical field of electronic circuits, and in particular, to a switch control circuit, an electronic device and a switch control method.
- the embodiments of the present application disclose a switch control circuit, an electronic device, and a switch control method, which can simplify the control mode of each switch, so as to simplify the switch control circuit, reduce the cost, and reduce the switching loss.
- the embodiment of the present application discloses a switch control circuit, including:
- the voltage conversion module includes a first switch and a third switch that form a first bridge arm, and a second switch and a fourth switch that form a second bridge arm, for receiving an input voltage and working in boosting based on the input voltage at least one of a mode, a buck mode, and a buck-boost mode;
- a control module for controlling the first switch and the third switch to switch between an on state and an off state at a first switching frequency, and the second switch and the fourth switch at a second switching frequency Switching between an on state and an off state, so that the voltage conversion module works in the boost mode, and boosts and converts the input voltage; and is used for controlling the first switch and the first switch Three switches switch between an on state and an off state at the second switching frequency, and the second switch and the fourth switch switch between an on state and an off state at the first switching frequency , so that the voltage conversion module works in the step-down mode, and performs step-down conversion on the input voltage, and the first switching frequency is smaller than the second switching frequency.
- the embodiment of the present application discloses an electronic device including the switch control circuit as described above.
- the embodiment of the present application discloses a switch control method, including:
- the received input voltage is converted by a voltage conversion module to obtain an output voltage;
- the voltage conversion module includes a first switch and a third switch that form the first bridge arm, and a second switch and a fourth switch that form the second bridge arm , the voltage conversion module operates in at least one of a boost mode, a buck mode, and a buck-boost mode based on the input voltage;
- the first switch and the third switch are controlled to switch between an on state and an off state at a first switching frequency, and the second switch and the fourth switch are on and off at a second switching frequency. switching between disconnected states, so that the voltage conversion module works in the boost mode, and performs boost conversion on the input voltage;
- An embodiment of the present application discloses an electronic device, including a memory and a processor, where a computer program is stored in the memory, and when the computer program is executed by the processor, the processor implements the above method.
- the embodiment of the present application discloses a computer-readable storage medium on which a computer program is stored, and when the computer program is executed by a processor, the above-mentioned method is implemented.
- Fig. 1 is the circuit structure diagram of Buck-Boost circuit in the related art
- FIG. 2 is a structural block diagram of a switch control circuit in one embodiment
- FIG. 3 is a structural block diagram of a switch control circuit in another embodiment
- 4A is a structural block diagram of a first driving circuit in one embodiment
- 4B is a circuit structure diagram of a switch control circuit in one embodiment
- 4C is a structural block diagram of a second driving circuit in one embodiment
- FIG. 5 is a structural block diagram of a switch control circuit in another embodiment
- FIG. 6 is a structural block diagram of a switch control circuit in another embodiment
- FIG. 7A is a schematic structural diagram of a switch control circuit in another embodiment
- FIG. 7B is a schematic structural diagram of a switch control circuit in another embodiment
- FIG. 9 is a structural block diagram of an electronic device in one embodiment.
- first, second, etc. used in this application may be used herein to describe various elements, but these elements are not limited by these terms. These terms are only used to distinguish a first element from another element.
- a first switch could be referred to as a second switch, and similarly, a second switch could be referred to as a first switch, without departing from the scope of this application.
- Both the first switch and the second switch are switches, but they are not the same switch.
- circuits composed of four switches with double bridge arms, such as a four-switch Buck-Boost circuit, a DC motor H-bridge drive circuit composed of four switches, etc., and a double bridge composed of four switches.
- the circuit of the arm can usually work in a variety of different working modes, and the switches that need to be turned on and off in different working modes are different. In some working modes, it is necessary to keep the switch of the upper half of a certain bridge arm in the always-on state. Therefore, a separate driving circuit needs to be designed to realize this function, resulting in complicated circuit design and high cost.
- the switches S1 and S3 on the left bridge arm need to maintain frequent switching states. , constantly switching back and forth between the on state and the off state.
- the switch S2 of the right bridge arm (connected to the output terminal VOUT) needs to be kept on and S4 is always off.
- the switch S1 on the left bridge arm needs to be kept on, while S2 is always off, and the switches S2, S4 needs to maintain a frequent switching state, constantly switching back and forth between the on state and the off state.
- the charge pump drive circuit can provide voltages for S1 and S2 so that S1 is always in a conductive state in Boost mode, and S2 is always in a conductive state in Buck mode. Or it is necessary to make a part of the circuit inside the controller to realize the normally-on function of S1 or S2. Therefore, the design of the entire control circuit is complicated and the cost is high.
- a switch control circuit 20 may include a voltage conversion module 210 and a control module 220 .
- the voltage conversion module 210 may include a first switch 211 , a second switch 212 , a third switch 213 and a fourth switch 214 .
- the first switch 211 and the third switch 213 can form a first bridge arm, the first switch 211 can be connected to the input terminal (VIN) of the voltage conversion module 210 , and the third switch 213 can be grounded.
- the second switch 212 and the fourth switch 214 can form a second bridge arm, the second switch 212 can be connected to the output terminal (VOUT) of the voltage conversion module 210 , and the fourth switch 214 can be grounded.
- the voltage conversion module 210 is configured to receive an input voltage and operate in at least one of a boost mode, a buck mode, and a buck-boost mode based on the input voltage.
- the voltage transformation module 210 can transform the received input voltage to obtain an output voltage
- the input voltage can be a DC voltage
- the input voltage can be a pulsed DC voltage, or a relatively unstable DC current, wherein the pulsating DC voltage refers to The direction is unchanged, but the magnitude of the DC voltage changes periodically with time.
- the pulsating wave of the input voltage may include square wave waveform, steamed bread waveform and so on.
- the output voltage can be a stable DC voltage.
- the output voltage can be a constant DC voltage or an approximately constant DC voltage (with a very small amplitude).
- Constant DC voltage refers to a DC voltage with a fixed voltage.
- the voltage conversion module 210 can convert the input input voltage to obtain a stable output voltage and output it.
- the voltage conversion module 210 can switch between different working modes based on the input voltage.
- the working modes can include a boost mode, a buck mode, and a buck-boost mode.
- the voltage conversion module 210 works in a boost mode.
- the voltage conversion module 210 can perform boost conversion on the received input voltage.
- the voltage conversion module 210 operates in a step-down mode, so that the voltage conversion module 210 can perform step-down conversion on the input voltage, thereby ensuring that the output voltage output by the voltage conversion module is stable.
- the control module 220 is used to control the first switch 211 and the third switch 213 to switch between the on state and the off state at the first switching frequency, and control the second switch 212 and the fourth switch 214 to conduct at the second switching frequency. It switches between the on state and the off state, so that the voltage conversion module 210 works in the boost mode, and boosts and converts the input voltage.
- the control module 220 is further configured to control the first switch 211 and the third switch 213 to switch between the on state and the off state at the second switching frequency, and control the second switch 212 and the fourth switch 214 to switch between the on state and the off state at the first switching frequency. Switching between the on state and the off state makes the voltage conversion module 210 work in a step-down mode, and performs step-down conversion on the input voltage.
- the voltage conversion module 210 may include a Buck-Boost circuit, and the Buck-Boost circuit may convert both an over-high or an over-low DC voltage into a stable DC voltage.
- the voltage conversion module 210 may include an inductance L1, and the first bridge arm and the second bridge arm may be connected through the inductance L1 to form a circuit similar to the letter "H".
- the control module 220 may include, but is not limited to, processing chips such as CPU (central processing unit, central processing unit), MCU (Microcontroller Unit, micro control unit), and the like.
- the control module 220 can switch the working mode of the voltage conversion module 210 according to the voltage comparison result between the input voltage input to the voltage conversion module 210 and the output voltage output by the voltage conversion module 210 .
- the control module 220 may control the voltage conversion module 210 to work in the boost mode.
- the control module 220 can control the voltage conversion module to work in a step-down mode.
- the control module 220 can respectively control the switching frequencies of the first switch 211 , the second switch 212 , the third switch 213 and the fourth switch 214 according to the operating mode currently required by the voltage conversion module 210 .
- the frequency may refer to the switching times of the switch in a unit time, and the switching times may be the number of times of switching to an on state in a unit time, or the number of times of switching to an off state in a unit time.
- the switching frequency can be used to characterize the speed at which the switch switches between the on-state and the off-state. The higher the switching frequency, the faster the switching speed; The slower the speed of the switch, the fewer times the switch is turned on and off, and the longer each time it is in the on state or off state.
- the first switch 211 needs to be kept on
- the third switch 213 needs to be kept off
- the second switch 212 and the fourth switch 214 need to be switched on and off frequently.
- the boost conversion of the input input voltage On to realize the boost conversion of the input input voltage.
- the control module 220 can control the first switch 211 and the third switch 213 to operate at the first switching frequency, and the second switch 212 and the fourth switch 214 to operate at the second switching frequency.
- the first switching frequency may be lower than the second switching frequency, for example, the first switching frequency may be 2KHz (kilohertz), 3KHz, 2.34KHz, etc., and the second switching frequency may be 2MHz (megahertz), 3MHz, 3.43MHz, etc., The specific value thereof is not limited in the embodiments of the present application.
- the first switch 211 and the third switch 213 can be in an extremely low-frequency switching operation state, so that the first switch 211 can realize the normally-on function.
- the second switch 212 and the fourth switch 214 It switches between the on state and the off state at a high frequency, realizes the chopper modulation of the input input voltage, and uses the inductor L1 to boost the voltage to obtain a stable output voltage to ensure that the voltage conversion module 210 works normally in the boosted state. in pressure mode.
- the first switch 211 and the third switch 212 need to be switched on and off frequently, the second switch 212 needs to be kept normally on, and the third switch 213 needs to be kept normally off , in order to realize the step-down conversion of the input input voltage.
- the control module 220 can control the first switch 211 and the third switch 213 to operate at the second switching frequency, and the second switch 212 and the fourth switch 214 to operate at the first switching frequency.
- the second switch 212 and the fourth switch 214 can be in an extremely low-frequency switching operation state, so that the second switch 211 can realize the normally-on function.
- the first switch 211 and the third switch 213 It switches between the on state and the off state at a high frequency, realizes the chopper modulation of the input input voltage, and uses the inductor L1 to step down, so as to obtain a stable output voltage, and ensure that the voltage conversion module 210 works normally at a reduced voltage. in pressure mode.
- the four switches of the voltage conversion module 210 are always in a state of switching between on and off, and the control module only needs to control each
- the switching frequency of the switch simplifies the control mode of each switch, and does not need to design an independent driving circuit or control circuit to keep the first switch 211 or the second switch 212 in the conducting state, which simplifies the switch control circuit and reduces the circuit cost.
- the first switch 211 and the third switch 213 can operate at a lower first switching frequency
- the second switch 212 And the fourth switch 214 can operate at a lower first switching frequency, which can reduce the loss of the switch and improve the product performance of the switch control circuit.
- the switches disposed on the same bridge arm in the voltage conversion module 210 will not be turned on or turned off at the same time, so as to ensure the normal operation of the voltage conversion module 210 .
- the third switch 213 is in an off state
- the third switch 213 is in an on state.
- the fourth switch 214 is in the OFF state
- the fourth switch 214 is in the ON state.
- the on-time of the first switch 211 in the on-state is longer than the off-time of the off-state
- the off-time of the third switch 213 in the off-state is longer than the on-time of the on-state
- the on-time of the first switch 211 is equal to the off-time of the third switch 213 . It can be ensured that the first switch 211 is in an on state most of the time in the boost mode, which meets the normally-on requirements of the first switch 211 and the normally-off requirements of the third switch 213 in the boost mode.
- the on-duration of the second switch 212 and the fourth switch 214 in the on-state may be close to or the same as the off-duration of the off-state.
- the on-time of the second switch 212 in the on-state is longer than the off-time of the off-state
- the off-time of the fourth switch 214 in the off-state is greater than the on-time of the on-state
- the on-time of the second switch 212 is equal to the off-time of the fourth switch 214 . It can be ensured that the second switch 212 is in an on state most of the time in the step-down mode, which meets the normally-on requirements of the second switch 212 and the normally-off requirements of the fourth switch 214 in the step-down mode.
- the on-time of the first switch 211 and the third switch 213 in the on-state may be close to or the same as the off-time of the off-state.
- the above-mentioned switch control circuit 20 includes a first driving circuit 230 and a second driving circuit 240 in addition to the voltage conversion module 210 and the control module 220 .
- the first drive circuit 230 can be connected to the first switch 211
- the second drive circuit 240 can be connected to the second switch 212
- the input end of the first drive circuit 230 and the input end of the second drive circuit 240 can be connected to the control module 220 output connection.
- the control module 220 is further configured to send the first pulse signal to the first driving circuit 230 according to the first switching frequency if the voltage conversion module 210 works in the boost mode, and if the voltage conversion module 210 works in the buck mode, then The first pulse signal is sent to the second driving circuit 240 according to the first switching frequency.
- the control module 220 may send the first pulse signal to the first driving circuit 230 , and when the voltage conversion module 210 is in the step-down mode, the control module 220 may send the first pulse signal to the second driving circuit 240 a pulse signal.
- the pulse frequency of the first pulse signal may be the above-mentioned first switching frequency, the pulse frequency may refer to the number of pulse periods included in a unit time, and one pulse period may include the first level signal and the second level signal
- the first level signal may be a high level signal
- the second level signal may be a low level signal
- the first level signal may be a low level signal
- the second level signal may be a high level signal, etc.
- the time ratio occupied by the first level signal in one pulse period is greater than the time ratio occupied by the second level signal, wherein the first level signal can be capable of triggering the first driving circuit 230 Or the second driving circuit 240 outputs the level of the driving voltage, and the second level signal may be a level that triggers the first switch 211 or the second switch 212 to be in an off state.
- the first level signal may be a high level signal or a low level signal, which may depend on the specific circuit structures of the first driving circuit 230 and the second driving circuit 240 .
- the first driving circuit 230 is configured to provide a driving voltage to the first switch 211 when the received first pulse signal is a first level signal, so as to drive the first switch 211 to maintain an on state.
- the second driving circuit 240 is configured to provide a driving voltage to the second switch 212 when the received first pulse signal is a first level signal, so as to drive the second switch to maintain an on state.
- the time ratio occupied by the first level signal can be the first level signal
- the duration of one pulse period accounts for the percentage of the duration of the entire pulse period
- the time ratio occupied by the second level signal is the percentage of the duration of the second level signal within one pulse period to the duration of the entire pulse period.
- the time ratio occupied by the first level signal is 90%, 88%, etc.
- the time ratio occupied by the second level signal can be correspondingly 10%, 12%, etc.
- the time ratio can be set according to actual needs, which is not limited here.
- the first switch 211 is in a long-term conduction state in the boost mode
- the second switch 212 is in a long-term conduction state in the step-down mode, which ensures that the voltage conversion module 210 is in different working modes. normal work.
- FIG. 4A is a structural block diagram of a first driving circuit in one embodiment.
- the first driving circuit 230 may include a fifth switch 232 , a sixth switch 234 and a first capacitor 236 , wherein the fifth switch 232 and the sixth switch 234 may be respectively connected with the control module 220 is connected, the first end of the first capacitor 236 can be connected to the first switch 211 through the fifth switch 232 , and the second end of the first capacitor 236 is connected to the sixth switch 234 .
- the fifth switch 232 is configured to be in an on state when the first pulse signal sent by the control module 220 is a first level signal, and is in an off state when the first pulse signal sent by the control module 220 is a second level signal. open state.
- the sixth switch 234 is configured to be in an on state when the first pulse signal sent by the control module 220 is a second level signal, and is in an off state when the first pulse signal sent by the control module 220 is a first level signal. open state.
- the first capacitor 236 is used to provide a driving voltage to the first switch 211 when the fifth switch 232 is in the conductive state, so as to drive the first switch 211 to be in the conductive state.
- the fifth switch 232 and the sixth switch 234 can exist in the circuit in a push-pull manner. During the operation of the fifth switch 232 and the sixth switch 234 , only one switch can be turned on to improve the driving force of the circuit.
- the first terminal of the first capacitor 236 is further connected to the power terminal, and the second terminal of the first capacitor 236 is further connected to the third switch 213 .
- the first capacitor is also used for charging according to the voltage provided by the power supply terminal when the fifth switch 232 is in an off state and the third switch 213 is in an on state.
- FIG. 4B is a circuit structure diagram of a switch control circuit in one embodiment.
- the first switch 211 , the second switch 212 , the third switch 213 and the fourth switch 214 may all be N-type MOS transistors (MOSFET, metal-oxide semiconductor field). effect transistor), wherein the first switch 211 may include a first field effect transistor Q1, the second switch 212 may include a second field effect transistor Q2, the third switch 213 may include a third field effect transistor Q3, and the fourth switch 214 may include Including the fourth field effect transistor Q4.
- MOSFET metal-oxide semiconductor field). effect transistor
- the first driving circuit 230 may include a fifth switch Q11, a sixth switch Q12 and a first capacitor C11.
- the first end of the first capacitor C11 may pass through the fifth switch Q11 and the gate (G pole) of the first field effect field Q1.
- the fifth switch Q11 can be a P-type MOS transistor
- the sixth switch Q12 can be an N-type MOS transistor.
- the G pole of the fifth switch Q11 can be connected to the output terminal of the control module 220, the source (S pole) of the fifth switch Q11 can be connected to the drain (D pole) of the sixth switch Q12, and the first field effect field
- the G pole of Q1 is connected, and the D pole of the fifth switch Q11 can be connected to the first end of the first capacitor C11.
- the D pole of the first field effect field Q1 can be connected to the input terminal (VIN), and the S pole of the first field effect field Q1 can be connected to the third switch 213 (ie the third field effect transistor Q3 in FIG. 4B ), the sixth switch Q12 is connected to the second end of the first capacitor C11.
- the voltage at the point s1 may be 0V (volt).
- the boost mode when the first pulse signal output by the control module 220 to the fifth switch Q11 and the sixth switch Q12 is a low level signal, the fifth switch Q11 is turned on, and the sixth switch Q12 is turned off. The three FETs Q3 are disconnected.
- the voltage at point a will be higher than the voltage at point s1, that is, the voltage of the G pole of the first field effect transistor Q1 is higher than the voltage of the S pole, and the voltage of the first field effect transistor Q1
- the voltage difference between the G pole and the S pole is the voltage of the first capacitor C11, so that the first field effect transistor Q1 can be triggered to conduct.
- the voltage at point s1 will increase and level with the voltage at the input terminal VIN.
- the voltage at point a will become the sum of the voltage at the input terminal VIN and the voltage at the first capacitor C11 , therefore, the voltage at point a will be higher than the voltage at point s1, the voltage difference between the G pole and the S pole of the first field effect transistor Q1 is still the voltage of the first capacitor C11, and the first field effect transistor Q1 continues to maintain conduction. pass status.
- the first capacitor C11 is used as a bootstrap capacitor.
- the first capacitor C11 can provide a driving voltage to the G pole of the first field effect transistor Q1, so that the G pole voltage is greater than the S pole voltage and the voltage between the two is higher.
- the difference is greater than a certain value (for example, 5V, etc.), so that the first field effect transistor Q1 is kept on.
- the control module 220 outputs the first pulse to the fifth switch Q11 and the sixth switch Q12 after the first field effect transistor Q1 is turned on for a period of time The signal becomes a high level signal.
- the fifth switch Q11 is turned off, and the sixth switch Q12 is turned on, that is, the first field effect transistor Q1 is turned off, and the third field effect transistor Q3 is turned on, and the power supply terminal VCC can be connected to The first capacitor C11 is charged.
- the first driving circuit 230 further includes a first diode D1, the first end of the first capacitor C11 can be connected to the cathode of the first diode D1, the first The anode of the diode D1 can be connected to the power terminal VCC.
- the third switch 213 ie, the third field effect transistor Q3 in FIG. 4B
- the power supply terminal VCC charges the first capacitor C11 through the first diode D1 .
- the voltage of the power supply terminal VCC will be greater than the voltage at point a, the first diode D1 is turned on, the power supply terminal VCC charges the first capacitor C11, and the voltage of the first capacitor C11 gradually increases, The voltage at point a is gradually boosted, the first diode D1 is turned off, and the power terminal VCC stops charging the first capacitor C11, so that the voltage of the first capacitor C11 is the same as the voltage of the power terminal VCC.
- the voltage at point a will be greater than the voltage of the power supply terminal VCC, and the first diode can prevent the voltage of the first capacitor C11 from being output to the power supply terminal VCC. , the circuit safety is protected, and unnecessary loss of the electric energy of the first capacitor C11 is prevented.
- the first capacitor C11 can provide a driving voltage to the first switch 211, keep the first switch 211 in an on state most of the time in the boost mode, and has a very high turn-on ratio. And because the four switches in the voltage conversion module 210 are all in the working state of continuously switching between the on state and the off state, after the third switch 213 is turned on, the first capacitor C11 can be charged, ensuring that the first capacitor C11 is charged. Therefore, the first capacitor C11 can work normally as a bootstrap capacitor.
- the first driving circuit 230 only adds the first capacitor C11 and the first diode D1 in the half-bridge driving method in the related art (ie, the fifth switch Q11 and the sixth switch Q12 mentioned above), which greatly simplifies the driving
- the design of the circuit can save the isolation drive or charge pump drive, etc., and can realize the free switching of the voltage conversion module 210 in different working modes, simplify the design of the switch control circuit, reduce the complexity and cost of the circuit, and ensure that the The efficiency of the product is basically not affected.
- the voltage conversion module 210 since the voltage conversion module 210 is in different working modes, the four switches are all in the working state of constantly switching between the on state and the off state, the voltage conversion module 210 will be smoother when switching modes, and the product is improved. performance.
- the capacitor C1 and the capacitor C2 can be used to filter the voltage to ensure stable output voltage.
- FIG. 4C is a structural block diagram of a second driving circuit in one embodiment.
- the second driving circuit 240 may include a seventh switch 242 , an eighth switch 244 and a second capacitor 246 , wherein the seventh switch 242 and the eighth switch 244 may be respectively connected with the control module 220 is connected, the first end of the second capacitor 246 can be connected to the second switch 212 through the seventh switch 242 , and the second end of the second capacitor 246 is connected to the eighth switch 244 .
- the seventh switch 242 is used to be in an on state when the first pulse signal sent by the control module 220 is a first level signal, and is in an off state when the first pulse signal sent by the control module 220 is a second level signal. open state.
- the eighth switch 244 is used to be in an on state when the first pulse signal sent by the control module 220 is a second level signal, and is in an off state when the first pulse signal sent by the control module 220 is a first level signal. open state.
- the second capacitor 246 is used for providing a driving voltage to the second switch 212 when the seventh switch 242 is in the on state, so as to drive the second switch 212 in the on state.
- the first terminal of the second capacitor 246 is further connected to the power supply terminal, and the second terminal of the second capacitor 246 is further connected to the fourth switch 214 .
- the second capacitor 246 is also used for charging according to the voltage provided by the power terminal when the seventh switch 242 is in an off state and the fourth switch 214 is in an on state.
- the second driving circuit 240 may include a seventh switch Q21 , an eighth switch Q22 and a second capacitor C21 , and the first end of the first capacitor C21 may pass through the seventh switch Q21 and the second capacitor C21 .
- the G poles of the two field effect fields Q2 are connected.
- the seventh switch Q21 can be a P-type MOS transistor
- the eighth switch Q22 can be an N-type MOS transistor.
- the G pole of the seventh switch Q21 can be connected to the output end of the control module 220
- the S pole of the seventh switch Q21 can be connected to the D pole of the eighth switch Q22, and the G pole of the second field effect field Q2.
- the D pole of the switch Q21 can be connected to the first end of the second capacitor C21.
- the D pole of the second field effect field Q2 can be connected to the output terminal (VOUT), and the S pole of the second field effect field Q2 can be connected to the fourth switch 214 (ie, the fourth field effect transistor Q4 in FIG. 4B ), the eighth switch
- the S pole of Q22 is connected to the second end of the second capacitor C21.
- the voltage at the point s2 may be 0V.
- the step-down mode when the first pulse signal output by the control module 220 to the seventh switch Q21 and the eighth switch Q22 is a low level signal, the seventh switch Q21 is turned on, and the eighth switch Q22 is turned off. The four FETs Q4 are turned off.
- the voltage at point b will be higher than the voltage at point s2, that is, the voltage of the G pole of the second field effect transistor Q2 is higher than the voltage of the S pole, and the second field effect transistor Q2
- the voltage difference between the G pole and the S pole is the voltage of the second capacitor C21, which can trigger the conduction of the second field effect transistor Q2.
- the voltage at point s2 will increase and level with the voltage at the output terminal VOUT.
- the voltage at point b will become the sum of the voltage at the output terminal VOUT and the voltage at the second capacitor C21 , therefore, the voltage at point b will be higher than the voltage at point s2, the voltage difference between the G pole and the S pole of the second field effect transistor Q2 is still the voltage of the second capacitor C21, and the second field effect transistor Q2 continues to maintain conduction. pass status.
- the second capacitor C21 is used as a bootstrap capacitor.
- the second capacitor C21 can provide a driving voltage to the G pole of the second FET Q2, so that the G pole voltage is greater than the S pole voltage and the voltage between the two The difference is greater than a certain value (for example, 5V, etc.), so that the second field effect transistor Q2 is kept on.
- a certain value for example, 5V, etc.
- the control module 220 outputs the first pulse to the seventh switch Q21 and the eighth switch Q22 The signal becomes a high-level signal.
- the seventh switch Q21 is turned off, and the eighth switch Q22 is turned on, that is, the second field effect transistor Q2 is turned off, and the fourth field effect transistor Q4 is turned on, and the power supply terminal VCC can be connected to The second capacitor C21 is charged.
- the second driving circuit 240 further includes a second diode D2, the first end of the second capacitor C21 can be connected to the negative electrode of the second diode D2, the second The anode of the diode D2 can be connected to the power terminal VCC.
- the fourth switch 214 ie, the third field effect transistor Q4 in FIG. 4B
- the power supply terminal VCC charges the second capacitor C21 through the second diode D2 .
- the second diode D2 is turned on, the power terminal VCC charges the second capacitor C21, and the voltage of the second capacitor C21 gradually increases, The voltage at point b is gradually boosted, the second diode D2 is turned off, and the power terminal VCC stops charging the second capacitor C21, so that the voltage of the second capacitor C21 is the same as the voltage of the power terminal VCC.
- the second capacitor C21 is discharged and the second FET Q2 is turned on, the voltage at point b will be greater than the voltage of the power supply terminal VCC, and the second diode can prevent the voltage of the second capacitor C21 from being output to the power supply terminal VCC. , the circuit safety is protected, and unnecessary loss of the electric energy of the second capacitor C21 is prevented.
- the second capacitor C21 can provide a driving voltage to the second switch 212, keep the second switch 212 in an on state most of the time in the buck mode, and has a very high conduction ratio. And since the four switches in the voltage conversion module 210 are all in the working state of constantly switching between the on state and the off state, after the fourth switch 214 is turned on, the second capacitor C21 can be charged, ensuring that the second capacitor C21 is charged. Therefore, the second capacitor C21 can work normally as a bootstrap capacitor.
- the second driving circuit 240 is the same as the first driving circuit 230, which greatly simplifies the design of the driving circuit, reduces the complexity and cost of the circuit, and at the same time ensures that the efficiency of the product is basically not affected.
- the above-mentioned fifth switch Q11 can also be an N-type MOS transistor, and the sixth switch Q12 can be a P-type MOS transistor.
- the fifth switch Q11 is turned on, the sixth switch Q12 is turned off, and triggers the first field effect transistor Q1 to be turned on.
- the above-mentioned seventh switch Q21 can also be an N-type MOS transistor, and the eighth switch Q22 can be a P-type MOS transistor.
- the seventh The switch Q21 is turned on, the eighth switch Q22 is turned off, and the second field effect transistor Q2 is triggered to be turned on.
- the level signal that can trigger the conduction of the fifth switch Q11 and the seventh switch Q21 is the first level signal, and the time ratio of the first level signal in one pulse period can be a high value, such as 90% , 91%, etc., thus ensuring that the switch in the upper half of the bridge arm is approximately always on.
- the above-mentioned fifth switch Q11, sixth switch Q12, seventh switch Q21, eighth switch Q22, etc. can also be other switch tubes, such as triodes, etc., and are not limited to MOS tubes.
- the switch control circuit 20 may further include an inversion module 250 , a third drive circuit 250 , a third drive circuit 240 , a voltage conversion module 210 , a control module 220 , a first drive circuit 230 and a second drive circuit 240 .
- the driving circuit 260 and the fourth driving circuit 270 are connected to the third switch 213
- the fourth drive circuit 270 is connected to the fourth switch 270
- the inversion module 250 can be connected to the control module 220 , the third drive circuit 260 and the fourth drive circuit 270 respectively .
- the inversion module 250 is further configured to invert the first pulse signal output by the control module 220 to obtain a second pulse signal, and if the determined working mode is the boost mode, send the second pulse signal to the third driving circuit 260 , and if the determined working mode is the step-down mode, the second pulse signal is sent to the fourth driving circuit 270 .
- the third driving circuit 260 is configured to drive the third switch 213 to maintain an on state when the received second pulse signal is a first level signal.
- the fourth driving circuit 270 is configured to drive the fourth switch 214 to maintain a conducting state when the received second pulse signal is a first level signal.
- the reversing module 250 can reverse the pulse signal output from the control module 220 to the first switch 211 , and output the reversed pulse signal to the third switch 213 , and can also reverse the pulse signal output from the control module 220 to the second switch 212 .
- the pulse signal is reversed, and the reversed pulse signal is output to the fourth switch 214 .
- Using the reverse module 250 can ensure that the pulse signals received by the two switches on the same bridge arm at the same time are reverse pulse signals, and the two switches on the same bridge arm will not be turned on or off at the same time.
- the control module 220 outputs a first pulse signal with a pulse frequency of the first switching frequency to the first driving circuit 230, and the first pulse signal can be simultaneously input to the inversion module 250, and the inversion module 250 performs After inversion, a second pulse signal with a pulse frequency of the first switching frequency can be obtained, and the second pulse signal is input to the third driving circuit 260 , and the second pulse signal is opposite to the first pulse signal.
- the control module 220 outputs a third pulse signal with a pulse frequency of the second switching frequency to the second driving circuit 240, and the third pulse signal can be input to the inversion module 250 at the same time, and the inversion module 250 performs After inversion, a fourth pulse signal with a pulse frequency of the second switching frequency can be obtained, and the fourth pulse signal is input to the fourth driving circuit 270, and the third pulse signal and the fourth pulse signal are reversed.
- the control module 220 outputs a third pulse signal with a pulse frequency of the second switching frequency to the second driving circuit 240, and the third pulse signal can be input to the inversion module 250 at the same time, and the inversion module 250 performs After inversion, a fourth pulse signal with a pulse frequency of the second switching frequency can be obtained, and the fourth pulse signal is input to the fourth driving circuit 270, and the third pulse signal and the fourth pulse signal are reversed.
- the control module 220 outputs a first pulse signal with a pulse frequency of the first switching frequency to the second driving circuit 240, and the first pulse signal can be simultaneously input to the inversion module 250, and the inversion module 250 After inversion, a second pulse signal with a pulse frequency of the first switching frequency can be obtained, and the second pulse signal is input to the fourth driving circuit 270 .
- the control module 220 outputs a third pulse signal with a pulse frequency of the second switching frequency to the first driving circuit 230, and the third pulse signal can be input to the inversion module 250 at the same time, and the inversion module 250 performs After inversion, a fourth pulse signal with a pulse frequency of the second switching frequency can be obtained, and the fourth pulse signal is input to the third driving circuit 260 to ensure that the first switch 211 and the third switch 213 are The second switching frequency switches the on state and the off state.
- the above-mentioned third driving circuit 260 and fourth driving circuit 260 may be push-pull output driving circuits, and both may include a pair of symmetrical switch tubes (for the specific circuit structure, please refer to the fifth switch Q11 and the fifth switch Q11 in FIG. 4B ).
- the sixth switch Q12 only one of the symmetrical switch tubes is turned on at a time to form a push-pull drive, which improves the switching speed.
- the difference from the first driving circuit 230 and the second driving circuit 240 is that the third switch 213 and the fourth switch 214 do not need to be in a normally-on state, so there is no need for a bootstrap capacitor to provide power to drive the third switch 213 And the fourth switch 214 remains on for a long time.
- the above-mentioned inversion module 250 can also be integrated inside the control module 220, and the control module 220 can reverse the output pulse signal internally, and then output two reverse pulse signals respectively, which can ensure Two switches on the same bridge arm receive signals with different levels synchronously.
- control module 220 is further configured to obtain a voltage comparison result between the input voltage and the output voltage of the voltage conversion module 210, and control the voltage conversion module 210 to work in the boost mode, the buck mode and the At least one of the buck-boost modes.
- the above-mentioned switch control module may further include a voltage acquisition module 280 , and the voltage acquisition module 280 may be respectively connected to the input terminal VIN and the output terminal VOUT of the voltage conversion module 210 .
- the output terminal of the voltage acquisition module 280 may be connected to the input terminal of the control module 220 .
- the voltage acquisition module 280 can be used to collect the input voltage input from the input terminal of the voltage conversion module 210 and the output voltage output from the output terminal of the voltage conversion module 210, and compare the input voltage with the output voltage to obtain a voltage comparison result. After obtaining the voltage comparison result, the voltage acquisition module 280 may send the voltage comparison result to the control module 220 .
- the control module 220 is further configured to control the voltage conversion module 210 to work in the boost mode if the voltage comparison result is that the input voltage is less than the output voltage, and the difference between the output voltage and the input voltage is greater than the first threshold, and if the voltage comparison The result is that the input voltage is greater than the output voltage, and the difference between the input voltage and the output voltage is greater than the second threshold, then the voltage conversion module 210 is controlled to work in the step-down mode.
- first and second thresholds can be set according to actual needs, which are not limited here.
- the first threshold is 5V
- the second threshold is 10V, etc.
- the control module 220 is further configured to control the first switch 211 , the second switch 212 , the third switch 213 and the fourth switch 214 if the absolute value of the difference between the input voltage and the output voltage is less than the third threshold as a result of the voltage comparison Both are switched between the on state and the off state at the first switching frequency, so that the voltage conversion module 210 works in the buck-boost mode.
- the voltage comparison result is that the absolute value of the difference between the input voltage and the output voltage is smaller than the third threshold, it means that the input voltage and the output voltage are relatively close, and the voltage conversion module 210 can be controlled to work in the buck-boost mode, and the voltage The four switches of the conversion module 210 can all operate at a lower first switching frequency, thereby reducing the switching loss of the circuit and improving the product efficiency.
- first threshold value, second threshold value and third threshold value may be the same voltage value, and the specific data thereof is not limited in the embodiment of the present application.
- control module 220 can switch the working mode of the voltage conversion module 210 according to the voltage comparison result, and in each working mode, the four switches are kept in a state of continuous switching between on and off.
- the control module only needs to control the switching frequency of each switch, which simplifies the control method of each switch, simplifies the circuit design, reduces the cost, and can reduce the switching loss of the circuit and improve the product performance.
- FIG. 7A is a schematic structural diagram of a switch control circuit in another embodiment.
- the switch control circuit 20 may include two LMG chips, and each LMG chip may include an upper tube driver and a lower tube driver connected to the corresponding bridge arms.
- the LMG chip connected to them may include the above-mentioned fifth switch Q11, sixth switch Q12, third driving circuit 260, and first diode D1.
- two reverse pulse signals PWM1H and PWM2H can be input to the LMG chip, and after passing through the LMG chip, they are respectively output to the first field effect transistor Q1 and the third field effect transistor Q3 to control the first field effect transistor Q1, The third field effect transistor Q3 is turned on or off.
- the LMG chip can also be replaced with other driver chips, which is not limited here.
- FIG. 7B is a schematic structural diagram of a switch control circuit in another embodiment.
- the bootstrap capacitor C11 and the bootstrap capacitor C21 can provide driving voltages for the upper switches Q1 and Q2 of the left and right bridge arms, so as to keep Q1 and Q2 in a long-term on state, simplifying the driving circuit, reducing the cost.
- an electronic device which may include the switch control circuit 20 described in the various embodiments above.
- the electronic device may include, but is not limited to, a power adapter, a motor product, etc., which is not limited herein.
- a switch control method is provided, which can be applied to the above-mentioned electronic equipment, and the method may include the following steps:
- step 810 the received input voltage is converted by the voltage conversion module to obtain the output voltage.
- the voltage conversion module includes a first switch and a third switch that form the first bridge arm, and a second switch and a fourth switch that form the second bridge arm.
- the voltage conversion module works in boost mode, step-down mode and at least one of the buck-boost mode.
- Step 820 Control the first switch and the third switch to switch between the on state and the off state at the first switching frequency, and control the second switch and the fourth switch to switch between the on state and the off state at the second switching frequency. Switch between the two, so that the voltage conversion module works in the boost mode, and the input voltage is boosted and converted.
- Step 830 control the first switch and the third switch to switch between the on state and the off state at the second switching frequency, and control the second switch and the fourth switch to switch between the on state and the off state at the first switching frequency Switch between states, so that the voltage conversion module works in the step-down mode, and the input voltage is step-down converted.
- the first switching frequency is lower than the second switching frequency. It should be noted that there is no limitation on the execution time sequence between step 820 and step 830, step 820 may be executed first, or step 830 may be executed first, depending on the working mode required by the voltage conversion module.
- the four switches of the voltage conversion module 2 are always in a state of continuous switching between on and off, and it is only necessary to control the switching of each switch.
- the switching frequency simplifies the control mode of each switch, and does not need to design an independent drive circuit or control circuit to keep the first switch or the second switch in an on state, which simplifies the switch control circuit and reduces the circuit cost.
- the third switch when the first switch is in an on state, the third switch is in an off state, and when the first switch is in an off state, the first switch is in an on state; in the boost mode, the first switch is in an off state.
- the on-time of the switch in the on-state is greater than the off-time of the off-state.
- the fourth switch When the second switch is in the on state, the fourth switch is in the off state, when the second switch is in the off state, the fourth switch is in the on state; in the buck mode, the second switch is in the on state
- the on-time is longer than the off-time in the off state.
- the step of controlling the first switch and the third switch to switch between an on state and an off state at a first switching frequency may include: sending the first switching frequency to the first driving circuit according to the first switching frequency. the pulse signal, so that when the first pulse signal is a first level signal, the first driving circuit provides a driving voltage to the first switch, so as to drive the first switch to maintain an on state.
- the step of controlling the second switch and the fourth switch to switch between the on state and the off state at the first switching frequency includes: sending a first pulse signal to the second driving circuit according to the first switching frequency, so that the second When the first pulse signal is the first level signal, the driving circuit provides a driving voltage to the second switch, so as to drive the second switch to maintain an on state.
- the time ratio occupied by the first level signal in one pulse period is greater than the time ratio occupied by the second level signal, and the second level signal is used to trigger the first switch or the second level signal.
- the second switch is off.
- the first drive circuit includes a first capacitor.
- the step sends a first pulse signal to the first drive circuit according to the first switching frequency, so that the first drive circuit provides a drive voltage to the first switch when the first pulse signal is a first level signal, so as to drive the first switch to maintain
- the on state includes: sending a first pulse signal to the first drive circuit according to the first switching frequency, so that when the first pulse signal is a first level signal, the first drive circuit provides the first switch through the first capacitor a driving voltage to drive the first switch to be in an on state.
- the above method further includes: when the first pulse signal received by the first driving circuit is a second level signal, charging the first capacitor with the voltage provided by the power supply terminal.
- the second drive circuit includes a second capacitor.
- the step sends a first pulse signal to the second drive circuit according to the first switching frequency, so that when the first pulse signal is the first level signal, the second drive circuit provides a drive voltage to the second switch to drive the second switch Keeping the switch in an on state includes: sending a first pulse signal to the second drive circuit according to the first switching frequency, so that when the first pulse signal is the first level signal, the second drive circuit sends the second capacitor to the second drive circuit through the second capacitor.
- the switch provides a driving voltage to drive the first switch in an on state.
- the above method further includes: when the first pulse signal received by the second driving circuit is a second level signal, charging the second capacitor with a voltage provided by the power supply terminal.
- the bootstrap capacitor is used to provide the driving voltage to the corresponding switch, so as to ensure that the switch is in an on state most of the time and has a very high conduction ratio.
- the bootstrap capacitor can be charged with an opportunity to ensure that the bootstrap capacitor can work normally.
- the above method further includes: acquiring a voltage comparison result between the input voltage and the output voltage of the voltage conversion module, and controlling the voltage conversion module to operate in a boost mode, a buck mode, and a boost mode according to the voltage comparison result. at least one of the buck modes.
- the step of controlling the voltage conversion module to operate in at least one of the boost mode, the buck mode, and the buck-boost mode according to the voltage comparison result includes: if the voltage comparison result is that the input voltage is less than the output voltage, and The difference between the output voltage and the input voltage is greater than the first threshold, the voltage conversion module is controlled to work in the boost mode, and if the voltage comparison result is that the input voltage is greater than the output voltage, and the difference between the input voltage and the output voltage is greater than With the second threshold value, the voltage conversion module is controlled to work in a step-down mode.
- the step of controlling the voltage conversion module to operate in at least one of a boost mode, a buck mode, and a buck-boost mode according to the voltage comparison result further includes: if the voltage comparison result is that the input voltage and the output The absolute value of the difference between the voltages is less than the third threshold, then the first switch, the second switch, the third switch and the fourth switch are controlled to switch between the on state and the off state at the first switching frequency, so that the The voltage conversion module works in a buck-boost mode.
- the working mode of the voltage conversion module can be switched according to the voltage comparison result, and in each working mode, the four switches are kept in a state of constantly switching between on and off, and the control module Only the switching frequency of each switch needs to be controlled, the control mode of each switch is simplified, the circuit design is simplified, the cost is reduced, the switching loss of the circuit can be reduced, and the product performance can be improved.
- an electronic device 900 including a processor 910 and a memory 920 , where a computer program is stored in the memory 920 , and when the computer program is executed by the processor 910 , the processor 910 The method as described in each of the above embodiments is implemented.
- the embodiments of the present application disclose a computer-readable storage medium, which stores a computer program, wherein, when the computer program is executed by a processor, the methods described in the foregoing embodiments are implemented.
- the embodiments of the present application disclose a computer program product, the computer program product includes a non-transitory computer-readable storage medium storing a computer program, and the computer program can be executed by a processor to implement the methods described in the foregoing embodiments.
- the processes in the methods of the above embodiments can be implemented by instructing relevant hardware through a computer program, and the program can be stored in a non-volatile computer-readable storage medium , when the program is executed, it may include the flow of the above-mentioned method embodiments.
- the storage medium may be a magnetic disk, an optical disk, a read-only memory (Read-Only Memory, ROM), and the like.
- Nonvolatile memory may include ROM, Programmable ROM (PROM), Erasable PROM (Erasable PROM, EPROM), Electrically Erasable PROM (EEPROM), or flash memory.
- Volatile memory may include random access memory (RAM), which acts as external cache memory.
- RAM is available in various forms, such as Static RAM (SRAM), Dynamic Random Access Memory (DRAM), Synchronous DRAM (SDRAM), Double Data Rate SDRAM ( Double Data Rate SDRAM, DDR SDRAM), Enhanced SDRAM (Enhanced Synchronous DRAM, ESDRAM), Synchlink DRAM (Synchlink DRAM, SLDRAM), Memory Bus Direct RAM (Rambus DRAM, RDRAM) and Direct Memory Bus Dynamic RAM (Direct Rambus DRAM, DRDRAM).
- SRAM Static RAM
- DRAM Dynamic Random Access Memory
- SDRAM Synchronous DRAM
- SDRAM Double Data Rate SDRAM
- DDR SDRAM Double Data Rate SDRAM
- Enhanced SDRAM Enhanced Synchronous DRAM
- ESDRAM Double Data Rate SDRAM
- Synchlink DRAM Synchlink DRAM
- Memory Bus Direct RAM Rabus DRAM, RDRAM
- Direct Memory Bus Dynamic RAM Direct Rambus DRAM, DRDRAM
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Abstract
本申请实施例公开了一种开关控制电路、电子设备及开关控制方法。该开关控制电路包括电压变换模块及控制模块,电压变换模块,用于接收输入电压,并基于输入电压工作在升压模式、降压模式及升降压模式中的至少一种模式,控制模块用于分别控制电压变换模块中的第一开关、第二开关、第三开关及第四开关的开关频率,在电压变换模块工作在升压模式时,第一开关及第三开关以第一开关频率在导通状态与断开状态之间切换,在电压变换模块工作在降压模式时,第二开关及第四开关以第一开关频率在导通状态与断开状态之间切换。上述的开关控制电路、电子设备及开关控制方法,能够简化开关控制电路,降低了成本,且可降低开关损耗。
Description
本申请要求于2021年05月07日提交、申请号为202110497098.6、发明名称为“开关
控制电路、电子设备及开关控制方法”的中国专利申请的优先权,其全部内容通过引用结
合在本申请中。
本申请涉及电子电路技术领域,具体涉及一种开关控制电路、电子设备及开关控制方法。
目前市面上的很多电子产品中均用到了由四开关组成的双桥臂的电路,为实现电压调制、变换等功能,例如四开关式的Buck-Boost(升降压)电路等。四开关组成的双桥臂的电路通常可工作在多种不同的工作模式下,不同工作模式下需要导通和闭合的开关不同,因此需要设计相应的控制电路来控制各个开关在不同工作模式下的导通及闭合。目前控制电路的设计复杂,成本较高。
发明内容
本申请实施例公开了一种开关控制电路、电子设备及开关控制方法,能够简化对各个开关的控制方式,以简化开关控制电路,降低了成本,且可降低开关损耗。
本申请实施例公开了一种开关控制电路,包括:
电压变换模块,包括组成第一桥臂的第一开关及第三开关,以及组成第二桥臂的第二开关及第四开关,用于接收输入电压,并基于所述输入电压工作在升压模式、降压模式及升降压模式中的至少一种模式;
控制模块,用于控制所述第一开关及所述第三开关以第一开关频率在导通状态与断开状态之间切换,所述第二开关及所述第四开关以第二开关频率在导通状态与断开状态之间切换,以使所述电压变换模块工作在所述升压模式,对所述输入电压进行升压变换;以及用于控制所述第一开关及所述第三开关以所述第二开关频率在导通状态与断开状态之间切换,所述第二开关及所述第四开关以所述第一开关频率在导通状态与断开状态之间切换,以使所述电压变换模块工作在所述降压模式,对所述输入电压进行降压变换,所述第一开关频率小于所述第二开关频率。
本申请实施例公开了一种电子设备,包括如上所述的开关控制电路。
本申请实施例公开了一种开关控制方法,包括:
通过电压变换模块对接收的输入电压进行变换,得到输出电压;所述电压变换模块包括组成第一桥臂的第一开关及第三开关,以及组成第二桥臂的第二开关及第四开关,所述电压变换模块基于所述输入电压工作在升压模式、降压模式及升降压模式中的至少一种模式;
控制所述第一开关及所述第三开关以第一开关频率在导通状态与断开状态之间切换,所述第二开关及所述第四开关以第二开关频率在导通状态与断开状态之间切换,以使所述电压变换模块工作在所述升压模式,对所述输入电压进行升压变换;
控制所述第一开关及所述第三开关以所述第二开关频率在导通状态与断开状态之间切换,所述第二开关及所述第四开关以所述第一开关频率在导通状态与断开状态之间切换,以使所述电压变换模块工作在所述降压模式,对所述输入电压进行降压变换,所述第一开关频率小于所述第二开关频率。
本申请实施例公开了一种电子设备,包括存储器及处理器,所述存储器中存储有计算机程序,所述计算机程序被所述处理器执行时,使得所述处理器实现如上所述的方法。
本申请实施例公开了一种计算机可读存储介质,其上存储有计算机程序,所述计算机程序被处理器执行时实现如上所述的方法。
本申请的一个或多个实施例的细节在下面的附图和描述中提出。本申请的其它特征和有益效果将从说明书、附图以及权利要求书中体现。
为了更清楚地说明本申请实施例中的技术方案,下面将对实施例中所需要使用的附图作简单地介绍,显而易见地,下面描述中的附图仅仅是本申请的一些实施例,对于本领域普通技术人员来讲,在不付出创造性劳动的前提下,还可以根据这些附图获得其他的附图。
图1为相关技术中Buck-Boost电路的电路结构图;
图2为一个实施例中开关控制电路的结构框图;
图3为另一个实施例中开关控制电路的结构框图;
图4A为一个实施例中第一驱动电路的结构框图;
图4B为一个实施例中开关控制电路的电路结构图;
图4C为一个实施例中第二驱动电路的结构框图;
图5为另一个实施例中开关控制电路的结构框图;
图6为另一个实施例中开关控制电路的结构框图;
图7A为另一个实施例中开关控制电路的结构示意图;
图7B为另一个实施例中开关控制电路的结构示意图;
图8为一个实施例中开关控制方法的流程图;
图9为一个实施例中电子设备的结构框图。
下面将结合本申请实施例中的附图,对本申请实施例中的技术方案进行清楚、完整地描述,显然,所描述的实施例仅是本申请一部分实施例,而不是全部的实施例。基于本申请中的实施例,本领域普通技术人员在没有做出创造性劳动前提下所获得的所有其他实施例,都属于本申请保护的范围。
需要说明的是,本申请实施例及附图中的术语“包括”和“具有”以及它们任何变形,意图在于覆盖不排他的包含。例如包含了一系列步骤或单元的过程、方法、***、产品或设备没有限定于已列出的步骤或单元,而是可选地还包括没有列出的步骤或单元,或可选地还包括对于这些过程、方法、产品或设备固有的其它步骤或单元。
可以理解,本申请所使用的术语“第一”、“第二”等可在本文中用于描述各种元件,但这些元件不受这些术语限制。这些术语仅用于将第一个元件与另一个元件区分。举例来说,在不脱离本申请的范围的情况下,可以将第一开关称为第二开关,且类似地,可将第二开关称为第一开关。第一开关和第二开关两者都是开关,但其不是同一个的开关。
目前市面上的很多电子产品中均用到了由四开关组成的双桥臂的电路,例如四开关式的Buck-Boost电路、四开关组成的直流电机H桥驱动电路等,四开关组成的双桥臂的电路通常可工作在多种不同的工作模式下,不同工作模式下需要导通和闭合的开关不同。在某些工作模式下,需要保持某一桥臂的上半部分的开关处于一直导通的状态,因此需要设计单独的驱动电路来实现该功能,导致电路的设计复杂,成本高。
以图1所示的Buck-Boost电路为例,在Buck-Boost电路处于Buck模式(降压模式)时,左桥臂(与输入端VIN连接)上的开关S1及S3需要保持频繁的开关状态,不断在导 通状态与断开状态来回切换,为了减少开关损耗,右桥臂(与输出端VOUT连接)的开关S2需要一直保持导通状态,S4则一直处于断开状态。在Buck-Boost电路处于Boost模式(升压模式)时,为了减少开关损耗,左桥臂上的开关S1需要一直保持导通状态,S2则一直处于断开状态,右桥臂上的开关S2、S4则需要保持频繁的开关状态,不断在导通状态与断开状态来回切换。
在传统的方式中,为了使得Buck-Boost电路在Buck模式或Boost模式下,S1或S2能够一直保持导通状态,需要增加额外的独立驱动电路,例如图1中需要在左右桥臂分别增加两个独立的电荷泵驱动电路,电荷泵驱动电路能够为S1、S2提供电压以使得S1在Boost模式下一直保持导通状态、S2在Buck模式一直保持导通状态。或者是需要在控制器内部单独做一部分电路来实现S1或S2的常导通功能,因此,导致整个控制电路设计复杂,且成本高。
如图2所示,在一个实施例中,提供一种开关控制电路20,该开关控制电路20可包括电压变换模块210及控制模块220。其中,电压变换模块210可包括第一开关211、第二开关212、第三开关213及第四开关214。第一开关211及第三开关213可组成第一桥臂,第一开关211可与电压变换模块210的输入端(VIN)连接,第三开关213可接地。第二开关212及第四开关214可组成第二桥臂,第二开关212可与电压变换模块210的输出端(VOUT)连接,第四开关214可接地。
电压变换模块210,用于接收输入电压,并基于所述输入电压工作在升压模式、降压模式及升降压模式中的至少一种模式。
电压变换模块210可对接收的输入电压进行变换,得到输出电压,该输入电压可为直流电压,如输入电压可为脉冲直流电压,或是较为不稳定的直流电,其中,脉动直流电压指的是方向不变,但大小随时间作周期性变化的直流电压,输入电压的脉动波有可包括方波波形、馒头波波形等。输出电压可为稳定的直流电压,如输出电压可以是恒定直流电压或是近似恒定的直流电压(波幅极小),恒定直流电压指的是电压固定的直流电压。电压变换模块210可对输入的输入电压进行变换,得到稳定的输出电压并输出。
电压变换模块210可基于输入电压工作在不同的工作模式中切换,该工作模式可包括升压模式、降压模式及升降压模式等,在输入电压过低时,电压变换模块210工作在升压模式,从而电压变换模块210可对接收的输入电压进行升压变换。在输入电压过高时,电压变换模块210工作在降压模式,从而电压变换模块210可对输入电压进行降压变换,从而可保证电压变换模块输出的输出电压稳定。
控制模块220,用于控制第一开关211及第三开关213以第一开关频率在导通状态与断开状态之间切换,控制第二开关212及第四开关214以第二开关频率在导通状态与断开状态之间切换,以使电压变换模块210工作在升压模式,对输入电压进行升压变换。
控制模块220,还用于控制第一开关211及第三开关213以第二开关频率在导通状态与断开状态之间切换,控制第二开关212及第四开关214以第一开关频率在导通状态与断开状态之间切换,以使电压变换模块210工作在降压模式,对输入电压进行降压变换。
在一些实施例中,电压变换模块210可包括Buck-Boost电路,Buck-Boost电路可将过高或过低的直流电压均转换为稳定的直流电压。电压变换模块210可包括电感L1,第一桥臂与第二桥臂可通过该电感L1连接,以形成类似字母“H”形状的电路。
控制模块220可包括但不限于CPU(central processing unit,中央处理器)、MCU(Microcontroller Unit,微控制单元)等处理芯片等。在一些实施例中,控制模块220可根据输入到电压变换模块210的输入电压,与电压变换模块210输出的输出电压之间的电压比较结果,对电压变换模块210的工作模式进行切换。可选地,在输入电压过低时,控制 模块220可控制电压变换模块210工作在升压模式。在输入电压过高时,控制模块220可控制电压变换模块工作在降压模式。
在本申请实施例中,控制模块220可根据电压变换模块210当前所需的工作模式,分别控制第一开关211、第二开关212、第三开关213及第四开关214的开关频率,该开关频率可指的是开关在单位时间内的开关次数,该开关次数可以是单位时间内切换至导通状态的次数,也可以是单位时间内切换至断开状态的次数。开关频率可用于表征开关在导通状态及断开状态之间进行切换的速度,开关频率越高,切换的速度越快,开关进行导通及断开的切换越频繁,开关频率越低,切换的速度越慢,开关进行导通及断开的切换次数越少,且每次处于导通状态或断开状态的时间越长。
在电压变换模块210工作在升压模式时,第一开关211需要保持常导通,第三开关213需要保持常断开,第二开关212及第四开关214则需要频繁地切换导通及断开,以实现对输入的输入电压的升压变换。
控制模块220可控制第一开关211及第三开关213以第一开关频率进行工作,第二开关212及第四开关214以第二开关频率进行工作。该第一开关频率可小于第二开关频率,例如,第一开关频率可为2KHz(千赫兹)、3KHz、2.34KHz等,第二开关频率可为2MHz(兆赫兹)、3MHz、3.43MHz等,其具体数值在本申请实施例中不作限定。通过降频的方式,可使得第一开关211及第三开关213处于极低频率的开关工作状态,从而使得第一开关211能够实现常导通的功能,通过第二开关212及第四开关214高频率地在导通状态及断开状态之间切换,实现对输入的输入电压的斩波调制,并利用电感L1进行升压,以得到稳定的输出电压,保证电压变换模块210正常工作在升压模式下。
在电压变换模块210工作在降压模式时,第一开关211及第三开关212需要频繁地切换导通及断开,第二开关212需要保持常导通,第三开关213需要保持常断开,以实现对输入的输入电压的降压变换。
控制模块220可控制第一开关211及第三开关213以第二开关频率进行工作,第二开关212及第四开关214以第一开关频率进行工作。通过降频的方式,可使得第二开关212及第四开关214处于极低频率的开关工作状态,从而使得第二开关211能够实现常导通的功能,通过第一开关211及第三开关213高频率地在导通状态及断开状态之间切换,实现对输入的输入电压的斩波调制,并利用电感L1进行降压,以得到稳定的输出电压,保证电压变换模块210正常工作在降压模式下。
在本申请实施例中,不论是在升压模式下还是降压模式下,电压变换模块210的四个开关均一直处于在导通与断开之间不断切换的状态,控制模块只需要控制各个开关的开关频率,简化了对各个开关的控制方式,且不需要设计独立的驱动电路或控制电路来使得第一开关211或第二开关212一直保持导通状态,简化了开关控制电路,降低了电路成本。
而且,在电压变换模块210工作在升压模式时,第一开关211及第三开关213能够以较低的第一开关频率工作,在电压变换模块210工作在降压模式时,第二开关212及第四开关214能够以较低的第一开关频率工作,能够降低开关的损耗,提高了开关控制电路的产品性能。
在本申请实施例中,电压变换模块210中设置于同一桥臂上的开关不会同时开启或同时关闭,以保证电压变换模块210的正常工作。具体地,在第一开关211处于导通状态时,第三开关213处于断开状态,在第一开关211处于断开状态时,第三开关213处于导通状态。在第二开关212处于导通状态时,第四开关214处于断开状态,在第二开关212处于断开状态时,第四开关214处于导通状态。
在升压模式下,第一开关211处于导通状态的导通时长大于处于断开状态的断开时长, 第三开关213处于断开状态的断开时长大于处于导通状态的导通时长,第一开关211的导通时长等于第三开关213的断开时长。可保证第一开关211在升压模式下大部分时间处于导通状态,满足升压模式下对于第一开关211的常导通、第三开关213的常关闭需求。可选地,在升压模式下,第二开关212和第四开关214处于导通状态的导通时长与处于断开状态的断开时长可接近或相同。
在降压模式下,第二开关212处于导通状态的导通时长大于处于断开状态的断开时长,第四开关214处于断开状态的断开时长大于处于导通状态的导通时长,第二开关212的导通时长等于第四开关214的断开时长。可保证第二开关212在降压模式下大部分时间处于导通状态,满足降压模式下对于第二开关212的常导通、第四开关214的常关闭需求。可选地,在降压模式下,第一开关211和第三开关213处于导通状态的导通时长与处于断开状态的断开时长可接近或相同。
如图3所示,在一个实施例中,上述的开关控制电路20,除了包括电压变换模块210及控制模块220以外,还包括第一驱动电路230及第二驱动电路240。其中,第一驱动电路230可与第一开关211连接,第二驱动电路240可与第二开关212连接,第一驱动电路230的输入端、第二驱动电路240的输入端可与控制模块220的输出端连接。
控制模块220,还用于若电压变换模块210工作在升压模式,则按照第一开关频率向第一驱动电路230发送第一脉冲信号,以及若电压变换模块210工作在为降压模式,则按照第一开关频率向第二驱动电路240发送第一脉冲信号。
在电压变换模块210处于升压模式时,控制模块220可向第一驱动电路230发送第一脉冲信号,在电压变换模块210处于降压模式时,控制模块220可向第二驱动电路240发送第一脉冲信号。该第一脉冲信号的脉冲频率可为上述的第一开关频率,该脉冲频率可指的是单位时间内包含的脉冲周期的数量,一个脉冲周期可包括第一电平信号及第二电平信号,例如,第一电平信号可为高电平信号,第二电平信号可为低电平信号,或第一电平信号为低电平信号,第二电平信号为高电平信号等。
在第一脉冲信号中,第一电平信号在一个脉冲周期内所占的时间比率大于第二电平信号所占的时间比率,其中,第一电平信号可为能够触发第一驱动电路230或第二驱动电路240输出驱动电压的电平,第二电平信号可以是触发第一开关211或第二开关212处于断开状态的电平。该第一电平信号可为高电平信号,也可为低电平信号,具体可取决于第一驱动电路230及第二驱动电路240中的具体电路结构。
第一驱动电路230,用于在接收的第一脉冲信号为第一电平信号时,向第一开关211提供驱动电压,以驱动第一开关211保持导通状态。
第二驱动电路240,用于在接收的第一脉冲信号为第一电平信号时,向第二开关212提供驱动电压,以驱动第二开关保持导通状态。
由于在第一脉冲信号的脉冲周期内,第一电平信号所占的时间比率大于第二电平信号所占的时间比率,第一电平信号所占的时间比率可为第一电平信号在一个脉冲周期内的时长占整个脉冲周期时长的百分比,第二电平信号所占的时间比率为第二电平信号在一个脉冲周期内的时长占整个脉冲周期时长的百分比。例如,第一电平信号所占的时间比率为90%、88%等,第二电平信号所占的时间比率相应地可为10%、12%等,该第一电平信号所占的时间比率可根据实际需求进行设置,在此不作限定。因此,可保证第一开关211在升压模式下处于长时间的导通状态,第二开关212在降压模式下处于长时间的导通状态,保证了电压变换模块210在不同工作模式下的正常工作。
图4A为一个实施例中第一驱动电路的结构框图。在一个实施例中,如图4A所示,第一驱动电路230可包括第五开关232、第六开关234及第一电容236,其中,第五开关232、 第六开关234可分别与控制模块220连接,第一电容236的第一端可通过第五开关232与第一开关211连接,第一电容236的第二端与第六开关234连接。
第五开关232,用于在控制模块220发送的第一脉冲信号为第一电平信号时,处于导通状态,在控制模块220发送的第一脉冲信号为第二电平信号时,处于断开状态。
第六开关234,用于在控制模块220发送的第一脉冲信号为第二电平信号时,处于导通状态,在控制模块220发送的第一脉冲信号为第一电平信号时,处于断开状态。
第一电容236,用于在第五开关232处于导通状态时,向第一开关211提供驱动电压,以驱动第一开关211处于导通状态。
第五开关232及第六开关234可以推挽方式存在于电路中,在第五开关232及第六开关234工作的过程中,仅有一个开关可处于导通状态,以提高电路的驱动力。
在一些实施例中,第一电容236的第一端还与电源端连接,第一电容236的第二端还与第三开关213连接。第一电容,还用于第五开关232处于断开状态且第三开关213处于导通状态时,根据电源端提供的电压进行充电。
图4B为一个实施例中开关控制电路的电路结构图。如图4B所示,在一个实施例中,上述的第一开关211、第二开关212、第三开关213及第四开关214可均为N型的MOS管(MOSFET,金属-氧化物半导体场效应晶体管),其中,第一开关211可包括第一场效应管Q1,第二开关212可包括第二场效应管Q2,第三开关213可包括第三场效应管Q3,第四开关214可包括第四场效应管Q4。
第一驱动电路230可包括第五开关Q11、第六开关Q12及第一电容C11,第一电容C11的第一端可通过第五开关Q11与第一场效应场Q1的栅极(G极)连接,进一步地,第五开关Q11可为P型的MOS管,第六开关Q12可为N型MOS管。第五开关Q11的G极可与控制模块220的输出端连接,第五开关Q11的源极(S极)可与第六开关Q12的漏极(D极)连接、以及与第一场效应场Q1的G极连接,第五开关Q11的D极可与第一电容C11的第一端连接。
第一场效应场Q1的D极可与输入端(VIN)连接,第一场效应场Q1的S极可与第三开关213(即图4B中的第三场效应管Q3)、第六开关Q12及第一电容C11的第二端连接。
在第三场效应管Q3导通时,由于第三场效应管Q3的S极接地,因此,s1点的电压可为0V(伏)。在升压模式下,在控制模块220向第五开关Q11及第六开关Q12输出的第一脉冲信号为低电平信号时,第五开关Q11导通,第六开关Q12断开,此时第三场效应管Q3断开。由于第一电容C11为充满电的状态,因此a点的电压会高于s1点的电压,也即,第一场效应管Q1的G极电压高于S极电压,且第一场效应管Q1的G极与S极之间的压差为第一电容C11的电压,从而可触发第一场效应管Q1导通。
在第一场效应管Q1导通后,s1点的电压会提升,并与输入端VIN的电压拉平,此时a点的电压会变为输入端VIN的电压与第一电容C11的电压之和,因此,a点的电压会高于s1点的电压,第一场效应管Q1的G极与S极之间的压差依然为第一电容C11的电压,第一场效应管Q1继续保持导通状态。第一电容C11作为自举电容,利用电容两端不能突变的特征,第一电容C11可向第一场效应管Q1的G极提供驱动电压,使得G极电压大于S极电压且二者的压差大于一定的值(例如5V等),使第一场效应管Q1保持导通。
在一些实施例中,由于第一电容C11的电压会逐渐下降,因此在第一场效应管Q1导通的一段时间后,控制模块220向第五开关Q11及第六开关Q12输出的第一脉冲信号变为高电平信号,此时,第五开关Q11断开,第六开关Q12导通,即断开第一场效应管Q1,并导通第三场效应管Q3,电源端VCC可对第一电容C11进行充电。
作为一种具体实施方式,可如图4B所示,第一驱动电路230还包括第一二极管D1, 第一电容C11的第一端可与第一二极管D1的负极连接,第一二极管D1的正极可与电源端VCC连接。在第三开关213(即图4B中的第三场效应管Q3)处于导通状态时,电源端VCC通过该第一二极管D1向第一电容C11充电。在第一电容C11的电压下降后,电源端VCC的电压会大于a点的电压,第一二极管D1导通,电源端VCC向第一电容C11充电,第一电容C11的电压逐渐上升,a点的电压逐渐升压,第一二极管D1截止,则电源端VCC停止向第一电容C11充电,使得第一电容C11的电压与电源端VCC的电压相同。且在第一电容C11放电,触发第一场效应管Q1导通时,a点的电压会大于电源端VCC的电压,利用第一二极管可防止第一电容C11的电压向电源端VCC输出,保护了电路安全,且防止第一电容C11的电能出现不必要的损失。
在本申请实施例中,第一电容C11能够给第一开关211提供驱动电压,保持第一开关211在升压模式下的大部分时间处于开通状态,具有非常高的导通占比。且由于电压变换模块210中的四个开关均处于不断在导通状态与断开状态之间切换的工作状态,因此在第三开关213导通后,能够给第一电容C11充电的机会,保证了第一电容C11作为自举电容能够正常工作。
该第一驱动电路230仅是在相关技术中的半桥驱动方式(即上述的第五开关Q11及第六开关Q12)下增加了第一电容C11及第一二极管D1,大大简化了驱动电路的设计,能够省去隔离驱动或是电荷泵驱动等,即可实现电压变换模块210在不同工作模式下的自由切换,简化了开关控制电路的设计,降低电路的复杂度和成本,同时保证了产品的效率基本不受影响。此外,由于电压变换模块210在不同工作模式下,四个开关均处于不断在导通状态与断开状态之间切换的工作状态,电压变换模块210在进行模式切换时会更加平滑,提高了产品性能。
可选地,电容C1及电容C2可用于对电压进行滤波处理,以保证输出电压稳定。
图4C为一个实施例中第二驱动电路的结构框图。在一个实施例中,如图4C所示,第二驱动电路240可包括第七开关242、第八开关244及第二电容246,其中,第七开关242、第八开关244可分别与控制模块220连接,第二电容246的第一端可通过第七开关242与第二开关212连接,第二电容246的第二端与第八开关244连接。
第七开关242,用于在控制模块220发送的第一脉冲信号为第一电平信号时,处于导通状态,在控制模块220发送的第一脉冲信号为第二电平信号时,处于断开状态。
第八开关244,用于在控制模块220发送的第一脉冲信号为第二电平信号时,处于导通状态,在控制模块220发送的第一脉冲信号为第一电平信号时,处于断开状态。
第二电容246,用于在第七开关242处于导通状态时,向第二开关212提供驱动电压,以驱动第二开关212处于导通状态。
在一些实施例中,第二电容246的第一端还与电源端连接,第二电容246的第二端还与第四开关214连接。第二电容246,还用于第七开关242处于断开状态且第四开关214处于导通状态时,根据电源端提供的电压进行充电。
在一个实施例中,如图4B所示,第二驱动电路240可包括第七开关Q21、第八开关Q22及第二电容C21,第一电容C21的第一端可通过第七开关Q21与第二场效应场Q2的G极连接,进一步地,第七开关Q21可为P型的MOS管,第八开关Q22可为N型的MOS管。第七开关Q21的G极可与控制模块220的输出端连接,第七开关Q21的S极可与第八开关Q22的D极连接、以及与第二场效应场Q2的G极连接,第七开关Q21的D极可与第二电容C21的第一端连接。
第二场效应场Q2的D极可与输出端(VOUT)连接,第二场效应场Q2的S极可与第四开关214(即图4B中的第四场效应管Q4)、第八开关Q22的S极、第二电容C21的第 二端连接。
在第四场效应管Q4导通时,由于第四场效应管Q4的S极接地,因此,s2点的电压可为0V。在降压模式下,在控制模块220向第七开关Q21及第八开关Q22输出的第一脉冲信号为低电平信号时,第七开关Q21导通,第八开关Q22断开,此时第四场效应管Q4断开。由于第二电容C21为充满电的状态,因此b点的电压会高于s2点的电压,也即,第二场效应管Q2的G极电压高于S极电压,且第二场效应管Q2的G极与S极之间的压差为第二电容C21的电压,从而可触发第二场效应管Q2导通。
在第二场效应管Q2导通后,s2点的电压会提升,并与输出端VOUT的电压拉平,此时b点的电压会变为输出端VOUT的电压与第二电容C21的电压之和,因此,b点的电压会高于s2点的电压,第二场效应管Q2的G极与S极之间的压差依然为第二电容C21的电压,第二场效应管Q2继续保持导通状态。第二电容C21作为自举电容,利用电容两端不能突变的特征,第二电容C21可向第二场效应管Q2的G极提供驱动电压,使得G极电压大于S极电压且二者的压差大于一定的值(例如5V等),使第二场效应管Q2保持导通。
在一些实施例中,由于第二电容C21的电压会逐渐下降,因此在第二场效应管Q2导通的一段时间后,控制模块220向第七开关Q21及第八开关Q22输出的第一脉冲信号变为高电平信号,此时,第七开关Q21断开,第八开关Q22导通,即断开第二场效应管Q2,并导通第四场效应管Q4,电源端VCC可对第二电容C21进行充电。
作为一种具体实施方式,可如图4B所示,第二驱动电路240还包括第二二极管D2,第二电容C21的第一端可与第二二极管D2的负极连接,第二二极管D2的正极可与电源端VCC连接。在第四开关214(即图4B中的第三场效应管Q4)处于导通状态时,电源端VCC通过该第二二极管D2向第二电容C21充电。在第二电容C21的电压下降后,电源端VCC的电压会大于b点的电压,第二二极管D2导通,电源端VCC向第二电容C21充电,第二电容C21的电压逐渐上升,b点的电压逐渐升压,第二二极管D2截止,则电源端VCC停止向第二电容C21充电,使得第二电容C21的电压与电源端VCC的电压相同。且在第二电容C21放电,触发第二场效应管Q2导通时,b点的电压会大于电源端VCC的电压,利用第二二极管可防止第二电容C21的电压向电源端VCC输出,保护了电路安全,且防止第二电容C21的电能出现不必要的损失。
在本申请实施例中,第二电容C21能够给第二开关212提供驱动电压,保持第二开关212在降压模式下的大部分时间处于开通状态,具有非常高的导通占比。且由于电压变换模块210中的四个开关均处于不断在导通状态与断开状态之间切换的工作状态,因此在第四开关214导通后,能够给第二电容C21充电的机会,保证了第二电容C21作为自举电容能够正常工作。
该第二驱动电路240与第一驱动电路230相同,大大简化了驱动电路的设计,降低电路的复杂度和成本,同时保证了产品的效率基本不受影响。
需要说明的是,上述的第五开关Q11也可为N型的MOS管,第六开关Q12可为P型的MOS管,则在控制模块220发送的第一脉冲信号为高电平信号时,第五开关Q11导通,第六开关Q12断开,并触发第一场效应管Q1导通。同理,上述的第七开关Q21也可为N型的MOS管,第八开关Q22可为P型的MOS管,则在控制模块220发送的第一脉冲信号为高电平信号时,第七开关Q21导通,第八开关Q22断开,并触发第二场效应管Q2导通。能够触发第五开关Q11及第七开关Q21导通的电平信号即为第一电平信号,该第一电平信号在一个脉冲周期内的时间占比可为较高的值,例如90%、91%等,从而可保证桥臂上半部分的开关近似于一直导通。
可选地,上述的第五开关Q11、第六开关Q12、第七开关Q21、第八开关Q22等也可 以是其它开关管,例如三极管等,并不限于MOS管。
如图5所示,在一个实施例中,开关控制电路20除了包括电压变换模块210、控制模块220、第一驱动电路230及第二驱动电路240以外,还可包括反向模块250、第三驱动电路260及第四驱动电路270。其中,第三驱动电路260与第三开关213连接,第四驱动电路270与第四开关270连接,该反向模块250可分别与控制模块220、第三驱动电路260及第四驱动电路270连接。
反向模块250,还用于对控制模块220输出的第一脉冲信号进行反向,得到第二脉冲信号,若确定的工作模式为升压模式,则向第三驱动电路260发送第二脉冲信号,以及若确定的工作模式为降压模式,则向第四驱动电路270发送第二脉冲信号。
第三驱动电路260,用于在接收的第二脉冲信号为第一电平信号时,驱动第三开关213保持导通状态。
第四驱动电路270,用于在接收的第二脉冲信号为第一电平信号时,驱动第四开关214保持导通状态。
反向模块250可对控制模块220向第一开关211输出的脉冲信号进行反向,并将反向后的脉冲信号输出给第三开关213,同时可对控制模块220向第二开关212输出的脉冲信号进行反向,并将反向后的脉冲信号输出给第四开关214。利用反向模块250,可保证同一桥臂上的两个开关在同一时刻接收到的脉冲信号是反向的脉冲信号,同一桥臂上的两个开关不会同时导通或断开。
例如,在升压模式下,控制模块220向第一驱动电路230输出脉冲频率为第一开关频率的第一脉冲信号,该第一脉冲信号可同时被输入反向模块250,反向模块250进行反向后可得到脉冲频率为第一开关频率的第二脉冲信号,并将该第二脉冲信号输入到第三驱动电路260,第二脉冲信号与第一脉冲信号反向。同时,在升压模式下,控制模块220向第二驱动电路240输出脉冲频率为第二开关频率的第三脉冲信号,该第三脉冲信号可同时被输入反向模块250,反向模块250进行反向后可得到脉冲频率为第二开关频率的第四脉冲信号,并将该第四脉冲信号输入到第四驱动电路270,第三脉冲信号与第四脉冲信号反向。以保证第二开关212及第四开关214在升压模式下以第二开关频率进行导通状态及断开状态的切换
又例如,在降压模式下,控制模块220向第二驱动电路240输出脉冲频率为第一开关频率的第一脉冲信号,该第一脉冲信号可同时被输入反向模块250,反向模块250进行反向后可得到脉冲频率为第一开关频率的第二脉冲信号,并将该第二脉冲信号输入到第四驱动电路270。同时,在降压模式下,控制模块220向第一驱动电路230输出脉冲频率为第二开关频率的第三脉冲信号,该第三脉冲信号可同时被输入反向模块250,反向模块250进行反向后可得到脉冲频率为第二开关频率的第四脉冲信号,并将该第四脉冲信号输入到第三驱动电路260,以保证第一开关211及第三开关213在降压模式下以第二开关频率进行导通状态及断开状态的切换。
可选地,上述的第三驱动电路260及第四驱动电路260可为推挽输出驱动电路,均可包含一对对称的开关管(具体的电路结构可参考图4B中的第五开关Q11及第六开关Q12),该对称的开关管中每次仅有一个导通,以形成推挽驱动,提高了开关速度。与第一驱动电路230及第二驱动电路240的区别在于,第三开关213及第四开关214不需要保持常导通的状态,因此不需要有自举电容提供电能,以驱动第三开关213及第四开关214长时间保持导通状态。
需要说明的是,上述的反向模块250也可集成在控制模块220内部,控制模块220可将输出的脉冲信号先在内部进行反向后,再分别输出两路反向的脉冲信号,可保证同一桥 臂上的两个开关同步接收到电平不同的信号。
在一个实施例中,控制模块220,还用于获取输入电压与电压变换模块210的输出电压之间的电压比较结果,根据电压比较结果控制电压变换模块210工作在升压模式、降压模式及升降压模式中的至少一种模式。
如图6所示,在一个实施例中,上述的开关控制模块还可包括电压采集模块280,该电压采集模块280可分别与电压变换模块210的输入端VIN及输出端VOUT连接。电压采集模块280的输出端可与控制模块220的输入端连接。
电压采集模块280可用于采集电压变换模块210的输入端输入的输入电压,以及采集电压变换模块210的输出端输出的输出电压,并将输入电压与输出电压进行比较,得到电压比较结果。电压采集模块280在得到电压比较结果后,可将电压比较结果发送给控制模块220。
控制模块220,还用于若电压比较结果为输入电压小于输出电压,且输出电压与输入电压之间的差值大于第一阈值,则控制电压变换模块210工作在升压模式,以及若电压比较结果为输入电压大于输出电压,且输入电压与输出电压之间的差值大于第二阈值,则控制电压变换模块210工作在降压模式。
上述的第一阈值与第二阈值可根据实际需求进行设置,在此不作限定,例如第一阈值为5V,第二阈值为10V等,或是第一阈值、第二阈值均为23V等。
控制模块220,还用于若电压比较结果为输入电压与输出电压之间的差值绝对值小于第三阈值,则控制第一开关211、第二开关212、第三开关213及第四开关214均以第一开关频率在导通状态与断开状态之间切换,以使电压变换模块210工作在升降压模式。若电压比较结果为输入电压与输出电压之间的差值绝对值小于第三阈值,可说明输入电压与输出电压之间较为接近,则可控制电压变换模块210在升降压模式下工作,电压变换模块210的四个开关均可以较低的第一开关频率进行工作,从而可降低电路的开关损耗,提升产品效率。
作为一种具体实施方式,上述的第一阈值、第二阈值及第三阈值可为相同的电压值,其具体数据在本申请实施例中不作限定。
在本申请实施例中,控制模块220可根据电压比较结果对电压变换模块210的工作模式进行切换,且在各个工作模式下均保持四个开关一直处于在导通与断开之间不断切换的状态,控制模块只需要控制各个开关的开关频率,简化了对各个开关的控制方式,精简了电路设计,降低了成本,且可降低电路的开关损耗,提高了产品性能。
图7A为另一个实施例中开关控制电路的结构示意图。如图7所示,该开关控制电路20可包括有2个LMG芯片,每个LMG芯片内部可包含相应连接桥臂的上管驱动及下管驱动。以第一场效应管Q1、第三场效应管Q3为例,与其连接的LMG芯片内部可包括有上述的第五开关Q11、第六开关Q12、第三驱动电路260、第一二极管D1等,可向该LMG芯片输入两路反向的脉冲信号PWM1H及PWM2H,经由LMG芯片后,分别向第一场效应管Q1、第三场效应管Q3输出,以控制第一场效应管Q1、第三场效应管Q3导通或关闭。可选地,该LMG芯片也可换成其它驱动芯片,在此不作限定。
需要说明的是,本申请实施例提供的开关控制电路20并不仅仅可用于Buck-Boost电路,还可应用于其它需要实现半桥桥臂上管常开的功能电路,例如直流电机H桥驱动、BLDC电机驱动器等。图7B为另一个实施例中开关控制电路的结构示意图。如图7B所示,自举电容C11及自举电容C21可为左、右桥臂的上开关管Q1及Q2提供驱动电压,以保持Q1及Q2能够处于长时间的导通状态,精简了驱动电路,降低了成本。
在一个实施例中,提供一种电子设备,该电子设备可包括上述各实施例中所描述的开 关控制电路20。可选地,该电子设备可包括但不限于电源适配器、电机产品等,在此不作限定。
如图8所示,在一个实施例中,提供一种开关控制方法,可应用于上述的电子设备,该方法可包括以下步骤:
步骤810,通过电压变换模块对接收的输入电压进行变换,得到输出电压。
其中,电压变换模块包括组成第一桥臂的第一开关及第三开关,以及组成第二桥臂的第二开关及第四开关,电压变换模块基于该输入电压工作在升压模式、降压模式及升降压模式中的至少一种模式。
步骤820,控制第一开关及第三开关以第一开关频率在导通状态与断开状态之间切换,控制第二开关及第四开关以第二开关频率在导通状态与断开状态之间切换,以使电压变换模块工作在升压模式,对输入电压进行升压变换。
步骤830,控制第一开关及所述第三开关以第二开关频率在导通状态与断开状态之间切换,控制第二开关及第四开关以第一开关频率在导通状态与断开状态之间切换,以使电压变换模块工作在降压模式,对输入电压进行降压变换。
其中,第一开关频率小于第二开关频率。需要说明的是,步骤820与步骤830之间没有执行时序的限定,可以先执行步骤820,也可以先执行步骤830,取决于电压变换模块所需的工作模式。
在本申请实施例中,不论是在升压模式下还是降压模式下,电压变换模块2的四个开关均一直处于在导通与断开之间不断切换的状态,只需要控制各个开关的开关频率,简化了对各个开关的控制方式,且不需要设计独立的驱动电路或控制电路来使得第一开关或第二开关一直保持导通状态,简化了开关控制电路,降低了电路成本。
在一个实施例中,在第一开关处于导通状态时,第三开关处于断开状态,在第一开关处于断开状态时,第一开关处于导通状态;在升压模式下,第一开关处于导通状态的导通时长大于处于断开状态的断开时长。
在第二开关处于导通状态时,第四开关处于断开状态,在第二开关处于断开状态时,第四开关处于导通状态;在降压模式下,第二开关处于导通状态的导通时长大于处于断开状态的断开时长。
在一个实施例中,步骤控制第一开关及所述第三开关以第一开关频率在导通状态与断开状态之间切换,可包括:按照第一开关频率向第一驱动电路发送第一脉冲信号,以使第一驱动电路在第一脉冲信号为第一电平信号时,向第一开关提供驱动电压,以驱动第一开关保持导通状态。
步骤控制第二开关及所述第四开关以第一开关频率在导通状态与断开状态之间切换,包括:按照第一开关频率向第二驱动电路发送第一脉冲信号,以使第二驱动电路在第一脉冲信号为所述第一电平信号时,向第二开关提供驱动电压,以驱动第二开关保持导通状态。
其中,第一脉冲信号中,第一电平信号在一个脉冲周期内所占的时间比率大于第二电平信号所占的时间比率,第二电平信号用于触发第一开关或所述第二开关处于断开状态。
在一个实施例中,第一驱动电路包括第一电容。
步骤按照第一开关频率向第一驱动电路发送第一脉冲信号,以使第一驱动电路在第一脉冲信号为第一电平信号时,向第一开关提供驱动电压,以驱动第一开关保持导通状态,包括:按照第一开关频率向第一驱动电路发送第一脉冲信号,以使第一驱动电路在第一脉冲信号为第一电平信号时,通过第一电容向第一开关提供驱动电压,以驱动第一开关处于导通状态。
在一个实施例中,上述的方法还包括:在第一驱动电路接收到的第一脉冲信号为第二 电平信号时,通过电源端提供的电压对第一电容进行充电。
在一个实施例中,第二驱动电路包括第二电容。
步骤按照第一开关频率向第二驱动电路发送第一脉冲信号,以使第二驱动电路在第一脉冲信号为所述第一电平信号时,向第二开关提供驱动电压,以驱动第二开关保持导通状态,包括:按照第一开关频率向第二驱动电路发送第一脉冲信号,以使第二驱动电路在第一脉冲信号为第一电平信号时,通过第二电容向第二开关提供驱动电压,以驱动第一开关处于导通状态。
在一个实施例中,上述的方法还包括:在第二驱动电路接收到的第一脉冲信号为第二电平信号时,通过电源端提供的电压对第二电容进行充电。
在本申请实施例中,利用自举电容对相应的开关提供驱动电压,保证开关在大部分时间处于开通状态,具有非常高的导通占比。且由于电压变换模块中的四个开关均处于不断在导通状态与断开状态之间切换的工作状态,因此能够给自举电容充电的机会,保证了自举电容能够正常工作。
在一个实施例中,上述的方法还包括:获取输入电压与电压变换模块的输出电压之间的电压比较结果,根据所述电压比较结果控制电压变换模块工作在升压模式、降压模式及升降压模式中的至少一种模式。
在一个实施例中,步骤根据电压比较结果控制电压变换模块工作在升压模式、降压模式及升降压模式中的至少一种模式,包括:若电压比较结果为输入电压小于输出电压,且输出电压与输入电压之间的差值大于第一阈值,则控制电压变换模块工作在升压模式,以及若电压比较结果为输入电压大于输出电压,且输入电压与输出电压之间的差值大于第二阈值,则控制电压变换模块工作在降压模式。
在一个实施例中,步骤根据电压比较结果控制电压变换模块工作在升压模式、降压模式及升降压模式中的至少一种模式,还包括:若电压比较结果为输入电压与所述输出电压之间的差值绝对值小于第三阈值,则控制第一开关、第二开关、第三开关及第四开关均以第一开关频率在导通状态与断开状态之间切换,以使电压变换模块工作在升降压模式。
在本申请实施例中,可根据电压比较结果对电压变换模块的工作模式进行切换,且在各个工作模式下均保持四个开关一直处于在导通与断开之间不断切换的状态,控制模块只需要控制各个开关的开关频率,简化了对各个开关的控制方式,精简了电路设计,降低了成本,且可降低电路的开关损耗,提高了产品性能。
如图9所示,在一个实施例中,提供一种电子设备900,包括处理器910及存储器920,该存储器920中存储有计算机程序,该计算机程序被处理器910执行时,使得处理器910实现如上述各实施例中所描述的方法。
本申请实施例公开一种计算机可读存储介质,其存储计算机程序,其中,该计算机程序被处理器执行时实现如上述各实施例中描述的方法。
本申请实施例公开一种计算机程序产品,该计算机程序产品包括存储了计算机程序的非瞬时性计算机可读存储介质,且该计算机程序可被处理器执行时实现如上述各实施例描述的方法。
本领域普通技术人员可以理解实现上述实施例方法中的全部或部分流程,是可以通过计算机程序来指令相关的硬件来完成,所述的程序可存储于一非易失性计算机可读取存储介质中,该程序在执行时,可包括如上述各方法的实施例的流程。其中,所述的存储介质可为磁碟、光盘、只读存储记忆体(Read-Only Memory,ROM)等。
如此处所使用的对存储器、存储、数据库或其它介质的任何引用可包括非易失性和/或易失性存储器。合适的非易失性存储器可包括ROM、可编程ROM(Programmable ROM, PROM)、可擦除PROM(Erasable PROM,EPROM)、电可擦除PROM(Electrically Erasable PROM,EEPROM)或闪存。易失性存储器可包括随机存取存储器(random access memory,RAM),它用作外部高速缓冲存储器。作为说明而非局限,RAM以多种形式可得,诸如静态RAM(Static RAM,SRAM)、动态RAM(Dynamic Random Access Memory,DRAM)、同步DRAM(synchronous DRAM,SDRAM)、双倍数据率SDRAM(Double Data Rate SDRAM,DDR SDRAM)、增强型SDRAM(Enhanced Synchronous DRAM,ESDRAM)、同步链路DRAM(Synchlink DRAM,SLDRAM)、存储器总线直接RAM(Rambus DRAM,RDRAM)及直接存储器总线动态RAM(Direct Rambus DRAM,DRDRAM)。
以上所述实施例的各技术特征可以进行任意的组合,为使描述简洁,未对上述实施例中的各个技术特征所有可能的组合都进行描述,然而,只要这些技术特征的组合不存在矛盾,都应当认为是本说明书记载的范围。
以上所述实施例仅表达了本申请的几种实施方式,其描述较为具体和详细,但并不能因此而理解为对发明专利范围的限制。应当指出的是,对于本领域的普通技术人员来说,在不脱离本申请构思的前提下,还可以做出若干变形和改进,这些都属于本申请的保护范围。因此,本申请专利的保护范围应以所附权利要求为准。
Claims (20)
- 一种开关控制电路,其特征在于,包括:电压变换模块,包括组成第一桥臂的第一开关及第三开关,以及组成第二桥臂的第二开关及第四开关,用于接收输入电压,并基于所述输入电压工作在升压模式、降压模式及升降压模式中的至少一种模式;控制模块,用于控制所述第一开关及所述第三开关以第一开关频率在导通状态与断开状态之间切换,控制所述第二开关及所述第四开关以第二开关频率在导通状态与断开状态之间切换,以使所述电压变换模块工作在所述升压模式,对所述输入电压进行升压变换;以及用于控制所述第一开关及所述第三开关以所述第二开关频率在导通状态与断开状态之间切换,控制所述第二开关及所述第四开关以所述第一开关频率在导通状态与断开状态之间切换,以使所述电压变换模块工作在所述降压模式,对所述输入电压进行降压变换,所述第一开关频率小于所述第二开关频率。
- 根据权利要求1所述的开关控制电路,其特征在于,所述第一开关与所述电压变换模块的输入端连接,所述第二开关与所述电压变换模块的输出端连接;在所述第一开关处于导通状态时,所述第三开关处于断开状态,在所述第一开关处于断开状态时,所述第三开关处于导通状态;在所述升压模式下,所述第一开关处于导通状态的导通时长大于处于断开状态的断开时长;在所述第二开关处于导通状态时,所述第四开关处于断开状态,在所述第二开关处于断开状态时,所述第四开关处于导通状态;在所述降压模式下,所述第二开关处于导通状态的导通时长大于处于断开状态的断开时长。
- 根据权利要求2所述的开关控制电路,其特征在于,所述开关控制电路还包括第一驱动电路及第二驱动电路,所述第一驱动电路与所述第一开关连接,所述第二驱动电路与所述第二开关连接;所述控制模块,还用于若所述电压变换模块工作在所述升压模式,则按照所述第一开关频率向所述第一驱动电路发送第一脉冲信号,以及若所述电压变换模块工作在所述降压模式,则按照所述第一开关频率向所述第二驱动电路发送所述第一脉冲信号;所述第一驱动电路,用于在接收的第一脉冲信号为第一电平信号时,向所述第一开关提供驱动电压,以驱动所述第一开关保持导通状态;所述第二驱动电路,用于在接收的第一脉冲信号为所述第一电平信号时,向所述第二开关提供驱动电压,以驱动所述第二开关保持导通状态。
- 根据权利要求3所述的开关控制电路,其特征在于,所述第一驱动电路包括第五开关、第六开关及第一电容,所述第五开关、第六开关分别与所述控制模块连接;所述第一电容的第一端通过所述第五开关与所述第一开关连接,所述第一电容的第二端与所述第六开关连接;所述第五开关,用于在所述控制模块发送的第一脉冲信号为所述第一电平信号时,处于导通状态,在所述控制模块发送的第一脉冲信号为第二电平信号时,处于断开状态;所述第六开关,用于在所述控制模块发送的第一脉冲信号为所述第二电平信号时,处于导通状态,在所述控制模块发送的第一脉冲信号为所述第一电平信号时,处于断开状态;所述第一电容,用于在所述第五开关处于导通状态时,向所述第一开关提供驱动电压,以驱动所述第一开关处于导通状态;其中,所述第一脉冲信号中,所述第一电平信号在一个脉冲周期内所占的时间比率大于所述第二电平信号所占的时间比率。
- 根据权利要求4所述的开关控制电路,其特征在于,所述第一开关包括N型的第 一场效应管,所述第一场效应管的漏极与所述输入端连接,所述第一场效应管的栅极通过所述第五开关与所述第一电容的第一端连接;所述第一场效应管的源极分别与所述第三开关、第六开关及所述第一电容的第二端连接。
- 根据权利要求4所述的开关控制电路,其特征在于,所述第一电容的第一端还与电源端连接,所述第一电容的第二端还与所述第三开关连接,所述第三开关接地;所述第一电容,还用于在所述第五开关处于断开状态且所述第三开关处于导通状态时,根据所述电源端提供的电压进行充电。
- 根据权利要求6所述的开关控制电路,其特征在于,所述第一驱动电路还包括第一二极管,所述第一电容的第一端与所述第一二极管的负极连接,所述第一二极管的正极与所述电源端连接;在所述第三开关处于导通状态时,所述电源端通过所述第一二极管向所述第一电容充电。
- 根据权利要求3所述的开关控制电路,其特征在于,所述第二驱动电路包括第七开关、第八开关及第二电容,所述第七开关、第八开关分别与所述控制模块连接;所述第二电容的第一端通过所述第七开关与所述第二开关连接,所述第二电容的第二端与所述第八开关连接;所述第七开关,用于在所述控制模块发送的第一脉冲信号为所述第一电平信号时,处于导通状态,在所述控制模块发送的第一脉冲信号为第二电平信号时,处于断开状态;所述第八开关,用于在所述控制模块发送的第一脉冲信号为所述第二电平信号时,处于导通状态,在所述控制模块发送的第一脉冲信号为所述第一电平信号时,处于断开状态;所述第二电容,用于在所述第七开关处于导通状态时,向所述第二开关提供驱动电压,以驱动所述第二开关处于导通状态;其中,所述第一脉冲信号中,所述第一电平信号在一个脉冲周期内所占的时间比率大于第二电平信号所占的时间比率。
- 根据权利要求8所述的开关控制电路,其特征在于,所述第二开关包括N型的第二场效应管,所述第二场效应管的漏极与所述输出端连接,所述第二场效应管的栅极通过所述第七开关与所述第二电容的第一端连接;所述第二场效应管的源极分别与所述第四开关、第八开关及所述第二电容的第二端连接。
- 根据权利要求3-9任一所述的开关控制电路,其特征在于,所述开关控制电路还包括反向模块、第三驱动电路及第四驱动电路,所述第三驱动电路与所述第三开关连接,所述第四驱动电路与所述第四开关连接;所述反向模块分别与所述控制模块、第三驱动电路及第四驱动电路连接;所述反向模块,还用于对所述控制模块输出的第一脉冲信号进行反向,得到第二脉冲信号,若所述确定的工作模式为所述升压模式,则向所述第三驱动电路发送所述第二脉冲信号,以及若所述确定的工作模式为降压模式,则向所述第四驱动电路发送所述第二脉冲信号;所述第三驱动电路,用于在接收的第二脉冲信号为所述第一电平信号时,驱动所述第三开关保持导通状态;所述第四驱动电路,用于在接收的第二脉冲信号为所述第一电平信号时,驱动所述第四开关保持导通状态。
- 根据权利要求1-9任一所述的开关控制电路,其特征在于,所述控制模块,还用于获取所述输入电压与所述电压变换模块的输出电压之间的电压比较结果,根据所述电压比较结果控制所述电压变换模块工作在所述升压模式、降压模式及升降压模式中的至少一种模式。
- 根据权利要求11所述的开关控制电路,其特征在于,所述控制模块,还用于若所述电压比较结果为所述输入电压小于所述输出电压,且所述输出电压与所述输入电压之间的差值大于第一阈值,则控制所述电压变换模块工作在所述升压模式,以及若所述电压比较结果为所述输入电压大于所述输出电压,且所述输入电压与所述输出电压之间的差值大于第二阈值,则控制所述电压变换模块工作在所述降压模式。
- 根据权利要求11所述的开关控制电路,其特征在于,所述控制模块,还用于若所述电压比较结果为所述输入电压与所述输出电压之间的差值绝对值小于第三阈值,则控制所述第一开关、第二开关、第三开关及第四开关均以所述第一开关频率在导通状态与断开状态之间切换,以使所述电压变换模块工作在所述升降压模式。
- 一种电子设备,其特征在于,包括如权利要求1~13任一所述的开关控制电路。
- 一种开关控制方法,其特征在于,包括:通过电压变换模块对接收的输入电压进行变换,得到输出电压;所述电压变换模块包括组成第一桥臂的第一开关及第三开关,以及组成第二桥臂的第二开关及第四开关,所述电压变换模块基于所述输入电压工作在升压模式、降压模式及升降压模式中的至少一种模式;控制所述第一开关及所述第三开关以第一开关频率在导通状态与断开状态之间切换,所述第二开关及所述第四开关以第二开关频率在导通状态与断开状态之间切换,以使所述电压变换模块工作在所述升压模式,对所述输入电压进行升压变换;控制所述第一开关及所述第三开关以所述第二开关频率在导通状态与断开状态之间切换,控制所述第二开关及所述第四开关以所述第一开关频率在导通状态与断开状态之间切换,以使所述电压变换模块工作在所述降压模式,对所述输入电压进行降压变换,所述第一开关频率小于所述第二开关频率。
- 根据权利要求15所述的方法,其特征在于,所述第一开关与所述电压变换模块的输入端连接,所述第二开关与所述电压变换模块的输出端连接;在所述第一开关处于导通状态时,所述第三开关处于断开状态,在所述第一开关处于断开状态时,所述第一开关处于导通状态;在所述升压模式下,所述第一开关处于导通状态的导通时长大于处于断开状态的断开时长;在所述第二开关处于导通状态时,所述第四开关处于断开状态,在所述第二开关处于断开状态时,所述第四开关处于导通状态;在所述降压模式下,所述第二开关处于导通状态的导通时长大于处于断开状态的断开时长。
- 根据权利要求16所述的方法,其特征在于,所述控制所述第一开关及所述第三开关以第一开关频率在导通状态与断开状态之间切换,包括:按照所述第一开关频率向第一驱动电路发送第一脉冲信号,以使所述第一驱动电路在所述第一脉冲信号为第一电平信号时,向所述第一开关提供驱动电压,以驱动所述第一开关保持导通状态;所述控制所述第二开关及所述第四开关以所述第一开关频率在导通状态与断开状态之间切换,包括:按照所述第一开关频率向第二驱动电路发送所述第一脉冲信号,以使所述第二驱动电路在所述第一脉冲信号为所述第一电平信号时,向所述第二开关提供驱动电压,以驱动所述第二开关保持导通状态;其中,所述第一脉冲信号中,所述第一电平信号在一个脉冲周期内所占的时间比率大于第二电平信号所占的时间比率,所述第二电平信号用于触发所述第一开关或所述第二开关处于断开状态。
- 根据权利要求17所述的方法,其特征在于,所述第一驱动电路包括第一电容,所述按照所述第一开关频率向第一驱动电路发送第一脉冲信号,以使所述第一驱动电路在所述第一脉冲信号为第一电平信号时,向所述第一开关提供驱动电压,以驱动所述第一开关保持导通状态,包括:按照所述第一开关频率向第一驱动电路发送第一脉冲信号,以使所述第一驱动电路在所述第一脉冲信号为第一电平信号时,通过所述第一电容向所述第一开关提供驱动电压,以驱动所述第一开关处于导通状态。
- 一种电子设备,其特征在于,包括存储器及处理器,所述存储器中存储有计算机程序,所述计算机程序被所述处理器执行时,使得所述处理器实现如权利要求14至18任一所述的方法。
- 一种计算机可读存储介质,其上存储有计算机程序,其特征在于,所述计算机程序被处理器执行时实现如权利要求14~18任一所述的方法。
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US20180287496A1 (en) * | 2017-04-03 | 2018-10-04 | Texas Instruments Incorporated | Inverting buck-boost power converter |
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