WO2022217842A1 - 一种面向光载无线通信***的双信号调制和解调方法及装置 - Google Patents

一种面向光载无线通信***的双信号调制和解调方法及装置 Download PDF

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WO2022217842A1
WO2022217842A1 PCT/CN2021/120189 CN2021120189W WO2022217842A1 WO 2022217842 A1 WO2022217842 A1 WO 2022217842A1 CN 2021120189 W CN2021120189 W CN 2021120189W WO 2022217842 A1 WO2022217842 A1 WO 2022217842A1
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signal
dual
real
wireless communication
valued
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PCT/CN2021/120189
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English (en)
French (fr)
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朱敏
蔡沅成
王鹏远
岳凌昊
黄永明
尤肖虎
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网络通信与安全紫金山实验室
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/50—Transmitters
    • H04B10/516—Details of coding or modulation
    • H04B10/5165—Carrier suppressed; Single sideband; Double sideband or vestigial
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/60—Receivers

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  • the present application relates to the technical field of optical carrier wireless communication, and in particular, to a dual-signal modulation and demodulation method and device for an optical carrier wireless communication system.
  • the 5G era has arrived, which can provide a communication rate of over 1Gbps.
  • the future 6G wireless communication technology requires far more bandwidth and capacity than the current 5G technology.
  • One of the distinctive features is that it requires "full spectrum” communication capabilities. .
  • Optical carrier wireless communication systems especially optical carrier millimeter wave/terahertz communication systems, combine the advantages of optical fiber communication with large capacity, high bandwidth, low latency, and flexible access to wireless communication, which can provide strong support for the realization of 6G "full spectrum” communication. Strong support.
  • a feasible scheme is to use a double-driven Mach-Zehnder modulator (MZM) to modulate the single-sideband signal in the fiber. transmission.
  • MZM Mach-Zehnder modulator
  • three problems are usually faced: First, the linear conversion of the signal from the electrical to the optical domain cannot be realized, and usually the dual-drive MZM can only work at the quadrature transmission point.
  • twin single sideband scheme In order to improve the spectral efficiency of the system and make full use of the device bandwidth of the system, a common method is to use the twin single sideband scheme, so that both sideband signals carry valid information, which can not only make full use of the device bandwidth of the system hardware equipment, but also can Double the capacity of the system.
  • the traditional optical carrier wireless communication system usually requires two sets of electrical filters, analog-to-digital converters and receiving DSP modules, and the duplicated hardware will significantly increase the hardware cost of the system, and greatly Reduces the likelihood of this system merging with already deployed mature commercial systems.
  • the embodiments of the present application provide a dual-signal modulation and demodulation method and system for an optical carrier wireless communication system.
  • an embodiment of the present application provides a dual-signal modulation method for an optical-borne wireless communication system, including:
  • the recombined signal is a twin double sideband signal or a twin single sideband signal
  • twin double sideband signal or twin single sideband signal is represented by polar coordinates
  • two driving signals are constructed for digital-to-analog conversion, and used as two RF input signals of the modulator during electro-optical modulation;
  • Electro-optic modulation based on two RF input signals Electro-optic modulation based on two RF input signals.
  • performing signal reorganization based on the first real-valued signal and the second real-valued signal to obtain a reorganized signal includes:
  • the reconstructed signal is obtained by performing signal recombination based on the first real-valued signal and the second real-valued signal; wherein, the first relational model includes:
  • A is a real number and represents the DC term
  • s 1 (t) and s 2 (t) represent the two recombined signals obtained after the signal recombination, respectively
  • j represents the imaginary unit
  • t represents the time
  • s(t) represents the recombination obtained after twin double sideband signal or twin single sideband signal.
  • two driving signals are constructed for digital-to-analog conversion based on the polar coordinate representation results, and used as two radio frequency input signals of the modulator during electro-optical modulation, including:
  • two driving signals are constructed based on the results expressed in polar coordinates for digital-to-analog conversion, and used as two RF input signals of the dual-driven Mach-Zehnder modulator during electro-optical modulation;
  • the second relation Models include:
  • V ⁇ represents the half-wave voltage parameter of the dual-driven Mach-Zehnder modulator
  • ⁇ represents the pi ratio
  • cos -1 represents the inverse cosine function
  • r max represents the maximum amplitude of the signal
  • t represents the time
  • V 1 (t) represents the The first driving signal
  • V 2 (t) represents the second driving signal
  • ⁇ (t) represents the amplitude of the twin double sideband or twin single sideband signal in the polar coordinate system
  • r(t) represents the twin double sideband or twin single sideband signal The phase of the sideband signal in polar coordinates.
  • an embodiment of the present application provides a dual-signal demodulation method for an optical-borne wireless communication system, including:
  • Carrier extraction is performed based on the sampled digital signal;
  • the sampled digital signal includes a carrier, and, a twin double sideband signal or a twin single sideband signal;
  • the signal recovery is that the extracted carrier wave and the sampled digital signal component are multiplied, and then the high-frequency term is filtered out to obtain the recovered first-path signal and second-path signal;
  • Signal demodulation is performed based on the first real-valued signal and the second real-valued signal.
  • the dual-signal demodulation method also includes:
  • the carrier is extracted according to the preset guard interval when the carrier is extracted based on the sampled digital signal.
  • an embodiment of the present application provides a dual-signal modulation device for an optical-borne wireless communication system, including:
  • a first signal recombination module configured to perform signal recombination based on the first real-valued signal and the second real-valued signal to obtain a recombined signal;
  • the recombined signal is a twin double sideband signal or a twin single sideband signal;
  • an electrical dispersion pre-compensation module for performing electrical dispersion pre-compensation on the recombined signal
  • a polar coordinate signal conversion module configured to perform polar coordinate signal conversion on the recombined signal after electrical dispersion pre-compensation, so that the twin double sideband signal or twin single sideband signal is represented in polar coordinates;
  • the signal construction module is used to construct two driving signals for digital-to-analog conversion based on the polar coordinate representation results, and serve as two radio frequency input signals of the modulator during electro-optical modulation;
  • a modulation module for electro-optic modulation based on two RF input signals A modulation module for electro-optic modulation based on two RF input signals.
  • an embodiment of the present application provides a dual-signal demodulation device for an optical-borne wireless communication system, including:
  • a carrier extraction module for carrier extraction based on a sampled digital signal;
  • the sampled digital signal includes a carrier, and a twin double sideband signal or a twin single sideband signal;
  • the signal recovery module is used for signal recovery based on the extracted carrier wave; the signal recovery is to multiply the extracted carrier wave and the sampled digital signal component, and then filter out the high-frequency term to obtain the recovered first signal and the second signal;
  • the second signal recombination module is used for performing signal recombination based on the recovered first and second signals to obtain corresponding recombined signals;
  • an electrical dispersion post-compensation module for performing electrical dispersion post-compensation on the recombined signal
  • a signal decomposition module configured to perform signal decomposition on the recombined signal after electrical dispersion compensation to obtain a first real-valued signal and a second real-valued signal;
  • a signal demodulation module configured to perform signal demodulation based on the first real-valued signal and the second real-valued signal.
  • an embodiment of the present application provides an optical carrier wireless communication system supporting dual-signal modulation and demodulation, including: an optical transceiver and a wireless transceiver;
  • the wireless transceiver implements the following steps of a dual-signal demodulation method for an optical carrier wireless communication system:
  • Carrier extraction is performed based on the sampled digital signal;
  • the sampled digital signal includes a carrier, and, a twin double sideband signal or a twin single sideband signal;
  • the signal recovery is that the extracted carrier wave and the sampled digital signal component are multiplied, and then the high-frequency term is filtered out to obtain the recovered first-path signal and second-path signal;
  • Signal demodulation is performed based on the first real-valued signal and the second real-valued signal.
  • an embodiment of the present application provides an optical carrier wireless communication system that supports dual-signal modulation and demodulation, including: an optical transceiver and a wireless transceiver,
  • the recombined signal is a twin double sideband signal or a twin single sideband signal
  • Electro-optic modulation based on two RF input signals Electro-optic modulation based on two RF input signals.
  • an embodiment of the present application further provides an electronic device, including a memory, a processor, and a computer program stored in the memory and running on the processor, the processor implementing the above-mentioned first program when the processor executes the program
  • the processor implementing the above-mentioned first program when the processor executes the program
  • an embodiment of the present application further provides an electronic device, including a memory, a first processor, a second processor, and a first computer stored on the memory and running on the first processor A program and a second computer program stored on the memory and executable on the second processor, when the first processor executes the first computer program, the optical carrier described in the first aspect is implemented Steps of a dual-signal modulation method for a wireless communication system; when the second processor executes the second computer program, implements the steps of the dual-signal demodulation method for an optical-borne wireless communication system as described in the second aspect above.
  • an embodiment of the present application further provides a non-transitory computer-readable storage medium, on which a computer program is stored, and when the computer program is executed by a processor, realizes the optical carrier-oriented wireless communication as described in the first aspect above
  • an embodiment of the present application further provides a non-transitory computer-readable storage medium on which a first computer program and a second computer program are stored, and the first computer program is implemented as described above when executed by the first processor
  • the steps of the method for dual-signal modulation for an optical carrier wireless communication system described in the first aspect; when the second computer program is executed by the second processor, the dual-signal solution for the optical carrier wireless communication system as described in the second aspect above is implemented. Steps to adjust the method.
  • the modulation method includes: performing signal reorganization based on the first real-valued signal and the second real-valued signal to obtain a reorganized signal.
  • the recombined signal is a twin double sideband signal or a twin single sideband signal; electric dispersion pre-compensation is performed on the recombined signal;
  • the band signal or twin single-sideband signal is represented by polar coordinates; based on the results of polar coordinates, two driving signals are constructed for digital-to-analog conversion, and used as two RF input signals of the modulator during electro-optical modulation; based on the two RF inputs
  • the signal is electro-optically modulated.
  • the modulation method provided by the embodiment of the present application can fully utilize the bandwidth of the transceiver, thereby reducing the cost of system components on the one hand, and improving the communication capacity of the system on the other hand.
  • FIG. 1 is a schematic flowchart of a dual-signal modulation method for an optical carrier wireless communication system provided by an embodiment of the present application;
  • FIG. 2 is a schematic structural diagram of a photon-assisted millimeter-wave/terahertz signal transmitter supporting dual-signal modulation provided by an embodiment of the present application;
  • FIG. 3 is a schematic flowchart of a sending DSP module supporting dual-signal modulation provided by an embodiment of the present application
  • FIG. 4 is a schematic diagram of an electrical spectrum before and after linear modulation of a twin double-sideband signal provided by an embodiment of the application;
  • FIG. 5 is a schematic diagram of an electrical spectrum before and after linear modulation of a twin single-sideband signal provided by an embodiment of the present application;
  • FIG. 6 is a schematic flowchart of a dual-signal demodulation method for an optical-borne wireless communication system provided by an embodiment of the present application
  • FIG. 7 is a schematic structural diagram of a millimeter-wave/terahertz signal receiver supporting dual-signal demodulation provided by an embodiment of the present application;
  • FIG. 8 is a schematic structural diagram of a traditional twin single-sideband signal transceiver in an optical carrier wireless communication system
  • FIG. 9 is a schematic structural diagram of another traditional twin SSB signal receiver in the optical carrier wireless communication system.
  • FIG. 10 is a schematic flowchart of a receiving DSP module supporting dual-signal demodulation provided by an embodiment of the application;
  • FIG. 11 is a schematic structural diagram of a dual-signal modulation apparatus for an optical carrier wireless communication system provided by an embodiment of the present application.
  • FIG. 12 is a schematic structural diagram of a dual-signal demodulation device for an optical carrier wireless communication system provided by an embodiment of the application;
  • FIG. 13 is a schematic diagram of an optical carrier wireless communication system supporting dual-signal modulation and demodulation provided by another embodiment of the present application;
  • 14 is a schematic diagram of a relationship curve between the dual-signal error vector magnitude recovered by the receiving end and the received optical power according to an embodiment of the application;
  • FIG. 15 is a relationship curve between two double-sideband signal error vector amplitudes and received optical power, which are recovered by the receiving end using electrical dispersion pre-compensation and electrical dispersion post-compensation, respectively, according to an embodiment of the application, under the twin double-sideband signal modulation scheme.
  • 16 is a schematic diagram of a physical structure of an electronic device provided in an embodiment of the application.
  • Sending DSP module 121. First digital-to-analog converter; 122, Second digital-to-analog converter; 13. Sending laser; 14. Electro-optic modulation; 15. Local oscillator laser; 16. Standard single-mode fiber; 17. Optical Heterodyne detection; 18, bandpass filter; 19, transmit antenna; 111, first signal generation module; 112, second signal generation module; 113, signal recombination; 114, electrical dispersion pre-compensation; 115, polar coordinate signal conversion ; 116, the first drive signal; 117, the second drive signal; 21, the receiving antenna; 22, the frequency down-conversion; 23, the analog-to-digital converter; 24, the receiving DSP module; 25, the LSB processing; 26, the RSB processing; 252, LSB photodetector; 253, LSB transmitting antenna; 254, LSB receiving antenna 254; 255, LSB frequency down-conversion; 256, LSB analog-to-digital converter; 257, LSB receiving DSP module;
  • FIG. 1 is a schematic flowchart of a dual-signal modulation method for an optical carrier wireless communication system provided by an embodiment of the present application; as shown in FIG. 1 , the method includes:
  • Step 101 Perform signal recombination based on the first real-valued signal and the second real-valued signal to obtain a recombined signal; the recombined signal is a twin double sideband signal or a twin single sideband signal.
  • Step 102 Perform electrical dispersion pre-compensation on the recombined signal.
  • Step 103 Perform polar coordinate signal conversion on the recombined signal after electrical dispersion pre-compensation, so that the twin double sideband signal or the twin single sideband signal is represented by polar coordinates.
  • Step 104 Constructing two driving signals for digital-to-analog conversion based on the results expressed in polar coordinates, and using them as two radio frequency input signals of the modulator during electro-optical modulation.
  • Step 105 Perform electro-optic modulation based on the two radio frequency input signals.
  • the dual-signal modulation method for an optical carrier wireless communication system provided by the embodiment of this application is applied to a photon-assisted millimeter-wave/terahertz signal transmitter that supports dual-signal modulation.
  • the schematic diagram of the structure of the photon-assisted millimeter-wave/terahertz signal transmitter for signal modulation is shown in FIG. 2 .
  • the photon-assisted millimeter-wave/terahertz signal transmitter supporting dual-signal modulation includes: a sending DSP module 11 and a first digital-to-analog converter 121 , the second digital-to-analog converter 122, the sending laser 13, the electro-optical modulation 14, the local oscillator laser 15, the standard single-mode fiber 16, the optical heterodyne detection 17, the band-pass filter 18 and the transmitting antenna 19; wherein, the sending DSP module 11
  • the detailed structure is shown in Figure 3, including a first signal generation module 111, a second signal generation module 112, a signal recombination 113, an electrical dispersion pre-compensation 114, a polar coordinate signal conversion 115, a first drive signal 116 and a second drive signal 117.
  • the sending DSP module 11 completes the digital signal processing required for dual-signal modulation, which mainly includes the following steps.
  • a(t) and b(t) represent real-valued signals generated by the first signal generation module 111 and the second signal generation module 112, respectively, namely the first real-valued signal and the second real-valued signal, (the format is not limited, such as PAM, DMT, CAP, etc.), the first real-valued signal and the second real-valued signal may be any real-valued signal, and whether the spectrums of the real-valued signals overlap or not will not affect the modulation method involved in the embodiments of the present application.
  • the spectrum of the two is completely overlapped as an example (that is, the two signals have the same intermediate frequency and the same bandwidth), hereinafter a(t) is referred to as signal 1, and b(t) is referred to as signal 2.
  • signal 1 a(t) is referred to as signal 1
  • b(t) is referred to as signal 2.
  • the output signal is:
  • A is a real number, representing the DC term
  • s 1 (t) and s 2 (t) respectively represent the two recombined signals obtained after the signal recombination.
  • s(t) represents a pair of double-sideband signals (twin double-sideband signals), in which the spectrum of signal 1 (ie, the first real-valued signal) and signal 2 (ie, the second real-valued signal) overlap each other, but in phase
  • a signal having such a frequency spectrum is called a twin double-sideband signal.
  • s(t) represents a pair of single-sideband signals (twin single-sideband signals), including the left side band (LSB) of signal 1, and the expression is and the right side band (RSB) of signal 2, the expression is The two spectrums do not overlap, as shown in Figure 5.
  • a signal with this spectrum is referred to in this application as a twin single sideband signal.
  • the target signal of twin double sideband or twin single sideband (that is, the recombination signal after electrical dispersion pre-compensation) is represented in polar coordinates, that is,
  • abs and angle represent the calculated modulus and phase angle functions, respectively.
  • V ⁇ represents the half-wave voltage parameter of the dual-driven MZM
  • ⁇ represents the pi
  • cos -1 represents the arc cosine function.
  • E in (t) represents the light wave output by the transmission laser 13 .
  • this implementation is different from the existing linear modulation method based on dual-drive MZM.
  • the existing method only performs linear modulation on the single-sideband signal, and cannot fully utilize the bandwidth of the system device.
  • the dual-drive MZM is still biased at the quadrature transmission point, that is, the phase difference caused by the DC bias of the two arms is Therefore, in order to cancel the phase difference caused by the DC offset of the quadrature point, it is necessary to set the two driving signals as Obviously, the input RF signal at this time is constrained by the DC bias of the modulator.
  • the DC bias of the modulator is easy to drift with the increase of operating temperature. Once it deviates from the quadrature operating point, it will cause the DC bias to not match the driving signal, thus destroying the linear modulation of the signal. As a result, the modulation quality of the signal at the sending end is reduced.
  • the embodiments of the present application this problem is solved, and the limitation of the DC bias of the modulator on the input radio frequency signal can be released.
  • the DC bias of the dual-drive MZM is set at the maximum transmission point, that is, the difference between the DC bias voltages of the two arms is zero, which is well implemented in the actual system.
  • the same DC bias voltage is divided into two channels to supply the upper and lower sides of the dual-drive MZM Two arms, so that no matter how the DC bias voltage drifts with the working environment, the bias characteristic of the maximum transmission point will not be destroyed. Therefore, the DC drift will not affect the effect of linear modulation.
  • the embodiments of the present application support linear modulation of dual signals including twin double sideband and twin single sideband signals, which can not only increase the communication capacity of the sending end, but also make full use of the bandwidth of the sending end device.
  • the above process realizes the linear modulation of the twin double sideband and twin single sideband signals.
  • the signal light is transmitted to the remote base station through the standard single-mode fiber 16, and is coupled with a local oscillator laser 15 using optical heterodyne detection 17 for photoelectricity.
  • the conversion, the beat frequency of the signal light and the local oscillator light can generate the desired millimeter wave/terahertz (Mm&THz) signal, which can be extracted by the band pass filter 18 and then transmitted through the transmitting antenna 19 .
  • Mm&THz millimeter wave/terahertz
  • the embodiment of this application can be applied to the transmitting end.
  • the polar coordinate signal conversion method is used to realize the linear modulation of the dual-signal, which can release the relationship between the driving signal and the DC bias of the modulator. Constraints between the two, while linear modulation supports efficient electrical dispersion compensation for twin double sideband or twin single sideband signals.
  • the dual-signal modulation in the embodiment of the present application can not only fully utilize the bandwidth of the system device, but also improve the communication rate and capacity of the system.
  • the dual-signal modulation method for an optical carrier wireless communication system obtaineds a recombined signal by performing signal recombination based on the first real-valued signal and the second real-valued signal; the recombined signal is a twin.
  • Double sideband signal or twin single sideband signal perform electrical dispersion pre-compensation on the recombined signal; perform polar coordinate signal conversion on the recombined signal after electrical dispersion precompensation so that the twin double sideband signal or twin single sideband signal It is represented by polar coordinates; based on the results of polar coordinates, two driving signals are constructed for digital-to-analog conversion, and used as two RF input signals of the modulator during electro-optic modulation; electro-optic modulation is performed based on the two RF input signals.
  • the modulation method provided by the embodiment of the present application can fully utilize the bandwidth of the transceiver, thereby reducing the cost of system components on the one hand, and improving the communication capacity of the system on the other hand.
  • performing signal reorganization based on the first real-valued signal and the second real-valued signal to obtain a reorganized signal includes:
  • the reconstructed signal is obtained by performing signal recombination based on the first real-valued signal and the second real-valued signal; wherein, the first relational model includes:
  • A is a real number and represents the DC term
  • s 1 (t) and s 2 (t) represent the two recombined signals obtained after the signal recombination, respectively
  • j represents the imaginary unit
  • t represents the time
  • s(t) represents the recombination obtained after twin double sideband signal or twin single sideband signal.
  • a recombined signal is obtained by performing signal recombination based on the first real-valued signal and the second real-valued signal, and the recombined signal is a twin double sideband signal or a twin single sideband signal It is beneficial to make full use of the bandwidth of the transmitting end device and improve the electrical spectrum efficiency, thereby realizing cost savings.
  • two driving signals are constructed to perform digital-to-analog conversion based on the results expressed in polar coordinates, and are used as two radio frequency input signals of the modulator during electro-optical modulation, including:
  • two driving signals are constructed based on the results expressed in polar coordinates for digital-to-analog conversion, and used as two RF input signals of the dual-driven Mach-Zehnder modulator during electro-optical modulation;
  • the second relation Models include:
  • V ⁇ represents the half-wave voltage parameter of the dual-driven Mach-Zehnder modulator
  • ⁇ represents the pi ratio
  • cos -1 represents the inverse cosine function
  • r max represents the maximum amplitude of the signal
  • t represents the time
  • V 1 (t) represents the The first driving signal
  • V 2 (t) represents the second driving signal
  • ⁇ (t) represents the amplitude of the twin double sideband or twin single sideband signal in the polar coordinate system
  • r(t) represents the twin double sideband or twin single sideband signal The phase of the sideband signal in polar coordinates.
  • the implementation of the signal linear modulation scheme in this embodiment releases the DC of the dual-drive Mach-Zehnder modulator by biasing the dual-drive Mach-Zehnder modulator at the maximum transmission point.
  • the constraint of the bias on the RF input signal can avoid the influence of the DC drift on the linear modulation effect of the signal.
  • FIG. 6 is a schematic flowchart of a dual-signal demodulation method for an optical carrier wireless communication system provided by an embodiment of the present application; as shown in FIG. 6 , the method includes:
  • Step 601 Perform carrier extraction based on a sampled digital signal; the sampled digital signal includes a carrier, and a twin double sideband signal or a twin single sideband signal.
  • Step 602 Perform signal recovery based on the extracted carrier wave; the signal recovery is to multiply the extracted carrier wave and the sampled digital signal component, and then filter out the high-frequency term to obtain the recovered first signal and the second signal. road signal.
  • Step 603 Perform signal recombination based on the recovered first-channel signal and the second-channel signal to obtain a corresponding recombined signal.
  • Step 604 Perform electrical dispersion post-compensation on the recombined signal.
  • Step 605 Perform signal decomposition on the reconstructed signal compensated by electrical dispersion to obtain a first real-valued signal and a second real-valued signal.
  • Step 606 Perform signal demodulation based on the first real-valued signal and the second real-valued signal.
  • the dual-signal demodulation method for an optical carrier wireless communication system provided in this embodiment of the application is applied to a millimeter-wave/terahertz signal receiver supporting dual-signal demodulation.
  • the schematic diagram of the millimeter-wave/terahertz signal receiver for signal demodulation is shown in Figure 7.
  • the photon-assisted millimeter-wave/terahertz signal transmitter supporting dual-signal modulation includes: a receiving antenna 21, a frequency down-conversion 22 and an analog-to-digital converter 23 and the receiving DSP module 24; wherein, the receiving DSP module 24 is composed of a band-pass filter 241, a Hilbert transform 242, a first multiplier 243, a second multiplier 244, a first low-pass filter 245, a second low-pass filter
  • the pass filter 246, the electrical dispersion post-compensation 247, the signal decomposition 248, the first signal demodulation 249 and the second signal demodulation 2410 are composed of units, see FIG. 10 .
  • Fig. 8 shows a schematic structural diagram of a traditional twin-sideband signal transceiver in an optical carrier wireless communication system
  • Fig. 8 includes the left side band (LSB) processing 25 and right side band (RSB) processing 26, wherein LSB processing 25 consists of LSB optical filter 251, LSB photodetector 252, LSB transmit antenna 253, LSB receive antenna 254, LSB frequency down-conversion 255, LSB analog-to-digital converter 256 and
  • the LSB receiving DSP module 257 is constituted, while the RSB processing 26 consists of the RSB optical filter 261, the RSB photodetector 262, the RSB transmitting antenna 263, the RSB receiving antenna 264, the RSB frequency down-conversion 265, the RSB analog-to-digital converter 266 and the RSB receiving DSP Module 267 is formed; the system uses an optical filter to separate the LSB and RS
  • FIG. 9 is a schematic structural diagram of another traditional twin-sideband signal receiver in an optical carrier wireless communication system.
  • the LSB receiver 27 is composed of a low-pass filter 271 , an LSB analog-to-digital converter 272 and an LSB receiver DSP module 273
  • the RSB receiver 28 is composed of a low-pass filter 281 , an RSB analog-to-digital converter 282 and an RSB receiver DSP module 283 .
  • the receiver shown in Fig. 9 saves a lot of hardware cost.
  • the optical path does not need to repeat the hardware, and the circuit only needs a set of antenna and frequency down-conversion module.
  • the millimeter-wave/terahertz signal receiver proposed in this application can significantly reduce the hardware cost of the receiver, and can not only support the solution of twin double sideband or twin single sideband signals. It is compatible with optical carrier wireless communication systems based on single-signal modulation and demodulation.
  • the receiving end adopts the heterodyne mixing method to complete the down-conversion of the millimeter wave/terahertz signal, and the signal output by the frequency down-conversion 22 can be expressed as:
  • E IF (t) M ⁇ Acos[ ⁇ IF t+ ⁇ (t)]+s 1 (t) ⁇ cos[ ⁇ IF t+ ⁇ (t)]+s 2 (t) ⁇ sin[ ⁇ IF t + ⁇ (t)] ⁇ (7)
  • M is a constant, which is proportional to the average optical power output by the sending laser 13 and the local oscillator laser 15, and ⁇ IF and ⁇ (t) represent the center angular frequency and the phase carried by the down-converted millimeter wave/terahertz signal, respectively. noise.
  • the first term is the intermediate frequency carrier, and the second term and the third term represent two different signals respectively.
  • receiving DSP module 24 includes a band-pass filter 241, a Hilbert transform 242, a first multiplier 243, a second multiplier 244, a first low-pass filter 245, a second low-pass filter Pass filter 246, electrical dispersion post-compensation 247, signal decomposition 248, first signal demodulation 249 and second signal demodulation 2410 units.
  • Receiving DSP module 24 to realize the demodulation of dual signals includes the following steps:
  • Carrier extraction step The carrier is extracted by a bandpass filter 241, and its expression is:
  • a small guard interval (such as 500MHz) can be reserved between the carrier and the signal (sideband signal, that is, the sampled signal is actually composed of the carrier and the sideband signal).
  • the bandwidth of the signal can be as high as 10 GHz or more, so such an interval will not bring about a significant decrease in spectral efficiency.
  • the first multiplier 243 is used to multiply the extracted carrier wave with the original signal (ie, the sampled signal, including the carrier wave and sideband signals) components, and then the first low-pass filter 245 is used to filter out the high-frequency items. Restore the first signal, as shown in the following formula:
  • Receive-side signal decomposition is the reverse process of sender-side signal recombination, in order to separate the target signals a(t) and b(t) from the obtained sums s 1 (t) and s 2 (t).
  • a(t) and b(t) can be recovered by the following equations:
  • a(t) and b(t) can be recovered by the following equations:
  • Signal demodulation After signal decomposition 248, we separate a(t) and b(t), and then use the first signal demodulation 249 and the second signal demodulation 2410 to complete the demodulation of a(t) and b(t), respectively,
  • the demodulation operation is consistent with the conventional signal demodulation steps, and will not be introduced separately here.
  • the embodiment of the present application can be applied to the receiving end, without two sets of duplicate hardware devices, and the dual signals can be recovered separately by only receiving a single set of hardware and cooperating with specific DSP processing. Therefore, Significantly reduces the hardware requirements for dual-signal demodulation. In fact, dual-signal modulation and demodulation are fully compatible with traditional single-sideband/double-sideband modulation systems in hardware requirements.
  • the dual-signal demodulation method oriented to the optical carrier wireless communication system extracts the carrier wave based on the sampled digital signal; Single sideband signal; signal recovery is performed based on the extracted carrier wave; the signal recovery is to multiply the extracted carrier wave and the sampled digital signal component, and then filter out the high-frequency term to obtain the recovered first signal and The second channel signal; performing signal recombination based on the restored first channel signal and the second channel signal to obtain a corresponding recombined signal; performing electrical dispersion post-compensation on the recombined signal; decomposing the recombined signal after electrical dispersion compensation to obtain a first real-valued signal and a second real-valued signal; signal demodulation is performed based on the first real-valued signal and the second real-valued signal; the embodiment of the present application is applied to a wireless receiving end of a twin double sideband or twin single sideband signal , which can significantly reduce the demand for hardware
  • this embodiment also includes:
  • the carrier is extracted according to the preset guard interval when the carrier is extracted based on the sampled digital signal.
  • a small guard interval (such as 500 MHz) can be reserved between the carrier and the signal.
  • the bandwidth can be as high as more than 10 GHz, so such spacing will not bring about a significant drop in spectral efficiency.
  • the preset guard interval may be 0.3 GHz to 1.0 GHz.
  • the dual-signal demodulation method for the optical carrier wireless communication system provided by the embodiment of the present application, because the signal recovery adopts the method of carrier and signal mixing, so that the system is completely unaffected by SSBI, and only needs to be It is sufficient to reserve a small preset guard interval for carrier extraction.
  • FIG. 11 is a schematic structural diagram of a dual-signal modulation device for an optical carrier wireless communication system provided by an embodiment of the application. As shown in FIG. 11 , the system includes: a first signal recombination module 1101 , an electrical dispersion pre-compensation module 1102 , a polar Coordinate signal conversion module 1103, signal construction module 1104 and modulation module 1105, wherein:
  • the first signal recombination module 1101 is configured to perform signal recombination based on the first real-valued signal and the second real-valued signal to obtain a recombined signal;
  • the recombined signal is a twin double sideband signal or a twin single sideband signal;
  • an electrical dispersion pre-compensation module 1102 configured to perform electrical dispersion pre-compensation on the recombined signal
  • the polar coordinate signal conversion module 1103 is configured to perform polar coordinate signal conversion on the reconstituted signal after electrical dispersion pre-compensation, so that the twin double sideband signal or twin single sideband signal is represented in polar coordinates;
  • the signal construction module 1104 is used to construct two driving signals for digital-to-analog conversion based on the polar coordinate representation result, and serve as two radio frequency input signals of the modulator during electro-optical modulation;
  • the modulation module 1105 is configured to perform electro-optic modulation based on the two radio frequency input signals.
  • the dual-signal modulation device oriented to an optical carrier wireless communication system provided by the embodiment of the present application can be specifically used to implement the dual-signal modulation method oriented to the optical carrier wireless communication system of the above-mentioned embodiment, and its technical principles and beneficial effects are similar. For details, please refer to the above-mentioned Examples are not repeated here.
  • FIG. 12 is a schematic structural diagram of a dual-signal demodulation device for an optical carrier wireless communication system provided by an embodiment of the application.
  • the system includes: a carrier extraction module 1201 , a signal recovery module 1202 , and a second signal recombination module 1203, electrical dispersion post-compensation module 1204, signal decomposition module 1205 and signal demodulation module 1206, wherein:
  • the carrier extraction module 1201 is used for carrier extraction based on a sampled digital signal;
  • the sampled digital signal includes a carrier, and a twin double sideband signal or a twin single sideband signal;
  • the signal recovery module 1202 is used for signal recovery based on the extracted carrier wave; the signal recovery is to multiply the extracted carrier wave and the sampled digital signal component, and then filter out the high-frequency term to obtain the recovered first path signal and the second signal;
  • the second signal recombination module 1203 is configured to perform signal recombination based on the recovered first and second signals to obtain corresponding recombined signals;
  • a signal decomposition module 1205, configured to perform signal decomposition on the recombined signal after electrical dispersion compensation to obtain a first real-valued signal and a second real-valued signal;
  • a signal demodulation module 1206, configured to perform signal demodulation based on the first real-valued signal and the second real-valued signal.
  • the dual-signal demodulation device oriented to an optical carrier wireless communication system provided in the embodiment of the present application can be specifically used to execute the dual-signal demodulation method oriented to the optical carrier wireless communication system of the above-mentioned embodiment, and its technical principles and beneficial effects are similar. Refer to the above-mentioned embodiments, and details are not repeated here.
  • FIG. 13 is a schematic structural diagram of an optical carrier wireless communication system supporting dual-signal modulation and demodulation provided by an embodiment of the application. As shown in FIG. 13 , the system includes: an optical transceiver and a wireless transceiver, wherein:
  • the wireless transceiver implements the following steps of a dual-signal demodulation method for an optical carrier wireless communication system:
  • Carrier extraction is performed based on the sampled digital signal;
  • the sampled digital signal includes a carrier, and, a twin double sideband signal or a twin single sideband signal;
  • the signal recovery is that the extracted carrier wave and the sampled digital signal component are multiplied, and then the high-frequency term is filtered out to obtain the recovered first-path signal and second-path signal;
  • Signal demodulation is performed based on the first real-valued signal and the second real-valued signal.
  • an optical carrier wireless communication system supporting dual-signal modulation and demodulation includes: an optical transceiver and a wireless transceiver, wherein:
  • the steps of the method for dual-signal demodulation oriented to the optical carrier wireless communication system according to the second aspect are implemented in the wireless transceiver.
  • the recombined signal is a twin double sideband signal or a twin single sideband signal
  • Electro-optic modulation based on two RF input signals Electro-optic modulation based on two RF input signals.
  • FIG. 13 shows a schematic structural diagram of an optical carrier wireless communication system supporting dual-signal modulation and demodulation provided by an embodiment of the present application.
  • the whole system is composed of an optical transceiver and a wireless transceiver.
  • the polar coordinate signal conversion method is used to realize the modulation of the twin double sideband or twin single sideband signal based on a single dual-drive MZM, and then transmit it to the remote end through the optical fiber.
  • a channel of local oscillator light is coupled to generate a millimeter wave/terahertz signal using the optical heterodyne beat frequency, and the frequency of the millimeter wave/terahertz signal is adjustable.
  • the target millimeter wave/terahertz signal is down-converted first through the mixer, and then sent to the receiving DSP module after analog-to-digital conversion. .
  • Figure 14 shows the relationship between the error vector magnitude and the received optical power after dual-signal demodulation with a carrier frequency of 60 GHz and a total rate of 50 Gbps curve.
  • both signals are in CAP-32QAM modulation format with a baud rate of 5Gbaud/s. It can be found that the error vector amplitude of the two signals decreases with the increase of the optical power, regardless of whether it is twin single sideband or twin double sideband modulation. At -16dBm, the error vector amplitude is close to 6%.
  • Figure 15 further shows the relationship between the signal error vector amplitude recovered by the receiving end and the received optical power under the two methods of electrical dispersion pre-compensation and electrical dispersion post-compensation. It can be found that in The two double-sideband signals in this system can achieve the same effect as the electrical dispersion pre-compensation scheme after electrical dispersion compensation, which shows that the double-sideband signals do not have obvious power fading phenomenon through optical fiber transmission at this time. That is to say, the present application can overcome the power fading problem of double-sideband signals induced by optical fiber dispersion in conventional optical-borne wireless communication systems.
  • the optical transceiver can implement the steps of the above-mentioned dual-signal modulation methods for the optical carrier wireless communication system, so While realizing two different dual-signal linear electro-optic modulations of twin double-sideband or twin-sideband, it releases the constraint between the RF driving signal of the dual-drive MZM and the DC bias of the modulator, and supports the efficient electrical dispersion compensation of the dual-signal , which overcomes the power fading problem of traditional double-sideband signals; in addition, the bandwidth of the transceiver device can be fully utilized through twin-sideband or twin-sideband modulation, which reduces the cost of system components on the one hand, and improves the system communication capacity on the other hand;
  • the wireless transceiver can realize the steps of the above-mentioned dual-signal demodulation methods for optical-carrier wireless communication systems, so at the wireless receiving end of the
  • the optical carrier wireless communication system supporting dual signal modulation and demodulation can With a lower system complexity and deployment cost, improving the communication rate and spectral efficiency of existing optical-borne wireless communication systems will help to realize large-capacity, high-performance photonic millimeter-wave/terahertz communication systems for 6G.
  • an embodiment of the present application provides an electronic device.
  • the electronic device specifically includes the following contents: a processor 1601, a communication interface 1603, a memory 1602, and a communication bus 1604;
  • the processor 1601, the communication interface 1603, and the memory 1602 complete the communication with each other through the communication bus 1604; the communication interface 1603 is used to realize the information transmission between various modeling software and the intelligent manufacturing equipment module library and other related equipment; the processor 1601 For invoking the computer program in the memory 1602, the processor implements the methods provided by the above method embodiments when the computer program is executed. For example, when the processor executes the computer program, the following steps are implemented: based on the first real-valued signal and the second real-valued signal.
  • the recombined signal is a twin double sideband signal or a twin single sideband signal; perform electrical dispersion pre-compensation on the recombined signal; perform polar coordinates on the recombined signal after electrical dispersion pre-compensation
  • the signal conversion enables the twin double sideband signal or twin single sideband signal to be represented by polar coordinates; two driving signals are constructed based on the results of polar coordinates for digital-to-analog conversion, and are used as two radio frequency inputs of the modulator during electro-optical modulation signal; electro-optic modulation based on two radio frequency input signals; and/or; carrier extraction based on sampled digital signal; the sampled digital signal includes carrier, and, twin double sideband signal or twin single sideband signal; based on the extracted carrier Carry out signal recovery; the signal recovery is that the extracted carrier wave is multiplied by the sampled digital signal component, and then the high-frequency term is filtered
  • another embodiment of the present application further provides a non-transitory computer-readable storage medium, on which a computer program is stored, and the computer program is implemented when executed by a processor to execute the methods provided by the foregoing method embodiments.
  • the method for example, performs signal recombination based on the first real-valued signal and the second real-valued signal to obtain a recombined signal; the recombined signal is a twin double sideband signal or a twin single sideband signal; perform electrical dispersion pre-compensation on the reconstituted signal; Perform polar coordinate signal conversion on the recombined signal after electrical dispersion pre-compensation so that the twin double sideband signal or twin single sideband signal is represented by polar coordinates; two driving signals are constructed based on the polar coordinates representation result for digital-to-analog conversion , and as two radio frequency input signals of the modulator during electro-optic modulation; electro-optic modulation based on two radio frequency input signals; and/
  • each embodiment can be implemented by means of software plus a necessary general hardware platform, and certainly can also be implemented by hardware.
  • the above-mentioned technical solutions can be embodied in the form of software products in essence or the parts that make contributions to the prior art, and the computer software products can be stored in computer-readable storage media, such as ROM/RAM, magnetic Disks, optical discs, etc., include instructions for causing a computer device (which may be a personal computer, server, or network device, etc.) to perform the methods of various embodiments or portions of embodiments.
  • relational terms such as first and second, etc. are only used to distinguish one entity or operation from another entity or operation, and do not necessarily require or imply the existence between these entities or operations any such actual relationship or sequence.
  • the terms “comprising”, “comprising” or any other variation thereof are intended to encompass a non-exclusive inclusion such that a process, method, article or device that includes a list of elements includes not only those elements, but also includes not explicitly listed or other elements inherent to such a process, method, article or apparatus.
  • an element qualified by the phrase “comprising a" does not preclude the presence of additional identical elements in the process, method, article, or device that includes the element.

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Abstract

本申请提供了一种面向光载无线通信***的双信号调制和解调方法及装置，调制方法包括：基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；对所述重组信号进行电色散预补偿；将电色散预补偿后的所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；基于两个射频输入信号进行电光调制。本申请实施例提供的调制方法能够充分利用收发件的带宽，从而一方面降低***器件成本，另一方面提升***通信容量。

Description

一种面向光载无线通信***的双信号调制和解调方法及装置
相关申请的交叉引用
本申请要求于2021年4月13日提交的申请号为202110392030.1，发明名称为“面向光载无线通信***的双信号调制和解调方法及装置”的中国专利申请的优先权，其通过引用方式全部并入本文。
技术领域
本申请涉及光载无线通信技术领域，尤其涉及一种面向光载无线通信***的双信号调制和解调方法及装置。
背景技术
5G时代已经到来，它可以提供超1Gbps的通信速率，然而，未来的6G无线通信技术对带宽和容量的要求远远超过当前的5G技术，其中一个鲜明的特点就是要求具备“全频谱”通信能力。光载无线通信***尤其是光载毫米波/太赫兹通信***，结合了光纤通信大容量、高带宽、低延时和无线通信灵活接入的优势，可以为实现6G“全频谱”通信提供强有力地支撑。在光载无线通信***中，为了避免双边带调制信号由光纤色散诱导的功率衰落现象，一种可行的方案是采用双驱动马赫–曾德尔调制器(MZM)调制单边带信号在光纤中进行传输。然而，在利用双驱动MZM实现单边带信号调制时，通常会面临三个问题：第一，不能实现信号从电到光域的线性转换，通常只能使双驱动MZM工作于正交传输点来近似线性调制，这种近似的结果实际会导致信号在电色散补偿时存在误差，从而造成***性能的退化；第二，单边带信号不能充分利用发送端器件的带宽，导致电频谱效率降低一半，引起较大了成本浪费；最后，单边带信号经过平方律探测后会产生信号与信号拍频串扰(SSBI)，为了克服SSBI带来的性能退化，要么在发送端预留一个大小等于信号带宽的保护间隔，要么在接收端采用SSBI补偿技术，前者会让频谱效率减半而后者则增加了***的DSP成本和计算复杂度。
目前，已有人提出基于双驱动MZM的线性调制方法，可实现较好的电色散补偿效果。然而，一方面，该方案要求双驱动MZM的直流偏置电压与驱动信号必须完美匹配，一旦没有匹配会显著退化***的性能(实际***中直流漂移现象很容易导致两者不匹配)；另一方面，该方案只实现 单个边带信号的调制和传输，依然会浪费一半的器件带宽。为了改善***频谱效率、充分利用***的器件带宽，一种常用的方法是采用双生单边带方案，让两个边带信号都承载有效信息，既能充分利用***硬件设备的器件带宽，又可以使***的容量加倍。然而，在双生单边带信号的解调时，传统的光载无线通信***通常需要两套电滤波器、模数转换器和接收DSP模块，重复的硬件会显著增加***的硬件成本，并且大大降低该***与已部署的成熟商用***融合的可能性。
发明内容
针对现有技术中存在的问题，本申请实施例提供一种面向光载无线通信***的双信号调制和解调方法及***。
第一方面，本申请实施例提供一种面向光载无线通信***的双信号调制方法，包括：
基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；
对所述重组信号进行电色散预补偿；
将电色散预补偿后的所述重组信号进行极坐标信号转换，使得所述双生双边带信号或双生单边带信号用极坐标方式表示；
基于极坐标方式表示结果，构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；
基于两个射频输入信号进行电光调制。
进一步地，所述基于第一实值信号和第二实值信号进行信号重组得到重组信号，包括：
按第一关系模型，基于第一实值信号和第二实值信号进行信号重组得到重组信号；其中，所述第一关系模型包括：
s(t)＝A+s 1(t)-js 2(t)
其中，A为实数并且表示直流项，s 1(t)和s 2(t)分别表示信号重组后得到的两个重组信号，j表示虚数单位，t表示时间，s(t)表示重组后得到的双生双边带信号或双生单边带信号。
进一步地，基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号，包括：
按第二关系模型，基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为双驱动马赫–曾德尔调制器的两个射频输入信号；其中，所述第二关系模型包括：
Figure PCTCN2021120189-appb-000001
其中，V π代表双驱动马赫–曾德尔调制器的半波电压参数，π表示圆周率，cos -1表示反余弦函数，r max表示信号的最大幅值，t表示时间，V 1(t)表示第一驱动信号，V 2(t)表示第二驱动信号，θ(t)表示双生双边带或双生单边带信号在极坐标系下的幅值，r(t)表示双生双边带或双生单边带信号在极坐标系下的相位。
第二方面，本申请实施例提供了一种面向光载无线通信***的双信号解调方法，包括：
基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；
基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；
基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；
对所述重组信号进行电色散后补偿；
将电色散后补偿的重组信号进行信号分解得到第一实值信号和第二实值信号；
基于所述第一实值信号和第二实值信号进行信号解调。
进一步地，双信号解调方法还包括：
在载波与信号之间保留预设的保护间隔；
相应的，在基于采样数字信号进行载波提取时根据预设的保护间隔提取载波。
第三方面，本申请实施例提供了一种面向光载无线通信***的双信号调制装置，包括：
第一信号重组模块，用于基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；
电色散预补偿模块，用于对所述重组信号进行电色散预补偿；
极坐标信号转换模块，用于将电色散预补偿后的所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；
信号构造模块，用于基于极坐标方式表示结果构造两个驱动信号进行 数模转换，并在电光调制时作为调制器的两个射频输入信号；
调制模块，用于基于两个射频输入信号进行电光调制。
第四方面，本申请实施例提供了一种面向光载无线通信***的双信号解调装置，包括：
载波提取模块，用于基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；
信号恢复模块，用于基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；
第二信号重组模块，用于基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；
电色散后补偿模块，用于对所述重组信号进行电色散后补偿；
信号分解模块，用于将电色散后补偿的重组信号进行信号分解得到第一实值信号和第二实值信号；
信号解调模块，用于基于所述第一实值信号和第二实值信号进行信号解调。
第五方面，本申请实施例提供了一种支持双信号调制和解调的光载无线通信***，包括：光收发机和无线收发机；
在所述光收发机中实现如第一方面所述的面向光载无线通信***的双信号调制方法的步骤；和，
相应地，所述无线收发机中实现如下面向光载无线通信***的双信号解调方法的步骤：
基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；
基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；
基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；
将所述重组信号进行信号分解得到第一实值信号和第二实值信号；
基于所述第一实值信号和第二实值信号进行信号解调。
第六方面，本申请实施例提供了一种支持双信号调制和解调的光载无线通信***，包括:光收发机和无线收发机，
在所述无线收发机中实现如第二方面所述的面向光载无线通信***的双信号解调方法的步骤，和
相应地，在所述光收发机中实现如下面向光载无线通信***的双信号调制方法的步骤：
基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；
将所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；
基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；
基于两个射频输入信号进行电光调制。
第七方面，本申请实施例还提供了一种电子设备，包括存储器、处理器及存储在存储器上并可在处理器上运行的计算机程序，所述处理器执行所述程序时实现如上第一方面所述的面向光载无线通信***的双信号调制方法的步骤；或，该计算机程序被处理器执行时实现如上第二方面所述的面向光载无线通信***的双信号解调方法的步骤。
第八方面，本申请实施例还提供了一种电子设备，包括存储器、第一处理器、第二处理器、存储在所述存储器上并可在所述第一处理器上运行的第一计算机程序以及存储在所述存储器上并可在所述第二处理器上运行的第二计算机程序，所述第一处理器执行所述第一计算机程序时实现上第一方面所述的面向光载无线通信***的双信号调制方法的步骤；所述第二处理器执行所述第二计算机程序时实现如上第二方面所述的面向光载无线通信***的双信号解调方法的步骤。
第九方面，本申请实施例还提供了一种非暂态计算机可读存储介质，其上存储有计算机程序，该计算机程序被处理器执行时实现如上第一方面所述的面向光载无线通信***的双信号调制方法的步骤；或，该计算机程序被处理器执行时实现如上第二方面所述的面向光载无线通信***的双信号解调方法的步骤。
第十方面，本申请实施例还提供了一种非暂态计算机可读存储介质，其上存储有第一计算机程序和第二计算机程序，该第一计算机程序被第一处理器执行时实现如上第一方面所述的面向光载无线通信***的双信号调制方法的步骤；该第二计算机程序被第二处理器执行时实现如上第二方面所述的面向光载无线通信***的双信号解调方法的步骤。
由上述技术方案可知，本申请实施例提供的面向光载无线通信***的双信号调制和解调方法及装置，调制方法包括：基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；对所述重组信号进行电色散预补偿；将电色散预补偿后 的所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；基于两个射频输入信号进行电光调制。本申请实施例提供的调制方法能够充分利用收发件的带宽，从而一方面降低***器件成本，另一方面提升***通信容量。
附图说明
为了更清楚地说明本申请实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍，显而易见地，下面描述中的附图是本申请的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动的前提下，还可以根据这些附图获得其他的附图。
图1为本申请一实施例提供的面向光载无线通信***的双信号调制方法的流程示意图；
图2为本申请一实施例提供的支持双信号调制的光子辅助毫米波/太赫兹信号发射机结构示意图；
图3为本申请一实施例提供的支持双信号调制的发送DSP模块流程示意图；
图4为本申请一实施例提供的双生双边带信号在线性调制之前的电谱和之后的光谱示意图；
图5为本申请一实施例提供的双生单边带信号在线性调制之前的电谱和之后的光谱示意图；
图6为本申请一实施例提供的面向光载无线通信***的双信号解调方法的流程示意图；
图7为本申请一实施例提供的支持双信号解调的毫米波/太赫兹信号接收机结构示意图；
图8为光载无线通信***中一种传统的双生单边带信号收发机结构示意图；
图9为光载无线通信***中另一种传统的双生单边带信号接收机结构示意图；
图10为本申请一实施例提供的支持双信号解调的接收DSP模块流程示意图；
图11为本申请一实施例提供的面向光载无线通信***的双信号调制装置的结构示意图；
图12为本申请一实施例提供的面向光载无线通信***的双信号解调 装置的结构示意图；
图13为本申请另一实施例提供的支持双信号调制和解调的光载无线通信***的示意图；
图14为本申请一实施例提供的接收端恢复的双信号误差矢量幅度与接收光功率的关系曲线示意图；
图15为本申请一实施例提供的在双生双边带信号调制方案下，分别采用电色散预补偿和电色散后补偿方式接收端恢复的两个双边带信号误差矢量幅度与接收光功率的关系曲线示意图；
图16为本申请一实施例中提供的电子设备的实体结构示意图；
附图标记：
11、发送DSP模块；121、第一数模转换器；122、第二数模转换器；13、发送激光器；14、电光调制；15、本振激光器；16、标准单模光纤；17、光外差探测；18、带通滤波器；19、发射天线；111、第一信号生成模块；112、第二信号生成模块；113、信号重组；114、电色散预补偿；115、极坐标信号转换；116、第一驱动信号；117、第二驱动信号；21、接收天线；22、频率下变换；23、模数转换器；24、接收DSP模块；25、LSB处理；26、RSB处理；251、LSB光滤波器；252、LSB光电探测器；253、LSB发射天线；254、LSB接收天线254；255、LSB频率下变换；256、LSB模数转换器；257、LSB接收DSP模块；261、RSB光滤波器；262、RSB光电探测器；263、RSB发射天线；264、RSB接收天线；265、RSB频率下变换；266、RSB模数转换器；267、RSB接收DSP模块；27、LSB接收；28、RSB接收；271、低通滤波器；272、LSB模数转换器；273、LSB接收DSP模块；281、高通滤波器；282、RSB模数转换器；283、RSB接收DSP模块；241、带通滤波器；242、希尔伯特变换；243、第一乘法器；244、第二乘法器；245、第一低通滤波器；246、第二低通滤波器；247、电色散后补偿；248、信号分解；249、第一信号解调单元；2410、第二信号解调单元。
具体实施方式
为使本申请实施例的目的、技术方案和优点更加清楚，下面将结合本申请实施例中的附图，对本申请实施例中的技术方案进行清楚地描述，显然，所描述的实施例是本申请一部分实施例，而不是全部的实施例。基于本申请中的实施例，本领域普通技术人员在没有做出创造性劳动前提下所获得的所有其他实施例，都属于本申请保护的范围。下面将通过具体的实施例对本申请提供的面向光载无线通信***的双信号调制和解调方法进 行详细解释和说明。
图1为本申请一实施例提供的面向光载无线通信***的双信号调制方法的流程示意图；如图1所示，该方法包括：
步骤101：基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号。
步骤102：对所述重组信号进行电色散预补偿。
步骤103：将电色散预补偿后的所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示。
步骤104：基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号。
步骤105：基于两个射频输入信号进行电光调制。
在本实施例中，需要说明的是，本申请实施例提供的面向光载无线通信***的双信号调制方法应用于支持双信号调制的光子辅助毫米波/太赫兹信号发射机，所述支持双信号调制的光子辅助毫米波/太赫兹信号发射机结构示意图如图2所示，支持双信号调制的光子辅助毫米波/太赫兹信号发射机包括：发送DSP模块11、第一数模转换器121、第二数模转换器122、发送激光器13、电光调制14、本振激光器15、标准单模光纤16、光外差探测17、带通滤波器18和发射天线19；其中，发送DSP模块11的详细结构如图3所示，包括第一信号生成模块111、第二信号生成模块112、信号重组113、电色散预补偿114、极坐标信号转换115、第一驱动信号116和第二驱动信号117。
为了更好的理解本申请，下面结合实施例进一步阐述本申请的内容，但本申请不仅仅局限于下面的实施例。
具体地，发送DSP模块11完成双信号调制需要的数字信号处理，主要包括以下步骤。
信号重组步骤。假设a(t)和b(t)分别表示第一信号生成模块111和第二信号生成模块112产生的实值信号，即第一实值信号和第二实值信号，(格式不限，如PAM、DMT和CAP等)，所述第一实值信号和第二实值信号可以为任意实值信号，实值信号的频谱无论是否重叠均不影响本申请实施例所涉及的调制方法，本实施例中以两者频谱完全重叠为例(即两个信号具有相同的中频频率和相同的带宽)，下文中称a(t)为信号1，b(t)为信号2。经过信号重组113后，输出信号为：
s(t)＝A+s 1(t)-js 2(t)   (1)
其中，A为实数，代表直流项，s 1(t)和s 2(t)分别表示信号重组后得到的两个重组信号。当取：
Figure PCTCN2021120189-appb-000002
此时，s(t)表示一对双边带信号(双生双边带信号)，其中信号1(即第一实值信号)与信号2(即第二实值信号)频谱相互重叠，但在相位上呈90°正交关系，如图4所示，在本申请实施例中具有这种频谱的信号被称为双生双边带信号。另一方面，当改变s 1(t)和s 2(t)的表达式：
Figure PCTCN2021120189-appb-000003
其中，
Figure PCTCN2021120189-appb-000004
表示对实值信号x取希尔伯特变换。此时，s(t)表示一对单边带信号(双生单边带信号)，包括信号1的左边带(LSB)，表达式为
Figure PCTCN2021120189-appb-000005
以及信号2的右边带(RSB)，表达式为
Figure PCTCN2021120189-appb-000006
两者频谱不存在交叠，如图5所示。在本申请中具有这种频谱的信号被称为双生单边带信号。
电色散预补偿步骤。对重组的信号s(t)＝A+s 1(t)-js 2(t)进行电色散预补偿，以克服信号在光纤传输时色散带来的码间串扰。需要说明的是，这一步骤不是必须，比如可以在接收端采用电色散后补偿来替代。
极坐标信号转换步骤。把双生双边带或双生单边带的目标信号(即电色散预补偿后的重组信号)用极坐标方式表示，即
s(t)＝r(t)e jθ(t)    (4)
其中，r(t)＝abs[s(t)]和θ(t)＝angle[s(t)]分别代表双生双边带或双生单边带信号在极坐标系下的幅值和相位，abs和angle分别表示计算模值和相角函数。
构造两个驱动信号。用r max＝max[r(t)]表示信号的最大幅值，令
Figure PCTCN2021120189-appb-000007
其中，V π代表双驱动MZM的半波电压参数，π表示圆周率，cos -1表示反余弦函数。V 1(t)和V 2(t)在完成数模转换(DAC)操作后，分别作为双驱动MZM的上下两臂的射频驱动信号从而完成电光调制。
当双驱动MZM偏置在最大传输点，即上下两臂直流偏置引起的相位相等，用φ 0表示，在式(5)的驱动下，双驱动MZM输出的信号光表达式为：
Figure PCTCN2021120189-appb-000008
其中，E in(t)表示发送激光器13输出的光波。从式(6)可以看出，采用构造的两个信号驱动双驱动MZM时，双生双边带或双生单边带目标信号被线性调制到光场，两者的示意图分别如图4和图5所示。与传统正交偏置的双驱动MZM近似的线性调制不同，本实施可以实现目标信号从电域到光场理想的线性映射，因此，电色散补偿(发送端预补偿或接收端后补偿)能达到更好的效果。
在本实施例中，需要说明的是，本实施与之前已有的基于双驱动MZM的线性调制方法不同，已有方法一方面仅针对单边带信号进行线性调制，不能充分利用***器件的带宽；另一方面，已有方法在实现线性调制特性时，双驱动MZM仍偏置在正交传输点，即两臂直流偏置引起的相位差为
Figure PCTCN2021120189-appb-000009
因此，为了抵消正交点直流偏置带来的相位差，需把两个驱动信号分别设置为
Figure PCTCN2021120189-appb-000010
显而易见，此时输入的射频信号受到调制器直流偏置的约束。然而，在实际***中，调制器的直流偏置很容易随着工作温度的上升而发生漂移，一旦偏离正交工作点，就会导致直流偏置与驱动信号不匹配，从而破坏信号的线性调制效果，降低发送端信号的调制质量。
在本申请实施例中，这个问题得到解决，可释放调制器直流偏置对输入射频信号的限制。把双驱动MZM直流偏置设置在最大传输点，即两臂的直流偏置电压差为零，这一点在实际***中很好实现，同一个直流偏置电压分成两路分别供给双驱动MZM上下两臂，这样不管直流偏置电压随工作环境如何漂移，都不会破坏最大传输点这一偏置特性，因此，直流漂移不会影响线性调制的效果。除此之外，本申请实施例支持对双信号包括双生双边带和双生单边带信号的线性调制，既能增加发送端的通信容量，又可以充分利用发送端器件的带宽。
上述过程实现了双生双边带和双生单边带信号的线性调制，之后，信号光通过标准单模光纤16传输到达远端基站，在与一个本振激光器15耦合后采用光外差探测17进行光电转换，信号光与本振光拍频可产生所需的毫米波/太赫兹(Mm&THz)信号，该信号可通过带通滤波器18进行提取，然后通过发射天线19进行发射。
在本实施例中，需要说明的是，本申请实施例可应用于发送端，基于双驱动MZM，采用极坐标信号转换方法实现双信号的线性调制，可释放驱动信号与调制器直流偏置之间的约束，同时线性调制支持双生双边带或双生单边带信号高效的电色散补偿。此外，相对于传统的单边带信号调制方式，本申请实施例采用双信号调制既可以充分利用***器件的带宽，又 可以提升***的通信速率和容量。
在本实施例中，优选的，还包括设置双驱动马赫–曾德尔调制器工作于最大传输点，基于两个射频输入信号进行电光调制。
由上面技术方案可知，本申请实施例提供的面向光载无线通信***的双信号调制方法，通过基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；对所述重组信号进行电色散预补偿；将电色散预补偿后的所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；基于两个射频输入信号进行电光调制。本申请实施例提供的调制方法能够充分利用收发件的带宽，从而一方面降低***器件成本，另一方面提升***通信容量。
在上述实施例的基础上，在本实施例中，所述基于第一实值信号和第二实值信号进行信号重组得到重组信号，包括：
按第一关系模型，基于第一实值信号和第二实值信号进行信号重组得到重组信号；其中，所述第一关系模型包括：
s(t)＝A+s 1(t)-js 2(t)
其中，A为实数并且表示直流项，s 1(t)和s 2(t)分别表示信号重组后得到的两个重组信号，j表示虚数单位，t表示时间，s(t)表示重组后得到的双生双边带信号或双生单边带信号。
在本实施例中，需要说明的是，按第一关系模型，基于第一实值信号和第二实值信号进行信号重组得到重组信号，所述重组信号为双生双边带信号或双生单边带信号，有利于充分利用发送端器件的带宽，提高电频谱效率，从而实现节约成本。
在上述实施例的基础上，在本实施例中，基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号，包括：
按第二关系模型，基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为双驱动马赫–曾德尔调制器的两个射频输入信号；其中，所述第二关系模型包括：
Figure PCTCN2021120189-appb-000011
其中，V π代表双驱动马赫–曾德尔调制器的半波电压参数，π表示圆周 率，cos -1表示反余弦函数，r max表示信号的最大幅值，t表示时间，V 1(t)表示第一驱动信号，V 2(t)表示第二驱动信号，θ(t)表示双生双边带或双生单边带信号在极坐标系下的幅值，r(t)表示双生双边带或双生单边带信号在极坐标系下的相位。
在本实施例中，需要说明的是，本实施例这种实现信号线性调制方案，通过让双驱动马赫–曾德尔调制器偏置在最大传输点，释放了双驱动马赫–曾德尔调制器直流偏置对射频输入信号的约束，可避免直流漂移对信号线性调制效果的影响。
图6为本申请一实施例提供的面向光载无线通信***的双信号解调方法的流程示意图；如图6所示，该方法包括：
步骤601：基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号。
步骤602：基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号。
步骤603：基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号。
步骤604：对所述重组信号进行电色散后补偿。
步骤605：将电色散后补偿的重组信号进行信号分解得到第一实值信号和第二实值信号。
步骤606：基于所述第一实值信号和第二实值信号进行信号解调。
在本实施例中，需要说明的是，本申请实施例提供的面向光载无线通信***的双信号解调方法应用于支持双信号解调的毫米波/太赫兹信号接收机，所述支持双信号解调的毫米波/太赫兹信号接收机结构示意图如图7所示，支持双信号调制的光子辅助毫米波/太赫兹信号发射机包括：接收天线21、频率下变换22和模数转换器23和接收DSP模块24；其中，接收DSP模块24由带通滤波器241、希尔伯特变换242、第一乘法器243、第二乘法器244、第一低通滤波器245、第二低通滤波器246、电色散后补偿247、信号分解248、第一信号解调249和第二信号解调2410单元构成，参见图10。
为了更好的理解本申请，下面结合实施例进一步阐述本申请的内容，但本申请不仅仅局限于下面的实施例。
具体地，为了进一步体现本申请接收机的先进性，图8给出了光载无线通信***中一种传统的双生单边带信号收发机结构示意图，图8中包括左边带(LSB)处理25和右边带(RSB)处理26，其中，LSB处理25由 LSB光滤波器251、LSB光电探测器252、LSB发射天线253、LSB接收天线254、LSB频率下变换255、LSB模数转换器256和LSB接收DSP模块257构成，而RSB处理26由RSB光滤波器261、RSB光电探测器262、RSB发射天线263、RSB接收天线264、RSB频率下变换265、RSB模数转换器266和RSB接收DSP模块267构成；该***在光路上用光滤波器把LSB和RSB分开，然后用两套光电探测器、收发天线、频率下变换、模数转换器和DSP接收模块分别处理LSB和RSB信号。图9给出了光载无线通信***中另一种传统的双生单边带信号接收机结构示意图，图9中包括接收天线21、频率下变换22、LSB接收27和RSB接收28。其中，LSB接收27由低通滤波器271、LSB模数转换器272和LSB接收DSP模块273构成，而RSB接收28由低通滤波器281、RSB模数转换器282和RSB接收DSP模块283构成。图9所示接收机相对于图8来说，节省了大量的硬件成本，光路无需重复硬件，而电路则只需要一套天线和频率下变换模块，然而，在电路实现双生单边带信号的解调时，依然需要两套电滤波器、模数转换器和DSP接收模块。综上所述，与传统的双信号接收机相比，本申请提出的毫米波/太赫兹信号接收机可以显著降低接收机的硬件成本，不仅能支持双生双边带或双生单边带信号的解调，而且能兼容基于单信号调制和解调的光载无线通信***。
接收端采用外差混频方式完成毫米波/太赫兹信号的下变频，频率下变换22输出的信号可表示为：
E IF(t)＝M·{Acos[ω IFt+Δφ(t)]+s 1(t)·cos[ω IFt+Δφ(t)]+s 2(t)·sin[ω IFt+Δφ(t)]}    (7)
其中，M为常数，它与发送激光器13和本振激光器15输出的平均光功率成正比，ω IF和Δφ(t)分别表示毫米波/太赫兹信号下变频后的中心角频率和携带的相位噪声。式(7)中，第一项为中频载波，第二项和第三项分别表示两路不同信号。
进一步地，对上述中频信号进行模数转换，然后利用单个接收DSP模块完成双信号的解调。接收DSP模块24的详细结构如图10所示，包括带通滤波器241、希尔伯特变换242、第一乘法器243、第二乘法器244、第一低通滤波器245、第二低通滤波器246、电色散后补偿247、信号分解248、第一信号解调249和第二信号解调2410单元。接收DSP模块24实现双信号的解调包括以下步骤：
载波提取步骤。通过一个带通滤波器241提取载波，其表达式为：
E carr＝Acos[ω IFt+Δφ(t)]   (8)
进一步地，为了更好的提取载波，可以让载波与信号(边带信号，即采样信号实际由载波和边带信号)之间保留一个较小的保护间隔(如 500MHz)，由于在毫米波/太赫兹通信***中，信号的带宽可高达10GHz以上，因此，这样的间隔不会对频谱效率带来明显的下降。
信号恢复。首先，第一步用第一乘法器243让提取的载波与原始信号(即采样信号，包括载波和边带信号)分量相乘，再经过第一低通滤波器245滤除高频项即可恢复第一路信号，如下式所示：
LPF[E carr(t)×E IF(t)]∝s 1(t)    (9)
其中，LPF[·]代表低通滤波操作。其次，对提取的载波做希尔伯特变换可得
Figure PCTCN2021120189-appb-000012
随后采用与上述第一步同样的信号恢复方法，利用第二乘法器244和第二低通滤波器246可恢复第二路信号，如下式所示：
Figure PCTCN2021120189-appb-000013
电色散后补偿步骤。对恢复后的两路信号进行重组，即s r(t)＝s 1(t)-js 2(t)，然后进行电色散后补偿247，以克服信号在光纤传输时色散带来的码间串扰。需要说明的是，这一步骤不是必须，如果发送端已采用电色散预补偿则可以跳过。
信号分解步骤。接收端信号分解是发送端信号重组的逆向过程，目的是从获得的和s 1(t)和s 2(t)中分离目标信号a(t)和b(t)。对于双生双边带信号，根据式(2)，a(t)和b(t)可通过下式恢复：
Figure PCTCN2021120189-appb-000014
而对于双生单边带信号，根据式(3)，a(t)和b(t)可通过下式恢复：
Figure PCTCN2021120189-appb-000015
信号解调。经过信号分解248后，我们分离了a(t)和b(t)，随后，分别采用第一信号解调249和第二信号解调2410完成a(t)和b(t)的解调，解调操作与常规信号解调步骤一致，这里不做单独介绍。
在本实施中，需要说明的是，无论是双生双边带还是双生单边带信号，由于在信号恢复过程中没有信号与信号拍频操作，因此不存在SSBI的影响，这是本申请的又一特色之处。
在本实施例中，需要说明的是，本申请实施例可应用在接收端，无需两套重复的硬件设备，双信号仅通过单套硬件完成接收再配合特定DSP处理即可分别恢复，因此，显著降低了双信号解调对硬件设备的需求，实际上，双信号的调制及解调与传统的单边带/双边带调制***在硬件需求上 完全兼容。
由上面技术方案可知，本申请实施例提供的面向光载无线通信***的双信号解调方法，通过基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；对所述重组信号进行电色散后补偿；将电色散后补偿的重组信号进行信号分解得到第一实值信号和第二实值信号；基于所述第一实值信号和第二实值信号进行信号解调；本申请实施例应用在双生双边带或双生单边带信号的无线接收端，可显著降低双信号解调对硬件设备的需求，仅采用传统的无线接收链路(一个频率下变换模块、一个模数转换器)配合相应的数字信号处理(DSP)即可完成双信号的接收和解调工作。
在上述实施例基础上，在本实施例中，还包括：
在载波与信号之间保留预设的保护间隔；
相应的，在基于采样数字信号进行载波提取时根据预设的保护间隔提取载波。
在本实施例中，需要说明的是，为了更好的提取载波，可以让载波与信号之间保留一个较小的保护间隔(如500MHz)，由于在毫米波/太赫兹通信***中，信号的带宽可高达10GHz以上，因此，这样的间隔不会对频谱效率带来明显的下降。
在本实施例中，需要说明的是，针对预设的保护间隔，可以为0.3GHz～1.0GHz。
由上面技术方案可知，本申请实施例提供的面向光载无线通信***的双信号解调方法，由于信号恢复采用载波和信号混频的方式，因此使得***完全不受SSBI的影响，仅仅只需要保留一个很小的预设保护间隔用于提取载波即可。
图11为本申请一实施例提供的面向光载无线通信***的双信号调制装置的结构示意图，如图11所示，该***包括：第一信号重组模块1101、电色散预补偿模块1102、极坐标信号转换模块1103、信号构造模块1104和调制模块1105，其中：
其中，第一信号重组模块1101，用于基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；
电色散预补偿模块1102，用于对所述重组信号进行电色散预补偿；
极坐标信号转换模块1103，用于将电色散预补偿后的所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；
信号构造模块1104，用于基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；
调制模块1105，用于基于两个射频输入信号进行电光调制。
本申请实施例提供的面向光载无线通信***的双信号调制装置具体可以用于执行上述实施例的面向光载无线通信***的双信号调制方法，其技术原理和有益效果类似，具体可参见上述实施例，此处不再赘述。
图12为本申请一实施例提供的面向光载无线通信***的双信号解调装置的结构示意图，如图12所示，该***包括：载波提取模块1201、信号恢复模块1202、第二信号重组模块1203、电色散后补偿模块1204、信号分解模块1205和信号解调模块1206，其中：
其中，载波提取模块1201，用于基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；
信号恢复模块1202，用于基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；
第二信号重组模块1203，用于基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；
电色散后补偿模块1204，用于对所述重组信号进行电色散后补偿；
信号分解模块1205，用于将电色散后补偿的重组信号进行信号分解得到第一实值信号和第二实值信号；
信号解调模块1206，用于基于所述第一实值信号和第二实值信号进行信号解调。
本申请实施例提供的面向光载无线通信***的双信号解调装置具体可以用于执行上述实施例的面向光载无线通信***的双信号解调方法，其技术原理和有益效果类似，具体可参见上述实施例，此处不再赘述。
图13为本申请一实施例提供的支持双信号调制和解调的光载无线通信***的结构示意图，如图13所示，该***包括：光收发机和无线收发机，其中：
其中，在所述光收发机中实现如第一方面所述的面向光载无线通信***的双信号调制方法的步骤；和，
相应地，所述无线收发机中实现如下面向光载无线通信***的双信号解调方法的步骤：
基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；
基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；
基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；
将所述重组信号进行信号分解得到第一实值信号和第二实值信号；
基于所述第一实值信号和第二实值信号进行信号解调。
在上述实施例基础上，本申请一实施例提供的支持双信号调制和解调的光载无线通信***，该***包括:光收发机和无线收发机，其中：
在所述无线收发机中实现如第二方面所述的面向光载无线通信***的双信号解调方法的步骤。
相应地，在所述光收发机中实现如下面向光载无线通信***的双信号调制方法的步骤：
基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；
将所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；
基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；
基于两个射频输入信号进行电光调制。
在本实施例中，可以理解的是，发送端的电色散预补偿和接收端的电色散后补偿两者选其一使用。
在本实施例中，需要说明的是，图13给出了本申请实施例提供的一种支持双信号调制和解调的光载无线通信***结构示意图。整个***由光收发机和无线收发机构成，在光收发机中，利用极坐标信号转换方法基于单个双驱动MZM实现双生双边带或双生单边带信号的调制，然后通过光纤传输到远端，再耦合一路本振光利用光外差拍频产生毫米波/太赫兹信号，毫米波/太赫兹信号频率可调。在无线收发机中，目标毫米波/太赫兹信号先通过混频器完成下变换，再经过模数转换后送给接收DSP模块，在DSP中利用载波与信号相乘的方法依次恢复两路信号。
基于图13所示的***结构，经过25公里光纤传输并采用色散预补偿方案，图14给出了载波频率为60GHz、总速率为50Gbps的双信号解调后误差矢量幅度与接收光功率的关系曲线。其中，两个信号都采用 CAP-32QAM调制格式，波特率为5Gbaud/s。可以发现，无论是双生单边带还是双生双边带调制方式，两个信号的误差矢量幅度随着光功率的提升而下降，在－16dBm时，误差矢量幅度接近6％。针对双生双边带信号调制格式，图15进一步给出了在采用电色散预补偿和电色散后补偿两种方式下，接收端恢复的信号误差矢量幅度与接收光功率的关系曲线，可以发现，在本***中两个双边带信号经过电色散后补偿可以达到电色散预补偿方案同样的效果，说明此时双边带信号经过光纤传输没有出现明显的功率衰落现象。也就是说，本申请能够克服传统光载无线通信***中双边带信号由光纤色散诱导的功率衰落问题。
由此可见，本申请实施例提供的支持双信号调制和解调的光载无线通信***，因为所述光收发机能实现如上述的各面向光载无线通信***的双信号调制方法的步骤，所以在实现双生双边带或双生单边带两种不同的双信号线性电光调制的同时，释放了双驱动MZM的射频驱动信号与调制器直流偏置之间的约束，支持双信号高效的电色散补偿，克服了传统双边带信号的功率衰落问题；此外，通过双生双边带或双生单边带调制能够充分利用收发器件的带宽，一方面降低***器件成本，另一方面提升***通信容量；又因为所述无线收发机能实现如上述的各面向光载无线通信***的双信号解调方法的步骤，所以在双生双边带或双生单边带信号的无线接收端，可显著降低双信号解调对硬件设备的需求，仅采用一个频率下变换模块、一个模数转换器)配合相应的数字信号处理(DSP，即可完成双信号的接收和解调工作，除此之外，无论是双生双边带还是双生单边带调制方式，双信号的解调完全不受SSBI的影响，而代价仅需设置一个很小的保护间隔；因此，本申请提供的支持双信号调制和解调的光载无线通信***可以在一个较低的***复杂度和部署成本情况下，提高现有光载无线通信***的通信速率和频谱效率，有助于实现面向6G的大容量、高性能光子毫米波/太赫兹通信***。
基于相同的发明构思，本申请实施例提供一种电子设备，参见图16，电子设备具体包括如下内容：处理器1601、通信接口1603、存储器1602和通信总线1604；
其中，处理器1601、通信接口1603、存储器1602通过通信总线1604完成相互间的通信；通信接口1603用于实现各建模软件及智能制造装备模块库等相关设备之间的信息传输；处理器1601用于调用存储器1602中的计算机程序，处理器执行计算机程序时实现上述各方法实施例所提供的方法，例如，处理器执行计算机程序时实现下述步骤：基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带 信号或双生单边带信号；对所述重组信号进行电色散预补偿；将电色散预补偿后的所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；基于两个射频输入信号进行电光调制；和/或；基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；对所述重组信号进行电色散后补偿；将电色散后补偿的重组信号进行信号分解得到第一实值信号和第二实值信号；基于所述第一实值信号和第二实值信号进行信号解调。
基于相同的发明构思，本申请又一实施例还提供一种非暂态计算机可读存储介质，其上存储有计算机程序，该计算机程序被处理器执行时实现以执行上述各方法实施例提供的方法，例如，基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；对所述重组信号进行电色散预补偿；将电色散预补偿后的所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；基于两个射频输入信号进行电光调制；和/或；基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；对所述重组信号进行电色散后补偿；将电色散后补偿的重组信号进行信号分解得到第一实值信号和第二实值信号；基于所述第一实值信号和第二实值信号进行信号解调。
以上所描述的***实施例仅仅是示意性的，其中作为分离部件说明的单元可以是或者也可以不是物理上分开的，作为单元显示的部件可以是或者也可以不是物理单元，即可以位于一个地方，或者也可以分布到多个网络单元上。可以根据实际的需要选择其中的部分或者全部模块来实现本实施例方案的目的。本领域普通技术人员在不付出创造性的劳动的情况下，即可以理解并实施。
通过以上的实施方式的描述，本领域的技术人员可以清楚地了解到各 实施方式可借助软件加必需的通用硬件平台的方式来实现，当然也可以通过硬件。基于这样的理解，上述技术方案本质上或者说对现有技术做出贡献的部分可以以软件产品的形式体现出来，该计算机软件产品可以存储在计算机可读存储介质中，如ROM/RAM、磁碟、光盘等，包括若干指令用以使得一台计算机设备(可以是个人计算机，服务器，或者网络设备等)执行各个实施例或者实施例的某些部分的方法。
此外，在本申请中，诸如“第一”、“第二”仅用于描述目的，而不能理解为指示或暗示相对重要性或者隐含指明所指示的技术特征的数量。由此，限定有“第一”、“第二”的特征可以明示或者隐含地包括至少一个该特征。在本申请的描述中，“多个”的含义是至少两个，例如两个，三个等，除非另有明确具体的限定。
此外，在本申请中，诸如第一和第二等之类的关系术语仅仅用来将一个实体或者操作与另一个实体或操作区分开来，而不一定要求或者暗示这些实体或操作之间存在任何这种实际的关系或者顺序。而且，术语“包括”、“包含”或者其任何其他变体意在涵盖非排他性的包含，从而使得包括一系列要素的过程、方法、物品或者设备不仅包括那些要素，而且还包括没有明确列出的其他要素，或者是还包括为这种过程、方法、物品或者设备所固有的要素。在没有更多限制的情况下，由语句“包括一个……”限定的要素，并不排除在包括要素的过程、方法、物品或者设备中还存在另外的相同要素。
此外，在本说明书的描述中，参考术语“一个实施例”、“一些实施例”、“示例”、“具体示例”、或“一些示例”等的描述意指结合该实施例或示例描述的具体特征、结构、材料或者特点包含于本申请的至少一个实施例或示例中。在本说明书中，对上述术语的示意性表述不必须针对的是相同的实施例或示例。而且，描述的具体特征、结构、材料或者特点可以在任一个或多个实施例或示例中以合适的方式结合。此外，在不相互矛盾的情况下，本领域的技术人员可以将本说明书中描述的不同实施例或示例以及不同实施例或示例的特征进行结合和组合。
最后应说明的是：以上实施例仅用以说明本申请的技术方案，而非对其限制；尽管参照前述实施例对本申请进行了详细的说明，本领域的普通技术人员应当理解：其依然可以对前述各实施例所记载的技术方案进行修改，或者对其中部分技术特征进行等同替换；而这些修改或替换，并不使相应技术方案的本质脱离本申请各实施例技术方案的精神和范围。

Claims (13)

  1. 一种面向光载无线通信***的双信号调制方法，其特征在于，包括：
    基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；
    对所述重组信号进行电色散预补偿；
    将电色散预补偿后的所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；
    基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；
    基于两个射频输入信号进行电光调制。
  2. 根据权利要求1所述的面向光载无线通信***的双信号调制方法，其特征在于，所述基于第一实值信号和第二实值信号进行信号重组得到重组信号，包括：
    按第一关系模型，基于第一实值信号和第二实值信号进行信号重组得到重组信号；其中，所述第一关系模型包括：
    s(t)＝A+s 1(t)-js 2(t)
    其中，A为实数并且表示直流项，s 1(t)和s 2(t)分别表示信号重组后得到的两个重组信号，j表示虚数单位，t表示时间，s(t)表示重组后得到的双生双边带信号或双生单边带信号。
  3. 根据权利要求1所述的面向光载无线通信***的双信号调制方法，其特征在于，基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号，包括：
    按第二关系模型，基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为双驱动马赫–曾德尔调制器的两个射频输入信号；其中，所述第二关系模型包括：
    Figure PCTCN2021120189-appb-100001
    其中，V π代表双驱动马赫–曾德尔调制器的半波电压参数，π表示圆周率，cos -1表示反余弦函数，r max表示信号的最大幅值，t表示时间，V 1(t)表示第一驱动信号，V 2(t)表示第二驱动信号，θ(t)表示双生双边带或双生单边带信号在极坐标系下的幅值，r(t)表示双生双边带或双生单边带信号在 极坐标系下的相位。
  4. 一种面向光载无线通信***的双信号解调方法，其特征在于，包括：
    基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；
    基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；
    基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；
    对所述重组信号进行电色散后补偿；
    将电色散后补偿的重组信号进行信号分解得到第一实值信号和第二实值信号；
    基于所述第一实值信号和第二实值信号进行信号解调。
  5. 根据权利要求4所述的面向光载无线通信***的双信号解调方法，其特征在于，还包括：
    在载波与信号之间保留预设的保护间隔；
    相应的，在基于采样数字信号进行载波提取时根据预设的保护间隔提取载波。
  6. 一种面向光载无线通信***的双信号调制装置，其特征在于，包括：
    第一信号重组模块，用于基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；
    电色散预补偿模块，用于对所述重组信号进行电色散预补偿；
    极坐标信号转换模块，用于将电色散预补偿后的所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；
    信号构造模块，用于基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光调制时作为调制器的两个射频输入信号；
    调制模块，用于基于两个射频输入信号进行电光调制。
  7. 一种面向光载无线通信***的双信号解调装置，其特征在于，包括：
    载波提取模块，用于基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；
    信号恢复模块，用于基于提取到的载波进行信号恢复；所述信号恢复 为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；
    第二信号重组模块，用于基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；
    电色散后补偿模块，用于对所述重组信号进行电色散后补偿；
    信号分解模块，用于将电色散后补偿的重组信号进行信号分解得到第一实值信号和第二实值信号；
    信号解调模块，用于基于所述第一实值信号和第二实值信号进行信号解调。
  8. 一种支持双信号调制和解调的光载无线通信***，其特征在于，包括：光收发机和无线收发机；
    在所述光收发机中实现如权利要求1-3任一项所述的面向光载无线通信***的双信号调制方法的步骤；和，
    相应地，所述无线收发机中实现如下面向光载无线通信***的双信号解调方法的步骤：
    基于采样数字信号进行载波提取；所述采样数字信号包括载波，和，双生双边带信号或双生单边带信号；
    基于提取到的载波进行信号恢复；所述信号恢复为所述提取到的载波与所述采样数字信号分量相乘，再滤除高频项得到恢复后的第一路信号和第二路信号；
    基于恢复后的第一路信号和第二路信号进行信号重组得到对应的重组信号；
    将所述重组信号进行信号分解得到第一实值信号和第二实值信号；
    基于所述第一实值信号和第二实值信号进行信号解调。
  9. 一种支持双信号调制和解调的光载无线通信***，其特征在于，包括：光收发机和无线收发机；
    在所述无线收发机中实现如权利要求4或5所述的面向光载无线通信***的双信号解调方法的步骤；和，
    相应地，在所述光收发机中实现如下面向光载无线通信***的双信号调制方法的步骤：
    基于第一实值信号和第二实值信号进行信号重组得到重组信号；所述重组信号为双生双边带信号或双生单边带信号；
    将所述重组信号进行极坐标信号转换使得所述双生双边带信号或双生单边带信号用极坐标方式表示；
    基于极坐标方式表示结果构造两个驱动信号进行数模转换，并在电光 调制时作为调制器的两个射频输入信号；
    基于两个射频输入信号进行电光调制。
  10. 一种电子设备，包括存储器、处理器及存储在存储器上并可在处理器上运行的计算机程序，其特征在于，所述处理器执行所述程序时实现如权利要求1～3任一项所述的面向光载无线通信***的双信号调制方法的步骤；和/或，该计算机程序被处理器执行时实现如权利要求4或5所述的面向光载无线通信***的双信号解调方法的步骤。
  11. 一种电子设备，其特征在于，包括存储器、第一处理器、第二处理器、存储在所述存储器上并可在所述第一处理器上运行的第一计算机程序以及存储在所述存储器上并可在所述第二处理器上运行的第二计算机程序，所述第一处理器执行所述第一计算机程序时实现如权利要求1～3任一项所述的面向光载无线通信***的双信号调制方法的步骤；所述第二处理器执行所述第二计算机程序时实现如权利要求4或5所述的面向光载无线通信***的双信号解调方法的步骤。
  12. 一种非暂态计算机可读存储介质，其上存储有计算机程序，其特征在于，该计算机程序被处理器执行时实现如权利要求1～3任一项所述的面向光载无线通信***的双信号调制方法的步骤；和/或，该计算机程序被处理器执行时实现如权利要求4或5所述的面向光载无线通信***的双信号解调方法的步骤。
  13. 一种非暂态计算机可读存储介质，其特征在于，其上存储有第一计算机程序和第二计算机程序，该第一计算机程序被第一处理器执行时实现如权利要求1～3任一项所述的面向光载无线通信***的双信号调制方法的步骤；该第二计算机程序被第二处理器执行时实现如权利要求4或5所述的面向光载无线通信***的双信号解调方法的步骤。
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CN112804007B (zh) * 2021-04-13 2021-08-31 网络通信与安全紫金山实验室 面向光载无线通信***的双信号调制和解调方法及装置

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN110178321A (zh) * 2017-01-17 2019-08-27 华为技术有限公司 信号发射方法及装置、发射机、信号传输***
CN110995349A (zh) * 2019-11-22 2020-04-10 中山大学 一种基于ddmzm的无ssbi的直接检测方法
CN111130650A (zh) * 2019-12-30 2020-05-08 武汉邮电科学研究院有限公司 强度调制直接接收的光信号生成方法、接收方法及设备
CN111131122A (zh) * 2019-12-31 2020-05-08 武汉邮电科学研究院有限公司 基于dmt调制和拍频检测的光传输***均衡方法及装置
US20210044360A1 (en) * 2018-01-24 2021-02-11 Inphi Corporation Probabilistic shaping techniques for high performance coherent optical transceivers
CN112804007A (zh) * 2021-04-13 2021-05-14 网络通信与安全紫金山实验室 面向光载无线通信***的双信号调制和解调方法及装置

Family Cites Families (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7499653B2 (en) * 2003-07-14 2009-03-03 Hrl Laboratories, Llc Multiple wavelength photonic oscillator
US20060083520A1 (en) * 2004-10-15 2006-04-20 Peter Healey Communication by radio waves and optical waveguides
US8909065B2 (en) * 2011-07-15 2014-12-09 Intel Mobile Communications GmbH Adjustable delayer, method for delaying an input signal and polar transmitter
US8804874B2 (en) * 2012-01-20 2014-08-12 Mediatek Inc. Polar transmitter having digital processing block used for adjusting frequency modulating signal for frequency deviation of frequency modulated clock and related method thereof
CN105471804B (zh) * 2014-09-11 2019-03-15 北京计算机技术及应用研究所 一种毫米波非视距通信***及其方法
WO2017070949A1 (zh) * 2015-10-30 2017-05-04 华为技术有限公司 光通信***中处理信号的装置和方法
CN111064691B (zh) * 2016-01-27 2024-02-09 华为技术有限公司 发射机、接收机和信号处理的方法
CN105897339B (zh) * 2016-06-30 2018-04-13 山东大学 一种基于开关键控可调谐光滤波器的可重构RoF***及其工作方法与应用
CN108964779B (zh) * 2018-07-23 2019-10-29 南京航空航天大学 基于频谱交织光本振的信道化接收方法及装置
CN110932787B (zh) * 2019-11-29 2021-04-27 中国舰船研究设计中心 一种基于直调激光器的跳频通信***和跳频信号生成方法

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN110178321A (zh) * 2017-01-17 2019-08-27 华为技术有限公司 信号发射方法及装置、发射机、信号传输***
US20210044360A1 (en) * 2018-01-24 2021-02-11 Inphi Corporation Probabilistic shaping techniques for high performance coherent optical transceivers
CN110995349A (zh) * 2019-11-22 2020-04-10 中山大学 一种基于ddmzm的无ssbi的直接检测方法
CN111130650A (zh) * 2019-12-30 2020-05-08 武汉邮电科学研究院有限公司 强度调制直接接收的光信号生成方法、接收方法及设备
CN111131122A (zh) * 2019-12-31 2020-05-08 武汉邮电科学研究院有限公司 基于dmt调制和拍频检测的光传输***均衡方法及装置
CN112804007A (zh) * 2021-04-13 2021-05-14 网络通信与安全紫金山实验室 面向光载无线通信***的双信号调制和解调方法及装置

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