WO2022117985A1 - Circuit d'entraînement - Google Patents

Circuit d'entraînement Download PDF

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Publication number
WO2022117985A1
WO2022117985A1 PCT/GB2021/052943 GB2021052943W WO2022117985A1 WO 2022117985 A1 WO2022117985 A1 WO 2022117985A1 GB 2021052943 W GB2021052943 W GB 2021052943W WO 2022117985 A1 WO2022117985 A1 WO 2022117985A1
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WO
WIPO (PCT)
Prior art keywords
drive circuit
resonant
coil
inductor
low
Prior art date
Application number
PCT/GB2021/052943
Other languages
English (en)
Inventor
Samer ALDHAHER
Original Assignee
Dyson Technology Limited
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Dyson Technology Limited filed Critical Dyson Technology Limited
Priority to CN202180081401.2A priority Critical patent/CN116584027A/zh
Publication of WO2022117985A1 publication Critical patent/WO2022117985A1/fr

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B6/00—Heating by electric, magnetic or electromagnetic fields
    • H05B6/02—Induction heating
    • H05B6/06—Control, e.g. of temperature, of power
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4815—Resonant converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B6/00—Heating by electric, magnetic or electromagnetic fields
    • H05B6/02—Induction heating
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B6/00—Heating by electric, magnetic or electromagnetic fields
    • H05B6/02—Induction heating
    • H05B6/10—Induction heating apparatus, other than furnaces, for specific applications
    • H05B6/105—Induction heating apparatus, other than furnaces, for specific applications using a susceptor
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode

Definitions

  • the present invention relates to a drive circuit to drive an induction heating system.
  • Induction heating systems operate by inducing eddy currents in electrical conductors, with the eddy currents induced by varying a magnetic field applied to the electrical conductor.
  • a varying magnetic field may be achieved by using switches to change the current applied to a coil that is used to generate the magnetic field.
  • a drive circuit to drive an induction heating system comprising a full-bridge inverter having first and second legs, each of the first and second legs comprising a high-side switch and a low-side switch, a coil to be driven by the full-bridge inverter to generate a magnetic field, a first plurality of resonant networks to enable zero-voltage switching of the high- and low- side switches, and a second plurality of resonant networks each to provide a constant current output to the coil.
  • the drive circuit according to the first aspect of the present invention may be advantageous as the drive circuit comprises a first plurality of resonant networks to enable zero-voltage switching of the high- and low- side switches of, and a second plurality of resonant networks each to provide a constant current output to the coil.
  • the first plurality of resonant networks to enable zero-voltage switching, switching losses associated with the high-and low-side switches may be reduced, thereby enabling the switches to be operated at higher frequencies than switches operated with hard switching conditions.
  • a size of the coil required may be reduced, which may lead to a smaller form-factor for products incorporating the induction heating system.
  • the magnetic field transmitted by the coil may vary depending on the load presented by the susceptor, as the varying load may affect the effective resistive load, which brings about a change in the current passing through the coil. Such a variation in current may be undesirable, and may lead to less power being delivered to the load. Furthermore, if there is no load a short circuit may occur. Such problems may be mitigated by utilising the second plurality of resonant networks to provide a constant current output to the coil, ie a constant current irrespective of resistive load.
  • Each of the first resonant networks may comprise an inductor and a capacitor connected in series.
  • Each of the first resonant networks may comprise an inductor connected to a common node between the high- and low-side switches of a respective one of the first and second legs, and a capacitor connected in series with the inductor, the capacitor connected to ground.
  • Such an arrangement may minimise a number of inductors required compared to, for example, an arrangement where a resonant network is provided for each high-side and low-side switch.
  • Each of the first resonant networks may be connected in parallel with a respective one of the low-side switches.
  • Each of the first resonant networks may be connected in parallel with a respective higher low-side switch, for example such that there is one first resonant network associated with each high- or low-side switch. This may reduce a voltage rating required for each inductor of the first resonant networks, and may reduce switching losses where high voltage switching occurs.
  • Each of the second plurality of resonant networks may comprise an LCL resonant circuit.
  • Each of the second plurality of resonant networks may define an impedance transformation network. Use of such an LCL resonant circuit may provide a constant current output to the coil.
  • Each of the LCL resonant circuits may comprise first and second inductors connected in series, with a capacitor connected in parallel at a point between the first and second inductors.
  • the first and second inductors of each LCL resonant circuit may be connected in series with the coil, whilst the capacitor of each LCL resonant circuit may be connected in parallel with the coil.
  • the first and second inductors of each LCL resonant circuit may be connected in series with an effective resistive load, whilst the capacitor of each LCL resonant circuit may be connected in parallel with the effective resistive load.
  • each LCL resonant circuit may comprise a first inductor connected in series with the coil, and a capacitor connected in parallel at a point between the first inductor and the coil.
  • the coil may act as a second inductor for each of the LCL resonant circuits. This may reduce a number of components required for the drive circuit compared to, for example, a drive circuit where separate inductors are used for the LCL resonant circuits in addition to the coil, which may reduce complexity and cost.
  • the coil may have a total inductance value
  • the drive circuit may comprise a first capacitor connected in series with the coil on a first side of the coil, and a second capacitor connected in series with the coil on a second side of the coil.
  • the first and second capacitors may have a capacitance tuned to resonate with an inductance that corresponds to the total inductance minus the inductance that forms part of each of the LCL resonant networks.
  • the total inductance value of the coil may comprise first and second inductance values each corresponding to an inductance value of a respective LCL resonant network, and the first and second capacitors may have a capacitance tuned to resonate with an inductance that corresponds to the total inductance minus the first and second inductance values.
  • the first and second capacitors may smooth a voltage waveform provided to the coil, and having first and second capacitors may minimise EMI
  • the drive circuit may comprise a plurality of filters, each filter connected between the coil and a common node between the high- and low-side switches of a respective one of the first and second legs.
  • Each filter may be to smooth a voltage waveform from a respective high- or low- side switch of the first and second legs, for example to convert a square voltage waveform to a substantially sinusoidal waveform.
  • Each filter may comprise an inductor and a capacitor connected in series. Each filter may comprise a respective third resonant network. Each filter may comprise an LC series filter. Each filter may comprise a resonant frequency tuned to the switching frequency of the full-bridge inverter.
  • each of the second plurality of resonant networks comprises an LCL resonant circuit
  • the inductor of each filter may form part of a respective LCL resonant circuit.
  • Each of the LCL resonant circuits may comprise first and second inductors connected in series, with a capacitor connected in parallel at a point between the first and second inductors.
  • the inductor of each filter may act as the first inductor of a respective LCL resonant circuit. This may reduce component count, complexity and cost compared to, for example, an arrangement where the filters and the LCL resonant circuits comprise separate inductors.
  • each filter may have a resonant frequency that does not equal a switching frequency of the full-bridge inverter.
  • Each second resonant network may comprise an LCL resonant circuit defined by a first inductor that also forms part of a respective LC series filter, a second inductor connected in series with the first inductor, the second inductor defined by the coil, and a capacitor connected in parallel with the first and second inductors at a point between the first and second inductors.
  • a switching frequency of the full-bridge inverter may be greater than or equal to 1MHz.
  • the high- and low- side switches may be to operate at a switching frequency greater than or equal to 1MHz.
  • the high- and low- side switches may comprise gallium nitride (GaN) or silicon carbide (SiC) switches.
  • the drive circuit may comprise a full-wave rectifier to convert an AC voltage supply to a DC voltage, and the rectifier may be to output a waveform having a ripple of at least 50%.
  • the rectifier may be to output a waveform having a ripple of 100%. This may minimise or remove the need for a storage capacitor, which may reduce component cost, number and size.
  • the drive circuit may be to receive power from an AC power supply.
  • the drive circuit may comprise a power factor correction circuit connected between the full-wave rectifier and the full-bridge inverter. This may remove modulation by the mains frequency from current output to the coil
  • the drive circuit may be to receive power from a DC power supply.
  • Figure 1 is a schematic illustrating a first embodiment of a drive circuit according to the present invention
  • Figure 2 illustrates current output by an inverter of the drive circuit of Figure 1
  • Figure 3 is a schematic illustrating a second embodiment of a drive circuit according to the present invention.
  • Figure 4 illustrates current output by an inverter of the drive circuit of Figure 3
  • Figure 5 is a schematic illustrating a third embodiment of a drive circuit according to the present invention
  • Figure 6 is a schematic illustrating a fourth embodiment of a drive circuit according to the present invention.
  • Figure 7 is a schematic illustrating a fifth embodiment of a drive circuit according to the present invention.
  • Figure 8 is a schematic illustrating a sixth embodiment of a drive circuit according to the present invention.
  • Figure 9 is a schematic illustration of drive signals, voltages and currents utilised in the drive circuit of Figure 8.
  • a drive circuit, generally designated 10, to drive an induction heating system is shown in Figure 1.
  • the drive circuit 10 comprises an AC power supply 12, a rectifier 14, a full-bridge inverter 16, an induction coil 18, a first pair of resonant networks 20,22, a second pair of resonant networks 24,26, and a third pair of resonant networks 28,30.
  • the AC power supply 12 supplies AC voltage to the rectifier 14.
  • the rectifier 14 is a full-wave rectifier comprising a full-bridge of diodes D1-D4.
  • the rectifier 14 is to convert AC voltage received from the AC power supply 12 to DC rectified voltage to be supplied to the full-bridge inverter 16.
  • the rectifier 14 is connected to ground.
  • the full-bridge inverter 16 receives DC rectified voltage from the rectifier 14.
  • the fullbridge inverter 16 comprises a H-bridge of switches Q1-Q4, with the H-bridge comprising first 32 and second 34 legs.
  • the first leg 32 comprises the switch QI as a high-side switch and the switch Q2 as a low-side switch
  • the second leg 34 comprises the switch Q3 as a high-side switch and the switch Q4 as a low-side switch.
  • the full-bridge inverter 16 is to convert DC rectified voltage received from the rectifier 14 to AC current supplied to the induction coil 18 via appropriate switching of the switches Q1-Q4.
  • the induction coil 18 is depicted as an inductor L9, and is shown connected in series with a reflected load Rl.
  • Induction heating systems function by inducing eddy currents in electrical conductors by changing the applied magnetic field in the electrical conductor. Where the electrical conductor is fixed, the applied magnetic field must be varied to induce the required eddy current.
  • a varying magnetic field in the present embodiments is achieved via appropriate switching of the switches Q1-Q4 to drive alternating current through the induction coil 18. Operating induction heating systems at higher frequencies may allow for a reduction in size of the induction coil, which may enable a smaller form factor for a product employing the induction heating system, and may also allow for high efficiency heating of certain materials.
  • the switches Q1-Q4 discussed herein are either gallium nitride (GaN) or silicon carbide (SiC) switches. Whilst such switches facilitate high frequency switching, ie high-level kHz or MHz switching, switching losses may prohibit operation at such frequencies in practice.
  • GaN gallium nitride
  • SiC silicon carbide
  • the drive circuit 10 has the pair of first resonant networks 20,22 each to enable zero-voltage switching of the high- and low- side switches of a respective one of the first 32 and second legs 34 of the full-bridge inverter 16.
  • a first one 20 of the first pair of resonant networks 20,22 comprises an inductor LI connected to a common node between the high-side switch QI of the first leg 32 and the low-side switch Q2 of the first leg 32.
  • the first one 20 of the first pair of resonant networks 20,22 comprises a capacitor Cl connected in series with the inductor LI, and connected to ground.
  • the first one 20 of the first pair of resonant networks 20,22 may be thought of as being connected in parallel with the low-side switch Q2 of the first leg 32.
  • a second one 22 of the first pair of resonant networks 20,22 comprises an inductor L2 connected to a common node between the high-side switch Q3 of the second leg 30 and the low-side switch Q4 of the second leg 28.
  • the second one 20 of the first pair of resonant networks 20,22 comprises a capacitor C2 connected in series with the inductor L2, and connected to ground.
  • the second one 22 of the first pair of resonant networks 20,22 may be thought of as being connected in parallel with the low-side switch Q4 of the second leg 30.
  • the pair of first resonant networks 20,22 enable zero-voltage switching of the high- and low- side switches of a respective one of the first 28 and second legs 30 of the full-bridge inverter 16.
  • the inductor LI drives the voltage across high-side switch QI and low-side switch Q2 to zero by discharging the switches’ output capacitance.
  • the inductor L2 drives the voltage across high-side switch Q3 and low-side switch Q4 to zero by discharging the switches’ output capacitance.
  • the capacitors Cl and C2 of the first pair of resonant networks 20,22 are DC blocking capacitors
  • switching losses associated with the high-and low-side switches may be reduced, thereby enabling the switches to be operated at higher frequencies than switches operated with hard switching conditions.
  • a size of the coil required may be reduced, which may lead to a smaller form-factor for products incorporating the induction heating system.
  • a further issue encountered during inductive heating is that the magnetic field transmitted by the induction coil 18 may vary depending on the load presented by a susceptor that interacts with the magnetic field, and the varying load may affect the effective resistive load, which brings about a change in the current passing through the induction coil 18. Such a variation in current may be undesirable, and may lead to less power being delivered to the load. Furthermore, if there is no load a short circuit may occur.
  • the second pair of resonant networks 24,26 are to provide a constant current output to the induction coil 18.
  • a first one 24 of the second pair of resonant networks 24,26 comprises a first inductor L3 connected in series with a first one 28 of the third pair of resonant networks 28,30, a second inductor L4 connected in series with the first inductor L3, and a capacitor C3 connected in parallel with the first inductor L3 and the second inductor L4 at a point between the first inductor L3 and the second inductor L4.
  • the first one 24 of the second pair of resonant networks 24,26 may be thought of as an LCL resonant circuit, which may also be referred to as a T-network circuit.
  • the first one 26 of the second pair of resonant networks 24,26 acts as an impedance transformation network to transform the constant voltage across Q2 to a constant current.
  • current output to the coil 18 by the first one 24 of the second pair of resonant networks 24,26 may be independent of the reflected load Rl, and thus a constant current amplitude may be output to the coil 18.
  • a second one 26 of the second pair of resonant networks 24,26 comprises a first inductor L5 connected in series with a second one 30 of the third pair of resonant networks 28,30, a second inductor L6 connected in series with the first inductor L5, and a capacitor C4 connected in parallel with the first inductor L5 and the second inductor L6 at a point between the first inductor L5 and the second inductor L6.
  • the second one 26 of the second pair of resonant networks 24,26 may be thought of as an LCL resonant circuit, which may also be referred to as a T-network circuit.
  • the second one 26 of the second pair of resonant networks 24,26 acts as an impedance transformation network to transform the constant voltage across Q4 to a constant current .
  • current output to the coil 18 by the second one 26 of the second pair of resonant networks 24,26 may be independent of the reflected load Rl, and thus a constant current amplitude may be output to the coil 18.
  • the third pair of resonant networks 28,30 are to smooth voltage waveforms supplied from the full-bridge inverter 16 to the coil 18.
  • One 28 of the third pair of resonant networks 28,30 comprises a capacitor C5 connected in series with a common node between the high-side switch QI of the first leg 32 and the low-side switch Q2 of the first leg 32, and an inductor L7 connected in series with the capacitor C5.
  • Another one 30 of the third pair of resonant networks 28,30 comprises a capacitor C6 connected in series with a common node between the high-side switch Q3 of the second leg 34 and the low-side switch Q4 of the second leg 34, and an inductor L8 connected in series with the capacitor C6.
  • the drive circuit 10 comprises a first resonant capacitor C7 connected in series between the inductors L3 and L4 of one 24 of the second pair of resonant networks 24,26, and a second resonant capacitor C8 connected in series between the inductors L5 and L6 of the other one 26 of the second pair of resonant networks 24,26.
  • the first resonant capacitor C7 and the second resonant capacitor C8 are tuned to resonate with the inductance of the coil 18, and may smooth the voltage across the respective capacitors C3 and C4 of the second pair of resonant networks 24,26.
  • a further capacitor C9 is shown connected in parallel across the coil 18, and represents the capacitance of the coil 18.
  • FIG. 3 A second embodiment of a drive circuit 100 according to the present invention is shown in Figure 3.
  • the drive circuit 100 of the embodiment of Figure 3 differs from the drive circuit 10 of the embodiment of Figure 1 in that the drive circuit 100 of the embodiment of Figure 3 includes a power factor correction (PFC) circuit 102 located between the rectifier 14 and the full-bridge inverter 16.
  • PFC power factor correction
  • the exact form of the PFC circuit 102 can be chosen depending on other factors, for example cost or complexity, but the purpose of the PFC circuit 102 is to remove the ripple from the current supplied by the rectifier 14 to the fullbridge inverter 16, such that the current output to the induction coil 18 is not modulated by the frequency of the AC power supply 12, as seen in Figure 4.
  • a further embodiment of a drive circuit 200 according to the present invention is shown in Figure 5.
  • the drive circuit 200 of Figure 5 is powered by a DC power supply 202, for example a battery, and omits the rectifier 14.
  • the remainder of the drive circuit 200 of Figure 5 is the same as the drive circuit 10 of Figure 1, including the first pair of resonant networks 20,22, and the second pair of resonant networks 24,26.
  • the drive circuit 200 outputs current to the induction coil 18 similar to that shown in Figure 4.
  • Another embodiment of a drive circuit 300 according to the present invention is shown in Figure 6.
  • the inductors L7 and L8 of the pair of third resonant networks 28,30 of the embodiment of Figure 1 have been combined with the first inductors L3 and L5 of the second resonant networks 24,6 of the embodiment of Figure 1, and are now shown as single inductors L3 and L5 in Figure 6.
  • the single inductors L3 and L5 each form part of a respective second resonant network
  • the inductors L3 and L5 are tuned to resonate as part of the pair of second resonant networks 24,26 and the pair of third resonant networks 28,30, as appropriate.
  • the pair of third resonant networks 28,30 in the embodiment of Figure 6 have a resonant frequency that does not equal the switching frequency of the full-bridge inverter.
  • inductors L3 and L5 that form part of a respective second resonant network
  • a number of components, cost, and complexity of the drive circuit 300 of Figure 6 may be reduced compared to the drive circuit of Figure 1.
  • FIG. 7 Another embodiment of a drive circuit 400 according to the present invention is shown in Figure 7.
  • the drive circuit 400 of Figure 7 is substantially the same as the drive circuit 300 of Figure 6, save that the second inductors L4 and L6 of the pair of second resonant networks
  • the coil 18 acts as the induction coil that generates a magnetic field to interact with a susceptor, as well as acting as the second inductors of the pair of second resonant circuits 24,26.
  • the inductance of the coil 18 acts in the impedance transformation to provide a constant current output.
  • FIG. 8 Another embodiment of a drive circuit 500 according to the present invention is shown in Figure 8.
  • the drive circuit 500 of Figure 8 is substantially the same as the drive circuit 400 of Figure 7, save that the drive circuit 500 of Figure 8 has four first resonant networks 502,504,506,508 compared to the first pair of resonant networks 20,22 of the drive circuit 400 of Figure 7.
  • each first resonant network 502,504,506,508 comprises an inductor L1,L2,L11,L12 connected in series with a DC blocking capacitor Cl, C2, CIO, Cl 1, with each resonant network 502,504,506,508 being connected in parallel about a respective one of the switches Q4,Q2,Q1,Q3.
  • the inductors L1,L2,L11,L12 are to ensure the voltage across each switch Q4,Q2,Q1,Q3 is zero volts just before it switches on. Zero-voltage switching is achieved by discharging the switches’ output capacitance, Coss.
  • the value of the inductors L1,L2,L11,L12 is determined using the following equation: where Atzvs is the transition time of the switch from the off state to the on state, f is the switching frequency, Coss is the output capacitance of the switch as specified in the manufacturer’ s datasheet.
  • Capacitors C1,C2,C1O,C11 are DC blocking capacitors, with a very high value, typically above lOOnF.
  • resonant networks 502,504,506,508 of Figure 8 could be implemented in any of the drive circuits 10,100,200,300,400 of Figures 1, 3, 5, 6 and 7, as appropriate.
  • the drive circuits 10,200,300,400,500 disclosed herein are able to be driven at high frequencies by virtue of first resonant networks that enable zero-voltage switching, and second resonant networks that provide a constant current output to the induction coil 18.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Inverter Devices (AREA)
  • General Induction Heating (AREA)

Abstract

L'invention concerne un circuit d'entraînement pour entraîner un système de chauffage par induction comprenant un onduleur en pont complet ayant des première et seconde pattes. Chacune des première et seconde pattes a un commutateur côté haut et un commutateur côté bas. Le circuit d'entraînement a une bobine destinée à être entraînée par l'onduleur en pont complet pour générer un champ magnétique, une première pluralité de réseaux résonants pour permettre une commutation à tension nulle des commutateurs côté haut et côté bas, et une seconde pluralité de réseaux résonants chacun pour fournir une sortie de courant constant à la bobine.
PCT/GB2021/052943 2020-12-03 2021-11-15 Circuit d'entraînement WO2022117985A1 (fr)

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GB2019096.3A GB2601742B (en) 2020-12-03 2020-12-03 A drive circuit

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US6469919B1 (en) * 1999-07-22 2002-10-22 Eni Technology, Inc. Power supplies having protection circuits
WO2005074413A2 (fr) * 2004-01-16 2005-08-18 Mks Instruments, Inc. Amplificateur classe e avec pince a induction
JP2015164108A (ja) * 2014-02-28 2015-09-10 国立大学法人神戸大学 誘導加熱用高周波インバータ
WO2016049372A1 (fr) * 2014-09-25 2016-03-31 Navitias Semiconductor, Inc. Transfert d'énergie sans fil à étage unique à commutation souple
WO2018125041A1 (fr) * 2016-12-27 2018-07-05 Whirlpool Corporation Système de génération de rf à semi-conducteurs à faible coût pour cuisson électromagnétique
CN210608706U (zh) * 2019-08-20 2020-05-22 南京航空航天大学 一种实现恒流恒压输出切换的感应式无线电能传输***

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US6021053A (en) * 1998-07-24 2000-02-01 Ajax Magnethermic Corporation Method and apparatus for switching circuit system including a saturable core device with multiple advantages

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6469919B1 (en) * 1999-07-22 2002-10-22 Eni Technology, Inc. Power supplies having protection circuits
WO2005074413A2 (fr) * 2004-01-16 2005-08-18 Mks Instruments, Inc. Amplificateur classe e avec pince a induction
JP2015164108A (ja) * 2014-02-28 2015-09-10 国立大学法人神戸大学 誘導加熱用高周波インバータ
WO2016049372A1 (fr) * 2014-09-25 2016-03-31 Navitias Semiconductor, Inc. Transfert d'énergie sans fil à étage unique à commutation souple
WO2018125041A1 (fr) * 2016-12-27 2018-07-05 Whirlpool Corporation Système de génération de rf à semi-conducteurs à faible coût pour cuisson électromagnétique
CN210608706U (zh) * 2019-08-20 2020-05-22 南京航空航天大学 一种实现恒流恒压输出切换的感应式无线电能传输***

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CN116584027A (zh) 2023-08-11
GB2601742B (en) 2024-04-24
GB2601742A (en) 2022-06-15
GB202019096D0 (en) 2021-01-20

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