WO2022001240A1 - 一种检测方法、装置和通信设备 - Google Patents

一种检测方法、装置和通信设备 Download PDF

Info

Publication number
WO2022001240A1
WO2022001240A1 PCT/CN2021/083335 CN2021083335W WO2022001240A1 WO 2022001240 A1 WO2022001240 A1 WO 2022001240A1 CN 2021083335 W CN2021083335 W CN 2021083335W WO 2022001240 A1 WO2022001240 A1 WO 2022001240A1
Authority
WO
WIPO (PCT)
Prior art keywords
channel response
round
estimation
estimated value
detected
Prior art date
Application number
PCT/CN2021/083335
Other languages
English (en)
French (fr)
Inventor
赵淼
朱有团
赵晓沐
Original Assignee
华为技术有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 华为技术有限公司 filed Critical 华为技术有限公司
Publication of WO2022001240A1 publication Critical patent/WO2022001240A1/zh

Links

Images

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H04L25/0228—Channel estimation using sounding signals with direct estimation from sounding signals
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
    • Y02D30/00—Reducing energy consumption in communication networks
    • Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks

Definitions

  • the present invention relates to the field of communication technologies, and in particular, to a detection method, an apparatus and a communication device.
  • LTE Long Term Evolution
  • 5G 5th Generation
  • the embodiments of the present application provide a detection method, an apparatus, and a communication device.
  • the present application provides a detection method.
  • the method is performed by a network device, and includes: determining a received signal according to pilot signals sent by m user equipment UEs and channel responses to be detected of the m UEs.
  • the m is a positive integer greater than 1; according to the pilot signals of the m UEs and the received signals, determine the estimated value of the channel response to be detected of each UE under each round of estimation in the D round; determine the detection
  • the detection result is an estimated value of the to-be-detected channel response of each UE under the D-th round of estimation, where D is a positive integer greater than 1.
  • the network device after receiving pilot signals sent by multiple UEs, in order to eliminate the interference problem under the non-orthogonal pilot frequency and the interference problem between cells, uses a basic cancellation framework and a residual cancellation framework
  • the two interference contrast architectures process the received signal to detect the channel response of each UE to increase the number of pilot resources and system capacity within the network equipment.
  • signal to determine the estimated value of the channel response to be detected of each UE under the first round of estimation including: determining the channel response to be detected of the first UE according to the pilot signals of the m UEs and the received signal The estimated value under the first round of estimation; or the to-be-detected channel of each UE is determined according to the pilot signals of the m UEs, the received signals, and the previously determined channel responses of the UEs that need to be cancelled The estimated value of the response in the first round of estimation, wherein the channel response of the previously determined UE that needs to be canceled of the kth UE includes the channel responses to be detected of the 1st to k-1th UEs in the th
  • the k is a positive integer, and 1 ⁇ k ⁇ m.
  • the acquired received signal is processed through the basic cancellation framework, that is, the channel response estimate value of each UE is calculated through the received signal, and then the previously determined channel response estimate value of the UE is cancelled. Then, through multiple rounds of iterative reduction processing, the interference of the estimated channel response values of UEs other than itself in the previous round of estimation is cancelled, so that the channel response to each UE is infinitely close to the real value.
  • the N is a positive integer, and 1 ⁇ N ⁇ D; the received signal, and determining the estimated value of the channel response to be detected of each UE under the Nth round of estimation, including: according to the pilot signals of the m UEs, the received signal, and a previously determined value that needs to be canceled The channel response of the UE is determined, and the estimated value of the channel response to be detected of each UE under the Nth round of estimation is determined, wherein the previously determined channel response of the UE that needs to be cancelled includes other m-1 UEs The estimated value of the to-be-detected channel response under the N-1th round of estimation.
  • the acquired received signal is processed through the basic cancellation framework, that is, the channel response estimate value of each UE is calculated through the received signal, and then the previously determined channel response estimate value of the UE is cancelled. Then, through multiple rounds of iterative reduction processing, the interference of the estimated channel response values of UEs other than itself in the previous round of estimation is cancelled, so that the channel response to each UE is infinitely close to the real value.
  • the processing method for determining the estimated value of the channel response to be detected of each UE under the first round of estimation is specifically:
  • H 1,rebi represents the estimated value of the channel response to be detected of each UE determined first in the first round of estimation
  • k represents the identifier for numbering each UE
  • Sk * represents the conjugate of Sk
  • the processing method for determining the estimated value of the channel response to be detected of each UE under the n>1th round of estimation is specifically:
  • m represents the number of received pilot signals
  • k ⁇ m, H N-1, rebi represents the estimated value of the channel response to be detected of each UE under the N-1th round of estimation
  • N represents for each UE
  • Sk * denotes the conjugate of Sk.
  • the signal determined by the residual of the previous UE and the differential signal of the previous UE, the pilot signal of the previous UE and the signal determined by the residual of the previous UE, the residual is the UE's pending signal.
  • the estimated value under the sub-estimation, the N is a positive integer, and 1 ⁇ N ⁇ D.
  • the received signal is processed through the residual cancellation framework, that is, the residual of each UE and the differential signal of each UE are sequentially calculated through the received signal, and then combined with the historical channels of each UE In response, the estimated value of the channel response of each UE is calculated, and finally through multiple rounds of iterative incremental processing, the estimated value of each UE in the previous round is superimposed, so that the channel response to each UE is infinitely close to the real value.
  • the processing method for determining the estimated value of the channel response to be detected of each UE under multiple rounds of estimation is specifically:
  • k represents the identifier for numbering each UE
  • N represents the number of rounds of estimation for each UE
  • Y N represents the number of rounds of estimation for each UE
  • Y N represents the number of rounds of estimation for each UE
  • Y N represents the received signal of the kth UE in the Nth round of estimation
  • H N-1 represents the historical channel response of the kth UE in the N- 1th round of estimation
  • H 0,rebk 0.
  • the method further includes: determining a residual under the N+1th round of estimation of the kth UE, where the residual under the N+1th round of estimation of the kth UE is Obtained by subtracting the estimated value of the channel response to be detected of the kth UE under the Nth round of estimation minus the historical channel response of the kth UE under the Nth round of estimation, where k is positive Integer, and 1 ⁇ k ⁇ m.
  • the method further includes: determining differential information of the k+1th UE, where the differential information of the k+1th UE is obtained by subtracting the differential information of the kth UE from the obtained by multiplying the pilot signal of the kth UE and the residual of the kth UE.
  • the method further includes: determining historical channel responses under N+1 rounds of estimation of the m UEs, where the historical channel responses of the m UEs under N+1 rounds of estimation are: The estimated value of the to-be-detected channel responses of the m UEs under the Nth round of estimation.
  • the method further includes: performing an inverse Fourier transform (IDFT) on the obtained estimated value of the to-be-detected channel response of each UE under each round of estimation in the D rounds, to obtain a first time-domain estimated value;
  • IDFT inverse Fourier transform
  • the estimated value of the to-be-detected channel response of the UE under each round of estimation in round D is the first frequency domain estimated value; the first time domain estimated value is nonlinearly reconstructed to obtain the second time domain estimated value;
  • Fourier transform DFT is performed on the second time-domain estimated value to obtain a second frequency-domain estimated value.
  • the network device After obtaining the time-domain channel response, the network device reconstructs the waveform of the time-domain channel response, the purpose of which is that for interference cancellation, nonlinear processing must be added in each iteration process Compared with the channel response before processing, the channel response after the nonlinear processing is closer to the real channel response.
  • performing nonlinear reconstruction on the first time-domain estimated value to obtain a second time-domain estimated value includes: according to the sequence length of the pilot signal of each UE and the each The length of the waveform of the first time-domain estimated value of the channel response to be detected of the UE constructs an envelope function; through the set threshold, on the waveform of the first time-domain estimated value of the channel response to be detected of each UE Selecting a position with stronger power, and constructing an envelope waveform matrix; by inverting the envelope waveform matrix, calculate the third time domain estimated value of the channel response to be detected for each UE; The third time-domain estimated value of the channel response to be detected of each UE and the envelope function are used to calculate the second time-domain estimated value.
  • an embodiment of the present application further provides a detection apparatus, including at least one processor, where the processor is configured to execute an instruction stored in a memory, so that the terminal executes each possible implementation of the first aspect.
  • the embodiments of the present application further provide a communication device, which is configured to execute various possible implementations of the first aspect.
  • the embodiments of the present application further provide a computer-readable storage medium on which a computer program is stored, and when the computer program is executed in a computer, the computer is made to execute the various possible implementations of the first aspect. .
  • an embodiment of the present application further provides a computing device, including a memory and a processor, wherein the memory stores executable code, and when the processor executes the executable code, the first On the one hand various possible embodiments.
  • an embodiment of the present application further provides a communication system, including a base station and at least one user equipment UE, where the base station is configured to execute the various possible implementations of the first aspect.
  • FIG. 1 is a schematic structural diagram of a detection system provided by an embodiment of the present application.
  • FIG. 2 is a flowchart of processing a received signal through a basic cancellation framework to obtain channel information of each UE provided by an embodiment of the present application;
  • FIG. 3 is a schematic diagram of time-domain waveform reconstruction provided by an embodiment of the present application.
  • FIG. 5 is a flowchart of processing a received signal through a residual cancellation framework to obtain channel information of each UE according to an embodiment of the present application
  • FIG. 6 is a schematic structural diagram of a detection device provided by an embodiment of the present application.
  • FIG. 7 is a schematic structural diagram of a communication device according to an embodiment of the present application.
  • FIG. 8 is a schematic structural diagram of a base station according to an embodiment of the present application.
  • FIG. 1 is a schematic structural diagram of a detection system provided by an embodiment of the present application.
  • the system includes at least one base station 110_N and at least one user equipment (user equipment, UE) 120_M.
  • UE user equipment
  • one base station covers or manages one or more cells, and in one cell, there will be multiple UEs listening or receiving signals.
  • the base station 110_2 can not only allocate non-orthogonal pilot resources for UE 120_4, UE 120_5 and UE 120_6 in cell B of this base station, but also can allocate non-orthogonal pilot resources for UE 120_2 in other cell A and UE120_M- in cell C. 2 Allocate non-orthogonal pilot resources. After obtaining the non-orthogonal pilot resources allocated by the base station side, the UE side may send a pilot signal to the base station side through the allocated non-orthogonal pilot frequency resources.
  • the base station side of the present application uses two basic cancellation frameworks and residual cancellation frameworks.
  • This interference comparison architecture processes the received signal to detect the channel response of each UE to increase the number of pilot resources and system capacity in the base station.
  • the following two embodiments describe how the base station processes the received signal through two interference comparison architectures, namely the basic cancellation framework and the residual cancellation framework, to detect the channel response of each UE.
  • FIG. 2 is a flowchart of processing a received signal through a basic cancellation framework to obtain a channel response of each UE according to an embodiment of the present application.
  • the specific implementation process of the base station is as follows:
  • Step S201 the base station receives a pilot signal sent by at least one UE.
  • the pilot signal includes a common demodulation reference signal (cell-specific reference signal, CRS), a downlink demodulation reference signal (downlink demodulation reference signal, DL DMRS), an uplink demodulation reference signal (uplink demodulation reference signal, UL DMRS) , channel state information-reference signal (CSI-RS), positioning pilot signal (positioning reference signal, PRS), primary synchronization signal (PSS), secondary synchronization signal (secondary synchronization signal, SSS), discovery reference signal (discovery reference signal, DRS), SRS, etc.
  • CRS common demodulation reference signal
  • DL DMRS downlink demodulation reference signal
  • uplink demodulation reference signal uplink demodulation reference signal
  • UL DMRS uplink demodulation reference signal
  • CSI-RS channel state information-reference signal
  • positioning pilot signal positioning reference signal
  • PRS primary synchronization signal
  • PSS primary synchronization signal
  • SSS secondary synchronization signal
  • discovery reference signal discovery reference signal
  • DRS discovery reference
  • the base station After receiving the pilot signals sent by the multiple UEs, the base station numbers the multiple UEs, namely UE 1, UE 2,...UE k... .
  • the pilot signal sent by UE 1 is S1
  • the pilot signal sent by UE2 is S2
  • the pilot signal sent by UE k is Sk.
  • k represents an identifier for numbering each UE.
  • the base station sorts the priorities of each UE according to the priority.
  • the higher the ranking of the UE the more accurate the estimated channel response.
  • high-priority users are defined as users who have higher requirements on the capacity of the uplink and downlink systems, such as users of large-package services, users at near-point locations of cells, or users with large bandwidth, and so on.
  • the received signal Y is defined as:
  • k represents the sequence number for numbering each UE
  • Sk represents the coefficient matrix of the pilot signal sent by each UE
  • H k represents the channel response to be detected by each UE.
  • Step S202 the base station performs iterative estimation of interference cancellation on the channel response of each UE k to eliminate the interference of other channel responses in the channel response of each UE.
  • the to-be-detected channel response of the UE with 2 affects it; and so on.
  • the base station performs the first round of estimation on each UE
  • the second round of estimation process when performing the second round of estimation on each UE in turn, it is necessary to eliminate all UEs except its own UE from the first round of estimation.
  • the channel response to be detected is affected by the second estimation; in the third round of estimation, when performing the third round of estimation on each UE in turn, it is necessary to eliminate the second round of estimation for each UE except its own UE.
  • the channel response to be detected affects it; and so on.
  • the following formula (2-1) is used to obtain the frequency domain channel response H 1,lsk of each UE.
  • the formula (2-1) is specifically:
  • H 1,rebi represents the frequency domain channel response of each UE in the first round of estimation
  • k represents the identifier for numbering each UE
  • Sk * represents the conjugate of Sk.
  • m represents the number of pilot signals sent to the base station
  • k ⁇ m, H N-1, rebi represents the frequency domain channel response of each UE in the N-1th round of estimation
  • N represents the response to each UE.
  • S k * S k denotes the conjugate.
  • Step S203 the base station performs an inverse discrete fourier transform (IDFT) on the obtained frequency-domain channel response H N,lsk to obtain a time-domain channel response h N,lsk .
  • IDFT inverse discrete fourier transform
  • the base station performs IDFT on the frequency domain channel response H N,lsk through the following formula (3) to obtain the time domain channel response h N,lsk , and formula (3) is specifically:
  • Step S204 the base station performs nonlinear reconstruction on the obtained time-domain channel response h N,lsk to obtain a reconstructed time-domain channel response h N,rebk .
  • the base station After obtaining the time domain channel response h N,lsk , the base station reconstructs the waveform of the time domain channel response h N,lsk , and the variable is described as h N,rebk .
  • the purpose is that for interference cancellation, it is necessary to add a nonlinear processing process in each iteration process, so that h N,rebk after the nonlinear processing process is closer to the real than h N,lsk . channel response.
  • Step S205 the base station performs Fourier transform (discrete fourier transform, DFT) on the obtained time-domain channel response h N,rebk to obtain the frequency-domain channel response H N,rebk .
  • DFT discrete fourier transform
  • the base station performs DFT on the time-domain channel response h N,rebk through the following formula (4) to obtain the frequency-domain channel response H N,rebk , and formula (4) is specifically:
  • Step S206 the base station determines whether the frequency domain channel response H N,rebk obtained at this time is the channel response of the last UE to be sorted, and if so, executes step S207; if not, executes step S202.
  • Step S207 the base station determines whether the number of estimated rounds performed by the frequency domain channel response H N,rebk obtained at this time is the set round threshold D. If yes, it indicates that the frequency domain channel response H N obtained at this time, the number of estimated rounds performed by rebk is the channel response of the last sorted UE obtained by the last round of iteration, and step S208 is performed; if not, it indicates that The frequency domain channel response H N, the number of estimation rounds performed by rebk obtained at this time is not the channel response of the last sorted UE obtained by the last round of iteration, and step S202 is executed.
  • step S207 it is determined in step S207 that the frequency domain channel response H N,rebk obtained at this time is not obtained through the last round of iteration.
  • the frequency domain channel response of the UE in the next round is H N,rebk .
  • Step S208 the base station takes the frequency domain channel response H N,rebk of each UE in the last round of iterative processing as the final channel response of each UE.
  • the finally obtained channel responses for each UE last time a cancellation channel responses obtained, followed by H N, reb1, H N, reb2 whil H N, rebk.
  • the present application processes the acquired received signal through the basic cancellation framework, that is, through the received signal, calculates the estimated channel response value of each UE, and then cancels the previously determined channel response estimated value interference of the UE, and then Through multiple rounds of iterative decrement processing, the interference of the estimated value of the channel response of the UE other than itself in the previous round of estimation is cancelled, so that the channel response to each UE is infinitely close to the real value.
  • the purpose of identifying the detected channel response is different.
  • the base station performs nonlinear reconstruction on the obtained time-domain channel response h N,lsk to obtain the frequency-domain channel response h N,rebk .
  • the adopted nonlinear reconstruction mainly includes three reconstruction schemes: basic nonlinear reconstruction, high-speed sampling, and new waveform. The following describes how these three schemes reconstruct and transform the channel response h N,lsk to obtain the frequency domain channel response h N,rebk :
  • l represents the time domain channel response h N, lsk sample point number, L SC represents a non-orthogonal pilot pilot sequence length of the signal S k is, L represents the time domain channel response h N, the length of the waveform LSK of .
  • tapi represents the position of the sample point with strong power
  • i 1 and i 2 represent the number index of the sample point with strong power
  • I represents the number of sample points with strong power
  • a vector with a dimension of I*1 is formed by extracting the position of a sample point with strong power from the time-domain channel response h N,lsk , which is expressed as h N,lsk,tap .
  • i represents the number index of the sample point
  • the physical meaning of circshift(w, tap i ) is to cyclically shift the waveform of the envelope function w to the right by tap i samples.
  • the oversamp method is to fill zeros in the frequency domain, so as to respond to the frequency domain channel H N,lsk
  • the waveform length of H N,lsk It is expanded to an oversamp multiple of the original number of samples by zero-filling at the tail, and then IDFT is used to obtain the waveform of the time-domain channel response h N,lsk , and the number of dimension points on the waveform is N ovsamp .
  • oversamp represents the number of oversamp samples
  • N ovsamp represents the number of dimension points of the waveform of the time-domain channel response h N,lsk.
  • Step S401 specifying the time-domain waveform envelope function y of each time delay extension
  • Step S402 obtain the initial envelope function w 0 by constructing the time domain envelope function w in the formula (5);
  • Step S403 Substitute the obtained envelope function into formula (10), and calculate to obtain 2 sample point coefficients; wherein, formula (10) is:
  • x represents the sample coefficient
  • y represents the time-domain waveform envelope function of each delay extension.
  • Step S404 according to the obtained 2 sample point coefficients, substitute into formula (10), and calculate and obtain the updated reconstructed waveform w p ; wherein, formula (11) is:
  • step S406 the optimal reconstructed waveform w p under consideration of different delay spreads is obtained.
  • the base station after obtaining the time-domain channel response hN,lsk , the base station adopts any one of the above three nonlinear reconstruction schemes to perform nonlinear processing on the time-domain channel response hN,lsk to obtain the frequency-domain channel response hN,lsk.
  • the channel response h N,rebk makes the channel response of each UE detected by the base station closer to the real value.
  • the frequency domain channel response H 1,reb1 is obtained by formulas (3)-(11) in step S203-step S205; since k ⁇ m at this time, it is necessary to loop into step S202 to detect the channel response of UE2.
  • step S203-step S205 the frequency domain channel response H 1,reb2 is obtained through formulas (3)-(11) in step S203-step S205; since k ⁇ m at this time, it is necessary to loop into step S202 to detect the channel response of UE3.
  • step S202 a preliminary estimate for the UE3, in step S202 by the formula (2-2), the first cycle obtained by frequency-domain channel response H 1, reb1 and frequency domain channel response to obtain second cycle H 1, reb2, get:
  • the frequency domain channel response H 2,reb1 is obtained through formulas (3)-(11) in steps S203-step S205; since k ⁇ m at this time, it is necessary to loop into step S202 to detect the channel estimated by UE2 in the second round of estimation response.
  • the frequency domain channel response H 2,reb2 is obtained by formulas (3)-(11) in step S203-step S205; since k ⁇ m at this time, it is necessary to loop into step S202 to detect the channel estimated by UE3 in the second round response.
  • FIG. 5 is a flowchart of processing a received signal through a residual cancellation framework to obtain a channel response of each UE according to an embodiment of the present application.
  • the specific implementation process of the base station is as follows:
  • Step S501 the base station receives a pilot signal sent by at least one UE.
  • the base station After receiving the pilot signals sent by the multiple UEs, the base station numbers the multiple UEs, and defines the pilot signal sent by the UE k as Sk.
  • the historical channel response of each UE is defined as H histk , and it is specified to be set to 0 in the initial iteration.
  • Step S502 the base station estimates the channel response of each UE, and eliminates the interference of other channel responses in the channel response of each UE.
  • the signal Y at this time no longer represents the received signal of the frequency domain signal, but represents the remaining un-cancelled residual signal Y with each iteration of the cancellation process.
  • each UE performs channel estimation in sequence, it will estimate the residual signal Y and the pilot signal and add the historical channel response H histk of the previous round of reconstruction. After the estimation is completed, the estimated pilot signal will continue. Subtract from Y, so as to continue to estimate the next UE; after completing the estimation of the channel responses of all UEs in one round, perform the next round of user estimation; and so on.
  • the following formula (12) is used to calculate the channel response H 1,lsk of each UE.
  • the formula (12) is specifically:
  • k represents the sequence number for numbering each UE
  • N is the number of rounds of iterative estimation of the channel response of each UE by the base station
  • H N, lsk represents the channel response to be detected of the UE in the Nth round of estimation
  • Y N,lsk represents the residual result in the estimation process of the kth user in the Nth round
  • H N-1,histk represents the historical channel response of the UE in the N- 1th round of estimation
  • H 0,histk 0 .
  • Step S503 the base station performs IDFT on the obtained channel response H N,lsk of each UE to obtain the channel response h N,lsk .
  • the base station performs IDFT on the channel response H N,lsk by formula (3) to obtain the channel response h N,lsk .
  • Step S504 the base station performs nonlinear reconstruction on the obtained channel responses H N,lsk of each UE to obtain frequency domain channel responses h N,rebk .
  • the manner in which the base station performs nonlinear reconstruction on H N,lsk may be any one of the implementation manners in the above-mentioned Embodiment 1 "basic nonlinear reconstruction scheme, high-speed sampling scheme and new waveform scheme". The specific implementation process is detailed in See the above-mentioned FIG. 3-FIG. 4 and the corresponding description contents, which will not be repeated in this application.
  • Step S505 the base station performs DFT on the obtained frequency domain channel responses h N,rebk of each UE to obtain the frequency domain channel responses H N,rebk .
  • the base station performs DFT on the frequency domain channel response h N,rebk according to formula (4) to obtain the frequency domain channel response H N,rebk .
  • Step S506 the base station determines whether the number of estimated rounds performed by the frequency domain channel response H N,rebk obtained at this time is the set round threshold D. If not, it indicates that the estimated number of rounds of the frequency domain channel response H N, rebk obtained at this time is not the channel response of each UE obtained by the last round of iteration, and step S507 is performed; The number of estimation rounds performed by the frequency domain channel response H N,rebk is the channel response of each UE obtained by the last round of iteration, and step S510 is executed.
  • Step S507 the base station calculates the residual err of the channel response according to the obtained frequency domain channel response H N,rebk of the UE k.
  • the base station calculates the residual err of the channel response of each UE through formula (13), and formula (13) is specifically:
  • Step S508 the base station updates the received signal Y N,k according to the obtained residual err of the channel response of each UE.
  • Step S509 the base station updates the historical channel response of each UE to H N,histk , and then performs step S502.
  • the base station updates the historical channel response of each UE as H N,histk through formula (15), and formula (15) is specifically:
  • the order of updating the received signal Y N in step S508 and updating the historical channel response of each UE to H N in step S509 is not limited.
  • Step S510 the base station takes the frequency domain channel response H N,rebk of each UE in the last round of iterative processing as the final channel response of each UE.
  • the finally obtained channel responses for each UE last time a cancellation channel responses obtained, followed by H N, reb1, H N, reb2 whil H N, rebk.
  • the present application processes the received signal through the residual cancellation framework, that is, through the received signal, calculates the residual of each UE and the differential signal of each UE in turn, and then combines the historical channel responses of each UE to calculate The estimated value of the channel response of each UE is finally processed through multiple rounds of iterative incremental processing, and the estimated value of each UE in the previous round is superimposed, so that the channel response to each UE is infinitely close to the real value.
  • the frequency domain channel responses H 1,reb1 , H 1,reb2 and H 1,reb3 are obtained by formulas (3)-(11) in steps S503-step S505; since N ⁇ 2 at this time, it is necessary to loop into step S502 , and detect the channel response of each UE in the second round of estimation.
  • the residual err of the channel response of each UE is calculated as:
  • the received signal Y 2,1 is updated according to the formula (14-2), and the received signals Y 2,2 and Y 2,3 are updated according to the formula (14-1) to obtain:
  • Y 2,2 Y 2,1 -S 1 err 2,1
  • the H 2,reb1 , H 2,reb2 and H 2,reb3 estimated in the last round are directly used as the final channel response of each UE.
  • the detection apparatus includes corresponding hardware structures and/or software modules for performing each function.
  • the present application can be implemented in hardware or a combination of hardware and computer software with the units and algorithm steps of each example described in conjunction with the embodiments disclosed herein. Whether a function is performed by hardware or computer software driven hardware depends on the specific application and design constraints of the technical solution. Skilled artisans may implement the described functionality using different methods for each particular application, but such implementations should not be considered beyond the scope of this application.
  • the present application can divide the functional units of the detection device according to the above method examples. For example, each function can be divided into each functional unit, or two or more functions can be integrated into one processing unit.
  • the above-mentioned integrated units may be implemented in the form of hardware, or may be implemented in the form of software functional units. It should be noted that the division of units in this application is schematic, and is only a logical function division, and other division methods may be used in actual implementation.
  • the detection device 600 shown in FIG. 6 includes a transceiver unit 601 and a processing unit 602 .
  • the detection apparatus 600 is configured to support the base station to implement the functions of the base station in the detection method provided by the embodiment of the present application, for example, the transceiver unit 601 is configured to receive pilot signals sent by each of m user equipments UE; The processing unit 602 is configured to determine the received signal according to the pilot signals respectively sent by the m user equipment UEs and the channel responses to be detected of the m UEs, where m is a positive integer greater than 1; according to the pilot signals of the m UEs.
  • the base station determines the estimated value of the channel response to be detected of each UE under each round of estimation in the D round; determine the detection result, the detection result is the channel response to be detected of each UE in the first The estimated value under D rounds of estimation, where D is a positive integer greater than 1.
  • the processing unit 602 is configured to use the pilot signals of the m UEs according to the and the received signal, to determine the estimated value of the channel response to be detected of the first UE under the first round of estimation; or based on the pilot signals of the m UEs, the received signal and the priori Determine the channel response of the UE, determine the estimated value of the channel response to be detected of each UE under the first round of estimation, where the channel response of the kth UE that needs to be cancelled previously determined UE It includes the estimated values of the channel responses to be detected of the 1st to k-1th UEs under the first round of estimation, where k is a positive integer, and 1 ⁇ k ⁇ m.
  • the processing unit 602 is configured to perform the estimation according to the results of the m UEs. frequency signal, the received signal and the previously determined channel response of the UE that needs to be canceled, and determine the estimated value of the channel response to be detected of each UE under the Nth round of estimation, wherein the channel response to be canceled is determined.
  • the previously determined channel responses of the UEs include the estimated values of the channel responses to be detected of the other m-1 UEs under the N-1th round of estimation.
  • the processing unit 602 is configured to determine, according to the pilot signals of the m UEs, the differential signals of the m UEs, and the historical channel responses of the m UEs, the to-be-detected signal of each UE The estimated value of the channel response under the Nth round of estimation; the estimated value of the channel response to be detected of each UE under the Nth round of estimation is determined in order, and the differential signal is the received signal, which is determined by the The received signal, the pilot signal of the previous UE, the signal determined by the residual of the previous UE, the differential signal of the previous UE, the pilot signal of the previous UE, and the residual of the previous UE.
  • the residual is the difference between the estimated value of the UE's channel response to be detected in the Nth round of estimation and the historical channel response in the Nth round of estimation, and the historical channel response is The estimated value of the to-be-detected channel response of the UE under N-1 rounds of estimation, where N is a positive integer, and 1 ⁇ N ⁇ D.
  • the processing unit 602 is configured to determine the residual error under the N+1th round of estimation of the kth UE, and the residual error under the N+1th round of estimation of the kth UE is: Obtained by subtracting the estimated value of the channel response to be detected of the kth UE under the Nth round of estimation minus the historical channel response of the kth UE under the Nth round of estimation, where k is positive Integer, and 1 ⁇ k ⁇ m.
  • k positive Integer
  • 1 ⁇ k ⁇ m For the specific implementation of how to determine the residual error under the N+1 round estimation of the kth UE, reference may be made to some embodiments of the method in this application, such as the relevant content in the embodiment shown in FIG. 5 , which will not be repeated.
  • the processing unit 602 is configured to determine differential information of the k+1 th UE, where the differential information of the k+1 th UE is obtained by subtracting the differential information of the k th UE from the obtained by multiplying the pilot signal of the kth UE and the residual of the kth UE.
  • the differential information of the k+1 th UE is obtained by subtracting the differential information of the k th UE from the obtained by multiplying the pilot signal of the kth UE and the residual of the kth UE.
  • the processing unit 602 is configured to determine the historical channel responses under the N+1 rounds of estimation of the m UEs, and the historical channel responses under the N+1 rounds of estimation of the m UEs are: The estimated value of the to-be-detected channel responses of the m UEs under the Nth round of estimation.
  • the processing unit 602 is configured to determine the historical channel responses under the N+1 rounds of estimation of the m UEs, and the historical channel responses under the N+1 rounds of estimation of the m UEs are: The estimated value of the to-be-detected channel responses of the m UEs under the Nth round of estimation.
  • the processing unit 602 is configured to perform inverse Fourier transform IDFT on the obtained estimated value of the channel response to be detected of each UE under each round of estimation in round D, to obtain the first time domain estimated value; the estimated value of the to-be-detected channel response of each UE under each round of estimation in the D round is the first frequency domain estimated value; the first time domain estimated value is nonlinearly reconstructed to obtain second time-domain estimated value; performing Fourier transform DFT on the second time-domain estimated value to obtain a second frequency-domain estimated value.
  • inverse Fourier transform IDFT on the obtained estimated value of the channel response to be detected of each UE under each round of estimation in round D, to obtain the first time domain estimated value
  • the estimated value of the to-be-detected channel response of each UE under each round of estimation in the D round is the first frequency domain estimated value
  • the first time domain estimated value is nonlinearly reconstructed to obtain second time-domain estimated value
  • performing Fourier transform DFT on the second time-domain estimated value to obtain
  • the processing unit 602 is configured to construct the envelope according to the sequence length of the pilot signal of each UE and the length of the waveform of the first time-domain estimated value of the channel response to be detected of each UE function; through the set threshold, a position with stronger power is selected on the waveform of the first time-domain estimated value of the channel response to be detected of each UE, and an envelope waveform matrix is constructed; The method of matrix inversion is used to calculate the third time domain estimated value of the channel response to be detected of each UE; through the third time domain estimated value of the channel response to be detected of each UE and the envelope function , and calculate the second time-domain estimated value.
  • FIG. 7 shows a schematic structural diagram of a detection device 700 provided by the present application.
  • the detection apparatus 700 may be used to implement the detection method performed by the base station side described in the foregoing method embodiments.
  • the detection apparatus 700 may be a chip, a terminal, a base station, or other wireless communication equipment.
  • the detection apparatus 700 includes one or more processors 701, and the one or more processors 701 can support the detection apparatus 600 to implement the detection method performed by the base station described in the embodiments of this application, for example, as shown in FIG. 2 to FIG. 5 .
  • the processor 701 may be a general purpose processor or a special purpose processor.
  • the processor 701 may include a central processing unit (CPU) and/or a baseband processor.
  • the baseband processor may be used to process communication data (eg, the first message described above), and the CPU may be used to implement corresponding control and processing functions, execute software programs, and process data of software programs.
  • the detection apparatus 700 may further include a transceiving unit 705 to implement signal input (reception) and output (send).
  • the detection apparatus 700 may be a chip, and the transceiver unit 705 may be an input and/or output circuit of the chip, or the transceiver unit 705 may be an interface circuit of the chip, and the chip may be used as a component of a base station or other wireless communication equipment .
  • the detection apparatus 700 may be a base station.
  • the transceiver unit 705 may include a transceiver or a radio frequency chip.
  • Transceiver unit 705 may also include a communication interface.
  • the detection apparatus 700 may further include an antenna 706 , which may be used to support the transceiver unit 705 to implement the transceiver function of the detection apparatus 700 .
  • the detection apparatus 700 may include one or more memories 702 on which programs (or instructions or codes) 703 are stored, and the programs 703 may be executed by the processor 701, so that the processor 701 executes the foregoing method embodiments method described in .
  • data may also be stored in the memory 702 .
  • the processor 701 can also read data (eg, predefined information) stored in the memory 702, the data can be stored in the same storage address as the program 703, and the data can also be stored in a different address from the program 703 storage address.
  • the processor 701 and the memory 702 can be provided separately, or can be integrated together, for example, integrated on a single board or a system on chip (system on chip, SOC).
  • SOC system on chip
  • the detection apparatus 700 is a base station or a chip that can be used for access network equipment.
  • the transceiver unit 705 is configured to receive pilot signals sent by m user equipment UEs respectively;
  • the processor 701 is configured to determine the reception based on the pilot signals sent by m user equipment UEs and the channel responses to be detected of the m UEs.
  • the m is a positive integer greater than 1; according to the pilot signals of the m UEs and the received signal, determine the estimated value of the to-be-detected channel response of each UE under each round of estimation in the D rounds ; determine a detection result, where the detection result is an estimated value of the channel response to be detected of each UE under the D-th round of estimation, where D is a positive integer greater than 1.
  • the steps in the above method embodiments may be implemented by logic circuits in the form of hardware or instructions in the form of software in the processor 701 .
  • the processor 701 may be a CPU, a digital signal processor (DSP), an application specific integrated circuit (ASIC), a field programmable gate array (FPGA) or other programmable logic devices , for example, discrete gates, transistor logic devices, or discrete hardware components.
  • DSP digital signal processor
  • ASIC application specific integrated circuit
  • FPGA field programmable gate array
  • FIG. 8 is a schematic structural diagram of a base station provided by an embodiment of the present application. As shown in FIG. 8 , the functions of the network device in the detection method embodiments corresponding to FIG. 2 to FIG. 5 are performed.
  • Base station 800 may include one or more DUs 801 and one or more CUs 802.
  • the DU 801 may include at least one antenna 8011, at least one radio frequency unit 8012, at least one processor 8013 and at least one memory 8014.
  • the DU 801 part is mainly used for the transmission and reception of radio frequency signals, the conversion of radio frequency signals and baseband signals, and part of baseband processing.
  • CU 802 may include at least one processor 8022 and at least one memory 8021.
  • the CU 802 and the DU 801 can communicate through interfaces, wherein the control plane interface can be Fs-C, such as F1-C, and the user plane interface can be Fs-U, such as F1-U .
  • the CU 802 part is mainly used to perform baseband processing, control the base station, and the like.
  • the DU 801 and the CU 802 may be physically set together, or may be physically set apart, that is, a distributed base station.
  • the CU 802 is the control center of the base station, which can also be called a processing unit, and is mainly used to complete the baseband processing function.
  • the CU 802 may be used to control the base station to perform the operation procedures related to the network device in the foregoing method embodiments.
  • the baseband processing on the CU and DU can be divided according to the protocol layers of the wireless network.
  • the functions of the packet data convergence layer protocol (PDCP) layer and above are set in the protocol layers below the CU and PDCP.
  • functions such as a radio link control (radio link control, RLC) layer and a media access control (media access control, MAC) layer are set in the DU.
  • CU implements functions of radio resource control (radio resource control, RRC) and packet data convergence protocol (PDCP) layer
  • DU implements radio link control (radio link control, RLC), media access Control (media access control, MAC) and physical (physical, PHY) layer functions.
  • the base station 800 may include one or more radio frequency units (RUs), one or more DUs, and one or more CUs.
  • the DU may include at least one processor 8013 and at least one memory 8014
  • the RU may include at least one antenna 8011 and at least one radio frequency unit 8012
  • the CU may include at least one processor 8022 and at least one memory 8021 .
  • the CU802 may be composed of one or more single boards, and multiple single boards may jointly support a wireless access network (such as a 5G network) with a single access indication, or may respectively support wireless access systems of different access standards.
  • Access network such as LTE network, 5G network or other network.
  • the memory 8021 and the processor 8022 may serve one or more single boards. That is to say, the memory and processor can be provided separately on each single board. It can also be that multiple boards share the same memory and processor. In addition, necessary circuits may also be provided on each single board.
  • the DU 801 can be composed of one or more single boards, and multiple single boards can jointly support a wireless access network (such as a 5G network) with a single access indication, or can respectively support a wireless access network with different access standards (such as LTE network, 5G network or other network).
  • the memory 8014 and processor 8013 may serve one or more single boards. That is, the memory and processor can be set individually on each board. It can also be that multiple boards share the same memory and processor. In addition, necessary circuits may also be provided on each single board.
  • the DU and the CU may jointly perform the function of the processor 602 in the detection apparatus 600 shown in FIG. 6 or the function of the processor 701 in the detection apparatus 700 shown in FIG. 7 , which will not be described in detail.
  • the disclosed systems, devices and methods may be implemented in other manners.
  • some features of the method embodiments described above may be omitted, or not implemented.
  • the apparatus embodiments described above are only illustrative, and the division of units is only a logical function division. In actual implementation, there may be other division methods, and multiple units or components may be combined or integrated into another system.
  • the coupling between the various units or the coupling between the various components may be direct coupling or indirect coupling, and the above-mentioned coupling includes electrical, mechanical or other forms of connection.
  • the size of the sequence numbers of each process does not mean the sequence of execution, and the execution sequence of each process should be determined by its functions and inherent logic, rather than the embodiments of the present application. implementation constitutes any limitation.
  • the terminal and/or the network device may perform some or all of the steps in the embodiments of the present application, these steps or operations are only examples, and the embodiments of the present application may also perform other operations or variations of various operations .
  • various steps may be performed in different orders presented in the embodiments of the present application, and may not be required to perform all the operations in the embodiments of the present application.

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Power Engineering (AREA)
  • Mobile Radio Communication Systems (AREA)

Abstract

本申请提供了一种检测方法、装置和通信设备，涉及通信技术领域。其中，所述检测方法包括：根据m个用户设备UE各自发送的导频信号和m个UE的待检测信道响应确定接收信号，m为大于1的正整数；根据m个UE的导频信号和接收信号，确定每个UE的待检测信道响应在D轮中每个轮次估计下的估计值；确定检测结果，检测结果为每个UE的待检测信道响应在第D轮次估计下的估计值，D为大于1的正整数。本申请网络设备在接收到多个UE发送的导频信号后，为了消除非正交导频下的干扰问题和小区间的干扰问题，通过基础对消框架和残差对消框架这两种干扰对照架构对接收到的信号进行处理，从而检测出每个UE的信道响应，以提升基站内的导频资源数量和***容量。

Description

一种检测方法、装置和通信设备
本申请要求于2020年07月02日提交中国国家知识产权局、申请号为202010624975.7、申请名称为“一种检测方法、装置和通信设备”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本发明涉及通信技术领域，尤其涉及一种检测方法、装置和通信设备。
背景技术
随着移动通信和宽带无线接入技术的各自发展，两者的业务互相渗透越来越密切。为了满足移动通信带宽化的需求和对宽带通信移动化的调整，移动通信逐步引入长期演进(long term evolution，LTE)、5G等通信***。
现有技术中，在大规模多输入多输出***(massive multiple-input multiple-output，Massive MIMO)中，由于LTE、5G等***对频谱利用率要求较高，所以会引入同频组网的方式提高频谱利用率，以满足LTE、5G等***对频谱利用率要求。以探测参考信号(sounding reference signal，SRS)为例，当SRS调度比较频繁时，也即经常用于进行测量估计、信道质量探测等等，如果小区间导频信号采用同样频谱资源时，会出现严重的小区间干扰，造成了SRS的信噪比降低。
发明内容
为了解决上述造成导频信号的信噪比降低的问题，本申请的实施例提供了一种检测方法、装置和通信设备。
第一方面，本申请提供一种检测方法，所述方法由网络设备执行，包括：根据m个用户设备UE各自发送的导频信号和所述m个UE的待检测信道响应确定接收信号，所述m为大于1的正整数；根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在D轮中每个轮次估计下的估计值；确定检测结果，所述检测结果为每个UE的待检测信道响应在第D轮次估计下的估计值，所述D为大于1的正整数。
在该实施方式中，网络设备在接收到多个UE发送的导频信号后，为了消除非正交导频下的干扰问题和小区间的干扰问题，通过基础对消框架和残差对消框架这两种干扰对照架构对接收到的信号进行处理，从而检测出每个UE的信道响应，以提升网络设备内的导频资源数量和***容量。
在一种实施方式中，当UE的待检测信道响应在第N轮次估计时，所述N为正整数，且N＝1；所述根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在第1轮次估计下的估计值，包括：根据所述m个UE的导频信号和所述接收信号，确定第1个UE的待检测信道响应在第1轮次估计下的估计值；或者根 据所述m个UE的导频信号、所述接收信号和需要对消的在先已经确定的UE的信道响应，确定每个UE的待检测信道响应在第1轮次估计下的估计值，其中，第k个UE的所述需要对消的在先已经确定的UE的信道响应包括第1至k-1个UE的待检测信道响应在第1轮次估计下的估计值，所述k为正整数，且1<k≤m。
在该实施方式中，通过基础对消框架对获取的接收信号进行处理，也即通过接收信号，计算出每个UE的信道响应估计值，再对消已在先确定的UE的信道响应估计值干扰，然后再通过多个轮次迭代递减处理，对消上一轮次估计中除自身以外的UE的信道响应估计值干扰，使得到每个UE的信道响应无限接近真实值。
在一种实施方式中，当UE的待检测信道响应在第N轮次估计时，所述N为正整数，且1<N≤D；所述根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在第N轮次估计下的估计值，包括：根据所述m个UE的导频信号、所述接收信号和需要对消的在先已经确定的UE的信道响应，确定每个UE的待检测信道响应在第N轮次估计下的估计值，其中，所述需要对消的在先已经确定的UE的信道响应包括其他m-1个UE的待检测信道响应在第N-1轮次估计下的估计值。
在该实施方式中，通过基础对消框架对获取的接收信号进行处理，也即通过接收信号，计算出每个UE的信道响应估计值，再对消已在先确定的UE的信道响应估计值干扰，然后再通过多个轮次迭代递减处理，对消上一轮次估计中除自身以外的UE的信道响应估计值干扰，使得到每个UE的信道响应无限接近真实值。
在一种实施方式中，所述确定每个UE的待检测信道响应在第1轮次估计下的估计值的处理方式，具体为：
Figure PCTCN2021083335-appb-000001
其中，H 1,rebi表示先确定的各个UE的待检测信道响应在第一轮次估计的估计值，k表示对每个UE进行编号的标识，S k *表示S k的共轭；
所述确定每个UE的待检测信道响应在第n>1轮次估计下的估计值的处理方式，具体为：
Figure PCTCN2021083335-appb-000002
其中，m表示接收的导频信号的数量，且k≤m，H N-1,rebi表示各个UE的待检测信道响应在第N-1轮次估计下的估计值，N表示对每个UE正在进行估计的轮次数，S k *表示S k的共轭。
在一种实施方式中，所述根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在D轮中每个轮次估计下的估计值，包括：根据所述m个UE的导频信号、所述m个UE的差分信号和所述m个UE的历史信道响应，确定每个UE的待检测信道响应在第N轮次估计下的估计值；所述每个UE的待检测信道响应在第N轮次估计下的估计值是按序确定，所述差分信号为所述接收信号、由所述接收信号、上一个UE的导频信号和所述上一个UE的残差确定的信号和所述上一个UE 的差分信号、所述上一个UE的导频信号和所述上一个UE的残差确定的信号，所述残差为UE的待检测信道响应在第N轮次估计下的估计值与在第N轮次估计中的历史信道响应之间的差值，所述历史信道响应为所述UE的待检测信道响应在N-1轮次估计下的估计值，所述N为正整数，且1≤N≤D。
在该实施方式中，通过残差对消框架对接收到的信号进行处理，也即通过接收信号，依次计算出每个UE的残差和各个UE的差分信号，然后再结合各个UE的历史信道响应，计算出每个UE的信道响应估计值，最后通过多个轮次迭代递加处理，叠加每个UE在上一次轮中的估计值，使得到每个UE的信道响应无限接近真实值。
在一种实施方式中，所述确定每个UE的待检测信道响应在多个轮次估计下的估计值的处理方式，具体为：
Figure PCTCN2021083335-appb-000003
其中，k表示对每个UE进行编号的标识，N表示对每个UE正在进行估计的轮次数，Y N,lsk表示在第N轮次估计中第k个UE的接收信号，H N-1,rebk表示第N-1轮次估计中第k个UE的历史信道响应，H 0,rebk＝0。
在一种实施方式中，所述方法还包括：确定第k个UE的第N+1轮次估计下的残差，所述第k个UE的第N+1轮次估计下的残差是通过将所述第k个UE的待检测信道响应在第N轮次估计下的估计值减去所述第k个UE的第N轮次估计下的历史信道响应得到的，所述k为正整数，且1≤k≤m。
在一种实施方式中，所述方法还包括：确定第k+1个UE的差分信息，所述第k+1个UE的差分信息是通过将所述第k个UE的差分信息减去所述第k个UE的导频信号与所述第k个UE的残差的乘积得到的。
在一种实施方式中，所述方法还包括：确定所述m个UE的N+1轮次估计下的历史信道响应，所述m个UE的N+1轮次估计下的历史信道响应为所述m个UE的待检测信道响应在第N轮次估计下的估计值。
在一种实施方式中，在所述根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在D轮中每个轮次估计下的估计值之后，所述方法还包括：对得到的每个UE的待检测信道响应在D轮中每个轮次估计下的估计值进行傅里叶反变换IDFT，得到第一时域估计值；所述每个UE的待检测信道响应在D轮中每个轮次估计下的估计值为第一频域估计值；对所述第一时域估计值进行非线性重构，得到第二时域估计值；对所述第二时域估计值进行傅里叶变换DFT，得到第二频域估计值。
在该实施方式中，网络设备在得到时域信道响应后，对时域信道响应的波形进行重构，其目的在于对于干扰对消而言，必须要在每一次迭代过程中增加非线性的处理过程，使得通过非线性的处理过程之后的信道响应相比于处理之前的信道响应，更加接近真实的信道响应。
在一种实施方式中，所述对所述第一时域估计值进行非线性重构，得到第二时域估计值，包括：根据每个UE的导频信号的序列长度和所述每个UE的待检测信道响 应的第一时域估计值的波形的长度，构造包络函数；通过设定的阈值，在所述每个UE的待检测信道响应的第一时域估计值的波形上挑选出功率较强的位置，构造出包络波形矩阵；对所述包络波形矩阵求逆的方式，计算出所述每个UE的待检测信道响应的第三时域估计值；通过所述每个UE的待检测信道响应的第三时域估计值和所述包络函数，计算出所述第二时域估计值。
第二方面，本申请实施例还提供了一种检测装置，包括至少一个处理器，所述处理器用于执行存储器中存储的指令，以使得终端执行如第一方面各个可能实现的实施例。
第三方面，本申请实施例还提供了一种通信设备，用于执行如第一方面各个可能实现的实施例。
第四方面，本申请实施例还提供了一种计算机可读存储介质，其上存储有计算机程序，当所述计算机程序在计算机中执行时，令计算机执行如第一方面各个可能实现的实施例。
第五方面，本申请实施例还提供了一种计算设备，包括存储器和处理器，其特征在于，所述存储器中存储有可执行代码，所述处理器执行所述可执行代码时，实现第一方面各个可能实现的实施例。
第六方面，本申请实施例还提供了一种通信***，包括基站和至少一个用户设备UE，其中，所述基站用于执行如第一方面各个可能实现的实施例。
附图说明
下面对实施例或现有技术描述中所需使用的附图作简单地介绍。
图1为本申请实施例提供的一种检测***的架构示意图；
图2为本申请实施例提供的通过基础对消框架对接收到的信号进行处理得到每个UE的信道信息的流程图；
图3为本申请实施例提供的时域波形重构的示意图；
图4为本申请实施例提供的设计包络函数过程的流程图；
图5为本申请实施例提供的通过残差对消框架对接收到的信号进行处理得到每个UE的信道信息的流程图；
图6为本申请实施例提供的一种检测装置的结构示意图；
图7为本申请实施例提供的一种通信设备的结构示意图；
图8为本申请实施例提供的一种基站的结构示意图。
具体实施方式
下面将结合本申请实施例中的附图，对本申请实施例中的技术方案进行描述。
图1为本申请实施例提供的一种检测***的架构示意图。如图1所示，该***包括至少一个基站110_N和至少一个用户设备(user equipment，UE)120_M。一般而言，一个基站覆盖或管理一个或多个小区，一个小区内会有多个UE侦听或接收信号。
以基站110_2为例，基站110_2不仅可以为本基站小区B中的UE 120_4、UE 120_5和UE 120_6分配非正交导频资源，还可以为其它小区A内的UE 120_2和小区C内的UE120_M-2分配非正交导频资源。UE侧在得到基站侧分配的非正交导频资源后，可以通过分配的非正交导频资源向基站侧发送导频信号。基站侧在接收到多个UE发送的导频信号后，为了消除非正交导频下的干扰问题和小区间的干扰问题，本申请基站侧通过基础对消框架和残差对消框架这两种干扰对照架构对接收到的信号进行处理，从而检测出每个UE的信道响应，以提升基站内的导频资源数量和***容量。
下面通过两个实施例来讲述基站通过基础对消框架和残差对消框架这两种干扰对照架构，对接收到的信号进行处理，以检测出每个UE的信道响应。
实施例一
图2为本申请实施例提供的通过基础对消框架对接收到的信号进行处理得到每个UE的信道响应的流程图。如图2所示，基站具体实现过程如下：
步骤S201，基站接收至少一个UE发送的导频信号。
其中，导频信号包括公共解调参考信号(cell-specific reference signal，CRS)、下行解调参考信号(downlink demodulation reference signal，DL DMRS)、上行解调参考信号(uplink demodulation reference signal，UL DMRS)、信道状态信息参考信号(channel state information-reference signal，CSI-RS)、定位导频信号(positioning reference signal，PRS)、主同步信号(primary synchronization signal，PSS)、辅同步信号(secondary synchronization signal，SSS)、发现导频信号(discovery reference signal，DRS)、SRS等等，本申请实施例可以为任意一种，在此不作限定。
具体地，基站在接收到多个UE发送的导频信号后，对多个UE进行编号，分别为UE 1、UE 2、……UE k……。另外，定义UE 1发送的导频信号为S1，UE2发送的导频信号为S2，以此类推，UE k发送的导频信号为Sk。其中，k表示对每个UE进行编号的标识。
本申请基站对多个UE进行编号的原则，可选地，根据基站对各个UE的优先级进行排序，优选级越高，排序越靠前，因为在后续对每个UE的信道响应进行处理的过程中，排序越靠前的UE，估计出的信道响应越准确。其中，高优先级用户定义为对上下行***容量要求更高的用户，如大包业务用户、小区近点位置用户、或带宽大的用户等等。
为了后续描述方便，在此将基站接收到的多个导频信号进行数学建模，将接收到的多个导频信号与每个导频信号对应的UE的待检测信道响应进行建模，得到接收信号Y，定义为：
Figure PCTCN2021083335-appb-000004
其中，k表示对每个UE进行编号的序号，S k表示每个UE发送的导频信号的系数矩阵，H k表示每个UE待检测的信道响应。
步骤S202，基站对每个UE k的信道响应进行干扰对消的迭代估计，消除每个UE的信道响应中其它信道响应的干扰。
具体地，基站在得到接收信号Y后，在第一轮次估计中，对序号为k＝1的UE的待检测的信道响应进行估计；对序号为k＝2的UE待检测的信道响应进行估计时，需要消除序号为k＝1的UE的待检测的信道响应对其影响；对序号为k＝3的UE待检测的信道响应进行估计时，需要消除序号为k＝1和序号为k＝2的UE的待检测的信道响应对其影响；以此类推。
同时，基站对各个UE进行第一轮次估计之后，在第二轮次的估计过程中，依次对每个UE进行第二轮次估计时，需要消除除自身UE以外的各个UE在第一轮次估计的待检测的信道响应对其影响；在第三轮次的估计过程中，依次对每个UE进行第三轮次估计时，需要消除除自身UE以外的各个UE在第二轮次估计的待检测的信道响应对其影响；以此类推。
示例性地，对于第一轮次的估计，通过下列公式(2-1)计算，得到各个UE的频域信道响应H 1,lsk，公式(2-1)具体为：
Figure PCTCN2021083335-appb-000005
其中，H 1,rebi表示在第一轮次估计中每个UE的频域信道响应，k表示对每个UE进行编号的标识，S k *表示S k共轭。
对于第N(N不等于1)轮次的估计，通过下列公式(2-2)计算，得到各个UE的信道响应H N,lsk，公式(2-2)具体为：
Figure PCTCN2021083335-appb-000006
其中，m表示向基站发送的导频信号的数量，且k≤m，H N-1,rebi表示在第N-1轮次估计中每个UE的频域信道响应，N表示对每个UE正在进行估计的轮次数，S k *表示S k共轭。
步骤S203，基站对得到的频域信道响应H N,lsk进行傅里叶反变换(inverse discrete fourier transform，IDFT)，得到时域信道响应h N,lsk。
其中，基站通过下列公式(3)对频域信道响应H N,lsk进行IDFT，得到时域信道响应h N,lsk，公式(3)具体为：
h N,lsk＝IDFT(H N,lsk)。       (3)
步骤S204，基站对得到的时域信道响应h N,lsk进行非线性重构，得到重构的时域信道响应h N,rebk。
具体地，基站在得到时域信道响应h N,lsk后，对时域信道响应h N,lsk的波形进行重构，变量描述为h N,rebk。其目的在于对于干扰对消而言，必须要在每一次迭代过程中增加非线性的处理过程，使得通过非线性的处理过程之后的h N,rebk相比于h N,lsk，更加接近真实的信道响应。
步骤S205，基站对得到的时域信道响应h N,rebk进行傅里叶变换(discrete fourier transform，DFT)，得到频域信道响应H N,rebk。
其中，基站通过下列公式(4)对时域信道响应h N,rebk进行DFT，得到频域信道响应H N,rebk，公式(4)具体为：
H N,rebk＝DFT(h N,rebk)。        (4)
步骤S206，基站判断此时得到的频域信道响应H N,rebk是否为进行排序的最后一个UE的信道响应，如果是执行步骤S207；如果不是，执行步骤S202。
其中，在步骤S202-步骤S206循环计算UE的频域信道响应H N,rebk过程中，在步骤S206中确定此时得到的频域信道响应H N,rebk不是进行排序的最后一个UE的信道响应时，令k＝k+1，并将在此之前得到的各个UE的频域信道响应H N,rebk输入到步骤S202中，以便计算出下一个序号的UE的频域信道响应H N,rebk。
步骤S207，基站判断此时得到的频域信道响应H N,rebk所进行的估计轮次数是否为设定的轮次阈值D。如果是，则表明此时得到的频域信道响应H N,rebk所进行的估计轮次数为最后一轮次迭代得到的进行排序的最后一个UE的信道响应，执行步骤S208；如果不是，则表明此时得到的频域信道响应H N,rebk所进行的估计轮次数不是最后一轮次迭代得到的进行排序的最后一个UE的信道响应，执行步骤S202。
其中，在步骤S202-步骤S207循环计算UE的频域信道响应H N,rebk过程中，在步骤S207中确定此时得到的频域信道响应H N,rebk不是进行最后一轮次迭代得到的进行排序的最后一个UE的信道响应时，令N＝N+1且k＝1，并将在该轮次中得到的各个UE的频域信道响应H N,rebk输入到步骤S202中，以便计算出下一轮次的UE的频域信道响应H N,rebk。
步骤S208，基站将最后一轮次迭代处理的各个UE的频域信道响应H N,rebk作为最终的各个UE的信道响应。其中，最终得到的各个UE的信道响应为最后一轮次对消得到的信道响应，依次为H N,reb1、H N,reb2……H N,rebk。
本申请通过基础对消框架对获取的接收信号进行处理，也即通过接收信号，计算出每个UE的信道响应估计值，再对消已在先确定的UE的信道响应估计值干扰，然后再通过多个轮次迭代递减处理，对消上一轮次估计中除自身以外的UE的信道响应估计值干扰，使得到每个UE的信道响应无限接近真实值。针对不同的通信***传输信道而言，识别检测到信道响应的目的有所不同。以DMRS上行业务信道的导频为例，识别每个终端的信道响应后，有利于物理层的均衡处理，提升上行业务的服务质量；以SRS探测信号导频为例，识别每个终端的SRS信道响应后，有利于上行同步质量以及下行权值发送质量，从而提高上下行的***容量。
上述实施例一中提到基站对得到的时域信道响应h N,lsk进行非线性重构得到频域信道响应h N,rebk。在本本申请实施例中，采用的非线性重构主要包括基础非线性重构、高倍速采样和新波形这三种重构方案。下列具体讲述这三种方案如何将信道响应h N,lsk进行重构变换得到频域信道响应h N,rebk：
1、基础非线性重构方案
(1)如图3所示，根据接收到的非正交导频的导频信号S k的序列长度L sc和该导频信号对应的信道响应h N,lsk的波形的长度L，构造时域包络函数w，具体构成的公式为：
Figure PCTCN2021083335-appb-000007
其中，l表示为时域信道响应h N,lsk的样点编号，L sc表示非正交导频的导频信号S k的序列长度，L表示时域信道响应h N,lsk的波形的长度。
(2)通过预设门限Thr，在时域信道响应h N,lsk的波形上挑选出功率较强的位置tap i，然后构造出包络波形矩阵，具体构成的公式为：
Figure PCTCN2021083335-appb-000008
其中，tapi表示功率较强的样点位置，i 1和i 2表示功率较强样点的编号引索，I表示功率较强的样点数量。
另外，通过对时域信道响应h N,lsk提取功率较强的样点位置后，构成一个维度为I*1的向量，表示为h N,lsk,tap。
(3)通过矩阵求逆的方式，计算出重构的信道响应
Figure PCTCN2021083335-appb-000009
具体为：
Figure PCTCN2021083335-appb-000010
(4)通过用重构的信道响应
Figure PCTCN2021083335-appb-000011
和时域包络函数w，重构出时域信道响应h N,rebk，具体为：
Figure PCTCN2021083335-appb-000012
其中，i表示样点的编号引索，circshift(w，tap i)的物理含义是将包络函数w波形循环右移tap i个样点。
2、高倍速采样方案
(1)对频域信道响应H N,lsk的波形上的过采样(oversamp)样点进行过采样，oversamp的方式为频域上补零，从而对频域信道响应H N,lsk的波形长度通过尾部补零扩展成原来样本数目的oversamp倍数，此时再通过IDFT，获得的时域信道响应h N,lsk的波形，该波形上的维度点数为N ovsamp。
(2)根据公式(3)、(5)、(6)、(7)和(8)计算出重构出频域信道响应h N,rebk,ovsamp后，对时域信道响应h N,rebk,ovsamp的波形进行oversamp样点抽取，以得到时域信道响应h N,rebk，具体计算公式如下：
h N,rebk＝h N,rebk,ovsamp(1:oversamp:N ovsamp)；       (9)
其中，oversamp表示oversamp样点数，N ovsamp表示时域信道响应h N,lsk的波形的维度点数。
3、新波形方案
(1)根据接收到的非正交导频的导频信号S k的序列长度L sc和该导频信号对应的时域信道响应h N,lsk的波形的长度L，设计时域的包络函数w p。
示例性地，如图4所示，具体设计包络函数w p的过程如下：
步骤S401，指定每种时延扩展的时域波形包络函数y；
步骤S402，通过公式(5)中的构造时域包络函数w，得到初始包络函数w 0；
步骤S403，将得到的包络函数代入公式(10)中，计算得到2个样点系数；其中，公式(10)为：
Figure PCTCN2021083335-appb-000013
其中，x表示样点系数，y表示每种时延扩展的时域波形包络函数。
步骤S404，根据得到的2个样点系数，代入公式(10)中，计算得到更新重构波形w p；其中，公式(11)为：
Figure PCTCN2021083335-appb-000014
其中，x F是x的矩阵展开形式。
步骤S405，判断p值是否等于设定的阈值，如果等于，执行步骤S406；如果不等于，令p＝p+1，然后执行步骤S403；
其中，在步骤S403-步骤S405循环计算波形w p过程中，在步骤S405中确定此时得到的波形w p中p不等于阈值时，令p＝p+1，并将在此得到的波形w p输入到步骤S402中，以便计算出下一个波形w p。
步骤S406，得到考虑不同时延扩展下最优重构波形w p。
(2)在得到重构波形w p后，再根据公式(6)-(8)得到重构出时域信道响应h N,rebk。
本申请实施例中，基站在得到时域信道响应h N,lsk后，采用上述三个非线性重构中的任意一个方案，对时域信道响应h N,lsk进行非线性处理，得到频域信道响应h N,rebk，从而使得基站检测到的各个UE的信道响应更加接近真实值。
下面通过一个具体的例子来讲述实施例一的方案。此时，规定有三个UE向基站发送导频信号(也即m＝3)，且通过两个轮次迭代处理的每个UE的信道响应即可(也 即N＝2)。
基站在接收到三个UE发送的导频信号后，在第一轮次中对消处理过程中：
(1)对于UE 1进行初步估计，通过步骤S202中公式(2-1)，得到：
Figure PCTCN2021083335-appb-000015
然后通过步骤S203-步骤S205中公式(3)-(11)得到频域信道响应H 1,reb1；由于此时k＜m，所以需要循环进入步骤S202中，检测UE2的信道响应。
(2)对于UE 2进行初步估计，通过步骤S202中公式(2-1)和第一次循环得到的频域信道响应H 1,reb1，得到：
Figure PCTCN2021083335-appb-000016
然后通过步骤S203-步骤S205中公式(3)-(11)得到频域信道响应H 1,reb2；由于此时k＜m，所以需要循环进入步骤S202中，检测UE3的信道响应。
(3)对于UE3进行初步估计，通过步骤S202中公式(2-2)、第一次循环得到的频域信道响应H 1,reb1和第二次循环得到的频域信道响应H 1,reb2，得到：
Figure PCTCN2021083335-appb-000017
然后通过步骤S203-步骤S205中公式(5)-(11)得到频域信道响应H 1,reb3；由于此时k＝m，但此时N＜2，所以还需要循环进入步骤S202中，检测UE1第二轮次估计的信道响应。
在第二轮次中对消处理过程中：
(1)对于UE 1进行第二轮次估计，通过步骤S202中公式(2-2)、第一轮次估计中第二次循环得到的频域信道响应H 1,reb2和第一轮次估计中第三次循环得到的频域信道响应H 1,reb3，得到：
Figure PCTCN2021083335-appb-000018
然后通过步骤S203-步骤S205中公式(3)-(11)得到频域信道响应H 2,reb1；由于此时k＜m，所以需要循环进入步骤S202中，检测UE2第二轮次估计的信道响应。
(2)对于UE 2进行第二轮次估计，通过步骤S202中公式(3)、第一轮次估计中第一次循环得到的频域信道响应H 1,reb1和第一轮次估计中第三次循环得到的频域信道响应H 1,reb3，得到：
Figure PCTCN2021083335-appb-000019
然后通过步骤S203-步骤S205中公式(3)-(11)得到频域信道响应H 2,reb2；由于此时k＜m，所以需要循环进入步骤S202中，检测UE3第二轮次估计的信道响应。
(3)对于UE 3进行第二轮次估计，通过步骤S202中公式(3)、第一轮次估计中第一次循环得到的频域信道响应H 1,reb1和第一轮次估计中第二次循环得到的频域信道响应H 1,reb2，得到：
Figure PCTCN2021083335-appb-000020
然后通过步骤S203-步骤S205中公式(3)-(11)得到频域信道响应H 2,reb3；由于此时k＝m，且N＝2，所以不需要循环进入步骤S202中，直接将最后一轮次估计的H 2,reb1、H 2,reb2和H 2,reb3作为最终的各个UE的信道响应。
实施例二
图5为本申请实施例提供的通过残差对消框架对接收到的信号进行处理得到每个UE的信道响应的流程图。如图5所示，基站具体实现过程如下：
步骤S501，基站接收至少一个UE发送的导频信号。
具体地，基站在接收到多个UE发送的导频信号后，对多个UE进行编号，并且定义UE k发送的导频信号为Sk。另外，定义每个UE的历史信道响应为H histk，且规定在初始迭代是设置为0。
步骤S502，基站对每个UE的信道响应进行估计，消除每个UE的信道响应中其它信道响应的干扰。
具体地，此时的信号Y不再表示频域信号的接收信号，而是随着每次迭代对消过程，表示剩余未对消的残差信号Y。每个UE在依次进行信道估计时，都会对残差信号Y与导频信号进行估计并加上上一轮重构的历史信道响应H histk，在估计完成后把本次估计的导频信号继续从Y中减去，从而继续对下一个UE进行估计；完成一个轮次中所有UE的信道响应的估计后，再进行下一轮的用户估计；以此类推。
示例性地，对于每个UE进行估计时，通过下列公式(12)计算，得到各个UE的信道响应H 1,lsk，公式(12)具体为：
Figure PCTCN2021083335-appb-000021
其中，k表示对每个UE进行编号的序号，N为基站对每个UE的信道响应进行迭代估计的轮次数，H N,lsk表示第N轮次估计中UE的待检测的信道响应，Y N,lsk表示在第N轮次下第k个用户估计过程中时的残差结果，H N-1,histk表示第N-1轮次估计中UE的历史信道响应，H 0，histk＝0。
步骤S503，基站对得到的每个UE的信道响应H N,lsk进行IDFT，得到信道响应h N,lsk。其中，基站通过公式(3)对信道响应H N,lsk进行IDFT，得到信道响应h N,lsk。
步骤S504，基站对得到的各个UE的信道响应H N,lsk进行非线性重构，得到频域信道响应h N,rebk。其中，基站对H N,lsk进行非线性重构的方式可以为上述实施例一“基础非线性重构方案、高倍速采样方案和新波形方案”中的任意一种实现方式，具体实现过程详见上述图3-图4及相应的描述内容，本申请在此不再赘述了。
步骤S505，基站对得到的各个UE的频域信道响应h N,rebk进行DFT，得到频域信道响应H N,rebk。其中，基站通过公式(4)对频域信道响应h N,rebk进行DFT，得到频域信道响应H N,rebk。
步骤S506，基站判断此时得到的频域信道响应H N,rebk所进行的估计轮次数是否为设定的轮次阈值D。如果不是，则表明此时得到的频域信道响应H N,rebk所进行的估计轮次数不是最后一轮次迭代得到的各个UE的信道响应，执行步骤S507；如果是，则表明此时得到的频域信道响应H N,rebk所进行的估计轮次数为最后一轮次迭代得到的各个UE的信道响应，执行步骤S510。
步骤S507，基站根据得到的UE k的频域信道响应H N,rebk，计算信道响应的残差err。
具体地，基站通过公式(13)，计算各个UE的信道响应的残差err，公式(13)具体为：
err N,k＝H N,rebk-H N-1,histk。          (13)
步骤S508，基站根据得到各个UE的信道响应的残差err，更新接收信号Y N,k。
具体地，当迭代过程处于用户k增加过程时，基站通过公式(14-1)，更新接收信号Y N，公式(14-1)具体为：
Y N,k+1＝Y N,k-S kerr N,k。            (14-1)
当迭代过程处于迭代轮次N增加过程时，k此时已经累计到了m位置，基站通过公式(14-2)，更新接收信号Y N，公式(14-2)具体为：
Y N+1,1＝Y N,m-S merr N,m。            (14-2)
步骤S509，基站更新每个UE的历史信道响应为H N,histk，然后再执行步骤S502。
具体地，基站通过公式(15)，更新每个UE的历史信道响应为H  N,histk，公式(15)具体为：
H N,histk＝H N,rebk。          (15)
其中，步骤S508中更新接收信号Y N和步骤S509中更新每个UE的历史信道响应为H N,histk的顺序不限。
步骤S510，基站将最后一轮次迭代处理的各个UE的频域信道响应H N,rebk作为最终的各个UE的信道响应。其中，最终得到的各个UE的信道响应为最后一轮次对消得到的信道响应，依次为H N,reb1、H N,reb2……H N,rebk。
本申请通过残差对消框架对接收到的信号进行处理，也即通过接收信号，依次计算出每个UE的残差和各个UE的差分信号，然后再结合各个UE的历史信道响应，计算出每个UE的信道响应估计值，最后通过多个轮次迭代递加处理，叠加每个UE在上一次轮中的估计值，使得到每个UE的信道响应无限接近真实值。
下面通过一个具体的例子来讲述实施例二的方案。此时，规定有三个UE向基站发送导频信号(也即m＝3)，且通过两个轮次迭代处理的每个UE的信道响应即可(也即N＝2)。
基站在接收到三个UE发送的导频信号后，在第一轮次中对消处理过程中：
Figure PCTCN2021083335-appb-000022
其中，令H 0,reb1＝0，H 0,reb2＝0，H 0,reb3＝0，也即H 0,hist1＝0，H 0,hist2＝0，H 0,hist3＝0。
然后通过步骤S503-步骤S505中公式(3)-(11)得到频域信道响应H 1,reb1、H 1,reb2和H 1,reb3；由于此时N＜2，所以需要循环进入步骤S502中，检测各个UE第二轮次估计的信道响应。
此时根据公式(13)，计算各个UE的信道响应的残差err为：
err 1,1＝H 1,reb1-H 0,hist1＝H 1,reb1
err 1,2＝H 1,reb2-H 0,hist2＝H 1,reb2
err 1,3＝H 1,reb3-H 0,hist3＝H 1,reb3
根据得到各个UE的信道响应的残差err，根据公式(14-2)更新接收信号Y 2,1，根据公式(14-1)更新接收信号Y 2,2和Y 2,3，得到：
Y 2,1＝Y 1,3-S 3err 1,3
Y 2,2＝Y 2,1-S 1err 2,1
Y 2,3＝Y 2,2-S 2err 2,2
根据公式(15)，更新每个UE的历史信道响应H N,histk为：
H 1,hist1＝H 1,reb1
H 1,hist2＝H 1,reb2
H 1,hist3＝H 1,reb3
在第二轮次中对消处理过程中：
Figure PCTCN2021083335-appb-000023
Figure PCTCN2021083335-appb-000024
Figure PCTCN2021083335-appb-000025
然后通过步骤S503-步骤S505中公式(3)-(11)得到频域信道响应H 2,reb1、H 2,reb2和H 2reb3；由于此时N＝2，所以不需要循环进入步骤S502中，直接将最后一轮次估计的H 2,reb1、H 2,reb2和H 2,reb3作为最终的各个UE的信道响应。
上文详细介绍了本申请提供的一种由基站侧执行的检测方法的示例。可以理解的是，检测装置为了实现上述功能，其包含了执行各个功能相应的硬件结构和/或软件模块。本领域技术人员应该很容易意识到，结合本文中所公开的实施例描述的各示例的单元及算法步骤，本申请能够以硬件或硬件和计算机软件的结合形式来实现。某个功能究竟以硬件还是计算机软件驱动硬件的方式来执行，取决于技术方案的特定应用和 设计约束条件。专业技术人员可以对每个特定的应用来使用不同方法来实现所描述的功能，但是这种实现不应认为超出本申请的范围。
本申请可以根据上述方法示例对检测装置进行功能单元的划分，例如，可以将各个功能划分为各个功能单元，也可以将两个或两个以上的功能集成在一个处理单元中。上述集成的单元既可以采用硬件的形式实现，也可以采用软件功能单元的形式实现。需要说明的是，本申请中对单元的划分是示意性的，仅仅为一种逻辑功能划分，实际实现时可以有另外的划分方式。
例如，图6所示的检测装置600中包括收发单元601与处理单元602。
在本申请的一个实施方式中，检测装置600用于支持基站实现本申请实施例提供的检测方法中基站的功能，例如，收发单元601用于接收m个用户设备UE各自发送的导频信号；处理单元602用于根据m个用户设备UE各自发送的导频信号和所述m个UE的待检测信道响应确定接收信号，所述m为大于1的正整数；根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在D轮中每个轮次估计下的估计值；确定检测结果，所述检测结果为每个UE的待检测信道响应在第D轮次估计下的估计值，所述D为大于1的正整数。关于如何基站在接收到多个UE发送的导频信号后，检测各个UE的信道响应的具体实现方式，可以参考本申请方法部分实施例，例如图2-图5所示实施例中的相关内容，不做赘述。
在一个可能的实现方式中，当UE的待检测信道响应在第N轮次估计时，所述N为正整数，且N＝1；处理单元602用于根据所述m个UE的导频信号和所述接收信号，确定第1个UE的待检测信道响应在第1轮次估计下的估计值；或者根据所述m个UE的导频信号、所述接收信号和需要对消的在先已经确定的UE的信道响应，确定每个UE的待检测信道响应在第1轮次估计下的估计值，其中，第k个UE的所述需要对消的在先已经确定的UE的信道响应包括第1至k-1个UE的待检测信道响应在第1轮次估计下的估计值，所述k为正整数，且1<k≤m。关于如何确定每个UE的待检测信道响应在第1轮次估计下的估计值的具体实现方式，可以参考本申请方法部分实施例，例如图2所示实施例中的相关内容，不做赘述。
在一个可能的实现方式中，当UE的待检测信道响应在第N轮次估计时，所述N为正整数，且1<N≤D，处理单元602用于根据所述m个UE的导频信号、所述接收信号和需要对消的在先已经确定的UE的信道响应，确定每个UE的待检测信道响应在第N轮次估计下的估计值，其中，所述需要对消的在先已经确定的UE的信道响应包括其他m-1个UE的待检测信道响应在第N-1轮次估计下的估计值。关于如何确定每个UE的待检测信道响应在第N轮次估计下的估计值的具体实现方式，可以参考本申请方法部分实施例，例如图2所示实施例中的相关内容，不做赘述。
在一个可能的实现方式中，处理单元602用于根据所述m个UE的导频信号、所述m个UE的差分信号和所述m个UE的历史信道响应，确定每个UE的待检测信道响应在第N轮次估计下的估计值；所述每个UE的待检测信道响应在第N轮次估计下的估计值是按序确定，所述差分信号为所述接收信号、由所述接收信号、上一个UE 的导频信号和所述上一个UE的残差确定的信号和所述上一个UE的差分信号、所述上一个UE的导频信号和所述上一个UE的残差确定的信号，所述残差为UE的待检测信道响应在第N轮次估计下的估计值与在第N轮次估计中的历史信道响应之间的差值，所述历史信道响应为所述UE的待检测信道响应在N-1轮次估计下的估计值，所述N为正整数，且1≤N≤D。关于如何确定每个UE的待检测信道响应在第N轮次估计下的估计值的具体实现方式，可以参考本申请方法部分实施例，例如图5所示实施例中的相关内容，不做赘述。
在一个可能的实现方式中，处理单元602用于确定第k个UE的第N+1轮次估计下的残差，所述第k个UE的第N+1轮次估计下的残差是通过将所述第k个UE的待检测信道响应在第N轮次估计下的估计值减去所述第k个UE的第N轮次估计下的历史信道响应得到的，所述k为正整数，且1≤k≤m。关于如何确定第k个UE的第N+1轮次估计下的残差的具体实现方式，可以参考本申请方法部分实施例，例如图5所示实施例中的相关内容，不做赘述。
在一个可能的实现方式中，处理单元602用于确定第k+1个UE的差分信息，所述第k+1个UE的差分信息是通过将所述第k个UE的差分信息减去所述第k个UE的导频信号与所述第k个UE的残差的乘积得到的。关于如何确定第k+1个UE的差分信息的具体实现方式，可以参考本申请方法部分实施例，例如图5所示实施例中的相关内容，不做赘述。
在一个可能的实现方式中，处理单元602用于确定所述m个UE的N+1轮次估计下的历史信道响应，所述m个UE的N+1轮次估计下的历史信道响应为所述m个UE的待检测信道响应在第N轮次估计下的估计值。关于如何确定所述m个UE的N+1轮次估计下的历史信道响应的具体实现方式，可以参考本申请方法部分实施例，例如图5所示实施例中的相关内容，不做赘述。
在一个可能的实现方式中，处理单元602用于对得到的每个UE的待检测信道响应在D轮中每个轮次估计下的估计值进行傅里叶反变换IDFT，得到第一时域估计值；所述每个UE的待检测信道响应在D轮中每个轮次估计下的估计值为第一频域估计值；对所述第一时域估计值进行非线性重构，得到第二时域估计值；对所述第二时域估计值进行傅里叶变换DFT，得到第二频域估计值。关于如何将第一频域估计值转换成第二频域估计值的具体实现方式，可以参考本申请方法部分实施例，例如图2-图5所示实施例中的相关内容，不做赘述。
在一个可能的实现方式中，处理单元602用于根据每个UE的导频信号的序列长度和所述每个UE的待检测信道响应的第一时域估计值的波形的长度，构造包络函数；通过设定的阈值，在所述每个UE的待检测信道响应的第一时域估计值的波形上挑选出功率较强的位置，构造出包络波形矩阵；对所述包络波形矩阵求逆的方式，计算出所述每个UE的待检测信道响应的第三时域估计值；通过所述每个UE的待检测信道响应的第三时域估计值和所述包络函数，计算出所述第二时域估计值。关于如何对所述第一时域估计值进行非线性重构得到第二时域估计值的具体实现方式，可以参考本申请方法部分实施例，例如图3-图4所示实施例中的相关内容，不做赘述。
图7示出了本申请提供的一种检测装置700的结构示意图。检测装置700可用于实现上述方法实施例中描述的基站侧执行的检测方法。该检测装置700可以是芯片、终端、基站或者其它无线通信设备等。
检测装置700包括一个或多个处理器701，该一个或多个处理器701可支持检测装置600实现本申请实施例中所述的由基站执行的检测方法，例如图2-图5所示的实施例中由基站执行的方法。
该处理器701可以是通用处理器或者专用处理器。例如，处理器701可以包括中央处理器(central processing unit，CPU)和/或基带处理器。其中，基带处理器可以用于处理通信数据(例如，上文所述第一消息)，CPU可以用于实现相应的控制和处理功能，执行软件程序，处理软件程序的数据。
进一步的，检测装置700还可以包括收发单元705，用以实现信号的输入(接收)和输出(发送)。
例如，检测装置700可以是芯片，收发单元705可以是该芯片的输入和/或输出电路，或者，收发单元705可以是该芯片的接口电路，该芯片可以作为基站或其它无线通信设备的组成部分。
又例如，检测装置700可以为基站。收发单元705可以包括收发器或射频芯片。收发单元705还可以包括通信接口。
可选地，检测装置700还可以包括天线706，可以用于支持收发单元705实现检测装置700的收发功能。
可选地，检测装置700中可以包括一个或多个存储器702，其上存有程序(也可以是指令或者代码)703，程序703可被处理器701运行，使得处理器701执行上述方法实施例中描述的方法。可选地，存储器702中还可以存储有数据。可选地，处理器701还可以读取存储器702中存储的数据(例如，预定义的信息)，该数据可以与程序703存储在相同的存储地址，该数据也可以与程序703存储在不同的存储地址。
处理器701和存储器702可以单独设置，也可以集成在一起，例如，集成在单板或者***级芯片(system on chip，SOC)上。
在一种可能的设计中，检测装置700是基站或者可用于接入网设备的芯片。例如，收发单元705用于接收m个用户设备UE各自发送的导频信号；处理器701用于根据m个用户设备UE各自发送的导频信号和所述m个UE的待检测信道响应确定接收信号，所述m为大于1的正整数；根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在D轮中每个轮次估计下的估计值；确定检测结果，所述检测结果为每个UE的待检测信道响应在第D轮次估计下的估计值，所述D为大于1的正整数。
关于检测装置700在上述各种可能的设计中执行的操作的详细描述可以参照本申请提供的检测方法的实施例中基站的行为，例如图2-图5所示实施例中的相关内容， 不做赘述。
应理解，上述方法实施例的各步骤可以通过处理器701中的硬件形式的逻辑电路或者软件形式的指令完成。处理器701可以是CPU、数字信号处理器(digital signal processor，DSP)、专用集成电路(application specific integrated circuit，ASIC)、现场可编程门阵列(field programmable gate array，FPGA)或者其它可编程逻辑器件，例如，分立门、晶体管逻辑器件或分立硬件组件。
在检测装置600为基站的情况下，图8是本申请实施例提供的一种基站的结构示意图。如图8所示，执行上述图2-图5对应的检测方法实施例中网络设备的功能。基站800可包括一个或多个DU 801和一个或多个CU 802。所述DU 801可以包括至少一个天线8011，至少一个射频单元8012，至少一个处理器8013和至少一个存储器8014。所述DU 801部分主要用于射频信号的收发以及射频信号与基带信号的转换，以及部分基带处理。CU 802可以包括至少一个处理器8022和至少一个存储器8021。CU 802和DU 801之间可以通过接口进行通信，其中，控制面(Control plane)接口可以为Fs-C，比如F1-C，用户面(User Plane)接口可以为Fs-U，比如F1-U。
所述CU 802部分主要用于进行基带处理，对基站进行控制等。所述DU 801与CU 802可以是物理上设置在一起，也可以物理上分离设置的，即分布式基站。所述CU 802为基站的控制中心，也可以称为处理单元，主要用于完成基带处理功能。例如所述CU 802可以用于控制基站执行上述方法实施例中关于网络设备的操作流程。
具体的，CU和DU上的基带处理可以根据无线网络的协议层划分，例如分组数据汇聚层协议(packet data convergence protocol，PDCP)层及以上协议层的功能设置在CU，PDCP以下的协议层，例如无线链路控制(radio link control，RLC)层和媒体接入控制(media access control，MAC)层等的功能设置在DU。又例如，CU实现无线资源控制(radio resource control，RRC)，分组数据汇聚层协议(packet data convergence protocol，PDCP)层的功能，DU实现无线链路控制(radio link control，RLC)、媒体接入控制(media access control，MAC)和物理(physical，PHY)层的功能。
此外，可选地，基站800可以包括一个或多个射频单元(RU)，一个或多个DU和一个或多个CU。其中，DU可以包括至少一个处理器8013和至少一个存储器8014，RU可以包括至少一个天线8011和至少一个射频单元8012，CU可以包括至少一个处理器8022和至少一个存储器8021。
在一个实例中，所述CU802可以由一个或多个单板构成，多个单板可以共同支持单一接入指示的无线接入网(如5G网)，也可以分别支持不同接入制式的无线接入网(如LTE网，5G网或其他网)。所述存储器8021和处理器8022可以服务于一个或多个单板。也就是说，可以每个单板上单独设置存储器和处理器。也可以是多个单板共用相同的存储器和处理器。此外每个单板上还可以设置有必要的电路。所述DU 801可以由一个或多个单板构成，多个单板可以共同支持单一接入指示的无线接入网(如5G网)，也可以分别支持不同接入制式的无线接入网(如LTE网，5G网或其他网)。所述存储器8014和处理器8013可以服务于一个或多个单板。也就是说，可以每个单 板上单独设置存储器和处理器。也可以是多个单板共用相同的存储器和处理器。此外每个单板上还可以设置有必要的电路。
其中，DU与CU可以共同执行图6所示的检测装置600中的处理器602的功能或者图7所示的检测装置700中的处理器701的功能，具体不做赘述。
本所属领域的技术人员可以清楚地了解到，本申请提供的各实施例的描述可以相互参照，为描述的方便和简洁，例如关于本申请实施例提供的各装置、设备的功能以及执行的步骤可以参照本申请方法实施例的相关描述，各方法实施例之间、各装置实施例之间也可以互相参考、结合或引用。
在本申请所提供的几个实施例中，所揭露的***、装置和方法，可以通过其它的方式实现。例如，以上所描述的方法实施例的一些特征可以忽略，或不执行。以上所描述的装置实施例仅仅是示意性的，单元的划分，仅仅为一种逻辑功能划分，实际实现时可以有另外的划分方式，多个单元或组件可以结合或者可以集成到另一个***。另外，各单元之间的耦合或各个组件之间的耦合可以是直接耦合，也可以是间接耦合，上述耦合包括电的、机械的或其它形式的连接。
应理解，在本申请的各种实施例中，各过程的序号的大小并不意味着执行顺序的先后，各过程的执行顺序应以其功能和内在逻辑确定，而不应对本申请的实施例的实施过程构成任何限定。此外，本申请实施例中，终端和/或网络设备可以执行本申请实施例中的部分或全部步骤，这些步骤或操作仅是示例，本申请实施例还可以执行其它操作或者各种操作的变形。此外，各个步骤可以按照本申请实施例呈现的不同的顺序来执行，并且有可能并非要执行本申请实施例中的全部操作。

Claims (16)

  1. 一种检测方法，所述方法由网络设备执行，其特征在于，包括：
    根据m个用户设备UE各自发送的导频信号和所述m个UE的待检测信道响应确定接收信号，所述m为大于1的正整数；
    根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在D轮中每个轮次估计下的估计值；
    确定检测结果，所述检测结果为每个UE的待检测信道响应在第D轮次估计下的估计值，所述D为大于1的正整数。
  2. 根据权利要求1所述的方法，其特征在于，当UE的待检测信道响应在第N轮次估计时，所述N为正整数，且N＝1；
    所述根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在第1轮次估计下的估计值，包括：
    根据所述m个UE的导频信号和所述接收信号，确定第1个UE的待检测信道响应在第1轮次估计下的估计值；或者
    根据所述m个UE的导频信号、所述接收信号和需要对消的在先已经确定的UE的信道响应，确定每个UE的待检测信道响应在第1轮次估计下的估计值，其中，第k个UE的所述需要对消的在先已经确定的UE的信道响应包括第1至k-1个UE的待检测信道响应在第1轮次估计下的估计值，所述k为正整数，且1<k≤m。
  3. 根据权利要求1所述的方法，其特征在于，当UE的待检测信道响应在第N轮次估计时，所述N为正整数，且1<N≤D；
    所述根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在第N轮次估计下的估计值，包括：
    根据所述m个UE的导频信号、所述接收信号和需要对消的在先已经确定的UE的信道响应，确定每个UE的待检测信道响应在第N轮次估计下的估计值，其中，所述需要对消的在先已经确定的UE的信道响应包括其他m-1个UE的待检测信道响应在第N-1轮次估计下的估计值。
  4. 根据权利要求2-3任意一项所述的方法，其特征在于，所述确定每个UE的待检测信道响应在第1轮次估计下的估计值的处理方式，具体为：
    Figure PCTCN2021083335-appb-100001
    其中，H 1,rebi表示先确定的各个UE的待检测信道响应在第一轮次估计的估计值，k表示对每个UE进行编号的标识，S k *表示S k的共轭；
    所述确定每个UE的待检测信道响应在第n>1轮次估计下的估计值的处理方式，具体为：
    Figure PCTCN2021083335-appb-100002
    其中，m表示接收的导频信号的数量，且k≤m，H N-1,rebi表示各个UE的待检测信道响应在第N-1轮次估计下的估计值，N表示对每个UE正在进行估计的轮次数，S k *表示S k的共轭。
  5. 根据权利要求1所述的方法，其特征在于，所述根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在D轮中每个轮次估计下的估计值，包括：
    根据所述m个UE的导频信号、所述m个UE的差分信号和所述m个UE的历史信道响应，确定每个UE的待检测信道响应在第N轮次估计下的估计值；所述每个UE的待检测信道响应在第N轮次估计下的估计值是按序确定，所述差分信号为所述接收信号、由所述接收信号、上一个UE的导频信号和所述上一个UE的残差确定的信号和所述上一个UE的差分信号、所述上一个UE的导频信号和所述上一个UE的残差确定的信号，所述残差为UE的待检测信道响应在第N轮次估计下的估计值与在第N轮次估计中的历史信道响应之间的差值，所述历史信道响应为所述UE的待检测信道响应在N-1轮次估计下的估计值，所述N为正整数，且1≤N≤D。
  6. 根据权利要求5所述的方法，其特征在于，所述确定每个UE的待检测信道响应在多个轮次估计下的估计值的处理方式，具体为：
    Figure PCTCN2021083335-appb-100003
    其中，k表示对每个UE进行编号的标识，N表示对每个UE正在进行估计的轮次数，Y N,lsk表示在第N轮次估计中第k个UE的接收信号，H N-1,rebk表示第N-1轮次估计中第k个UE的历史信道响应，H 0,rebk＝0。
  7. 根据权利要求5-6任意一项所述的方法，其特征在于，所述方法还包括：
    确定第k个UE的第N+1轮次估计下的残差，所述第k个UE的第N+1轮次估计下的残差是通过将所述第k个UE的待检测信道响应在第N轮次估计下的估计值减去所述第k个UE的第N轮次估计下的历史信道响应得到的，所述k为正整数，且1≤k≤m。
  8. 根据权利要求7所述的方法，其特征在于，所述方法还包括：
    确定第k+1个UE的差分信息，所述第k+1个UE的差分信息是通过将所述第k个UE的差分信息减去所述第k个UE的导频信号与所述第k个UE的残差的乘积得到的。
  9. 根据权利要求5-6任意一项所述的方法，其特征在于，所述方法还包括：
    确定所述m个UE的N+1轮次估计下的历史信道响应，所述m个UE的N+1轮次估计下的历史信道响应为所述m个UE的待检测信道响应在第N轮次估计下的估计值。
  10. 根据权利要求1-9任意一项所述的方法，其特征在于，在所述根据所述m个UE的导频信号和所述接收信号，确定每个UE的待检测信道响应在D轮中每个轮次估计下的估计值之后，所述方法还包括：
    对得到的每个UE的待检测信道响应在D轮中每个轮次估计下的估计值进行傅里叶反变换IDFT，得到第一时域估计值；所述每个UE的待检测信道响应在D轮中每个轮次估计下的估计值为第一频域估计值；
    对所述第一时域估计值进行非线性重构，得到第二时域估计值；
    对所述第二时域估计值进行傅里叶变换DFT，得到第二频域估计值。
  11. 根据权利要求10所述的方法，其特征在于，所述对所述第一时域估计值进行非线性重构，得到第二时域估计值，包括：
    根据每个UE的导频信号的序列长度和所述每个UE的待检测信道响应的第一时域估计值的波形的长度，构造包络函数；
    通过设定的阈值，在所述每个UE的待检测信道响应的第一时域估计值的波形上挑选出功率较强的位置，构造出包络波形矩阵；
    对所述包络波形矩阵求逆的方式，计算出所述每个UE的待检测信道响应的第三时域估计值；
    通过所述每个UE的待检测信道响应的第三时域估计值和所述包络函数，计算出所述第二时域估计值。
  12. 一种检测装置，包括至少一个处理器，所述处理器用于执行存储器中存储的指令，以使得终端执行如权利要求1-11任一所述的方法。
  13. 一种通信设备，用于执行如权利要求1-11中的任一项所述的方法。
  14. 一种计算机可读存储介质，其上存储有计算机程序，当所述计算机程序在计算机中执行时，令计算机执行权利要求1-11中任一项的所述的方法。
  15. 一种计算设备，包括存储器和处理器，其特征在于，所述存储器中存储有可执行代码，所述处理器执行所述可执行代码时，实现权利要求1-11中任一项所述的方法。
  16. 一种通信***，包括基站和至少一个用户设备UE，其中，所述基站用于执行如权利要求1-11任一所述的方法。
PCT/CN2021/083335 2020-07-02 2021-03-26 一种检测方法、装置和通信设备 WO2022001240A1 (zh)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN202010624975.7A CN113890575B (zh) 2020-07-02 2020-07-02 一种检测方法、装置和通信设备
CN202010624975.7 2020-07-02

Publications (1)

Publication Number Publication Date
WO2022001240A1 true WO2022001240A1 (zh) 2022-01-06

Family

ID=79012821

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2021/083335 WO2022001240A1 (zh) 2020-07-02 2021-03-26 一种检测方法、装置和通信设备

Country Status (2)

Country Link
CN (1) CN113890575B (zh)
WO (1) WO2022001240A1 (zh)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115242332A (zh) * 2022-06-01 2022-10-25 武汉船舶通信研究所（中国船舶重工集团公司第七二二研究所） 短波信道衰落估计方法、装置、通信设备和存储介质

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115834436B (zh) * 2022-11-24 2024-05-03 中国联合网络通信集团有限公司 网络连通性检测方法、装置及存储介质

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20070030914A1 (en) * 2005-08-02 2007-02-08 Samsung Electronics Co., Ltd. Method and system for channel estimation and interference cancellation in an orthogonal frequency division multiple access network
CN101917355A (zh) * 2010-07-16 2010-12-15 北京创毅视通科技有限公司 一种信道估计方法及***
CN102035767A (zh) * 2010-12-10 2011-04-27 华为技术有限公司 信道估计方法和装置
CN106911367A (zh) * 2017-03-10 2017-06-30 广东顺德中山大学卡内基梅隆大学国际联合研究院 基于迭代干扰消除的多小区大规模mimo信道估计方法和装置

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101043479A (zh) * 2006-03-22 2007-09-26 松下电器产业株式会社 正交频分复用***中的信道估计方法
US7978776B2 (en) * 2008-01-16 2011-07-12 Southern Taiwan University Of Technology Channel estimation device and related method of an orthogonal frequency division multiplexing system
CN103379048B (zh) * 2012-04-16 2016-08-24 南京中兴软件有限责任公司 信道估计和检测的方法及基站
WO2015113251A1 (zh) * 2014-01-29 2015-08-06 华为技术有限公司 干扰抑制方法与装置
CN107888523B (zh) * 2017-11-02 2020-07-31 四川九洲电器集团有限责任公司 一种基于自相关模型的信号对消处理***和方法
CN108540410B (zh) * 2018-03-06 2020-11-03 东南大学 免调度传输***联合活跃用户检测和信道估计方法

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20070030914A1 (en) * 2005-08-02 2007-02-08 Samsung Electronics Co., Ltd. Method and system for channel estimation and interference cancellation in an orthogonal frequency division multiple access network
CN101917355A (zh) * 2010-07-16 2010-12-15 北京创毅视通科技有限公司 一种信道估计方法及***
CN102035767A (zh) * 2010-12-10 2011-04-27 华为技术有限公司 信道估计方法和装置
CN106911367A (zh) * 2017-03-10 2017-06-30 广东顺德中山大学卡内基梅隆大学国际联合研究院 基于迭代干扰消除的多小区大规模mimo信道估计方法和装置

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115242332A (zh) * 2022-06-01 2022-10-25 武汉船舶通信研究所（中国船舶重工集团公司第七二二研究所） 短波信道衰落估计方法、装置、通信设备和存储介质

Also Published As

Publication number Publication date
CN113890575B (zh) 2023-04-28
CN113890575A (zh) 2022-01-04

Similar Documents

Publication Publication Date Title
JP5497966B2 (ja) 無線ネットワークの基地局内でアンテナ相互関係を較正する方法およびそのデバイス
US10033513B2 (en) Channel impulse response estimation for full-duplex communication networks
CN106664273B (zh) Mimo同信道全双工收发器中的干扰抵消
JP5633914B2 (ja) 部分的チャンネル状態情報による多層ビーム成形
EP3245760A1 (en) System and method for training signals for full-duplex communications systems
WO2022001240A1 (zh) 一种检测方法、装置和通信设备
JP6858237B2 (ja) スパース順序付け反復群マルチアンテナチャネル推定
CN110830133B (zh) 一种基于多阶信道预测方法、预测***及应用
EP2589192A1 (en) Mimo channel state information estimation with coupled iterative two-stage ranking
WO2017097269A1 (zh) 一种干扰估计方法和设备
WO2016150246A1 (zh) 一种信号检测方法及装置
WO2017152732A1 (zh) 通道校正方法及装置
CN104488214B (zh) 用于在无线通信***中联合执行信道估计和干扰估计的方法和装置
WO2022206328A1 (zh) 一种通信协作方法及装置
WO2015149709A1 (zh) 一种噪声功率估计方法及网络侧设备
JP2013506380A (ja) マルチユーザ無線システムのパイロット信号割当の方法および装置
CN112740564B (zh) 通信方法、装置及***
CN111181621B (zh) 一种天线选择的方法及装置
CN107204817B (zh) 一种干扰检测方法及终端
CN116210177A (zh) 用于训练神经网络的参考信号补偿
CN109150386B (zh) 用户终端、服务小区解调方法及存储介质、电子设备
CN112751792B (zh) 一种信道估计方法及装置
CN103813374A (zh) 一种参考信号接收功率测量方法、装置和终端
CN115842701B (zh) 信道估计方法、装置、通信设备和存储介质
WO2021047311A1 (zh) 上行多站点信道估计的方法、站点和接入点

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 21833225

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 21833225

Country of ref document: EP

Kind code of ref document: A1