WO2021134802A1

WO2021134802A1 - Integrated clustering-based phase noise compensation method and system of wireless communication system

Info

Publication number: WO2021134802A1
Application number: PCT/CN2020/070354
Authority: WO
Inventors: 谢宁; 胡天星
Original assignee: 深圳大学
Priority date: 2020-01-03
Filing date: 2020-01-03
Publication date: 2021-07-08

Abstract

The present invention relates to an integrated clustering-based phase noise compensation method of a wireless communication system, comprising: a transmitting end transmits a carrier signal to a wireless channel on the basis of channel coding, baseband modulation and radio frequency modulation, and generates a received signal which is received by a receiving end; the receiving end obtains a baseband signal on the basis of the radio frequency demodulation and a phase-locked loop circuit, obtains a gain baseband signal on the basis of automatic gain control, thus obtains, on the basis of a clustering model, standard constellation point, a plurality of clusters corresponding to a plurality of received sample points and a plurality of corresponding clustering center points, obtains a norm distance between any clustering center point and each standard constellation point on the basis of a distance calculation model, thus determines a target constellation point, thus replaces, on the basis of a cluster mapping model, the coordinates of the sample points corresponding to the clusters with the coordinates of the target constellation points corresponding to the clusters to realize phase noise compensation, and thus obtains a target received signal; the receiving end obtains a target signal on the basis of baseband demodulation, channel decoding and the target received signal.

Description

基于集成聚类的无线通信***的相位噪声补偿方法及***Phase noise compensation method and system of wireless communication system based on ensemble clustering

技术领域Technical field

本公开涉及无线通信技术领域，具体涉及一种基于集成聚类的无线通信***的相位噪声补偿方法及***。The present disclosure relates to the field of wireless communication technology, and in particular to a phase noise compensation method and system for a wireless communication system based on integrated clustering.

背景技术Background technique

在现代无线通信中，关于无线通信***的理论分析，都假设了完美的相位参考估计，但在实际无线通信中，由于不完美锁相环电路或不完美的信道估计，相位参考估计常常带有噪声(即相位噪声)，相位噪声会大大降低***的解调性能。In modern wireless communication, the theoretical analysis of wireless communication systems assumes a perfect phase reference estimation, but in actual wireless communication, due to imperfect phase-locked loop circuits or imperfect channel estimation, the phase reference estimation often contains Noise (ie phase noise), phase noise will greatly reduce the demodulation performance of the system.

现有的抑制相位噪声的方法都集中在提高相位参考估计的精确性上，然而相位参考估计的精确性往往不高。Existing methods for suppressing phase noise are all focused on improving the accuracy of phase reference estimation, but the accuracy of phase reference estimation is often not high.

发明内容Summary of the invention

本公开是有鉴于上述的状况而提出的，其目的在于提供一种容易与现有的无线通信***集成并能够降低相位噪声的负面影响的基于集成聚类的无线通信***的相位噪声补偿方法及***。The present disclosure is made in view of the above-mentioned situation, and its purpose is to provide a phase noise compensation method and method for a wireless communication system based on integrated clustering that is easy to integrate with existing wireless communication systems and can reduce the negative effects of phase noise. system.

为此，本公开的第一方面提供了一种基于集成聚类的无线通信***的相位噪声补偿方法，是具有发射端和接收端的无线通信***的相位噪声补偿方法，其特征在于，包括：所述发射端基于信道编码、基带调制和射频调制向无线信道发射载波信号，所述载波信号经过所述无线信道获得接收信号；所述接收端接收所述接收信号，基于射频解调和锁相环电路从所述接收信号中获得基带信号，基于所述基带信号和自动增益控制获得增益基带信号，所述接收端基于聚类模型与所述增益基带信号获得多个标准星座点和与所述增益基带信号对应的多个样本点对应的多个聚类以及与各个聚类一一对应的多个聚类中心点，进而基于距离计算模型获得任一聚类中心点与各个标准星座点之间的范数距离，进而从所述多个标准星座点中选出与该聚类中心点具有最小范数距离的目标星座点，基于聚类映射模型将所述各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，进而获得目标接收信号，基于基带解调、信道解码和所述目标接收信号获得目标信号，其中，所述聚类模型为加权集成聚类算法，基于多个不同的聚类算法和所述增益基带信号获得与各个聚类算法对应的聚类结果，基于各个聚类结果获得所述各个聚类结果对应的共聚类指示矩阵，基于所述聚类结果和所述共聚类指示矩阵获得集合矩阵，进而获得所述加权集成聚类算法。To this end, the first aspect of the present disclosure provides a phase noise compensation method for a wireless communication system based on ensemble clustering, which is a phase noise compensation method for a wireless communication system having a transmitting end and a receiving end, and is characterized in that it includes: The transmitting end transmits a carrier signal to a wireless channel based on channel coding, baseband modulation, and radio frequency modulation, and the carrier signal obtains a received signal through the wireless channel; the receiving end receives the received signal based on radio frequency demodulation and phase-locked loop The circuit obtains a baseband signal from the received signal, obtains a gain baseband signal based on the baseband signal and automatic gain control, and the receiving end obtains a plurality of standard constellation points and the gain based on the clustering model and the gain baseband signal. Multiple clusters corresponding to multiple sample points corresponding to the baseband signal and multiple cluster center points one-to-one corresponding to each cluster, and then obtain the distance between any cluster center point and each standard constellation point based on the distance calculation model Norm distance, and then select the target constellation point with the smallest norm distance from the cluster center point from the multiple standard constellation points, and replace the coordinates of the sample points corresponding to each cluster based on the cluster mapping model To the coordinates of the target constellation point corresponding to the cluster to achieve phase noise compensation, and then obtain the target received signal, and obtain the target signal based on baseband demodulation, channel decoding, and the target received signal, wherein the clustering model is a weighted Integrated clustering algorithm, based on multiple different clustering algorithms and the gain baseband signal to obtain clustering results corresponding to each clustering algorithm, based on each clustering result to obtain the co-clustering indicator matrix corresponding to each clustering result , Obtaining a set matrix based on the clustering result and the co-clustering indicator matrix, and then obtaining the weighted ensemble clustering algorithm.

在本公开中，发射端基于信道编码、基带调制和射频调制向无线信道发射载波信号，载波信号经过无线信道获得接收信号，接收端接收接收信号并从中获得基带信号，基于基带信号和自动增益控制获得增益基带信号，进而基于聚类模型获得各个标准星座点和与增益基带信号对应的多个样本点对应的多个聚类以及与各个聚类一一对应的多个聚类中心点，基于距离计算模型获得任一聚类中心点与各个标准星座点之间的范数距离，并将与该聚类中心点的最小范数距离对应的标准星座点标记为目标星座点，进而基于聚类映射模型将各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现进行相位噪声补偿，进而获得目标接收信号，接收端基于基带解调、信道解码和目标接收信号获得目标信号。由此，能够降低相位噪声的负面影响，提供较高精确性的相位参考估计。In this disclosure, the transmitter transmits a carrier signal to the wireless channel based on channel coding, baseband modulation, and radio frequency modulation. The carrier signal obtains a received signal through the wireless channel, and the receiver receives the received signal and obtains a baseband signal from it, based on the baseband signal and automatic gain control Obtain the gain baseband signal, and then obtain each standard constellation point, multiple clusters corresponding to multiple sample points corresponding to the gain baseband signal, and multiple cluster center points one-to-one corresponding to each cluster based on the clustering model. The calculation model obtains the norm distance between any cluster center point and each standard constellation point, and marks the standard constellation point corresponding to the minimum norm distance of the cluster center point as the target constellation point, and then based on the cluster mapping The model replaces the coordinates of the sample points corresponding to each cluster with the coordinates of the target constellation point corresponding to the cluster to achieve phase noise compensation, and then obtain the target received signal. The receiving end is based on baseband demodulation, channel decoding, and target received signal Obtain the target signal. As a result, the negative influence of phase noise can be reduced, and a relatively accurate phase reference estimation can be provided.

本公开的第一方面所涉及的相位噪声补偿方法中，可选地，所述无线通信***的调制阶数被所述接收端已知，所述多个聚类的数量与所述调制阶数相同。由此，能够确定聚类的数量。In the phase noise compensation method related to the first aspect of the present disclosure, optionally, the modulation order of the wireless communication system is known by the receiving end, and the number of the plurality of clusters is equal to the modulation order the same. Thus, the number of clusters can be determined.

本公开的第一方面所涉及的相位噪声补偿方法中，可选地，所述目标接收信号由各个聚类中心点对应的坐标均转换为各自对应的目标星座点的坐标后获得。由此，能够获得目标接收信号。In the phase noise compensation method involved in the first aspect of the present disclosure, optionally, the target received signal is obtained by converting the coordinates corresponding to each cluster center point to the coordinates of the corresponding target constellation points. In this way, the target reception signal can be obtained.

本公开的第一方面所涉及的相位噪声补偿方法中，可选地，第i个聚类中心点与第j个标准星座点的范数距离满足：d _ij＝||C _i-S _j|| ²,i＝1,...,M,j＝1,...,M，其中，C _i为第i个聚类中心点，S _j为第j个标准星座点，M为多进制频移键控***的调制阶数。由此，能够获得聚类中心点与标准星座点之间的范数距离。 In the phase noise compensation method involved in the first aspect of the present disclosure, optionally, the norm distance between the i-th cluster center point and the j-th standard constellation point satisfies: d _ij =||C _i -S _j | | ² ,i=1,...,M,j=1,...,M, where C _i is the i-th clustering center point, S _j is the j-th standard constellation point, and M is multi-entry The modulation order of the frequency shift keying system. Thus, the norm distance between the cluster center point and the standard constellation point can be obtained.

本公开的第一方面所涉及的相位噪声补偿方法中，可选地，所述多个不同的聚类算法包括K均值聚类算法、K中心点聚类算法和凝聚层次聚类算法。由此，能够基于多个聚类算法获得加权集成聚类算法。In the phase noise compensation method involved in the first aspect of the present disclosure, optionally, the multiple different clustering algorithms include a K-means clustering algorithm, a K-center point clustering algorithm, and an agglomerated hierarchical clustering algorithm. Thus, a weighted ensemble clustering algorithm can be obtained based on multiple clustering algorithms.

本公开的第二方面提供了一种基于集成聚类的无线通信***的相位噪声补偿***，是具有发射装置和接收装置的无线通信***的相位噪声补偿***，其特征在于，包括：所述发射装置基于信道编码、基带调制和射频调制器调制向无线信道发射载波信号，所述载波信号经过所述无线信道获得接收信号；所述接收装置接收所述接收信号，基于射频解调和锁相环电路从所述接收信号中获得基带信号，基于所述基带信号和自动增益控制获得增益基带信号，所述接收装置基于聚类模型与所述增益基带信号获得多个标准星座点和与所述增益基带信号对应的多个样本点对应的多个聚类以及与各个聚类一一对应的多个聚类中心点，进而基于距离计算模型获得任一聚类中心点与各个标准星座点之间的范数距离，进而从所述多个标准星座点中选出与该聚类中心点具有最小范数距离的目标星座点，基于聚类映射模型将所述各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，进而获得目标接收信号，基于基带解调、信道解码和所述目标接收信号获得目标信号，其中，所述聚类模型为加权集成聚类算法，基于多个不同的聚类算法和所述增益基带信号获得与各个聚类算法对应的聚类结果，基于各个聚类结果获得所述各个聚类结果对应的共聚类指示矩阵，基于所述聚类结果和所述共聚类指示矩阵获得集合矩阵，进而获得所述加权集成聚类算法。The second aspect of the present disclosure provides a phase noise compensation system of a wireless communication system based on ensemble clustering, which is a phase noise compensation system of a wireless communication system having a transmitting device and a receiving device, and is characterized in that it comprises: the transmitting device The device transmits a carrier signal to a wireless channel based on channel coding, baseband modulation, and radio frequency modulator modulation, and the carrier signal obtains a received signal through the wireless channel; the receiving device receives the received signal, based on radio frequency demodulation and phase-locked loop The circuit obtains a baseband signal from the received signal, obtains a gain baseband signal based on the baseband signal and automatic gain control, and the receiving device obtains a plurality of standard constellation points and the gain based on the clustering model and the gain baseband signal. Multiple clusters corresponding to multiple sample points corresponding to the baseband signal and multiple cluster center points one-to-one corresponding to each cluster, and then obtain the distance between any cluster center point and each standard constellation point based on the distance calculation model Norm distance, and then select the target constellation point with the smallest norm distance from the cluster center point from the multiple standard constellation points, and replace the coordinates of the sample points corresponding to each cluster based on the cluster mapping model To the coordinates of the target constellation point corresponding to the cluster to achieve phase noise compensation, and then obtain the target received signal, and obtain the target signal based on baseband demodulation, channel decoding, and the target received signal, wherein the clustering model is a weighted Integrated clustering algorithm, based on multiple different clustering algorithms and the gain baseband signal to obtain clustering results corresponding to each clustering algorithm, based on each clustering result to obtain the co-clustering indicator matrix corresponding to each clustering result , Obtaining a set matrix based on the clustering result and the co-clustering indicator matrix, and then obtaining the weighted ensemble clustering algorithm.

在本公开中，发射装置基于信道编码、基带调制和射频调制向无线信道发射载波信号，载波信号经过无线信道获得接收信号，接收装置接收接收信号并从中获得基带信号，基于基带信号和自动增益控制获得增益基带信号，进而基于聚类模型获得各个标准星座点和与增益基带信号对应的多个样本点对应的多个聚类以及与各个聚类一一对应的多个聚类中心点，基于距离计算模型获得任一聚类中心点与各个标准星座点之间的范数距离，并将与该聚类中心点的最小范数距离对应的标准星座点标记为目标星座点，进而基于聚类映射模型将各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，进而获得目标接收信号，接收装置基于基带解调、信道解码和目标接收信号获得目标信号。In the present disclosure, the transmitting device transmits a carrier signal to a wireless channel based on channel coding, baseband modulation and radio frequency modulation, the carrier signal obtains a received signal through the wireless channel, and the receiving device receives the received signal and obtains a baseband signal from it, based on the baseband signal and automatic gain control Obtain the gain baseband signal, and then obtain each standard constellation point, multiple clusters corresponding to multiple sample points corresponding to the gain baseband signal, and multiple cluster center points one-to-one corresponding to each cluster based on the clustering model. The calculation model obtains the norm distance between any cluster center point and each standard constellation point, and marks the standard constellation point corresponding to the minimum norm distance of the cluster center point as the target constellation point, and then based on the cluster mapping The model replaces the coordinates of the sample points corresponding to each cluster with the coordinates of the target constellation points corresponding to the cluster to achieve phase noise compensation, and then obtain the target received signal. The receiving device is based on baseband demodulation, channel decoding and target received signal acquisition Target signal.

本公开的第二方面所涉及的相位噪声补偿***中，可选地，所述无线通信***的调制阶数被所述接收装置已知，所述多个聚类的数量与所述调制阶数相同。由此，能够确定聚类的数量。In the phase noise compensation system related to the second aspect of the present disclosure, optionally, the modulation order of the wireless communication system is known by the receiving device, and the number of the plurality of clusters and the modulation order the same. Thus, the number of clusters can be determined.

本公开的第二方面所涉及的相位噪声补偿***中，可选地，所述目标接收信号由各个聚类中心点对应的坐标均转换为各自对应的目标星座点的坐标后获得。由此，能够获得目标接收信号。In the phase noise compensation system involved in the second aspect of the present disclosure, optionally, the target received signal is obtained by converting the coordinates corresponding to each cluster center point to the coordinates of the corresponding target constellation points. In this way, the target reception signal can be obtained.

本公开的第二方面所涉及的相位噪声补偿***中，可选地，第i个聚类中心点与第j个标准星座点的范数距离满足：d _ij＝||C _i-S _j|| ²,i＝1,...,M,j＝1,...,M，其中，C _i为第i个聚类中心点，S _j为第j个标准星座点，M为多进制频移键控***的调制阶数。由此，能够获得聚类中心点与标准星座点之间的范数距离。 Phase noise compensation system of the present disclosure relates to the second aspect, the norm in the distance satisfy Alternatively, the i-th and j-th cluster center constellation points _{_{standard: d ij = || C i -S}} j | | ² ,i=1,...,M,j=1,...,M, where C _i is the i-th clustering center point, S _j is the j-th standard constellation point, and M is multi-entry The modulation order of the frequency shift keying system. Thus, the norm distance between the cluster center point and the standard constellation point can be obtained.

本公开的第二方面所涉及的相位噪声补偿***中，可选地，所述多个不同的聚类算法包括K均值聚类算法、K中心点聚类算法和凝聚层次聚类算法。由此，能够基于多个聚类算法获得加权集成聚类算法。In the phase noise compensation system involved in the second aspect of the present disclosure, optionally, the multiple different clustering algorithms include a K-means clustering algorithm, a K-center point clustering algorithm, and an agglomerated hierarchical clustering algorithm. Thus, a weighted ensemble clustering algorithm can be obtained based on multiple clustering algorithms.

根据本公开，能够提供一种容易与现有的无线通信***集成并能够降低相位噪声的负面影响的基于集成聚类的无线通信***的相位噪声补偿方法及***。According to the present disclosure, it is possible to provide a phase noise compensation method and system for a wireless communication system based on integrated clustering that is easily integrated with an existing wireless communication system and can reduce the negative influence of phase noise.

附图说明Description of the drawings

图1是示出了本公开的示例所涉及的经典无线通信***框图。FIG. 1 is a block diagram showing a classic wireless communication system involved in an example of the present disclosure.

图2是示出了本公开的示例所涉及的基于集成聚类的无线通信***的相位噪声补偿方法框图。FIG. 2 is a block diagram showing a phase noise compensation method of a wireless communication system based on ensemble clustering involved in an example of the present disclosure.

图3是示出了本公开的示例所涉及的基于集成聚类的无线通信***的相位噪声补偿方法的流程示意图。FIG. 3 is a schematic flowchart showing a phase noise compensation method of a wireless communication system based on ensemble clustering involved in an example of the present disclosure.

图4是示出了本公开的示例所涉及的多进制键控***中的星座图。FIG. 4 is a diagram showing a constellation diagram in the multi-ary keying system involved in the example of the present disclosure.

图5是示出了本公开的示例所涉及的确定目标星座点的星座图。FIG. 5 is a constellation diagram showing the determination of target constellation points involved in an example of the present disclosure.

图6示出了本公开的示例所涉及的固定相位噪声下正交相移键控调制***的星座图。FIG. 6 shows a constellation diagram of a quadrature phase shift keying modulation system under fixed phase noise involved in an example of the present disclosure.

图7示出了本公开的示例所涉及的固定相位噪声下正交幅度调制 ***的星座图。Fig. 7 shows a constellation diagram of a quadrature amplitude modulation system under fixed phase noise involved in an example of the present disclosure.

图8是示出了本公开的示例所涉及的固定相位噪声下平均归一化互信息与正确率随接收信噪比变化的波形图。FIG. 8 is a waveform diagram showing the variation of the average normalized mutual information and the accuracy rate with the received signal-to-noise ratio under fixed phase noise involved in the example of the present disclosure.

图9是示出了本公开的示例所涉及的固定相位噪声下平均误码率随接收信噪比变化的波形图。FIG. 9 is a waveform diagram showing the variation of the average bit error rate with the received signal-to-noise ratio under fixed phase noise involved in the example of the present disclosure.

图10是示出了本公开的示例所涉及的固定相位噪声下平均归一化互信息与正确率随相位隔移变化的波形图。FIG. 10 is a waveform diagram showing the variation of the average normalized mutual information and the accuracy rate with the phase shift under the fixed phase noise involved in the example of the present disclosure.

图11是示出了本公开的示例所涉及的固定相位噪声下平均误码率随相位隔移变化的波形图。FIG. 11 is a waveform diagram showing the variation of the average bit error rate with the phase shift under the fixed phase noise involved in the example of the present disclosure.

图12是示出了本公开的示例所涉及的随机相位噪声下平均归一化互信息随接收信噪比变化的波形图。FIG. 12 is a waveform diagram showing the variation of the average normalized mutual information with the received signal-to-noise ratio under random phase noise involved in the example of the present disclosure.

图13是示出了本公开的示例所涉及的随机相位噪声下平均误码率随接收信噪比变化的波形图。FIG. 13 is a waveform diagram showing the variation of the average bit error rate with the received signal-to-noise ratio under random phase noise involved in the example of the present disclosure.

图14是示出了本公开的示例所涉及的基于集成聚类的无线通信***的相位噪声补偿***框图。FIG. 14 is a block diagram showing a phase noise compensation system of a wireless communication system based on ensemble clustering involved in an example of the present disclosure.

具体实施方式Detailed ways

以下，参考附图，详细地说明本公开的优选实施方式。在下面的说明中，对于相同的部件赋予相同的符号，省略重复的说明。另外，附图只是示意性的图，部件相互之间的尺寸的比例或者部件的形状等可以与实际的不同。Hereinafter, with reference to the drawings, preferred embodiments of the present disclosure will be described in detail. In the following description, the same symbols are assigned to the same components, and repeated descriptions are omitted. In addition, the drawings are only schematic diagrams, and the ratio of dimensions between components or the shapes of components may be different from actual ones.

本公开提供一种基于集成聚类的无线通信***的相位噪声补偿方法及***(也可以简称“相位噪声补偿方法和相位噪声补偿***”)。在本公开中，基于集成聚类(即“集成聚类算法”)的无线通信***的相位噪声补偿方法及***可以较为广泛地应用在现有的无线通信***中，能够更加容易与现有的无线通信***进行集成，并能够较为明显地降低相位噪声对相位参考估计的影响，能够提高无线通信***的解调性能进而提高通信质量。以下结合附图进行详细描述本公开。The present disclosure provides a phase noise compensation method and system for a wireless communication system based on integrated clustering (also referred to as "phase noise compensation method and phase noise compensation system"). In the present disclosure, the phase noise compensation method and system of a wireless communication system based on integrated clustering (ie, "integrated clustering algorithm") can be widely used in existing wireless communication systems, and can be more easily compared with existing wireless communication systems. The integration of the wireless communication system can significantly reduce the influence of phase noise on the phase reference estimation, and can improve the demodulation performance of the wireless communication system and thus the communication quality. The present disclosure will be described in detail below with reference to the accompanying drawings.

图1是示出了本公开的示例所涉及的经典无线通信***框图。图2是示出了本公开的示例所涉及的基于集成聚类的无线通信***的相位噪声补偿方法框图。如图1和图2所示，本公开的相位噪声补偿方法可以应用于经典无线通信***，但本公开的示例不限于此，也可以应用于其他的无线通信***。本公开的相位噪声补偿方法及***可以更加容易与现有的无线通信***进行集成。FIG. 1 is a block diagram showing a classic wireless communication system involved in an example of the present disclosure. FIG. 2 is a block diagram showing a phase noise compensation method of a wireless communication system based on ensemble clustering involved in an example of the present disclosure. As shown in Figs. 1 and 2, the phase noise compensation method of the present disclosure can be applied to classic wireless communication systems, but the examples of the present disclosure are not limited to this, and can also be applied to other wireless communication systems. The phase noise compensation method and system of the present disclosure can be more easily integrated with the existing wireless communication system.

在一些示例中，本公开的相位噪声补偿方法可以仅在基带电路上工作，由此能够减少成本和复杂性。在一些示例中，本公开的相位噪声补偿方法可以是基带解调370前增加一个预处理过程(稍后描述)，可以不改变其他部分，因此能够使本公开的相位噪声补偿方法更加容易与现有的无线通信***进行集成。In some examples, the phase noise compensation method of the present disclosure may only work on the baseband circuit, thereby reducing cost and complexity. In some examples, the phase noise compensation method of the present disclosure may add a pre-processing process (described later) before the baseband demodulation 370, and other parts may not be changed. Therefore, the phase noise compensation method of the present disclosure can be easier and more modern. Some wireless communication systems are integrated.

在本公开中，如图1和图2所示，相位噪声补偿方法具有发射端10和接收端30的无线通信***的相位噪声补偿方法，其中，发射端10可以向接收端30发射信号，并被接收端30接收。In the present disclosure, as shown in FIG. 1 and FIG. 2, the phase noise compensation method has the phase noise compensation method of the wireless communication system of the transmitting end 10 and the receiving end 30, wherein the transmitting end 10 can transmit a signal to the receiving end 30, and Received by the receiving end 30.

在本公开中，发射端10(例如接入点)可以是指接入网中在空中接口上通过一个或多个扇区与无线终端通信的设备。发射端10可用于将收到的空中帧与IP帧进行相互转换，作为无线终端与接入网的其余部分之间的路由器，其中，接入网的其余部分可包括网际协议(IP)网络。发射端10还可以协调对空中接口的属性管理。例如，发射端10可以是GSM或CDMA中的基站(BTS，Base Transceiver Station)，也可以是WCDMA中的基站(NodeB)，还可以是LTE中的演进型基站(NodeB或eNB或e-NodeB，evolutional Node B)。In the present disclosure, the transmitting terminal 10 (for example, an access point) may refer to a device that communicates with a wireless terminal through one or more sectors on an air interface in an access network. The transmitting terminal 10 can be used to convert the received air frame and IP frame to each other, as a router between the wireless terminal and the rest of the access network, where the rest of the access network can include an Internet Protocol (IP) network. The transmitting end 10 can also coordinate the attribute management of the air interface. For example, the transmitter 10 may be a base station (BTS, Base Transceiver Station) in GSM or CDMA, a base station (NodeB) in WCDMA, or an evolved base station (NodeB or eNB or e-NodeB) in LTE. evolutional Node B).

在本公开中，接收端30可以是用户。其中，用户可以包括但不限于用户设备。用户设备可以包括但不限于智能手机、笔记本电脑、个人计算机(Personal Computer，PC)、个人数字助理(Personal Digital Assistant，PDA)、移动互联网设备(Mobile Internet Device，MID)、穿戴设备(如智能手表、智能手环、智能眼镜)等各类电子设备，其中，该用户设备的操作***可包括但不限于Android操作***、IOS操作***、Symbian(塞班)操作***、Black Berry(黑莓)操作***、Windows Phone8操作***等等。In the present disclosure, the receiving end 30 may be a user. Among them, the user may include but is not limited to user equipment. User equipment can include, but is not limited to, smart phones, laptops, personal computers (Personal Computer, PC), personal digital assistants (Personal Digital Assistant, PDA), mobile Internet devices (Mobile Internet Device, MID), wearable devices (such as smart watches) , Smart bracelets, smart glasses) and other electronic devices, where the operating system of the user device may include but not limited to Android operating system, IOS operating system, Symbian operating system, BlackBerry operating system , Windows Phone8 operating system and so on.

在本实施方式中，如图3所示，相位噪声补偿方法可以包括以下步骤：发射端10基于信道编码100、基带调制110和射频调制120向无线信道20发射载波信号，载波信号经过无线信道20获得接收信号(步骤S10)；接收端30接收接收信号，基于射频解调310和锁相环电路320从接收信号中获得基带信号，基于基带信号和自动增益控制330获得增益基带信号(步骤S20)；接收端30基于聚类模型340与增益基带信号获得各个标准星座点和与增益基带信号对应的多个样本点(也称“样本星座点”)对应的多个聚类以及与各个聚类一一对应的多个聚类中心点(步骤S30)；基于距离计算模型350获得任一聚类中心点与各个标准星座点之间的范数距离，进而从多个标准星座点中选出与该聚类中心点具有最小范数距离的目标星座点(步骤S40)；基于聚类映射模型360将各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，进而获得目标接收信号，基于基带解调370、信道解码380和目标接收信号获得目标信号(步骤S50)。In this embodiment, as shown in FIG. 3, the phase noise compensation method may include the following steps: the transmitter 10 transmits a carrier signal to the wireless channel 20 based on channel coding 100, baseband modulation 110, and radio frequency modulation 120, and the carrier signal passes through the wireless channel 20. Obtain the received signal (step S10); the receiving end 30 receives the received signal, obtains the baseband signal from the received signal based on the radio frequency demodulation 310 and the phase-locked loop circuit 320, and obtains the gain baseband signal based on the baseband signal and automatic gain control 330 (step S20) ; The receiving end 30 obtains multiple standard constellation points and multiple sample points corresponding to the gain baseband signal (also called "sample constellation points") based on the clustering model 340 and the gain baseband signal, and multiple clusters corresponding to each cluster. One corresponding multiple cluster center points (step S30); based on the distance calculation model 350, the norm distance between any cluster center point and each standard constellation point is obtained, and then the standard constellation point is selected from the multiple standard constellation points. The cluster center point has the target constellation point with the smallest norm distance (step S40); based on the cluster mapping model 360, the coordinates of the sample points corresponding to each cluster are replaced with the coordinates of the target constellation point corresponding to the cluster to realize the phase Noise compensation is used to obtain the target received signal, and the target signal is obtained based on the baseband demodulation 370, channel decoding 380 and the target received signal (step S50).

在本公开中，发射端10可以基于信道编码100、基带调制110和射频调制120向无线信道20发射载波信号，载波信号可以经过无线信道20获得接收信号，接收端30可以接收接收信号并从中获得基带信号，基于基带信号和自动增益控制获得增益基带信号，进而基于聚类模型340获得各个标准星座点和与增益基带信号对应的星座图中的多个样本点对应的多个聚类以及与各个聚类一一对应的多个聚类中心点，基于距离计算模型350获得任一聚类中心点与各个标准星座点之间的范数距离，并将与该聚类中心点的最小范数距离对应的标准星座点标记为目标星座点，进而基于聚类映射模型360将各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，进而获得目标接收信号，接收端30可以基于基带解调370、信道解码380和目标接收信号获得目标信号。In the present disclosure, the transmitting end 10 can transmit a carrier signal to the wireless channel 20 based on the channel coding 100, baseband modulation 110, and radio frequency modulation 120. The carrier signal can obtain the received signal through the wireless channel 20, and the receiving end 30 can receive the received signal and obtain it from it. The baseband signal is based on the baseband signal and automatic gain control to obtain the gain baseband signal, and then based on the clustering model 340 to obtain each standard constellation point and multiple clusters corresponding to multiple sample points in the constellation diagram corresponding to the gain baseband signal, and multiple clusters corresponding to each Cluster a number of cluster center points corresponding to each other one-to-one, and obtain the norm distance between any cluster center point and each standard constellation point based on the distance calculation model 350, and calculate the minimum norm distance from the cluster center point The corresponding standard constellation point is marked as the target constellation point, and then based on the cluster mapping model 360, the coordinates of the sample points corresponding to each cluster are replaced with the coordinates of the target constellation point corresponding to the cluster to achieve phase noise compensation, thereby obtaining the target Receiving the signal, the receiving end 30 can obtain the target signal based on the baseband demodulation 370, channel decoding 380, and the target received signal.

在步骤S10中，发射端10基于信道编码100、基带调制110和射频调制120向无线信道20发射载波信号，载波信号经过无线信道20获得接收信号。In step S10, the transmitter 10 transmits a carrier signal to the wireless channel 20 based on the channel coding 100, the baseband modulation 110, and the radio frequency modulation 120, and the carrier signal obtains a received signal through the wireless channel 20.

在一些示例中，如图1所示，发射端10中可以先将数据源经过信道编码100和基带调制110获得基带调制信号，其中，基带调制110的调制阶数为M，然后可以将导频符号周期性地嵌入基带调制符号中，之后可以经过射频调制120获得载波信号，发射端10可以将载波信号发射到无线信道20上，其中，载波信号的发射功率可以表示为P _s。 In some examples, as shown in FIG. 1, the transmitting terminal 10 may first obtain a baseband modulated signal from the data source through channel coding 100 and baseband modulation 110, where the modulation order of the baseband modulation 110 is M, and then the pilot The symbol is periodically embedded in the baseband modulation symbol, and then the carrier signal can be obtained through radio frequency modulation 120. The transmitter 10 can transmit the carrier signal to the wireless channel 20, where the transmission power of the carrier signal can be expressed as P _s .

在一些示例中，载波信号经过无线信道20获得接收信号，并被接收端30接收。在一些示例中，接收端30接收到的接收信号可以满足：

其中，h(t)表示为衰落振幅η(t)和衰落相位θ(t)的信道响应(即实际的信道衰落估计)且满足：h(t)＝η(t)exp(jθ(t))，s(t)表示为基带调制信号，ω ₀表示为载波频率，φ(t)表示为接收的载波随机相位，n(t)表示为接收噪声且为复高斯白噪声且满足：

其中，

是方差。 In some examples, the carrier signal obtains a received signal through the wireless channel 20 and is received by the receiving terminal 30. In some examples, the received signal received by the receiving end 30 may satisfy:

Among them, h(t) is expressed as the channel response of fading amplitude η(t) and fading phase θ(t) (that is, the actual channel fading estimation) and satisfies: h(t)=η(t)exp(jθ(t) ), s(t) represents the baseband modulation signal, ω ₀ represents the carrier frequency, φ(t) represents the random phase of the received carrier, n(t) represents the received noise and is complex Gaussian white noise and satisfies:

among them,

Is the variance.

在一些示例中，无线信道20可以是平坦衰落信道，其中，每个数据帧都可以经历一个独立的信道衰落，并且该信道衰落可以在其持续时间内保持不变，但可以在不同的数据帧上发生改变。其中，帧长度可以为L，衰落幅值和衰落相位可以分别在[-π,π]上建模为Nakagami-m分布和均匀分布，Nakagami-m分布的概率密度函数可以满足：

η≥0，其中，m∈[1/2,∞)，Γ(·)为Gamma函数。在一些示例中，瞬时接收信噪比可以满足：

平均接收信噪比(也称“接收信噪比”)表示为

其中，s表示为基带调制信号，η表示为衰落振幅。 In some examples, the wireless channel 20 can be a flat fading channel, where each data frame can experience an independent channel fading, and the channel fading can remain unchanged for its duration, but can be in different data frames Changes. Among them, the frame length can be L, and the fading amplitude and fading phase can be modeled as Nakagami-m distribution and uniform distribution on [-π,π] respectively. The probability density function of Nakagami-m distribution can satisfy:

η≥0, where m∈[1/2,∞), and Γ(·) is the Gamma function. In some examples, the instantaneous received signal-to-noise ratio can satisfy:

The average received signal-to-noise ratio (also called "received signal-to-noise ratio") is expressed as

Among them, s represents the baseband modulation signal, and η represents the fading amplitude.

在步骤S20中，接收端30接收接收信号，基于射频解调310和锁相环电路320从接收信号中获得基带信号，基于基带信号和自动增益控制330获得增益基带信号。In step S20, the receiving terminal 30 receives the received signal, obtains the baseband signal from the received signal based on the radio frequency demodulation 310 and the phase-locked loop circuit 320, and obtains the gain baseband signal based on the baseband signal and automatic gain control 330.

在一些示例中，如图1所示，接收端30可以接收接收信号。接收端30中接收信号可以经过射频解调310和锁相环电路320获得基带信号。在一些示例中，锁相环电路320可以为不理想的，从而可以导致第一相位误差，第一相位误差可以满足：

其中，

表示为锁相环电路320获得的第一相位，φ(t)表示为实际的第一相位。在一些示例中，第一相位误差可以建模为Tikhonov，由此可以获得第一相位误差(第一相位噪声)的概率密度函数满足：

其中，α表示为锁相环电路320的归一化循环信噪比，I ₀(·)表示为第零阶修正贝塞尔函数。在一些示例中，保留给导频符号的部分传输功率可以满足：P _c＝χP _s，其中χ为P _s的固定系数。α的近似值满足：

其中，B _L表示为环路带宽，T _b表示为位间隔。 In some examples, as shown in FIG. 1, the receiving end 30 may receive the received signal. The received signal in the receiving end 30 can obtain a baseband signal through radio frequency demodulation 310 and a phase-locked loop circuit 320. In some examples, the phase-locked loop circuit 320 may be undesirable, which may cause a first phase error, and the first phase error may satisfy:

among them,

It is expressed as the first phase obtained by the phase-locked loop circuit 320, and φ(t) is expressed as the actual first phase. In some examples, the first phase error can be modeled as Tikhonov, so that the probability density function of the first phase error (first phase noise) can be obtained as follows:

Among them, α represents the normalized cyclic signal-to-noise ratio of the phase-locked loop circuit 320, and I ₀ (·) represents the zeroth order modified Bessel function. In some examples, part of the transmission power reserved for pilot symbols may satisfy: P _c =χP _s , where χ is a fixed coefficient _{of P s.} The approximate value of α satisfies:

Among them, B _L represents the loop bandwidth, and T _b represents the bit interval.

在一些示例中，射频解调310可以利用发射端10的射频调制120的抑制码间干扰，并通过导频符号和导频观测值，可以使接收端30获得信道衰落估计且满足：

其中，

表示为接收端30基于信道估计获得的衰落振幅。在一些示例中，存在第二相位误差，第二相位误差满足：

其中，

表示为接收端30基于信道估计获得的衰落相位，θ(t)表示为实际的衰落相位。在一些示例中，第二相位误差(第二相位噪声)的概率密度函数可以满足：

其中，ρ为相关系数且满足：

在一些示例中，ρ可以设置为常数。 In some examples, the radio frequency demodulation 310 can use the radio frequency modulation 120 of the transmitter 10 to suppress inter-symbol interference, and through pilot symbols and pilot observations, the receiver 30 can obtain the channel fading estimation and satisfy:

among them,

It is expressed as the fading amplitude obtained by the receiving end 30 based on the channel estimation. In some examples, there is a second phase error, and the second phase error satisfies:

among them,

It is expressed as the fading phase obtained by the receiving end 30 based on the channel estimation, and θ(t) is expressed as the actual fading phase. In some examples, the probability density function of the second phase error (second phase noise) may satisfy:

Among them, ρ is the correlation coefficient and satisfies:

In some examples, ρ can be set as a constant.

在一些示例中，如图1所示，基带信号可以经过自动增益控制330获得增益基带信号。其中，增益基带信号可以满足：

在一些示例中，基带信号经过自动增益控制330获得增益基带信号，可以将增益基带信号除以信道衰落估计

的商来补偿信道衰落获得补偿信道衰落后的增益基带信号，满足：

其中，

表示为总残余相位噪声(即总相位误差)且满足：

表示为残余接收噪声，残余接收噪声可以为接收噪声受到信道估计的影响后获得的且满足：

In some examples, as shown in FIG. 1, the baseband signal may undergo automatic gain control 330 to obtain a gain baseband signal. Among them, the gain baseband signal can satisfy:

In some examples, the baseband signal undergoes automatic gain control 330 to obtain the gain baseband signal, and the gain baseband signal can be divided by the channel fading estimate

To compensate for channel fading to obtain a gain baseband signal that compensates for channel fading, which satisfies:

among them,

Expressed as the total residual phase noise (that is, the total phase error) and satisfies:

Denoted as residual received noise, the residual received noise can be obtained after the received noise is affected by the channel estimation and satisfies:

在一些示例中，如图1所示，在经典无线通信***中增益基带信号可以经过基带解调370获得发射端10传递的信息(即数据源)，但由于存在相位噪声，相位噪声可以使星座点偏离原始位置，会大大降低接收端30的解调性能，导致接收端30无法获得准确的信息。In some examples, as shown in Figure 1, in the classic wireless communication system, the gain baseband signal can be demodulated 370 to obtain the information (ie data source) transmitted by the transmitter 10, but due to the presence of phase noise, the phase noise can make the constellation If the point deviates from the original position, the demodulation performance of the receiving end 30 will be greatly reduced, and the receiving end 30 cannot obtain accurate information.

在一些示例中，图4和图5的横坐标I为相位振幅，纵坐标Q为正交振幅。In some examples, the abscissa I of FIGS. 4 and 5 is the phase amplitude, and the ordinate Q is the quadrature amplitude.

图4是示出了本公开的示例所涉及的多进制键控***中的星座图。其中，图4(a)是在不存在相位噪声时的星座图，图4(b)是在存在相位噪声时的星座图。FIG. 4 is a diagram showing a constellation diagram in the multi-ary keying system involved in the example of the present disclosure. Among them, Figure 4 (a) is a constellation diagram when phase noise is not present, and Figure 4 (b) is a constellation diagram when phase noise is present.

在一些示例中，如图4(a)和图4(b)所示，在多进制频移键控***中，相位噪声可以使星座点偏离原始位置。在图4(a)中，星座点的位置未受到相位噪声的影响，其中任一星座点区域即该星座点区域对应的中心点到两个最近的决策区域边缘的距离相等，即d ₁＝d ₂。在图4(b)中，相位噪声使星座点的位置发生偏移，偏移后的星座点区域到两个最近的决策区域边缘的距离是不同的，即d ₃≠d ₄。在一些示例中，解调误差概率可以由星座点到两个决策区域边缘的距离中较小的一方决定，即在图4(b)中，解调误差概率由d ₄决定，在这种情况下，相位噪声会降低解调性能。 In some examples, as shown in Fig. 4(a) and Fig. 4(b), phase noise can cause the constellation point to deviate from the original position in the M-ary frequency shift keying system. In Figure 4(a), the position of the constellation point is not affected by the phase noise, and the distance between any constellation point area, that is, the center point corresponding to the constellation point area, to the edges of the two closest decision areas is equal, that is, d ₁ = d ₂ . In Figure 4(b), the phase noise shifts the position of the constellation point, and the distance from the shifted constellation point area to the edge of the two closest decision areas is different, that is, d ₃ ≠d ₄ . In some examples, the demodulation error probability can be determined by the smaller of the distance between the constellation point and the edge of the two decision-making regions, that is, in Figure 4(b), the demodulation error probability is _{determined by d 4} , in this case Below, the phase noise will degrade the demodulation performance.

本公开提供一种能够降低相位噪声对相位参考估计的影响的无线通信***的相位噪声补偿方法，可以将增益基带信号进行预处理获得目标接收信号。The present disclosure provides a phase noise compensation method of a wireless communication system that can reduce the influence of phase noise on phase reference estimation, and can preprocess the gain baseband signal to obtain a target received signal.

在步骤S30中，接收端30可以基于聚类模型340与增益基带信号获得各个标准星座点和与增益基带信号(这里的增益基带信号可以是“补偿信道衰落后的增益基带信号”)对应的星座图中的多个样本点对应的多个聚类以及与各个聚类一一对应的多个聚类中心点。其中，聚类模型340可以为加权集成聚类算法(也称“集成聚类算法”)，基于多个不同的聚类算法和增益基带信号获得与各个聚类算法对应的聚类结果，基于各个聚类结果获得各个聚类结果对应的共聚类指示矩阵，基于聚类结果和共聚类指示矩阵获得集合矩阵，进而获得加权集成聚类算法(稍后具体描述)。In step S30, the receiving end 30 can obtain the respective standard constellation points and the constellation corresponding to the gain baseband signal (here the gain baseband signal may be the "gain baseband signal compensated for channel fading") based on the clustering model 340 and the gain baseband signal. Multiple clusters corresponding to multiple sample points in the figure and multiple cluster center points corresponding to each cluster one-to-one. Among them, the clustering model 340 may be a weighted ensemble clustering algorithm (also called an "integrated clustering algorithm"), which is based on multiple different clustering algorithms and gain baseband signals to obtain clustering results corresponding to each clustering algorithm, and based on each The clustering result obtains the co-clustering indicator matrix corresponding to each clustering result, the ensemble matrix is obtained based on the clustering result and the co-clustering indicator matrix, and then the weighted ensemble clustering algorithm (described in detail later) is obtained.

在一些示例中，如图5所示，增益基带信号经过聚类模型340可以获得与增益基带信号对应的星座图中的多个样本点，也即聚类模型340可以从增益基带信号中接收到多个样本点(例如，样本点401、样本点402和样本点403等)，多个样本点可以和星座图中的星座点相对应，可以基于加权集成聚类算法获得集成聚类结果(具体稍后描述)，集成聚类结果包括多个样本点对应的多个聚类(例如，样本点401、样本点402和样本点403可以对应聚类400)(聚类可以类比上述的星座点区域)以及与各个聚类对应的聚类中心点，例如，聚类400以及对应的聚类中心点C ₁、聚类410对应的中心点C ₂、聚类420对应的中心点C ₃、聚类430对应的中心点C ₄。在一些示例中，接收端30可以获得与增益基带信号对应的星座图中的各个标准星座点，例如标准星座点S ₁、标准星座点S ₂、标准星座点S ₃和标准星座点S ₄。标准星座点的数量可以和聚类的数量相同。 In some examples, as shown in FIG. 5, the gain baseband signal passes through the clustering model 340 to obtain multiple sample points in the constellation diagram corresponding to the gain baseband signal, that is, the clustering model 340 can receive from the gain baseband signal Multiple sample points (for example, sample point 401, sample point 402, sample point 403, etc.), multiple sample points can correspond to the constellation points in the constellation diagram, and the ensemble clustering results can be obtained based on the weighted ensemble clustering algorithm (specifically (To be described later), the integrated clustering result includes multiple clusters corresponding to multiple sample points (for example, sample point 401, sample point 402, and sample point 403 may correspond to cluster 400) (clusters can be analogous to the above-mentioned constellation point region ) And the cluster center points corresponding to each cluster, for example, cluster 400 and corresponding cluster center point C ₁ _{, center point C 2} corresponding to cluster 410, center _{point C 3} corresponding to cluster 420, cluster 430 corresponds to the center point C ₄ . In some examples, the receiving end 30 may obtain various standard constellation points in the constellation diagram corresponding to the gain baseband signal, such as the standard constellation point S ₁ , the standard constellation point S ₂ , the standard constellation point S _3, and the standard constellation point S ₄ . The number of standard constellation points can be the same as the number of clusters.

在一些示例中，调制阶数M可以被接收端30已知，聚类的数量可以与调制阶数M相同。由此，能够确定聚类的数量。在一些示例中，聚类模型340可以为加权集成聚类算法(稍后描述)，加权集成聚类算法可以基于多个不同的聚类算法和增益基带信号确定。在一些示例中，多个不同的聚类算法可以包括K均值聚类算法、K中心点聚类算法和凝聚层次聚类算法等不同类型的聚类算法。由此，能够基于多个聚类算法获得加权集成聚类算法。In some examples, the modulation order M may be known by the receiving end 30, and the number of clusters may be the same as the modulation order M. Thus, the number of clusters can be determined. In some examples, the clustering model 340 may be a weighted ensemble clustering algorithm (described later), and the weighted ensemble clustering algorithm may be determined based on multiple different clustering algorithms and gain baseband signals. In some examples, multiple different clustering algorithms may include different types of clustering algorithms such as K-means clustering algorithm, K-center point clustering algorithm, and agglomerative hierarchical clustering algorithm. Thus, a weighted ensemble clustering algorithm can be obtained based on multiple clustering algorithms.

在步骤S40中，接收端30可以基于距离计算模型350获得任一聚类中心点与各个标准星座点之间的范数距离，进而从多个标准星座点中选出与该聚类中心点具有最小范数距离的目标星座点。In step S40, the receiving end 30 can obtain the norm distance between any cluster center point and each standard constellation point based on the distance calculation model 350, and then select from a plurality of standard constellation points with the cluster center point. The target constellation point of the minimum norm distance.

在一些示例中，接收端30基于距离计算模型350和聚类模型340获得的聚类中心点以及标准星座点可以获得任意一个聚类中心点与各个标准星座点之间的范数距离。在一些示例中，任意一个聚类中心点与各个标准星座点之间的范数距离可以满足： d _ij＝||C _i-S _j|| ²,i＝1,...,M,j＝1,...,M(5)，其中，C _i为第i个中心点，S _j为第j个标准星座点，M为调制阶数。由此，能够获得聚类中心点与标准星座点之间的范数距离。在一些示例中，接收端30基于

可以获得与第i个聚类中心点的范数距离最小的标准星座点，将该标准星座点标记为第i个聚类中心点的目标星座点。由此，能够确定各个聚类中心点对应的目标星座点，也即确定各个聚类对应的目标星座点。例如，如图5所示，聚类400对应的聚类中心点C ₁(即第1个聚类中心点)，可以基于式(5)可以获得聚类中心点C ₁与各个标准星座点(例如标准星座点S ₁、标准星座点S ₂、标准星座点S ₃和标准星座点S ₄)之间的范数距离，并通过式(6)可以获得与聚类中心点C ₁的范数距离最小的标准星座点(例如标准星座点S ₂)，故可以将标准星座点S ₂标记为聚类中心点C ₁的目标星座点，也即标准星座点S ₂可以为聚类400对应的目标星座点，由此能够获得各个聚类对应的目标星座点，例如标准星座点S ₃可以为聚类410对应的目标星座点，标准星座点S ₄可以为聚类420对应的目标星座点，标准星座点S ₁可以为聚类430对应的目标星座点。 In some examples, the receiving end 30 can obtain the norm distance between any cluster center point and each standard constellation point based on the cluster center points obtained by the distance calculation model 350 and the cluster model 340 and the standard constellation points. In some examples, the norm distance between any cluster center point and each standard constellation point can satisfy: d _ij =||C _i -S _j || ² ,i=1,...,M,j = 1,...,M(5), where C _i is the i-th central point, S _j is the j-th standard constellation point, and M is the modulation order. Thus, the norm distance between the cluster center point and the standard constellation point can be obtained. In some examples, the receiving end 30 is based on

The standard constellation point with the smallest norm distance from the i-th cluster center point can be obtained, and the standard constellation point is marked as the target constellation point of the i-th cluster center point. Thus, the target constellation point corresponding to each cluster center point can be determined, that is, the target constellation point corresponding to each cluster can be determined. For example, as shown in Figure 5, the cluster center point C ₁ corresponding to the cluster 400 (that is, the first cluster center point) can be obtained based on formula (5) to obtain the cluster center point C ₁ and each standard constellation point ( For example, the norm distance between the standard constellation point S ₁ , the standard constellation point S ₂ , the standard constellation point S ₃ and the standard constellation point S ₄ ), and the norm to the cluster center point C _{1 can be obtained by formula (6)} The standard constellation point with the smallest distance (for example, the standard constellation point S ₂ ), so the standard constellation point S ₂ can be marked as the target constellation point of the cluster center point C ₁ , that is, the standard constellation point S ₂ can correspond to the cluster 400 target constellation points, thereby obtaining the target constellation points corresponding to each cluster, such as a standard constellation point S ₃ may be a cluster 410 corresponding to the target constellation points, constellation points S ₄ standard may be a cluster corresponding to the target constellation points 420, The standard constellation point S ₁ may be the target constellation point corresponding to the cluster 430.

在步骤S50中，接收端30可以基于聚类映射模型360将各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，进而获得目标接收信号，基于基带解调370、信道解码380和目标接收信号获得目标信号。In step S50, the receiving end 30 may replace the coordinates of the sample points corresponding to each cluster with the coordinates of the target constellation point corresponding to the cluster based on the cluster mapping model 360 to achieve phase noise compensation, thereby obtaining the target received signal. The target signal is obtained based on the baseband demodulation 370, channel decoding 380, and target reception signal.

在一些示例中，接收端30可以基于聚类映射模型360以及距离计算模型350获得的与各个聚类分别对应的目标星座点，将各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标，也就是说，各个聚类区域将发生移动使其对应的聚类中心点的坐标移动到与该聚类中心点对应的目标星座点的坐标。例如，如图5所示，聚类400中的样本点401、样本点402、样本点403，均将移动到标准星座点S ₂，图5中的其他聚类(例如聚类410、聚类420、聚类430)中的样本点也将发生相应的移动。在这种情况下，可以将各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，由此能够获得目标星座图，进而可以获得目标接收信号。 In some examples, the receiving end 30 may replace the target constellation points corresponding to each cluster obtained by the cluster mapping model 360 and the distance calculation model 350 with the coordinates of the sample points corresponding to each cluster to those corresponding to the cluster. The coordinates of the target constellation point, that is, each cluster area will move so that the coordinates of the corresponding cluster center point move to the coordinates of the target constellation point corresponding to the cluster center point. For example, as shown in Figure 5, the sample point 401, sample point 402, and sample point 403 in the cluster 400 will all move to the standard constellation point S ₂ , and other clusters in Figure 5 (for example, cluster 410, cluster 420. The sample points in the cluster 430) will also move accordingly. In this case, the coordinates of the sample points corresponding to each cluster can be replaced with the coordinates of the target constellation point corresponding to the cluster to achieve phase noise compensation, so that the target constellation diagram can be obtained, and the target received signal can be obtained. .

在一些示例中，增益基带信号可以进行预处理(即增益基带信号依次经过聚类模型340、距离计算模型350、聚类映射模型360)可以获得目标接收信号。在一些示例中，目标接收信号可以经过基带解调370、信道解码380获得目标信号，由此接收端30能够较为准确的获得发射端10发送的信息。In some examples, the gain baseband signal may be preprocessed (that is, the gain baseband signal passes through the clustering model 340, the distance calculation model 350, and the cluster mapping model 360 in sequence) to obtain the target received signal. In some examples, the target received signal can be obtained by baseband demodulation 370 and channel decoding 380 to obtain the target signal, so that the receiving terminal 30 can obtain the information sent by the transmitting terminal 10 more accurately.

在一些示例中，聚类模型340可以为加权集成聚类算法，可以基于多个不同的聚类算法和增益基带信号获得与各个聚类算法对应的聚类结果，基于各个聚类结果获得各个聚类结果对应的共聚类指示矩阵，基于聚类结果和共聚类指示矩阵获得集合矩阵，进而获得加权集成聚类算法。In some examples, the clustering model 340 may be a weighted ensemble clustering algorithm. The clustering results corresponding to each clustering algorithm may be obtained based on multiple different clustering algorithms and gain baseband signals, and the clustering results may be obtained based on each clustering result. The co-clustering indicator matrix corresponding to the class result is used to obtain the set matrix based on the clustering result and the co-clustering indicator matrix, and then the weighted ensemble clustering algorithm is obtained.

在一些示例中，从增益基带信号即式(4)中获得多个样本点的实部和虚部可以作为所选的聚类算法的二维输入信号。在一些示例中，可以选择采用基于分区和基于层次的两种类型的聚类算法进行聚类划分，例如，基于分区的聚类算法包括K均值聚类算法和K中心点聚类算法等，可以快速的确定所有聚类，可以对所有样本点进行聚类划分，并可以使每个聚类包含至少一个样本点；基于层次的聚类算法可以包括凝聚层次聚类算法等。在本实施方式中，可以采用加权集成聚类算法，由此能够获得较高质量的聚类结果。在一些示例，可以基于多个不同的聚类算法和增益基带信号获得与各个聚类算法对应的聚类结果，例如，可以采用K均值聚类算法、K均值(绝对值距离)聚类算法、K均值(夹角余弦)聚类算法、K中心点聚类算法、K中心点(绝对值距离)聚类算法、K中心点(夹角余弦)聚类算法、凝聚层次聚类算法、凝聚层次聚类算法(平均)、凝聚层次聚类算法(加权)共9个聚类算法分别对从增益基带信号中获得的多个样本点进行聚类划分获得9个聚类结果(也称为“基聚类结果”)，可以对9个基聚类结果进行集成获得集成聚类结果。In some examples, the real and imaginary parts of multiple sample points obtained from the gain baseband signal, that is, equation (4), can be used as the two-dimensional input signal of the selected clustering algorithm. In some examples, two types of clustering algorithms based on partition and hierarchy can be selected for clustering. For example, partition-based clustering algorithms include K-means clustering algorithm and K-center point clustering algorithm, etc. To quickly determine all clusters, all sample points can be divided into clusters, and each cluster can contain at least one sample point; hierarchical clustering algorithms can include agglomerative hierarchical clustering algorithms, etc. In this embodiment, a weighted ensemble clustering algorithm can be used, so that a higher-quality clustering result can be obtained. In some examples, clustering results corresponding to each clustering algorithm can be obtained based on multiple different clustering algorithms and gain baseband signals. For example, K-means clustering algorithm, K-means (absolute distance) clustering algorithm, K-means (angle cosine) clustering algorithm, K center point clustering algorithm, K center point (absolute value distance) clustering algorithm, K center point (angle cosine) clustering algorithm, agglomerative hierarchical clustering algorithm, aggregation level Clustering algorithm (average), agglomerative hierarchical clustering algorithm (weighted), a total of 9 clustering algorithms are divided into multiple sample points obtained from the gain baseband signal to obtain 9 clustering results (also called "basic"). Clustering results"), 9 base clustering results can be integrated to obtain integrated clustering results.

在一些示例中，不同的聚类算法对多个样本点进行聚类划分可以获得多个基聚类结果。在一些示例中，在给定的无线信道20中，多个基聚类结果之间的性能可以是不同的，因此可以采用一种加权集成方法对每个基聚类结果分配权值。由此，能够获得集成聚类结果。In some examples, different clustering algorithms can cluster multiple sample points to obtain multiple base clustering results. In some examples, in a given wireless channel 20, the performance between multiple base clustering results may be different, so a weighted integration method may be used to assign a weight to each base clustering result. Thus, the integrated clustering result can be obtained.

在一些示例中，获得集成聚类算法可以包括两个阶段：生成阶段和星座检测阶段。在一些示例中，生成阶段包括：基于各个聚类结果可以获得各个聚类结果对应的共聚类指示矩阵，即可以将获得的多个基聚类结果分别转化为各自对应的共聚类指示矩阵。例如，可以获得N _b个基聚类结果，并可以将N _b个基聚类结果分别转化为各自对应的共聚类指示矩阵D _i(i＝1,2,...,N _b)。其中，在第t个基聚类结果中，假如第i个和第j个样本点属于同一聚类，则D _i(i,j)＝1；否则D _i(i,j)＝0。 In some examples, obtaining the integrated clustering algorithm may include two stages: a generation stage and a constellation detection stage. In some examples, the generation stage includes: obtaining the co-clustering indicator matrix corresponding to each clustering result based on each clustering result, that is, converting the obtained multiple base clustering results into respective co-clustering indicator matrices. . For example, N _b base clustering results can be obtained, and the N _b base clustering results can be converted into respective co-clustering indicator matrices _Di (i=1, 2,..., N _b ). Wherein, in the t-th groups clustering result, if the i-th and j-th points belong to the same cluster, then _{D i (i, j) =} 1; otherwise, _{D i (i, j) =} 0.

在一些示例中，基于聚类结果和共聚类指示矩阵可以获得集合矩阵，进而可以获得加权集成聚类算法。在一些示例中，可以根据加权组合规则，多个(即N _b个)基聚类结果可以归纳为集合矩阵E满足：

其中，ω _i是D _i的权重，i＝1,2,...,N _b，s.t.表示为满足约束。W是权重的矢量，满足：

在一些示例中，为了抑制参数W过度拟合到其中一个基聚类结果，可以引入一个正则化项

其可以表示为各个基聚类结果的权重的负熵的总和。 In some examples, the aggregate matrix can be obtained based on the clustering result and the co-clustering indicator matrix, and then the weighted ensemble clustering algorithm can be obtained. In some examples, according to the weighted combination rule, multiple (ie, N _b ) basis clustering results can be summarized as a set matrix E that satisfies:

Wherein, ω _i is the heavy weight of D _i, i = 1,2, ..., N b, st expressed to satisfy the constraint. W is a vector of weights, which satisfies:

In some examples, in order to prevent the parameter W from overfitting to one of the base clustering results, a regularization term can be introduced

It can be expressed as the sum of the negative entropy of the weights of each base clustering result.

在一些示例中，星座检测阶段包括：可以假设集合矩阵E中的每一项E _i,j代表基聚类结果提供的证据，即第i个和第j个样本点属于同一个星座点(例如，标准星座点)，也即第i个和第j个样本点属于同一个聚类。在一些示例中，假设本公开的解调***包括M个星座点，对于第i个样本点，可以引入一个预设参数β _i,k用于表示第i个样本点来自于第k个星座点的强度，即β _i,k的值越高则表示第i个样本点来自于第k个星座点的可能性越高，其中，k＝1,2,...,M。在一些示例中，聚类的数量可以和调制阶数相等，即可以满足：K＝M。 In some examples, the constellation detection stage includes: it can be assumed that each item E _i,j in the set matrix E represents the evidence provided by the base clustering result, that is, the i-th and j-th sample points belong to the same constellation point (for example, , Standard constellation points), that is, the i-th and j-th sample points belong to the same cluster. In some examples, it is assumed that the demodulation system of the present disclosure includes M constellation points. For the i-th sample point, a preset parameter β _i,k can be introduced to indicate that the i-th sample point comes from the k-th constellation point. That is _{, the higher the value of β i,k} , the higher the probability that the i-th sample point comes from the k-th constellation point, where k=1, 2,...,M. In some examples, the number of clusters can be equal to the modulation order, which can satisfy: K=M.

在一些示例中，可以令B表示为符号-星座点倾向矩阵满足：

其中，

表示为通用的集合表示符号，M表示为星座点的数量，N _L表示为接收的样本点的数量，

的值可以表示为第i个和第j个样本点属于同一个星座点的可能性。在一些示例中，E _i,j的值可以表示第i个和第j个样本点位于同一聚类的可能性。在集合矩阵E中的双向关联可以受到未观察到的非负参数Q的影响，Q可以满足： Q＝BB ^T，其中的每个元素β _i,kβ _j,k可以表示第k个星座点对Q _i,j的贡献，其中非负参数Q的每一项Q _i,j可以满足：

Q _i,j可以表示为(BB ^T) _i,j。在一些示例中，假设单个元素E _i,j(即集合矩阵E中的每一项E _i,j)的似然性可以由

给出，其中，

且可以为泊松概率密度函数，Γ(·)是Gamma函数。由上所述，集成解调***概率可以表示为

在一些示例中，可以通过最大化式(9)中定义的条件概率估计B的值。可以通过对式(9)取负对数和下降常数获得加权集成聚类算法的目标函数，并且由于Γ(1)＝Γ(2)＝1，E _i,j值在0和1之间值在0和1之间，可以假设Γ(E _i,j+1)＝1，因此目标函数可以满足：

In some examples, B can be expressed as a symbol-constellation point tendency matrix that satisfies:

among them,

Represented as a set of generic representation symbols, M is the number of constellation points, N _L represents the number of sample points is received,

The value of can be expressed as the probability that the i-th and j-th sample points belong to the same constellation point. In some examples, _{the value of E i,j} may indicate the possibility that the i-th and j-th sample points are located in the same cluster. The two-way association in the set matrix E can be affected by the unobserved non-negative parameter Q, Q can satisfy: Q=BB ^T , where each element β _i,k β _j,k can represent the k-th constellation point Contribution to Q _i,j , where each item of non-negative parameter Q Q _i,j can satisfy:

Q _i,j can be expressed as (BB ^T ) _i,j . In some examples, it is assumed that _{the likelihood of a single element E i,j} (that is, each item E _i,j in the set matrix E) can be determined by

Gives, where,

And it can be a Poisson probability density function, and Γ(·) is a Gamma function. From the above, the probability of the integrated demodulation system can be expressed as

In some examples, the value of B can be estimated by maximizing the conditional probability defined in equation (9). The objective function of the weighted ensemble clustering algorithm can be obtained by taking the negative logarithm of equation (9) and the descent constant, and since Γ(1)=Γ(2)=1, the _{value of E i,j} is between 0 and 1. Between 0 and 1, it can be assumed that Γ(E _i,j +1) = 1, so the objective function can satisfy:

在一些示例中，可以加入在式(8)中定义的正则化项R，并用式(7)取代E，例如，E _i,j可以表示为ω _t(D _t) _i,j，其中，t＝1,2,...,N _p，ω _t可以等同于ω _i，D _t可以等同于D _i以及后续的D _m，由此能够将目标函数即式(10)转化为

其中，D _t表示为第t个基聚类结果对应的共聚类指示矩阵，λ是权衡参数其满足：λ≥0，其可以控制定义在式(10)中的目标函数和正则化项R之间的平衡。 In some examples, the regularization term R defined in formula (8) can be added, and the formula (7) can be substituted for E. For example, E _i,j can be expressed as ω _t (D _t ) _i,j , where t =1,2,...,N _p , ω _t can be equal to ω _i , D _t can be equal to D _i and the subsequent D _m , so that the objective function, that is, equation (10) can be transformed into

Among them, D _{t is} expressed as the co-clustering indicator matrix corresponding to the t-th basis clustering result, and λ is a trade-off parameter which satisfies: λ≥0, which can control the objective function and regularization term R defined in formula (10) Balance between.

在一些示例中，若给定W，式(11)可以退化为：

s.t.表示满足于。可以根据B最小化J(B)。在一些示例中，为了解决式(12)中的约束优化问题，可以采用乘法更新规则，假设φ _i,k为拉格朗日乘子，其可以约束于β _i,k≥0和Φ＝[φ _i,k]，则拉格朗日函数可以满足：

在一些示例中，可以根据β _i，k获得拉格朗日函数

的梯度满足：

β _i,k的估计值可以满足：

由此可以获得

In some examples, if W is given, equation (11) can be reduced to:

st means to be satisfied. J(B) can be minimized according to B. In some examples, in order to solve the constrained optimization problem in equation (12), the multiplicative update rule can be adopted, assuming that φ _i,k is a Lagrangian multiplier, which can be constrained to β _i,k ≥ 0 and Φ=[ φ _i,k ], the Lagrangian function can satisfy:

In some examples, the Lagrangian function can be obtained according to β _i,k

The gradient satisfies:

The estimated value of β _{i,k can satisfy:}

From this you can get

在一些示例中，根据阶优化条件，φ _i,kβ _i,k＝0，可以获得：

由此可以获得β _i,k的更新规则：

在一些示例中，参考实际情况，可以基于式(17)获得：

In some examples, according to the order optimization condition, φ _i,k β _i,k = 0, we can obtain:

From this, the update rule of _{β i,k} can be obtained:

In some examples, referring to the actual situation, it can be obtained based on equation (17):

在一些示例中，可以使用乘法更新规则，若使用的为非负值初始化β _i,k,则β _i,k的值可以保持非负性。更新B后并固定，式(11)可以退化为：

可以使用拉格朗日乘子解决下式的无约束最小化问题:

，其中，χ是约束于

的拉格朗日乘子。在一些示例中，为了获得

的最小值，可以假设所有变量的梯度消失，因此可以获得：

和

从式(21)可以获得：

在一些示例中，可以将式(23)代入式(22)可以获得ω _m的更新规则满足：

其中，ω _m等同于前文中的ω _t。 In some examples, the multiplicative update rule can be used. If a non-negative value is used to initialize β _i,k , _{the value of β i,k} can remain non-negative. After updating B and fixing it, equation (11) can be reduced to:

The Lagrangian multiplier can be used to solve the unconstrained minimization problem of the following formula:

, Where χ is constrained to

Lagrange multiplier. In some examples, in order to obtain

The minimum value of can be assumed that the gradients of all variables disappear, so you can get:

with

From equation (21), we can get:

In some examples, equation (23) can be substituted into equation (22) to obtain the update rule of _{ω m that satisfies:}

Among them, ω _{m is} _{equivalent to ω t} in the preceding text.

在一些示例中，可以基于多个基聚类结果、式(11)、式(18)和式(24)获得加权集成聚类算法。在一些示例中，可以基于不同的聚类算法获得多个基聚类结果，并预定义一个权衡参数λ，若设置λ＝∞，则可以强制所有要素***的权重相等，若设置λ＝0，则丢弃正则化项。In some examples, a weighted ensemble clustering algorithm can be obtained based on multiple base clustering results, formula (11), formula (18), and formula (24). In some examples, multiple base clustering results can be obtained based on different clustering algorithms, and a trade-off parameter λ can be predefined. If λ=∞, the weights of all element systems can be forced to be equal. If λ=0, The regularization item is discarded.

在一些示例中，可以通过式(24)确定λ取决于

的值。权衡参数λ可以满足：

在一些示例中，为了确定合适的λ值，可以通过改变λ ₀的值来评估相应的性能。若λ ₀的值足够大，则可以使分配给各个基聚类结果的权重近似相等，除非一部分基聚类结果很差，相应的性能不会随着λ ₀增加而显着变化。在一些示例，加权集成聚类算法包括：基于多个基聚类结果获得集合矩阵E，并基于权衡参数λ、β _i,k的更新规则式(18)以及ω _m的更新规则式(24)迭代地更新B和W，直至B和W满足标准。并可以基于式(11)获得目标函数的值。例如，当迭代的次数达到150时停止。在一些示例中，为了抑制局部最小值的出现，可以用随机的初始条件重复上述算法多次，例如，可以用随机的初始条件重复算法10次，并从中选出目标函数的值为最小时对应的B和W。由此，能够获得由多个基聚类结果集成获得的集成聚类结果。 In some examples, it can be determined by formula (24) that λ depends on

Value. The trade-off parameter λ can satisfy:

In some examples, in order to determine the appropriate value of λ, the corresponding performance can be evaluated _{by changing the value of λ 0.} If _{the value of λ 0} is large enough, the weights assigned to each base clustering result can be approximately equal, unless a part of the base clustering results are very poor, the corresponding performance will not change significantly with the increase _{of λ 0.} In some examples, the weighted ensemble clustering algorithm includes: obtaining a set matrix E based on multiple basis clustering results, and _{an update regular expression (18) based on the trade-off parameters λ, β i,k and} an update regular expression (24) of ω _m Update B and W iteratively until B and W meet the criteria. And the value of the objective function can be obtained based on formula (11). For example, stop when the number of iterations reaches 150. In some examples, in order to suppress the occurrence of local minimums, the above algorithm can be repeated multiple times with random initial conditions. For example, the algorithm can be repeated 10 times with random initial conditions, and the value of the objective function can be selected from when the value of the objective function is the smallest. B and W. Thus, an integrated clustering result obtained by integrating multiple base clustering results can be obtained.

图6示出了本公开的示例所涉及的固定相位噪声下正交相移键控调制***的星座图。图7示出了本公开的示例所涉及的固定相位噪声下正交幅度调制***的星座图。其中，如图6和图7所示，图6(a)和图7(a)分别为各自对应***下的标准星座点即不含相位噪声时的星座图，图6(b)和图7(b)分别为各自对应***下的未使用本实施方式时接收到的多个样本点，图6(c)和图7(c)分别为各自对应***下的使用K均值聚类算法对应的聚类中心点的星座图，图6(d)和图7(d)分别为各自对应***下的使用凝聚层次聚类算法对应的聚类中心点的星座图。在图6和图7中，L＝100，

m＝1.5。 FIG. 6 shows a constellation diagram of a quadrature phase shift keying modulation system under fixed phase noise involved in an example of the present disclosure. FIG. 7 shows a constellation diagram of a quadrature amplitude modulation system under fixed phase noise involved in an example of the present disclosure. Among them, as shown in Figure 6 and Figure 7, Figure 6 (a) and Figure 7 (a) are the standard constellation points under their respective systems, that is, the constellation diagram without phase noise, Figure 6 (b) and Figure 7 (b) are the multiple sample points received when this embodiment is not used in the respective corresponding systems. Figures 6(c) and 7(c) are the corresponding K-means clustering algorithms in their respective systems. The constellation diagrams of the cluster center points. Figures 6(d) and 7(d) are respectively the constellation diagrams of the cluster center points corresponding to the agglomerative hierarchical clustering algorithm under their respective systems. In Figure 6 and Figure 7, L=100,

m=1.5.

在一些示例中，如图6和图7所示，通过比较图6(b)和图6(a)或图7(b)和图7(a)可以发现由于相位噪声

存在，使得所有星座点均以0.1π旋转，多个样本点均沿对应星座点以相同角度旋转。由图6(c)和图6(d)、图7(c)和图7(d)可知，由于两个星座点之间的距离足够大，K均值聚类算法和凝聚层次聚类算法都可以找到对应于旋转星座点的正确的星系团中心，即可以使各个聚类中心点获得正确的目标星座点能够使接收端30获得较为准确的信息，这是聚类映射模型360工作良好的前提条件。随着调制阶数的增加，两个星座点之间的距离变小，使得不同的聚类算法产生不同的聚类中心，可能导致一些聚类算法效果不佳。例如，如图6(c)所示，K均值聚类算法生成了一些明显错误的聚类中心点。然而，如图6(d)所示，凝聚层次聚类算法工作良好。故可以寻找一种在不同条件下自适应选择合适聚类算法的方法(即加权集成聚类算法)。 In some examples, as shown in Figure 6 and Figure 7, by comparing Figure 6 (b) and Figure 6 (a) or Figure 7 (b) and Figure 7 (a) can be found due to phase noise

Existence, so that all constellation points are rotated at 0.1π, and multiple sample points are rotated at the same angle along the corresponding constellation points. From Figure 6(c) and Figure 6(d), Figure 7(c) and Figure 7(d), it can be seen that since the distance between the two constellation points is large enough, both the K-means clustering algorithm and the agglomerative hierarchical clustering algorithm The correct galaxy cluster center corresponding to the rotating constellation point can be found, that is, the correct target constellation point can be obtained for each cluster center point, so that the receiving end 30 can obtain more accurate information, which is a prerequisite for the cluster mapping model 360 to work well condition. As the modulation order increases, the distance between the two constellation points becomes smaller, which makes different clustering algorithms produce different clustering centers, which may cause some clustering algorithms to perform poorly. For example, as shown in Figure 6(c), the K-means clustering algorithm has generated some obviously wrong cluster center points. However, as shown in Figure 6(d), the agglomerative hierarchical clustering algorithm works well. Therefore, we can find a method for adaptively selecting the appropriate clustering algorithm under different conditions (ie, weighted ensemble clustering algorithm).

在一些示例中，基于聚类模型340和增益基带信号对多个样本点进行聚类划分，由于每个聚类对应的样本点的数量是未知的，不同的聚类可以接收不同数量的样本点，在本实施方式中，采用解调误差概率和平均归一化互信息检测聚类算法的性能。其中，平均归一化互信息可以检测聚类样本集(即划分的多个聚类)与参考星座点集之间的相似性，如上所述，C _i表示为第i个聚类对应的聚类中心点，这里令C _i特指对应的第i个聚类，即令C _i表示为第i个聚类样本集，G _j表示为第j个地面真实聚类的样本集(即参考星座点集)。则C _i相对于G _j的平均归一化互信息可以满足：

其中，K表示为聚类的数量，N表示多个样本点的数量，N _C,i表示为第i个聚类样本集对应的样本点的数量，N _G,j表示为第j个参考星座点集对应的样本点的数量，N _ij表示为第i个聚类样本集和第j个参考星座点集共享的接收到的样本点的数量。 In some examples, multiple sample points are clustered based on the clustering model 340 and the gain baseband signal. Since the number of sample points corresponding to each cluster is unknown, different clusters can receive different numbers of sample points. In this embodiment, the demodulation error probability and the average normalized mutual information are used to detect the performance of the clustering algorithm. Among them, the average normalized mutual information can detect the similarity between the cluster sample set (ie, the divided clusters) and the reference constellation point set. As mentioned above, C _i is the cluster corresponding to the i-th cluster. class center point, so that here especially C _i corresponding to the i-th cluster, and even if C _i represents the i th sample set clusters, G _j represents the j-th sample set as the ground truth clusters (i.e. the reference constellation points set). Then the average normalized mutual information of _{C i} relative to G _{j can satisfy:}

Among them, K represents the number of clusters, N represents the number of multiple sample points, N _C,i represents the number of sample points corresponding to the i-th cluster sample set, and N _G,j represents the j-th reference constellation The number of sample points corresponding to the point set, N _{ij is} expressed as the number of received sample points shared by the i-th cluster sample set and the j-th reference constellation point set.

在一些示例中，在理想情况下，平均归一化互信息的值可以等于1，即所有的样本点均被正确识别，在不理想的情况下例如低的接收信噪比，可以使平均归一化互信息的值降低。在一些示例中，由于平均归一化互信息仅考虑集群性能，在本实施方式中可以将平均归一化互信息作为一个中间指标，可以将解调误差概率作为检测聚类算法的最终的性能指标。In some examples, under ideal conditions, the value of the average normalized mutual information can be equal to 1, that is, all sample points are correctly identified. Under unsatisfactory conditions, such as a low received signal-to-noise ratio, the average can be The value of unified mutual information decreases. In some examples, since the average normalized mutual information only considers cluster performance, in this embodiment, the average normalized mutual information can be used as an intermediate index, and the demodulation error probability can be used as the final performance of the detection clustering algorithm. index.

在一些示例中，如图8至图13所示，对平均归一化互信息或解调误差概率在不同***条件下进行分析，其中，A为采用加权集成聚类算法的情况，B为采用K均值聚类算法的情况，C为采用K均值(绝对值距离)聚类算法的情况，D为采用K均值(夹角余弦)聚类算法的情况，E为采用K中心点聚类算法的情况，F为采用K中心点(绝对值距离)聚类算法的情况，G为采用K中心点(夹角余弦)聚类算法的情况，H为采用凝聚层次聚类算法的情况，I为采用凝聚层次聚类算法(平均)的情况，J为采用凝聚层次聚类算法(加权)的情况，在图9、图11和图13中。K为普通方案的情况。In some examples, as shown in Figure 8 to Figure 13, the average normalized mutual information or demodulation error probability is analyzed under different system conditions, where A is the use of weighted ensemble clustering algorithm, and B is the use of In the case of K-means clustering algorithm, C is the case of using K-means (absolute value distance) clustering algorithm, D is the case of using K-means (angle cosine) clustering algorithm, and E is the case of using K center point clustering algorithm Case, F is the case of using the K center point (absolute value distance) clustering algorithm, G is the case of using the K center point (angle cosine) clustering algorithm, H is the case of using agglomerative hierarchical clustering algorithm, I is the case of using In the case of the agglomerated hierarchical clustering algorithm (average), J is the case of using the agglomerated hierarchical clustering algorithm (weighted), in Figure 9, Figure 11 and Figure 13. K is the case of the ordinary plan.

图8是示出了本公开的示例所涉及的固定相位噪声下平均归一化互信息与正确率随接收信噪比变化的波形图。图9是示出了本公开的示例所涉及的固定相位噪声下平均误码率随接收信噪比变化的波形图。其中，如图8和图9所示，均采用正交相移键控调制***，L＝100，m＝1.5，

FIG. 8 is a waveform diagram showing the variation of the average normalized mutual information and the accuracy rate with the received signal-to-noise ratio under fixed phase noise involved in the example of the present disclosure. FIG. 9 is a waveform diagram showing the variation of the average bit error rate with the received signal-to-noise ratio under fixed phase noise involved in the example of the present disclosure. Among them, as shown in Figure 8 and Figure 9, the quadrature phase shift keying modulation system is adopted, L=100, m=1.5,

在一些示例中，如图8所示，图8(a)示出了平均归一化互信息随接收信噪比变化的波形图，图8(b)示出了正确率随接收信噪比变化的波形图。由图8可知，随着接收信噪比的增加，平均归一化互信息和正确率的值明显提高，即聚类性能有所提高。图8示出了10种聚类算法的平均归一化互信息随接收信噪比变化波形图，其中，K均值(绝对值距离)聚类算法对高接收信噪比区域的聚类性能最差，凝聚层次聚类算法(加权)对低接收信噪比区域的聚类性能最差。由图8可知，虽然其他基聚类算法的聚类性能相似，但加权集成聚类算法是其中的最佳选择。其中，基聚类算法为曲线B～曲线J对应的聚类算法。In some examples, as shown in Fig. 8, Fig. 8(a) shows a waveform diagram of the average normalized mutual information as a function of the received signal-to-noise ratio, and Fig. 8(b) shows the correctness rate as a function of the received signal-to-noise ratio Waveform graph of change. It can be seen from Fig. 8 that as the received signal-to-noise ratio increases, the values of the average normalized mutual information and the correct rate increase significantly, that is, the clustering performance is improved. Figure 8 shows the average normalized mutual information of 10 clustering algorithms with the change of the received signal-to-noise ratio. Among them, the K-means (absolute value distance) clustering algorithm has the best clustering performance for areas with high received signal-to-noise ratios. Poor, the clustering performance of the agglomerated hierarchical clustering algorithm (weighted) is the worst in the low-reception SNR area. It can be seen from Figure 8 that although the clustering performance of other base clustering algorithms is similar, the weighted ensemble clustering algorithm is the best choice among them. Among them, the base clustering algorithm is the clustering algorithm corresponding to curve B to curve J.

在一些示例中，如图9所示，图9(a)示出了解调的平均误码率随接收信噪比变化的波形图，图9(b)示出了解调和解码的平均误码率随接收信噪比变化的波形图。由图9可知，随着接收信噪比的增加，两种情况下的平均误码率的值明显减小，即对应的最终性能得到了提高(即接收端30的解调和解码性能得到了提高)。由图8和图9可知，任意两种聚类算法之间的平均误码率的差距明显大于两者之间的平均归一化互信息的差距，可知***条件的改变对平均误码率的影响更大。由图9(a)可知，加权集成聚类算法对应的解调性能最好，K均值(绝对值距离)聚类算法的解调性能较差。并且在较高的接收信噪比情况下，使用K均值(绝对值距离)聚类算法的最终性能比普通方案(即正常处理信号，例如，采用图1中公开的经典无线通信***)的更差，因为在K均值(绝对值距离)聚类算法中出现了一些过度的映射。由图9(b)可知，采用加权集成聚类算法时解调和解码的平均误码率分别优于普通方案，例如，与普通方案的平均误码率为10 ^-3相比，加权集成聚类算法提高了约10dB的解调性能，提高了约8dB的解码性能。 In some examples, as shown in Fig. 9, Fig. 9(a) shows a waveform diagram of the demodulation average bit error rate varying with the received signal-to-noise ratio, and Fig. 9(b) shows the average bit error rate of demodulation and decoding. Waveform graph that varies with the received signal-to-noise ratio. It can be seen from Figure 9 that as the received signal-to-noise ratio increases, the value of the average bit error rate in the two cases is significantly reduced, that is, the corresponding final performance is improved (that is, the demodulation and decoding performance of the receiving end 30 is improved. improve). It can be seen from Figure 8 and Figure 9 that the average bit error rate gap between any two clustering algorithms is significantly larger than the average normalized mutual information gap between the two. It can be seen that changes in system conditions have an effect on the average bit error rate. The impact is greater. It can be seen from Figure 9(a) that the demodulation performance of the weighted ensemble clustering algorithm is the best, and the demodulation performance of the K-means (absolute value distance) clustering algorithm is poor. And in the case of a higher received signal-to-noise ratio, the final performance of the K-means (absolute value distance) clustering algorithm is better than that of the ordinary scheme (that is, the normal signal processing, for example, using the classic wireless communication system disclosed in Figure 1) Poor, because there are some excessive mappings in the K-means (absolute distance) clustering algorithm. It can be seen from Figure 9(b) that the average bit error rate of demodulation and decoding is better than that of the ordinary scheme when the weighted ensemble clustering algorithm is used. For example, compared with the average bit error rate of the ordinary scheme of 10 ^-3 , the weighted ensemble clustering algorithm The similar algorithm improves the demodulation performance by about 10dB and the decoding performance by about 8dB.

图10是示出了本公开的示例所涉及的固定相位噪声下平均归一化互信息与正确率随相位隔移变化的波形图。图11是示出了本公开的示例所涉及的固定相位噪声下平均误码率随相位隔移变化的波形图。其中，如图10和图11所示，均采用正交相移键控调制***，L＝100，m＝1.5，接收信噪比为20dB，即

FIG. 10 is a waveform diagram showing the variation of the average normalized mutual information and the accuracy rate with the phase shift under the fixed phase noise involved in the example of the present disclosure. FIG. 11 is a waveform diagram showing the variation of the average bit error rate with the phase shift under the fixed phase noise involved in the example of the present disclosure. Among them, as shown in Figure 10 and Figure 11, the quadrature phase shift keying modulation system is adopted, L=100, m=1.5, and the received signal-to-noise ratio is 20dB, that is

在一些示例中，如图10所示，图10(a)示出了平均归一化互信息随相位隔移变化的波形图，图10(b)示出了正确率随相位隔移变化的波形图中。由图10可知，加权集成聚类算法对应的性能是最好的，而K均值(绝对值距离)聚类算法对应的性能是最差的，由此可以看出单个聚类算法(例如，使用一个基聚类算法)的不稳定性。由图10可知，除了K均值(绝对值距离)聚类算法，其他聚类算法对应的平均归一化互信息和正确率的值几乎与相位隔移无关，由此能够突出本公开的加权集成聚类算法的鲁棒性。In some examples, as shown in Fig. 10, Fig. 10(a) shows a waveform diagram of the average normalized mutual information changing with the phase shift, and Fig. 10(b) shows the correct rate changing with the phase shift. Waveform diagram. It can be seen from Figure 10 that the performance of the weighted ensemble clustering algorithm is the best, while the performance of the K-means (absolute distance) clustering algorithm is the worst. It can be seen that a single clustering algorithm (for example, using A base clustering algorithm) instability. It can be seen from Figure 10 that in addition to the K-means (absolute value distance) clustering algorithm, the average normalized mutual information and correctness values corresponding to other clustering algorithms are almost independent of the phase shift, which can highlight the weighted integration of the present disclosure. Robustness of the clustering algorithm.

在一些示例中，如图11所示，图11(a)示出了解调的平均误码率随相位隔移变化的波形图，图11(b)示出了解调和解码的平均误码率随相位隔移变化的波形图。图11示出了10种聚类算法的平均误码率随接收信噪比变化波形图，由图11可知，随着相位噪声的增加，所有聚类算法的平均误码率，包括普通方案的平均误码率的值都在增加。对于较大的相位隔移，各个聚类算法和普通方案的平均误码率的值收敛到最大值，例如，当

时，最大的平均误码率值是0.5。 In some examples, as shown in Fig. 11, Fig. 11(a) shows a waveform diagram of the demodulation average bit error rate varying with the phase shift, and Fig. 11(b) shows the demodulation and decoding average bit error rate varying with the phase shift. Waveform diagram of phase shift change. Figure 11 shows the average bit error rate of 10 clustering algorithms as a function of the received signal-to-noise ratio. It can be seen from Figure 11 that with the increase of phase noise, the average bit error rate of all clustering algorithms, including those of the common scheme The value of the average bit error rate is increasing. For larger phase shifts, the average bit error rate of each clustering algorithm and common scheme converges to the maximum value, for example, when

When, the maximum average bit error rate value is 0.5.

在一些示例中，由图11可知，例如，当

时，一些基聚类算法不如普通方案，而加权集成聚类算法仍能保持较好的性能。对于一个较大的相位噪声，由于旋转后的星座点更接近于决策区域的边缘(如图4所示)，且会出现一些过度的映射，所有的基聚类算法和加权集成聚类算法都比普通方案差。然而，较大的相位噪声在实际中很少发生，因为其很容易被接收端30的校准电路捕获，并且可以被抑制到一个小的相位噪声。对比图10(a)和(b)可以看出，在较小的相位隔移下，加权集成聚类算法在解调和解码方面的平均误码率分别优于普通方案。此外，对于一些相位隔移，例如

加权集成聚类算法的解码性能比普通方案的解码性能好。 In some examples, it can be seen from Figure 11, for example, when

However, some basic clustering algorithms are inferior to common schemes, while weighted ensemble clustering algorithms can still maintain better performance. For a larger phase noise, because the rotated constellation points are closer to the edge of the decision area (as shown in Figure 4), and some excessive mapping will occur, all base clustering algorithms and weighted ensemble clustering algorithms are It is worse than the ordinary plan. However, a large phase noise rarely occurs in practice because it is easily captured by the calibration circuit of the receiving end 30 and can be suppressed to a small phase noise. Comparing Figure 10 (a) and (b), it can be seen that under a smaller phase shift, the average bit error rate of the weighted ensemble clustering algorithm in demodulation and decoding is better than that of the ordinary scheme. In addition, for some phase shifts, such as

The decoding performance of the weighted ensemble clustering algorithm is better than that of the common scheme.

在一些示例中，分析了帧长度L、Nakagami信道参数m可以对平均归一化互信息、正确率和平均误码率的影响，分别如表1、表2所示。其中，对于解调误差概率提出了一个新的度量来说明本实施方式的加权集成聚类算法所提供的相对改进比，满足：

其中，PDE _Normal表示为普通方案的解调误差概率，PDE _Ensemble表示为加权集成聚类算法的解调误差概率。其中，表1和表2均采用正交相移键控调制***，接收信噪比为10dB，相位噪声

In some examples, the influence of the frame length L and the Nakagami channel parameter m on the average normalized mutual information, the correct rate and the average bit error rate is analyzed, as shown in Table 1 and Table 2, respectively. Among them, a new metric is proposed for the demodulation error probability to illustrate the relative improvement ratio provided by the weighted ensemble clustering algorithm of this embodiment, which satisfies:

Among them, PDE _Normal represents the demodulation error probability of the ordinary scheme, and PDE _Ensemble represents the demodulation error probability of the weighted ensemble clustering algorithm. Among them, Table 1 and Table 2 both use a quadrature phase shift keying modulation system, the received signal-to-noise ratio is 10dB, and the phase noise

表1Table 1

在一些示例中，如表1所示，表1示出了帧长度L对平均归一化互信息、正确率和平均误码率的影响，其中，m＝1.5，解调的平均误码率和解码的平均误码率对应的相对改进比的获取可以类比式(25)。从表1可以看出，不同的帧长度L对平均归一化互信息和正确率的影响并不敏感，只是略有波动。从表1可以看出，随着帧长度L的增加，解调的平均误码率和解码的平均误码率降低，即其对应的性能有所提高，但是平均误码率对应的性能提升速度逐渐变慢甚至下降，因为接收的样本点的数量越多，聚类性能越差(即聚类精度降低)。例如，当帧长度L的值从75更改为150时，解调的平均误码率和解码的平均误码率的相对改进比分别从65.60％增加到72.81％以及从45.41％增加到59.44％。通过比较解调的平均误码率和解码的平均误码率对应的性能提高，当帧长度L值太小时，本公开的加权集成聚类算法对译码性能的提高率变得很小，因为解调误差超出了所采用的信道编码100的纠错能力。In some examples, as shown in Table 1, Table 1 shows the influence of the frame length L on the average normalized mutual information, the correct rate and the average bit error rate, where m=1.5, the average bit error rate of the demodulation The relative improvement ratio corresponding to the average bit error rate of decoding can be obtained by analogy to equation (25). It can be seen from Table 1 that different frame lengths L are not sensitive to the influence of the average normalized mutual information and accuracy, but slightly fluctuate. It can be seen from Table 1 that as the frame length L increases, the average bit error rate of demodulation and the average bit error rate of decoding decrease, that is, the corresponding performance is improved, but the average bit error rate corresponds to the performance improvement speed Gradually slow down or even decrease, because the more the number of sample points received, the worse the clustering performance (that is, the lower the clustering accuracy). For example, when the value of the frame length L is changed from 75 to 150, the relative improvement ratios of the demodulated average bit error rate and the decoded average bit error rate increase from 65.60% to 72.81% and from 45.41% to 59.44%, respectively. By comparing the performance improvement corresponding to the average bit error rate of demodulation and the average bit error rate of decoding, when the value of the frame length L is too small, the improvement rate of the decoding performance of the weighted ensemble clustering algorithm of the present disclosure becomes very small, because The demodulation error exceeds the error correction capability of the channel code 100 used.

表2Table 2

在一些示例中，如表2所示，表2示出了Nakagami信道参数m对平均归一化互信息、正确率和平均误码率的影响，其中，L＝100。从表2可以看出，随着m的值的增加，平均归一化互信息和正确率都在增加，说明信道衰落较小的无线信道20显著提高了聚类性能。此外，随着m的值的增加，解调的平均误码率和解码的平均误码率对应的性能都有所提高，表明信道衰落也会影响最终的性能。In some examples, as shown in Table 2, Table 2 shows the influence of the Nakagami channel parameter m on the average normalized mutual information, the correct rate, and the average bit error rate, where L=100. It can be seen from Table 2 that as the value of m increases, the average normalized mutual information and the accuracy rate both increase, indicating that the wireless channel 20 with smaller channel fading significantly improves the clustering performance. In addition, as the value of m increases, the performance corresponding to the average bit error rate of demodulation and the average bit error rate of decoding is improved, indicating that channel fading will also affect the final performance.

如上所述，由表1和表2可知，本实施方式的加权集成聚类算法可以为最优的选择。As mentioned above, it can be seen from Table 1 and Table 2 that the weighted ensemble clustering algorithm of this embodiment can be the optimal choice.

图12是示出了本公开的示例所涉及的随机相位噪声下平均归一化互信息随接收信噪比变化的波形图。图13是示出了本公开的示例所涉及的随机相位噪声下平均误码率随接收信噪比变化的波形图。其中，如图12和图13所示，均采用正交相移键控调制***，χ＝0.1，B _LT _b＝2，ρ＝1-10 ^-3，L＝300，m＝1.5。 FIG. 12 is a waveform diagram showing the variation of the average normalized mutual information with the received signal-to-noise ratio under random phase noise involved in the example of the present disclosure. FIG. 13 is a waveform diagram showing the variation of the average bit error rate with the received signal-to-noise ratio under random phase noise involved in the example of the present disclosure. Among them, as shown in FIG. 12 and FIG. 13, both adopt a quadrature phase shift keying modulation system, χ=0.1, B _L T _b =2, ρ=1-10 ^-3 , L=300, m=1.5.

在一些示例中，如图12所示，图12(a)为不完美的锁相环电路导致的随机相位噪声，其对应的概率密度函数可以由式(2)获得，图12(b)为不完美的信道估计导致的随机相位噪声，其对应的概率密度函数可以由式(3)获得。如图12和图8所示，图12的平均归一化互信息与图8的变化几乎相同。因为平均归一化互信息的值几乎独立于固定相位噪声，但依赖于接收信噪比。In some examples, as shown in Figure 12, Figure 12(a) shows the random phase noise caused by an imperfect phase-locked loop circuit. The corresponding probability density function can be obtained from equation (2). Figure 12(b) is The random phase noise caused by imperfect channel estimation, its corresponding probability density function can be obtained by formula (3). As shown in FIG. 12 and FIG. 8, the average normalized mutual information of FIG. 12 is almost the same as that of FIG. 8. Because the value of the average normalized mutual information is almost independent of the fixed phase noise, but depends on the received signal-to-noise ratio.

在一些示例中，如图13所示，图13(a)为不完美的锁相环电路导致的随机相位噪声，其对应的概率密度函数可以由式(2)获得，图13(b)为不完美的信道估计导致的随机相位噪声，其对应的概率密度函数可以由式(3)获得。如图13所示，将大的相位噪声和小的相位噪声混合在一起平均求得到平均误码率，当小相位噪声占主导地位时，所提出的相位噪声补偿方法仍显示出其优越性，如图13(a)所示。通过对比图13(a)和图9(b)的结果可以看出，由于相位噪声是随机的而不是固定的，本公开的相位噪声补偿方法在普通方案之间的改进差距变得很小，解调性能接近于普通方案的译码性能。然而，当大相位噪声占主导地位时，本公开的相位噪声补偿方法和普通方案都会出现位误差下限。In some examples, as shown in Figure 13, Figure 13(a) shows the random phase noise caused by an imperfect phase-locked loop circuit. The corresponding probability density function can be obtained from equation (2). Figure 13(b) is The random phase noise caused by imperfect channel estimation, its corresponding probability density function can be obtained by formula (3). As shown in Figure 13, the average bit error rate is obtained by mixing large phase noise and small phase noise together. When small phase noise is dominant, the proposed phase noise compensation method still shows its superiority. As shown in Figure 13(a). By comparing the results of Fig. 13(a) and Fig. 9(b), it can be seen that since the phase noise is random rather than fixed, the improvement gap between the ordinary schemes of the phase noise compensation method of the present disclosure becomes very small. The demodulation performance is close to the decoding performance of the common scheme. However, when large phase noise is dominant, both the phase noise compensation method of the present disclosure and the general scheme will have a lower limit of bit error.

图14是示出了本公开的示例所涉及的基于加权集成聚类的无线通信***的相位噪声补偿***框图。FIG. 14 is a block diagram showing a phase noise compensation system of a wireless communication system based on weighted ensemble clustering involved in an example of the present disclosure.

本公开涉及一种基于加权集成聚类的无线通信***的相位噪声补偿***1。相位噪声补偿***1包括发射装置50和接收装置60。在本公开中，相位噪声补偿***1中的发射装置50可以类比上述相位噪声补偿方法中的发射端10，接收装置60可以类比上述相位噪声补偿方法中的接收端30。The present disclosure relates to a phase noise compensation system 1 of a wireless communication system based on weighted ensemble clustering. The phase noise compensation system 1 includes a transmitting device 50 and a receiving device 60. In the present disclosure, the transmitting device 50 in the phase noise compensation system 1 can be analogous to the transmitting end 10 in the aforementioned phase noise compensation method, and the receiving device 60 can be analogous to the receiving end 30 in the aforementioned phase noise compensation method.

在一些示例中，如图14所示，相位噪声补偿***1可以包括发射装置50和接收装置60。在一些示例中，发射装置50可以向接收装置60发射信号，并被接收装置60接收。In some examples, as shown in FIG. 14, the phase noise compensation system 1 may include a transmitting device 50 and a receiving device 60. In some examples, the transmitting device 50 may transmit a signal to the receiving device 60 and be received by the receiving device 60.

在一些示例中，发射装置50可以基于信道编码、基带调制和射频调制器调制向无线信道发射载波信号，载波信号经过无线信道获得接收信号。发射装置50可以向接收装置60发送信息。具体过程可以参见上述相位噪声补偿方法中的步骤S10。In some examples, the transmitting device 50 may transmit a carrier signal to a wireless channel based on channel coding, baseband modulation, and radio frequency modulator modulation, and the carrier signal obtains a received signal through the wireless channel. The transmitting device 50 can send information to the receiving device 60. For the specific process, refer to step S10 in the above-mentioned phase noise compensation method.

在一些示例中，接收装置60可以接收接收信号，基于射频解调和锁相环电路从接收信号中获得基带信号，基于基带信号和自动增益控制获得增益基带信号。接收装置60能够接收接收信号并进行处理。具体过程可以参见上述相位噪声补偿方法中的步骤S20。In some examples, the receiving device 60 may receive the received signal, obtain a baseband signal from the received signal based on radio frequency demodulation and a phase-locked loop circuit, and obtain a gain baseband signal based on the baseband signal and automatic gain control. The receiving device 60 can receive and process the received signal. For the specific process, refer to step S20 in the above-mentioned phase noise compensation method.

在一些示例中，接收装置60可以基于聚类模型与增益基带信号获得各个标准星座点和与增益基带信号对应的星座图中的中多个样本点对应的多个聚类以及与各个聚类一一对应的多个聚类中心点。其中，聚类模型可以为加权集成聚类算法，加权集成聚类算法可以基于多个不同的聚类算法和增益基带信号确定。由此，能够获得与增益基带信号对应的星座图中的多个样本点对应的多个聚类、与各个聚类对应的聚类中心点以及各个标准星座点。具体过程可以参见上述相位噪声补偿方法中的步骤S30。In some examples, the receiving device 60 may obtain each standard constellation point and multiple clusters corresponding to multiple sample points in the constellation diagram corresponding to the gain baseband signal based on the clustering model and the gain baseband signal, and a number of clusters corresponding to each cluster. One corresponding multiple cluster center points. Among them, the clustering model may be a weighted ensemble clustering algorithm, and the weighted ensemble clustering algorithm may be determined based on multiple different clustering algorithms and gain baseband signals. In this way, a plurality of clusters corresponding to a plurality of sample points in a constellation diagram corresponding to the gain baseband signal, a cluster center point corresponding to each cluster, and each standard constellation point can be obtained. For the specific process, refer to step S30 in the above-mentioned phase noise compensation method.

在一些示例中，接收装置60可以基于距离计算模型获得任一聚类中心点与各个标准星座点之间的范数距离，进而从多个标准星座点中选出与该聚类中心点具有最小范数距离的目标星座点。由此，能够获得与各个聚类中心点对应的目标星座点，能够获得各个聚类对应的目标星座点。具体过程可以参见上述相位噪声补偿方法中的步骤S40。In some examples, the receiving device 60 may obtain the norm distance between any cluster center point and each standard constellation point based on the distance calculation model, and then select from a plurality of standard constellation points with the smallest distance from the cluster center point. The target constellation point of the norm distance. Thus, the target constellation point corresponding to each cluster center point can be obtained, and the target constellation point corresponding to each cluster can be obtained. For the specific process, refer to step S40 in the above-mentioned phase noise compensation method.

在一些示例中，接收装置60可以基于聚类映射模型将各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，进而获得目标接收信号，基于基带解调、信道解码和目标接收信号获得目标信号。由此接收装置60能够较为准确地获得发射装置50发送的信息。具体过程可以参见上述相位噪声补偿方法中的步骤S50。In some examples, the receiving device 60 may replace the coordinates of the sample points corresponding to each cluster with the coordinates of the target constellation points corresponding to the cluster based on the cluster mapping model to achieve phase noise compensation, and then obtain the target received signal based on Baseband demodulation, channel decoding and target reception signal to obtain the target signal. Therefore, the receiving device 60 can obtain the information sent by the transmitting device 50 more accurately. For the specific process, refer to step S50 in the above-mentioned phase noise compensation method.

如上所述，在本公开中，发射装置50基于信道编码、基带调制和射频调制向无线信道发射载波信号，载波信号经过无线信道获得接收信号，接收装置60接收接收信号并从中获得基带信号，基于基带信号和自动增益控制获得增益基带信号，进而基于聚类模型获得各个标准星座点和与增益基带信号对应的星座图中的多个样本点对应的多个聚类以及与各个聚类一一对应的多个聚类中心点，基于距离计算模型获得任一聚类中心点与各个标准星座点之间的范数距离，并将与该聚类中心点的最小范数距离对应的标准星座点标记为目标星座点，进而基于聚类映射模型将各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，进而获得目标接收信号，接收装置60基于基带解调、信道解码和目标接收信号获得目标信号。由此，接收装置60能够对产生的相位噪声进行补偿，能够较为准确地获得发射装置50发送的信息。As described above, in the present disclosure, the transmitting device 50 transmits a carrier signal to a wireless channel based on channel coding, baseband modulation, and radio frequency modulation, the carrier signal obtains a received signal through the wireless channel, and the receiving device 60 receives the received signal and obtains the baseband signal from it, based on The baseband signal and automatic gain control obtain the gain baseband signal, and then obtain each standard constellation point and multiple clusters corresponding to multiple sample points in the constellation diagram corresponding to the gain baseband signal based on the clustering model, and one-to-one correspondence with each cluster Based on the distance calculation model, obtain the norm distance between any cluster center point and each standard constellation point, and mark the standard constellation point corresponding to the minimum norm distance of the cluster center point Is the target constellation point, and then based on the cluster mapping model, the coordinates of the sample points corresponding to each cluster are replaced with the coordinates of the target constellation point corresponding to the cluster to achieve phase noise compensation, thereby obtaining the target received signal, the receiving device 60 is based on Baseband demodulation, channel decoding and target reception signal to obtain the target signal. As a result, the receiving device 60 can compensate for the generated phase noise, and the information sent by the transmitting device 50 can be obtained more accurately.

虽然以上结合附图和实施例对本公开进行了具体说明，但是可以理解，上述说明不以任何形式限制本公开。本领域技术人员在不偏离本公开的实质精神和范围的情况下可以根据需要对本公开进行变形和变化，这些变形和变化均落入本公开的范围内。Although the present disclosure has been specifically described above with reference to the drawings and embodiments, it can be understood that the foregoing description does not limit the present disclosure in any form. Those skilled in the art can make modifications and changes to the present disclosure as needed without departing from the essential spirit and scope of the present disclosure, and these modifications and changes fall within the scope of the present disclosure.

Claims

一种基于集成聚类的无线通信***的相位噪声补偿方法，是具有发射端和接收端的无线通信***的相位噪声补偿方法，其特征在于，A phase noise compensation method for a wireless communication system based on ensemble clustering is a phase noise compensation method for a wireless communication system having a transmitting end and a receiving end, and is characterized in that:

包括：include:

所述发射端基于信道编码、基带调制和射频调制向无线信道发射载波信号，所述载波信号经过所述无线信道获得接收信号；The transmitting end transmits a carrier signal to a wireless channel based on channel coding, baseband modulation, and radio frequency modulation, and the carrier signal obtains a received signal through the wireless channel;

所述接收端接收所述接收信号，基于射频解调和锁相环电路从所述接收信号中获得基带信号，基于所述基带信号和自动增益控制获得增益基带信号，所述接收端基于聚类模型与所述增益基带信号获得多个标准星座点和与所述增益基带信号对应的多个样本点对应的多个聚类以及与各个聚类一一对应的多个聚类中心点，进而基于距离计算模型获得任一聚类中心点与各个标准星座点之间的范数距离，进而从所述多个标准星座点中选出与该聚类中心点具有最小范数距离的目标星座点，基于聚类映射模型将所述各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，进而获得目标接收信号，基于基带解调、信道解码和所述目标接收信号获得目标信号，The receiving end receives the received signal, obtains a baseband signal from the received signal based on radio frequency demodulation and a phase-locked loop circuit, obtains a gain baseband signal based on the baseband signal and automatic gain control, and the receiving end is based on clustering The model and the gain baseband signal obtain multiple standard constellation points, multiple clusters corresponding to multiple sample points corresponding to the gain baseband signal, and multiple cluster center points one-to-one corresponding to each cluster, and then based on The distance calculation model obtains the norm distance between any cluster center point and each standard constellation point, and then selects the target constellation point with the smallest norm distance from the cluster center point from the multiple standard constellation points, Based on the cluster mapping model, the coordinates of the sample points corresponding to each cluster are replaced with the coordinates of the target constellation points corresponding to the cluster to achieve phase noise compensation, and then to obtain the target received signal, based on baseband demodulation, channel decoding and The target receiving signal obtains the target signal,

其中，所述聚类模型为加权集成聚类算法，基于多个不同的聚类算法和所述增益基带信号获得与各个聚类算法对应的聚类结果，基于各个聚类结果获得所述各个聚类结果对应的共聚类指示矩阵，基于所述聚类结果和所述共聚类指示矩阵获得集合矩阵，基于所述集合矩阵和预设参数获得所述加权集成聚类算法。Wherein, the clustering model is a weighted ensemble clustering algorithm, the clustering results corresponding to each clustering algorithm are obtained based on multiple different clustering algorithms and the gain baseband signal, and the clustering results are obtained based on each clustering result. A co-clustering indicator matrix corresponding to the class result is obtained, based on the clustering result and the co-clustering indicator matrix, a set matrix is obtained, and the weighted ensemble clustering algorithm is obtained based on the set matrix and preset parameters.
根据权利要求1所述的相位噪声补偿方法，其特征在于：The phase noise compensation method according to claim 1, wherein:

所述无线通信***的调制阶数被所述接收端已知，所述多个聚类的数量与所述调制阶数相同。The modulation order of the wireless communication system is known by the receiving end, and the number of the plurality of clusters is the same as the modulation order.
根据权利要求1所述的相位噪声补偿方法，其特征在于：The phase noise compensation method according to claim 1, wherein:

所述目标接收信号由各个聚类中心点对应的坐标均转换为各自对应的目标星座点的坐标后获得。The target received signal is obtained by converting the coordinates corresponding to each cluster center point to the coordinates of the corresponding target constellation points.
根据权利要求1所述的相位噪声补偿方法，其特征在于：The phase noise compensation method according to claim 1, wherein:

第i个聚类中心点与第j个标准星座点的范数距离满足：d _ij＝||C _i-S _j|| ²,i＝1,...,M,j＝1,...,M，其中，C _i为第i个聚类中心点，S _j为第j个标准星座点，M为多进制频移键控***的调制阶数。 The norm distance between the i-th cluster center point and the j-th standard constellation point satisfies: d _ij =||C _i -S _j || ² ,i=1,...,M,j=1,... ., M, where C _i is the i-th clustering center point, S _j is the j-th standard constellation point, and M is the modulation order of the multi-ary frequency shift keying system.
根据权利要求1所述的相位噪声补偿方法，其特征在于：The phase noise compensation method according to claim 1, wherein:

所述多个不同的聚类算法包括K均值聚类算法、K中心点聚类算法和凝聚层次聚类算法。The multiple different clustering algorithms include K-means clustering algorithm, K-center point clustering algorithm, and agglomerated hierarchical clustering algorithm.
一种基于集成聚类的无线通信***的相位噪声补偿***，是具有发射装置和接收装置的无线通信***的相位噪声补偿***，其特征在于，A phase noise compensation system of a wireless communication system based on ensemble clustering is a phase noise compensation system of a wireless communication system having a transmitting device and a receiving device, and is characterized in that:

包括：include:

所述发射装置基于信道编码、基带调制和射频调制器调制向无线信道发射载波信号，所述载波信号经过所述无线信道获得接收信号；The transmitting device transmits a carrier signal to a wireless channel based on channel coding, baseband modulation, and radio frequency modulator modulation, and the carrier signal obtains a received signal through the wireless channel;

所述接收装置接收所述接收信号，基于射频解调和锁相环电路从所述接收信号中获得基带信号，基于所述基带信号和自动增益控制获得增益基带信号，所述接收装置基于聚类模型与所述增益基带信号获得多个标准星座点和与所述增益基带信号对应的多个样本点对应的多个聚类以及与各个聚类一一对应的多个聚类中心点，进而基于距离计算模型获得任一聚类中心点与各个标准星座点之间的范数距离，进而从所述多个标准星座点中选出与该聚类中心点具有最小范数距离的目标星座点，基于聚类映射模型将所述各个聚类对应的样本点的坐标替换到与该聚类对应的目标星座点的坐标来实现相位噪声补偿，进而获得目标接收信号，基于基带解调、信道解码和所述目标接收信号获得目标信号，其中，所述聚类模型为加权集成聚类算法，基于多个不同的聚类算法和所述增益基带信号获得与各个聚类算法对应的聚类结果，基于各个聚类结果获得所述各个聚类结果对应的共聚类指示矩阵，基于所述聚类结果和所述共聚类指示矩阵获得集合矩阵，进而获得所述加权集成聚类算法。The receiving device receives the received signal, obtains a baseband signal from the received signal based on a radio frequency demodulation and phase-locked loop circuit, and obtains a gain baseband signal based on the baseband signal and automatic gain control, and the receiving device is based on clustering The model and the gain baseband signal obtain multiple standard constellation points, multiple clusters corresponding to multiple sample points corresponding to the gain baseband signal, and multiple cluster center points one-to-one corresponding to each cluster, and then based on The distance calculation model obtains the norm distance between any cluster center point and each standard constellation point, and then selects the target constellation point with the smallest norm distance from the cluster center point from the multiple standard constellation points, Based on the cluster mapping model, the coordinates of the sample points corresponding to each cluster are replaced with the coordinates of the target constellation points corresponding to the cluster to achieve phase noise compensation, and then to obtain the target received signal, based on baseband demodulation, channel decoding and The target received signal obtains the target signal, wherein the clustering model is a weighted ensemble clustering algorithm, and the clustering results corresponding to each clustering algorithm are obtained based on a plurality of different clustering algorithms and the gain baseband signal. Each clustering result obtains a co-clustering indicator matrix corresponding to each clustering result, and obtains a set matrix based on the clustering result and the co-clustering indicator matrix, and then obtains the weighted ensemble clustering algorithm.
根据权利要求6所述的相位噪声补偿***，其特征在于：The phase noise compensation system according to claim 6, characterized in that:

所述无线通信***的调制阶数被所述接收装置已知，所述多个聚类的数量与所述调制阶数相同。The modulation order of the wireless communication system is known by the receiving device, and the number of the plurality of clusters is the same as the modulation order.
根据权利要求6所述的相位噪声补偿***，其特征在于：The phase noise compensation system according to claim 6, characterized in that:

所述目标接收信号由各个聚类中心点对应的坐标均转换为各自对应的目标星座点的坐标后获得。The target received signal is obtained by converting the coordinates corresponding to each cluster center point to the coordinates of the corresponding target constellation points.
根据权利要求6所述的相位噪声补偿***，其特征在于：The phase noise compensation system according to claim 6, characterized in that:

第i个聚类中心点与第j个标准星座点的范数距离满足：d _ij＝||C _i-S _j|| ²,i＝1,...,M,j＝1,...,M，其中，C _i为第i个聚类中心点，S _j为第j个标准星座点，M为多进制频移键控***的调制阶数。 The norm distance between the i-th cluster center point and the j-th standard constellation point satisfies: d _ij =||C _i -S _j || ² ,i=1,...,M,j=1,... ., M, where C _i is the i-th clustering center point, S _j is the j-th standard constellation point, and M is the modulation order of the multi-ary frequency shift keying system.
根据权利要求6所述的相位噪声补偿***，其特征在于：The phase noise compensation system according to claim 6, characterized in that:

所述多个不同的聚类算法包括K均值聚类算法、K中心点聚类算法和凝聚层次聚类算法。The multiple different clustering algorithms include K-means clustering algorithm, K-center point clustering algorithm, and agglomerated hierarchical clustering algorithm.