WO2021127957A1 - 一种反激式转换器恒流控制电路 - Google Patents
一种反激式转换器恒流控制电路 Download PDFInfo
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- WO2021127957A1 WO2021127957A1 PCT/CN2019/127739 CN2019127739W WO2021127957A1 WO 2021127957 A1 WO2021127957 A1 WO 2021127957A1 CN 2019127739 W CN2019127739 W CN 2019127739W WO 2021127957 A1 WO2021127957 A1 WO 2021127957A1
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- flyback converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B47/00—Circuit arrangements for operating light sources in general, i.e. where the type of light source is not relevant
- H05B47/10—Controlling the light source
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps
- Y02B20/40—Control techniques providing energy savings, e.g. smart controller or presence detection
Definitions
- the application relates to the field of power supply control, and in particular to a flyback converter constant current control circuit.
- the charging problem of portable electronic devices represented by mobile phones has become increasingly prominent.
- the output accuracy of the charger during charging affects the safety of charging.
- the current accuracy of the power supply directly affects the brightness of the lighting.
- the flyback converter adopting the primary current feedback scheme is widely used in the field of power equipment because of the cost savings of optocouplers and the increase of system life. Since the accuracy of the constant current output of the flyback converter is directly affected by the current sampling accuracy, the demagnetization time sampling accuracy and the control scheme, and the current sampling error of the Miller platform caused by the power tube Miller capacitor, it causes the demagnetization in the prior art. The sampling accuracy of time and current is not high enough, which reduces the accuracy of the output current of the flyback converter.
- the technical problem to be solved by this application is to overcome the defects of inaccurate sampling of constant current control current and demagnetization time and low accuracy of output current in the prior art, thereby providing a flyback converter constant current control circuit.
- the present application provides a constant current control circuit for a flyback converter, including: a primary current peak value and demagnetization time generation module, a control module, and a power tube driving module.
- the power tube driving module is used for detecting current sampling Periodic flyback converter power tube gate terminal voltage zero crossing point, generate demagnetization end time, and send it to the primary side current peak value and demagnetization time generation module; primary side current peak value and demagnetization time generation module, used to obtain the current sampling
- the primary side sampling current of the periodic flyback converter generates the primary current peak value and the demagnetization start time, and generates the demagnetization time according to the demagnetization end time and the demagnetization start time, and sends the primary current peak value and demagnetization time of the current sampling period to Control module; control module, used to generate the primary current cut-off value according to the primary current peak value and demagnetization time of the current sampling period, and generate power when the primary sampling current of the next sampling cycle is equal to the primary current cut-
- the flyback converter constant current control circuit further includes: a linear voltage stabilizing module and an oscillator module, wherein the linear voltage stabilizing module is used to obtain the auxiliary winding power supply input voltage and high voltage start of the flyback converter The input voltage provides a stable power supply for other modules in the constant current control circuit of the flyback converter; the oscillator module is used to provide a clock signal for the control module.
- the constant current control circuit of the flyback converter further includes: a reference parameter circuit module, an over-temperature protection circuit module, a startup circuit module, and an over-voltage protection circuit module, wherein the reference parameter circuit module is used for The other modules in the constant current control circuit of the excited converter provide electrical parameters; the over-temperature protection circuit module is used to generate the power switch when it is detected that the positive temperature coefficient voltage in the reference parameter circuit module exceeds the over-temperature voltage reference value.
- the signal is cut off and sent to the control module; the start circuit module is used to start the constant current control circuit function when the voltage start input voltage is detected to reach the start voltage reference value; the overvoltage protection circuit module is used to start the input when the voltage is detected When the voltage exceeds the reference value of the overvoltage voltage, disconnect the power supply of other modules except the starting circuit module and the overvoltage protection circuit module.
- the electrical parameters include: a starting voltage reference value, an overvoltage voltage reference value, an overtemperature voltage reference value, a turn-on voltage reference value, and a constant current value.
- the primary-side current peak value and demagnetization time generating module includes: a primary-side current peak value generating circuit, a demagnetization start time generating circuit, and a demagnetization time generating circuit.
- the sampling current of the primary side of the flyback converter in the sampling period generates the peak current of the primary side and sends it to the control module and the demagnetization start time generating circuit;
- the demagnetization start time generating circuit is used to generate the reference value of the conduction voltage and the current sampling period
- the peak current of the primary side of the flyback converter generates the demagnetization start time;
- the demagnetization time circuit is used to generate the demagnetization time according to the demagnetization end time and the demagnetization start time and send it to the control module.
- control module includes: a primary side current turn-off value generating circuit and a drive signal generating circuit, wherein the primary side current turn-off value generating circuit is used to generate the primary side current peak value, demagnetization time, constant current value, The sampling period and the resistance value of the current cut-off resistance generate the primary current cut-off value; the drive signal generating circuit is used to compare the acquired primary sampling current of the next sampling cycle with the primary current cut-off value to generate the power tube shut-off value. Turn off the signal and send it to the power tube drive circuit module.
- the driving signal generating circuit is further used to generate a power tube turn-on signal according to the received clock signal, and send it to the power tube driving circuit module.
- the output current value of the secondary side of the flyback converter controlled by the constant current control circuit of the flyback converter is calculated by the following formula:
- I o is the output current of the secondary side of the flyback converter
- k N p /N s
- N p the number of turns of the primary winding of the transformer
- N s is the number of turns of the secondary winding of the transformer
- R is the current shutdown resistance Value
- R CS is the resistance value of the sampling resistor
- I c is the constant current value.
- the power tube driving module includes: a driving circuit field effect tube, the source of which is connected to the sampling resistor of the flyback converter, and is used to introduce the Miller platform current of the flyback converter power tube into the primary side In the current sampling circuit.
- a resistor is connected between the gate terminal of the field effect transistor of the driving circuit and the control module to filter out current spikes.
- the flyback converter constant current control circuit provided by this application compares the primary side current cut-off value generated by the primary side current peak value and demagnetization time with the primary side sampling current of the next sampling period, and according to the comparison result Control the off time of the power tube of the flyback converter to realize the constant current output of the secondary side of the flyback converter.
- the constant current control circuit of the flyback converter provided in this application takes into account the fact that the Miller platform brought by the Miller capacitor of the flyback converter power tube will sample the peak current of the primary side when the power tube is turned off. By collecting the current of the Miller platform, the sampling accuracy of the peak current of the primary side is improved; according to the peak current of the primary side, the demagnetization start time is obtained, and the power tube drive module collects the zero crossing point of the gate terminal voltage of the flyback converter power tube to obtain the demagnetization. The end time improves the sampling accuracy of the demagnetization time; the flyback converter controlled by the constant current control circuit of the flyback converter provided by this application can achieve a constant secondary side current by setting different turns ratios and sampling resistance values Output.
- FIG. 1 is a circuit principle topology diagram of a specific example of a flyback converter provided by an embodiment of the application;
- FIG. 2 is a schematic diagram of a specific example of a flyback converter constant current control circuit provided by an embodiment of the application;
- FIG. 3 is a schematic diagram of a specific example of a flyback converter constant current control circuit provided by an embodiment of the application;
- FIG. 4 is a schematic diagram of a specific example of a flyback converter constant current control circuit provided by an embodiment of the application;
- FIG. 5 is a schematic diagram of a specific example of a flyback converter constant current control circuit provided by an embodiment of the application;
- FIG. 6 is a schematic diagram of a specific example of a flyback converter constant current control circuit provided by an embodiment of the application.
- connection should be understood in a broad sense, unless otherwise clearly specified and limited.
- it can be a fixed connection or a detachable connection.
- Connected or integrally connected it can be a mechanical connection or an electrical connection; it can be directly connected, or indirectly connected through an intermediate medium, or it can be the internal connection of the two components, it can be a wireless connection, or it can be a wired connection connection.
- the specific meanings of the above terms in this application can be understood under specific circumstances.
- This embodiment provides a constant current control circuit for a flyback converter.
- the constant current control circuit can be integrated into a control chip for use in consumer electronic power supplies, portable electronic device charging, and replacement of other linear power supplies, etc.
- the embodiment of the application uses a flyback converter as a platform to verify the effectiveness of the constant current control function of the constant current control circuit.
- FIG. The circuit structure diagram of the side feedback flyback converter for constant current control.
- the main components include transformer, inductor, flyback converter power tube, rectifier diode, RCD circuit, auxiliary winding and constant current control circuit.
- the primary side current of the flyback converter is proportional to the secondary side current, and the proportional relationship is shown in equation (1),
- I sp is the peak current of the secondary side
- I pp is the peak current of the primary side
- N p is the number of turns of the primary winding of the transformer
- N s is the number of turns of the secondary winding of the transformer.
- I o is the output current of the flyback converter
- T dm is the demagnetization time
- T s is the sampling period.
- This embodiment provides a flyback converter constant current control circuit, as shown in FIG. 2, including:
- the power tube drive module is used to generate the demagnetization end time according to the detected zero crossing of the gate terminal voltage of the flyback converter power tube in the current sampling period, and send it to the primary current peak value and demagnetization time generation module.
- the demagnetization time after the power tube of the flyback converter is turned off is obtained from the demagnetization start time and the demagnetization end time.
- the demagnetization end time is detected by the power tube driving module.
- the working principle of the flyback converter demagnetization ends when the voltage on the secondary side of the flyback converter decreases.
- the residual energy in the equivalent inductance of the transformer will be transferred to the equivalent inductance of the transformer and the flyback converter.
- the parasitic capacitance of the power tube forms an oscillation. This oscillating waveform can be detected at the drain terminal of the power tube of the flyback converter.
- the oscillating voltage waveform is transmitted to the gate terminal through the parasitic capacitance of the power tube of the flyback converter.
- the gate terminal is in a high impedance state, and the phase difference between the gate terminal voltage signal and the drain terminal voltage signal is 90 degrees. Therefore, when the power tube drive module detects the zero crossing of the gate terminal voltage, it is the end of demagnetization. time.
- the primary side current peak value and demagnetization time generation module is used to generate the primary side current peak value and the demagnetization start time according to the acquired primary side sampling current of the flyback converter in the current sampling period, and generate according to the demagnetization end time and demagnetization start time Demagnetization time, the current peak value of the primary current of the current sampling period and the demagnetization time are sent to the control module.
- the control module is used to generate the primary current cut-off value according to the primary current peak value and demagnetization time of the current sampling period.
- the power tube is generated to turn off
- the signal control power tube drive circuit module turns off the flyback converter power tube.
- the embodiment of the present application generates the primary side current peak value and the demagnetization time by sampling the Miller platform current
- the module obtains a more accurate primary current peak value of the current sampling period.
- the control module generates the primary current cut-off value of the next sampling period according to the primary current peak value of the current sampling period and the demagnetization time. When the current and the primary side current turn-off value are equal, the flyback converter power tube is turned off.
- the constant current control of the flyback converter is realized by continuously adjusting the primary current cut-off value of each sampling period.
- the flyback converter constant current control circuit provided by the embodiment of the application compares the primary side current cut-off value generated by the primary side current peak value and the demagnetization time with the primary side sampling current of the next sampling period, and according to the comparison result Control the off time of the power tube of the flyback converter to realize the constant current output of the secondary side of the flyback converter.
- the constant current control circuit of the flyback converter further includes:
- the oscillator module is used to provide a clock signal for the control module.
- the control module when the primary side sampling current of the next cycle rises to the primary side current cut-off value, the control module generates a power tube turn-off signal to control the power tube drive circuit module to turn off the flyback converter power tube.
- the oscillator module provides a clock signal for the control module, and then the control module converts the clock signal into a power tube turn-on signal to control the power tube drive circuit module to turn on the flyback converter power tube.
- the linear voltage stabilizing module is used to obtain the auxiliary winding power supply input voltage and high-voltage start input voltage of the flyback converter, and provide stable power for other modules in the constant current control circuit of the flyback converter.
- the flyback converter circuit when the flyback converter circuit is not started, no current flows in the auxiliary winding. At this time, the high-voltage start input voltage provides power.
- the flyback converter circuit When the flyback converter circuit is operating normally, the converter The auxiliary winding power supply input voltage provides power.
- the Vs end of the flyback converter constant current control circuit is connected to one end of the voltage divider resistor, and the other end of the voltage divider resistor, Vsup, is connected to the auxiliary winding side.
- the output terminal VDD of the linear voltage regulator module outputs the supply voltage, which is used to provide stable power for other modules in the constant current control circuit of the flyback converter.
- the constant current control circuit of the flyback converter further includes:
- the reference parameter circuit module is used to provide electrical parameters for other modules in the constant current control circuit of the flyback converter.
- the high-voltage startup input voltage or the auxiliary winding power supply input voltage is combined with parameter circuits such as resistor divider and operational amplifier to obtain state parameters such as voltage or current required for the operation of the constant current control circuit.
- the over-temperature protection circuit module is used to generate a power tube shutdown signal and send it to the control module when it is detected that the positive temperature coefficient voltage in the reference parameter circuit module exceeds the over-temperature voltage reference value.
- the starting circuit module is used to start the constant current control circuit function when it is detected that the voltage starting input voltage reaches the starting voltage reference value.
- the HV terminal of the constant current control circuit of the flyback converter is connected to the high-voltage starting input voltage, which is generated by the DC voltage output by the ac-dc rectifier diode circuit after being filtered by a filter.
- the overvoltage protection circuit module is used to cut off the power supply of other modules except the starter circuit module and the overvoltage protection circuit module when it is detected that the high-voltage start input voltage exceeds the overvoltage voltage reference value.
- the electrical parameters include: a starting voltage reference value, an overvoltage voltage reference value, an overtemperature voltage reference value, a turn-on voltage reference value, and a constant current value.
- a starting voltage reference value an overvoltage voltage reference value
- an overtemperature voltage reference value an overtemperature voltage reference value
- a turn-on voltage reference value a constant current value.
- multiple reference values of electrical parameters are compared with actual values, so as to obtain the voltage, current, etc., which are normally operated in the constant current control circuit. This is only an example, and is not limited to this.
- the primary current peak value and demagnetization time generating module includes:
- the primary side current peak value generating circuit is used to generate the primary side current peak value according to the acquired primary side sampling current of the flyback converter in the current sampling period, and send it to the control module and the demagnetization start time generating circuit.
- the embodiment of the application builds the circuit as shown in FIG. 3.
- VDD is the power supply voltage output by the linear regulator module
- V cs is the sampling resistor voltage
- V ref is the reference value of the turn-on voltage
- t dm_on is the demagnetization start time
- M1 is the P-type MOS field effect tube
- A1 is the calculation Amplifier
- C1 is the charging capacitor
- R1 is the filter resistance.
- the embodiment of the present application charges the charging capacitor C1 with the sampling resistor voltage V cs through the operational amplifier A1 and the M1 field effect transistor. Due to the unidirectional conductivity of the MOS, the capacitor can only be charged and not discharged during the charging period, so after the power tube is turned off, the current peak value V csp during the charging capacitor charged by the sampling resistor voltage can be collected.
- the demagnetization start time generating circuit is used to generate the demagnetization start time according to the reference value of the conduction voltage and the peak value of the primary current of the flyback converter in the current sampling period. As shown in Figure 3(b), when the power tube of the flyback converter is completely turned off, the sampling resistor voltage V cs suddenly drops due to the sudden drop of the primary current peak value to zero. This time is the demagnetization start time. A1 pulls the gate terminal of M1 to a high level to turn off the M1 tube. By comparing the on-voltage reference value V ref with the output voltage of A1, the demagnetization start time information can be obtained.
- the demagnetization time circuit is used to generate the demagnetization time according to the demagnetization end time and the demagnetization start time and send it to the control module.
- control module includes:
- the primary current cut-off value generating circuit is used to generate the primary current cut-off value according to the primary current peak value, demagnetization time, constant current value, sampling period, and current cut-off resistance value.
- V C is the demagnetization time charging voltage
- R is the resistance value of the current shut-off resistance
- T s is the sampling period
- T dm is the demagnetization time.
- the peak value of the sampling resistor voltage V csp is compared with the demagnetization time charging voltage V C through the error amplifier.
- V csp is greater than V C
- V csp is lower than V C
- the cut-off value is increased to generate the sampling resistor voltage to turn off.
- the value V csgd is the primary current cut-off value.
- the driving signal generation circuit is used to compare the acquired primary side sampling current of the next sampling period with the primary side current turn-off value, generate a power tube turn-off signal and send it to the power tube drive circuit module.
- the embodiment of the present application uses the drive signal generating circuit to detect when the primary current of the next sampling period rises to reach the primary current cut-off value, that is, the sampling resistor voltage V cs reaches the sampling resistor voltage
- the turn-off value V csgd turns off the power tube of the flyback converter. After a certain period of time, the power tube of the flyback converter is completely turned off. At this time, the peak value of the sampling resistor voltage in the next sampling period can reach the peak value of the sampling resistor voltage V csp .
- the sampling resistor voltage cut-off value V csgd is continuously adjusted through the primary current peak value and demagnetization time generation module and control module to control the sampling resistor voltage peak value in the next sampling period to achieve sampling The peak value of the resistance voltage V csp .
- the driving signal generating circuit is further used to generate a power tube turn-on signal according to the received clock signal, and send it to the power tube driving circuit module.
- the output current value of the secondary side of the flyback converter controlled by the constant current control circuit of the flyback converter is calculated by the following formula:
- I o is the output current of the secondary side of the flyback converter
- k N p /N s
- N p the number of turns of the primary winding of the transformer
- N s is the number of turns of the secondary winding of the transformer
- R is the current shutdown resistance Value
- R CS is the resistance value of the sampling resistor
- I c is the constant current value.
- the power tube drive module includes: a drive circuit FET, the source of which is connected to the sampling resistor of the flyback converter, and is used to introduce the Miller platform current of the flyback converter power tube into the original Edge current sampling circuit. And a resistor is connected between the gate terminal of the field effect tube of the driving circuit and the control module to filter out current spikes.
- the source terminal of the field effect transistor of the driving circuit is not grounded, but is connected to the sampling resistor.
- the flyback converter power tube is turned off, the current overcharge caused by the Miller platform caused by the Miller capacitor can be sampled, and the accurate primary current peak value can be sampled.
- this connection will introduce a current spike in the primary current when the drive circuit FET is turned off, so a resistor is added to the gate of the drive tube to filter out the spike, such as As shown in Figure 6(c).
- the filter resistor after the filter resistor is connected, the current spike no longer affects the sampling.
- the embodiment of the application completes the design and simulation through Nuvoton's 350nm BCD process ntc1132 (this is only used as an example, not limited to this) , It is measured that when the input voltage of the chip in the flyback system varies from 85Vac to 220Vac, and the secondary side load changes from 6W to 23W, the deviation of the secondary side output current value is within ⁇ 1.46%.
- the flyback converter constant current control circuit controls the flyback converter according to the primary current cut-off value generated by the primary current peak value and the demagnetization time, and the primary sampling current of the next sampling period
- the turn-off time of the power tube realizes the constant current output of the secondary side of the flyback converter; considers the Miller platform brought by the miller capacitor of the power tube of the flyback converter to the primary side current when the power tube is turned off.
- the impact of peak sampling improves the sampling accuracy of the peak current of the primary side by collecting the current of the Miller platform; according to the peak current of the primary side, the demagnetization start time is obtained, and the power tube drive module collects the gate terminal voltage of the power tube of the flyback converter.
- the flyback converter provided by this application has a constant current
- the flyback converter controlled by the control circuit can achieve a constant output of the secondary side current by specifying different turns ratios and sampling resistance values.
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Abstract
一种反激式转换器恒流控制电路,包括:功率管驱动模块根据当前采样周期反激式转换器功率管栅端电压过零点,生成退磁结束时间;原边电流峰值及退磁时间生成模块根据获取的当前采样周期的原边采样电流,生成原边电流峰值及退磁开始时间,根据退磁开始和结束时间生成退磁时间;控制模块根据当前采样周期的原边电流峰值及退磁时间生成原边电流关断值,下一采样周期的原边采样电流与原边电流关断值相等时,控制功率管驱动电路模块关断反激式转换器功率管。将原边电流峰值及退磁时间生成的原边电流关断值,与下一采样周期的原边采样电流进行比较,根据比较结果控制反激式转换器功率管关断时间,实现对反激式转换器的恒流输出控制。
Description
本申请涉及电源控制领域,具体涉及一种反激式转换器恒流控制电路。
随着电子技术的快速发展,电子设备的种类和功能越来越多,以手机为代表的便携式电子设备的充电问题日益突出,在充电时充电器的输出精度影响到充电的安全问题。在另一类电子设备中,以LED照明为例,电源的电流精度直接影响了照明的亮度。当前,采用原边电流反馈方案的反激式转换器因节省了光耦成本、提高了***寿命在电源设备领域得到广泛应用。由于反激式转换器恒流输出的精度直接受电流采样精度、退磁时间采样精度及控制方案的影响,并且功率管密勒电容带来的密勒平台电流采样误差,造成现有技术中对退磁时间及电流的采样精度不够高,降低了反激式转换器输出电流的精度。
发明内容
因此,本申请要解决的技术问题在于克服现有技术中的恒流控制电流采样及退磁时间采样不精准,输出电流精度低的缺陷,从而提供一种反激式转换器恒流控制电路。
为达到上述目的,本申请提供如下技术方案:
本申请提供一种反激式转换器恒流控制电路,包括:原边电流峰值及退磁时间生成模块、控制模块及功率管驱动模块,其中,功率管驱动模块,用于根据检测得到的当前采样周期的反激式转换器功率管栅端电压过零点,生成退磁结束时间,并发送到原边电流峰值及退磁时间生成模块;原边电流峰值及退磁时间生成模块,用于根据获取的当前采样周期的反激式转换器的原边采样电流,生成原边电流峰值及退磁开始时间,以及根据退磁结束时间及退磁开始时间生成退磁时间,将当前采样周期的原边电流峰值及退磁时间发送到控制模块;控制模块,用于根据当前采样周期的原边电流峰值及退磁时间,生成原边电流关断值,当下一采样周期的原边采样电流与原边电流关断值相等时,生成功率管关断信号控制功率管驱动电路模块关断反激式转换器功率管。
在一实施例中,反激式转换器恒流控制电路还包括:线性稳压模块及振荡器模块,其中,线性稳压模块,用于获取反激式转换器辅助绕组供电输入电压及高压启动输入电压,为反激式转换器恒流控制电路中的其它模块提供稳定电源;振荡器模块,用于为控制模块提供时钟信号。
在一实施例中,反激式转换器恒流控制电路还包括:基准参数电路模块、过温保护电路模块、启动电路模块及过压保护电路模块,其中,基准参数电路模块,用于为反激式转换器恒流控制电路中的其它模块提供电气量参数;过温保护电路模块,用于当检测到基准参数电路模块中的正温系数电压超过过温电压基准值时,生成功率管关断信号并发送到控制模块;启动电路模块,用于当检测到电压启动输入电压达到启动电压基准值时,启动恒流控制电路功能运行;过压保护电路模块,用于当检测到电压启动 输入电压超过过压电压基准值时,断开除启动电路模块及过压保护电路模块外其它模块的供电。
在一实施例中,电气量参数包括:启动电压基准值、过压电压基准值、过温电压基准值、导通电压基准值及恒定电流值。
在一实施例中,原边电流峰值及退磁时间生成模块包括:原边电流峰值生成电路、退磁开始时间生成电路及退磁时间生成电路,其中,原边电流峰值生成电路,用于根据获取的当前采样周期的反激式转换器的原边采样电流,生成原边电流峰值,并发送到控制模块及退磁开始时间生成电路;退磁开始时间生成电路,用于根据导通电压基准值及当前采样周期的反激式转换器的原边电流峰值,生成退磁开始时间;退磁时间电路,用于根据退磁结束时间及退磁开始时间,生成退磁时间并发送到控制模块。
在一实施例中,控制模块包括:原边电流关断值生成电路及驱动信号生成电路,其中,原边电流关断值生成电路,用于根据原边电流峰值、退磁时间、恒定电流值、采样周期及电流关断电阻阻值,生成原边电流关断值;驱动信号生成电路,用于将获取的下一采样周期的原边采样电流与原边电流关断值比较,生成功率管关断信号并发送到功率管驱动电路模块。
在一实施例中,驱动信号生成电路还用于根据接收的时钟信号,生成功率管导通信号,并发送到功率管驱动电路模块。
在一实施例中,当反激式转换器处于稳态时,由反激式转换器恒流控制电路控制的反激式转换器副边输出电流值,通过以下公式计算:
其中,I
o为反激式转换器副边输出电流,k=N
p/N
s,N
p为变压器原边绕组匝数,N
s为变压器副边绕组匝数,R为电流关断电阻阻值,R
CS为采样电阻阻值,I
c为恒定电流值。
在一实施例中,功率管驱动模块包括:驱动电路场效应管,其源端与反激式转换器的采样电阻连接,用于将反激式转换器功率管的密勒平台电流引入原边电流采样电路中。
在一实施例中,在驱动电路场效应管的栅端与控制模块之间接入电阻,用于滤除电流尖刺。
本申请技术方案,具有如下优点:
1.本申请提供的反激式转换器恒流控制电路,通过将原边电流峰值及退磁时间生成的原边电流关断值,与下一采样周期的原边采样电流进行比较,根据比较结果控制反激式转换器功率管的关断时间,实现了反激式转换器副边恒定电流的输出。
2.本申请提供的反激式转换器恒流控制电路,考虑了由反激式转换器功率管密勒电容带来的密勒平台在功率管关断时对原边电流峰值采样带来的影响,通过采集密勒平台电流,提高了原边电流峰值的采样精度;根据原边电流峰值,获取退磁开始时间,功率管驱动模块采集反激式转换器功率管栅端电压过零点,获取退磁结束时间,提高了退磁时间采样精度;由本申请提供的反激式转换器恒流控制电路控制的反激式转换器,通过给定不同的匝数比和采样电阻值可以实现副边电流的恒定输出。
为了更清楚地说明本申请具体实施方式或现有技术中的技术方案,下面将对具体实施方式或现有技术描述中所需要使用的附图作简单地介绍,显而易见地,下面描述中的附图是本申请的一些实施方式,对于本领域普通技术人员来讲,在不付出创造性劳动的前提下,还可以根据这些附图获得其他的附图。
图1为本申请实施例提供的反激式转换器的一个具体示例的电路原理拓扑图;
图2为本申请实施例提供的反激式转换器恒流控制电路的一个具体示例的示意图;
图3为本申请实施例提供的反激式转换器恒流控制电路的一个具体示例的示意图;
图4为本申请实施例提供的反激式转换器恒流控制电路的一个具体示例的示意图;
图5为本申请实施例提供的反激式转换器恒流控制电路的一个具体示例的示意图;
图6为本申请实施例提供的反激式转换器恒流控制电路的一个具体示例的示意图。
下面将结合附图对本申请的技术方案进行清楚、完整地描述,显然,所描述的实施例是本申请一部分实施例,而不是全部的实施例。基于本申请中的实施例,本领域普通技术人员在没有做出创造性劳动前提下所获得 的所有其他实施例,都属于本申请保护的范围。
在本申请的描述中,需要说明的是,术语“中心”、“上”、“下”、“左”、“右”、“竖直”、“水平”、“内”、“外”等指示的方位或位置关系为基于附图所示的方位或位置关系,仅是为了便于描述本申请和简化描述,而不是指示或暗示所指的装置或元件必须具有特定的方位、以特定的方位构造和操作,因此不能理解为对本申请的限制。此外,术语“第一”、“第二”、“第三”仅用于描述目的,而不能理解为指示或暗示相对重要性。
在本申请的描述中,需要说明的是,除非另有明确的规定和限定,术语“安装”、“相连”、“连接”应做广义理解,例如,可以是固定连接,也可以是可拆卸连接,或一体地连接;可以是机械连接,也可以是电连接;可以是直接相连,也可以通过中间媒介间接相连,还可以是两个元件内部的连通,可以是无线连接,也可以是有线连接。对于本领域的普通技术人员而言,可以具体情况理解上述术语在本申请中的具体含义。
此外,下面所描述的本申请不同实施方式中所涉及的技术特征只要彼此之间未构成冲突就可以相互结合。
实施例
本实施例提供一种反激式转换器恒流控制电路,实际应用中,可该恒流控制电路集成在一控制芯片中,应用于消费类电子电源、便携式电子设备充电及替代其他线性电源等领域,本申请实施例以反激式转换器为平台,验证恒流控制电路的恒流控制功能的有效性,图1将反激式转换器恒流控制电路集成为一控制芯片时对一原边反馈反激式转换器进行恒流控制的电 路结构框图,主要器件包括变压器、电感、反激式转换器功率管、整流二极管、RCD电路、辅助绕组及恒流控制电路。
反激式变换器原边电流和副边电流成比例,比例关系如式(1)所示,
其中,I
sp为副边峰值电流,I
pp为原边峰值电流,N
p为变压器原边线圈匝数、N
s为变压器副边线圈匝数。
由如式(1)所示的原边电流和副边电流的比例关系式及式(2)所示的周期平均电流公式,可以得到副边峰值电流与原边电流峰值及退磁时间的关系,如式(3)所示。
其中,I
o为反激式转换器输出电流,T
dm为退磁时间,T
s为采样周期。
由式(3)可知,反激式转换器输出电流I
o与原边电流峰值I
pp、退磁时间T
dm、变压器原边线圈匝数N
p、变压器副边线圈匝数N
s及采样周期T
s有关,然而变压器原边线圈匝数N
p、变压器副边线圈匝数N
s及采样周期T
s为给定值,因此控制原边电流峰值I
pp和退磁时间T
dm就可以控制反激式转换器实现恒流输出。
本实施例提供一种反激式转换器恒流控制电路,如图2所示,包括:
功率管驱动模块,用于根据检测得到的当前采样周期的反激式转换器功率管栅端电压过零点,生成退磁结束时间,并发送到原边电流峰值及退磁时间生成模块。
反激式转换器功率管在关断后的退磁时间由退磁开始时间及退磁结束时间求得,本申请实施例中,退磁结束时间由功率管驱动模块检测获得。根据反激式转换器的工作原理可知,当反激式转换器副边电压降低时,退磁结束,此时变压器的等效电感中残留的能量,在变压器的等效电感和反激式转换器功率管的寄生电容间形成震荡,在反激式转换器功率管漏端可以检测到这一震荡波型,震荡电压波型经过反激式转换器功率管寄生电容传导至栅端,由于反激式转换器功率管在关断状态时,栅端为高阻态,栅端电压信号和漏端电压信号相位相差90度,因此当功率管驱动模块检测栅端电压过零时,即为退磁结束时间。
原边电流峰值及退磁时间生成模块,用于根据获取的当前采样周期的反激式转换器的原边采样电流,生成原边电流峰值及退磁开始时间,以及根据退磁结束时间及退磁开始时间生成退磁时间,将当前采样周期的原边电流峰值及退磁时间发送到控制模块。
控制模块,用于根据当前采样周期的原边电流峰值及退磁时间,生成原边电流关断值,当下一采样周期的原边采样电流与原边电流关断值相等时,生成功率管关断信号控制功率管驱动电路模块关断反激式转换器功率管。
在反激式转换器功率管关断后,由于变压器的等效电感的退磁时间,原边采样电流并不是迅速下降,而是反激式转换器功率管完全关断后,再突然降为零,同时由于反激式转换器的密勒电容的影响,原边电流峰值在密勒平台时间内产生,因此本申请实施例通过对密勒平台电流的采样,使得原边电流峰值及退磁时间生成模块获得更为精确的当前采样周期的原边 电流峰值,控制模块根据当前采样周期的原边电流峰值及退磁时间,生成下一采样周期的原边电流关断值,当在下一周期原边采样电流和原边电流关断值相等时,关断反激式转换器功率管。本申请实施例通过不断调整每个采样周期的原边电流关断值,从而实现对反激式转换器的恒流控制。
本申请实施例提供的反激式转换器恒流控制电路,通过将原边电流峰值及退磁时间生成的原边电流关断值,与下一采样周期的原边采样电流进行比较,根据比较结果控制反激式转换器功率管的关断时间,实现了反激式转换器副边恒定电流的输出。
在一具体实施例中,反激式转换器恒流控制电路还包括:
振荡器模块,用于为控制模块提供时钟信号。本申请实施例中,当下一周期的原边采样电流上升达到原边电流关断值时,控制模块生成功率管关断信号控制功率管驱动电路模块关断反激式转换器功率管,在反激式转换器功率管完全关断后,反激式转换器功率管需要驱动信号控制导通时,同时本申请实施例中反激式转换器功率管是通过PWM调制方式控制其导通的,因此振荡器模块为控制模块提供时钟信号,然后控制模块将时钟信号转换为功率管导通信号控制功率管驱动电路模块导通反激式转换器功率管。
线性稳压模块,用于获取反激式转换器辅助绕组供电输入电压及高压启动输入电压,为反激式转换器恒流控制电路中的其它模块提供稳定电源。本申请实施例中,在反激式转换器电路未启动时,辅助绕组中无电流流通,此时由高压启动输入电压提供电源,当反激式转换器电路正常运行时,此时由转换器辅助绕组供电输入电压提供电源,如图1所示,反激式转换器 恒流控制电路的Vs端连接在分压电阻的一端,分压电阻的另一端Vsup端连接到辅助绕组侧。线性稳压模块的输出端VDD端输出供电电压,用于为反激式转换器恒流控制电路中的其它模块提供稳定电源。
在一具体实施例中,反激式转换器恒流控制电路还包括:
基准参数电路模块,用于为反激式转换器恒流控制电路中的其它模块提供电气量参数。本申请实施例中,利用高压启动输入电压或是辅助绕组供电输入电压,经过电阻分压、运算放大器等参数电路联合作用,得到恒流控制电路运行需要的电压或是电流等状态量参数。
过温保护电路模块,用于当检测到基准参数电路模块中的正温系数电压超过过温电压基准值时,生成功率管关断信号并发送到控制模块。
启动电路模块,用于当检测到电压启动输入电压达到启动电压基准值时,启动恒流控制电路功能运行。如图1所示,反激式转换器恒流控制电路的HV端接高压启动输入电压,高压启动输入电压由ac-dc整流二极管电路输出的直流电压经过滤波器滤波后生成。
过压保护电路模块,用于当检测到高压启动输入电压超过过压电压基准值时,断开除启动电路模块及过压保护电路模块外其它模块的供电。
在一具体实施例中,电气量参数包括:启动电压基准值、过压电压基准值、过温电压基准值、导通电压基准值及恒定电流值。本申请实施例中利用多种电气量参数基准值与实际值比较,从而获取恒流控制电路中正常运行的电压、电流等,此仅以此举例,不以此为限。
在一具体实施例中,如图3所示,原边电流峰值及退磁时间生成模块 包括:
原边电流峰值生成电路,用于根据获取的当前采样周期的反激式转换器的原边采样电流,生成原边电流峰值,并发送到控制模块及退磁开始时间生成电路。
如图1所示,本申请实施例将电流采样电路接在采样电阻的一端,通过采集采样电阻电压V
cs作为当前采样周期的原边采样电流的相关电压,因此原边采样电流峰值可以由采样电阻电压峰值获取,即I
pp=V
csp/R
cs,其中I
pp为原边采样电路峰值,R
cs为采用电阻阻值,V
csp为采样电阻电压峰值,为了获取采样电阻电压峰值V
csp,本申请实施例搭建如图3所示电路。图3中VDD为线性稳压模块输出的供电电压,V
cs为采集采样电阻电压,V
ref为导通电压基准值,t
dm_on为退磁开始时间,M1为P型MOS场效应管,A1为运算放大器,C1为充电电容,R1为滤波电阻。
如图3(a)所示,在反激式转换器功率管关断后,由于功率管具有关断延时时间,且由于P型MOS管只能从VDD处拉高漏端电压,因此M1处于导通状态,本申请实施例通过运算放大器A1及M1场效应管,利用采样电阻电压V
cs向充电电容C1充电。由于MOS的单向导通性,电容在充电期间内只能充电不能放电,故功率管关断后可以采集到采样电阻电压对充电电容充电的期间的电流峰值V
csp。
退磁开始时间生成电路,用于根据导通电压基准值及当前采样周期的反激式转换器的原边电流峰值,生成退磁开始时间。如图3(b)所示,在反激式转换器功率管完全关断时,由于原边电流峰值突然下降至零,造成采样电阻电压V
cs突然下降,此时为退磁开始时间,此时A1将M1的栅端拉 至高电平,从而关断M1管,通过将导通电压基准值V
ref与A1输出电压比较,可以获得退磁开始时间信息。
退磁时间电路,用于根据退磁结束时间及退磁开始时间,生成退磁时间并发送到控制模块。
在一具体实施例中,控制模块包括:
原边电流关断值生成电路,用于根据原边电流峰值、退磁时间、恒定电流值、采样周期及电流关断电阻阻值,生成原边电流关断值。
本申请实施例,如图4(b)所示,当退磁未开始时,即原边电流峰值及退磁时间生成模块未生成退磁开始时间时,图4(a)中的功率管由于没有驱动信号,恒定电流源对电容C进行充电;当退磁开始时,电容C开始放电,在反激式转换器稳态时,电容C的充电电流等于放电电流,因此可以在电流关断电阻阻值R处检测到退磁时间充电电压V
C,并可以由式(4)计算得到:
其中,V
C为退磁时间充电电压,R为电流关断电阻阻值,T
s为采样周期,T
dm为退磁时间。
将采样电阻电压峰值V
csp与退磁时间充电电压V
C通过误差放大器比较,V
csp大于V
C时调低关断值,V
csp低于V
C时调高关断值,生成采样电阻电压关断值V
csgd,即得到原边电流关断值。
驱动信号生成电路,用于将获取的下一采样周期的原边采样电流与原边电流关断值比较,生成功率管关断信号并发送到功率管驱动电路模块。
如图5(a)所示,本申请实施例是通过驱动信号生成电路当检测到下一采样周期的原边电流上升达到原边电流关断值时,即采样电阻电压V
cs达到采 样电阻电压关断值V
csgd,关断反激式转换器功率管,在一定时间后彻底关断,此时下一采样周期的采样电阻电压峰值可以达到采样电阻电压峰值V
csp,当下一采样周期的采样电阻电压峰值不能达到采样电阻电压峰值V
csp时,通过原边电流峰值及退磁时间生成模块及控制模块不断调整采样电阻电压关断值V
csgd,以控制下一采样周期的采样电阻电压峰值可以达到采样电阻电压峰值V
csp。
在一具体实施例中,驱动信号生成电路还用于根据接收的时钟信号,生成功率管导通信号,并发送到功率管驱动电路模块。
在一具体实施例中,当反激式转换器处于稳态时,由反激式转换器恒流控制电路控制的反激式转换器副边输出电流值,通过以下公式计算:
其中,I
o为反激式转换器副边输出电流,k=N
p/N
s,N
p为变压器原边绕组匝数,N
s为变压器副边绕组匝数,R为电流关断电阻阻值,R
CS为采样电阻阻值,I
c为恒定电流值。
本申请实施例中,当反激式变换器电路达到稳态时,即副边输出电流为预设恒定值时,此时V
csp=V
c,如图5(b)所示,根据式(3)及式(4)可以得到式(5)。由式(5)可知,当反激式转换器处于稳态时,由反激式转换器恒流控制电路控制的反激式转换器副边输出电流值,只和变压器匝数比k、电流关断电阻阻值R、恒定电流值I
c以及采样电阻R
cs相关,且均为设计给定值,因此由本实施例提供的反激式转换器恒流控制电路控制的反激式转换器, 通过给定不同的匝数比和采样电阻值可以实现副边电流的恒定输出。
在一具体实施例中,功率管驱动模块包括:驱动电路场效应管,其源端与反激式转换器的采样电阻连接,用于将反激式转换器功率管的密勒平台电流引入原边电流采样电路中。并在驱动电路场效应管的栅端与控制模块之间接入电阻,用于滤除电流尖刺。
如图6(a)及图6(b)所示,本申请实施例中没有将驱动电路场效应管的源端接地,而是接到采样电阻上。通过这种方式可以采样到在关断反激式转换器功率管时,由密勒电容引起的密勒平台造成的电流过充,可以采样到准确的原边电流峰值。如图6(d)所示,这种接法会在驱动电路场效应管关断时,在原边电流中引入一个电流尖刺,因此在驱动管栅端加入一个电阻滤除该尖刺,如图6(c)所示。对比图6(d)及图6(e)所示,接入滤除电阻后,电流尖峰不再对采样造成影响。
为了验证本申请实施例提供的反激式转换器恒流控制电路的正确性,本申请实施例通过新唐350nm BCD工艺ntc1132完成设计并进行仿真(仅以此作为举例,不以此为限),测得芯片在反激式***输入电压在85Vac~220Vac间变化,副边负载由6W致23W区间变化时,副边输出电流值偏差在±1.46%以内。
本申请实施例提供的反激式转换器恒流控制电路,根据原边电流峰值及退磁时间生成的原边电流关断值,及下一采样周期的原边采样电流,控制反激式转换器功率管的关断时间,实现了反激式转换器副边恒定电流的输出;考虑了由反激式转换器功率管密勒电容带来的密勒平台在功率管关 断时对原边电流峰值采样带来的影响,通过采集密勒平台电流,提高了原边电流峰值的采样精度;根据原边电流峰值,获取退磁开始时间,功率管驱动模块采集反激式转换器功率管栅端电压过零点,获取退磁结束时间,原边电流峰值及退磁时间生成模块采集P型MOS管的导通电压,获取退磁开始时间,提高了退磁时间采样精度;由本申请提供的反激式转换器恒流控制电路控制的反激式转换器,通过给定不同的匝数比和采样电阻值可以实现副边电流的恒定输出。
显然,上述实施例仅仅是为清楚地说明所作的举例,而并非对实施方式的限定。对于所属领域的普通技术人员来说,在上述说明的基础上还可以做出其它不同形式的变化或变动。这里无需也无法对所有的实施方式予以穷举。而由此所引申出的显而易见的变化或变动仍处于本申请创造的保护范围之中。
Claims (10)
- 一种反激式转换器恒流控制电路,其特征在于,包括:原边电流峰值及退磁时间生成模块、控制模块及功率管驱动模块,其中,功率管驱动模块,用于根据检测得到的当前采样周期的反激式转换器功率管栅端电压过零点,生成退磁结束时间,并发送到所述原边电流峰值及退磁时间生成模块;原边电流峰值及退磁时间生成模块,用于根据获取的当前采样周期的反激式转换器的原边采样电流,生成原边电流峰值及退磁开始时间,以及根据所述退磁结束时间及所述退磁开始时间生成退磁时间,将当前采样周期的原边电流峰值及退磁时间发送到所述控制模块;控制模块,用于根据所述当前采样周期的原边电流峰值及退磁时间,生成原边电流关断值,当下一采样周期的原边采样电流与所述原边电流关断值相等时,生成功率管关断信号控制所述功率管驱动电路模块关断反激式转换器功率管。
- 根据权利要求1所述的反激式转换器恒流控制电路,其特征在于,还包括:线性稳压模块及振荡器模块,其中,线性稳压模块,用于获取反激式转换器辅助绕组供电输入电压及高压启动输入电压,为反激式转换器恒流控制电路中的其它模块提供稳定电源;振荡器模块,用于为所述控制模块提供时钟信号。
- 根据权利要求2所述的反激式转换器恒流控制电路,其特征在于,还包括:基准参数电路模块、过温保护电路模块、启动电路模块及过压保护 电路模块,其中,基准参数电路模块,用于为反激式转换器恒流控制电路中的其它模块提供电气量参数;过温保护电路模块,用于当检测到所述基准参数电路模块中的正温系数电压超过过温电压基准值时,生成功率管关断信号并发送到所述控制模块;启动电路模块,用于当检测到电压启动输入电压达到启动电压基准值时,启动恒流控制电路功能运行;过压保护电路模块,用于当检测到电压启动输入电压超过过压电压基准值时,断开除所述启动电路模块及所述过压保护电路模块外其它模块的供电。
- 根据权利要求3所述的反激式转换器恒流控制电路,其特征在于,所述电气量参数包括:启动电压基准值、过压电压基准值、过温电压基准值、导通电压基准值及恒定电流值。
- 根据权利要求4所述的反激式转换器恒流控制电路,其特征在于,所述原边电流峰值及退磁时间生成模块包括:原边电流峰值生成电路、退磁开始时间生成电路及退磁时间生成电路,其中,原边电流峰值生成电路,用于根据获取的当前采样周期的反激式转换器的原边采样电流,生成原边电流峰值,并发送到所述控制模块及所述退磁开始时间生成电路;退磁开始时间生成电路,用于根据所述导通电压基准值及当前采样周期的反激式转换器的原边电流峰值,生成退磁开始时间;退磁时间电路,用于根据所述退磁结束时间及所述退磁开始时间,生成退磁时间并发送到所述控制模块。
- 根据权利要求5所述的反激式转换器恒流控制电路,其特征在于,所述控制模块包括:原边电流关断值生成电路及驱动信号生成电路,其中,原边电流关断值生成电路,用于根据所述原边电流峰值、所述退磁时间、所述恒定电流值、采样周期及电流关断电阻阻值,生成原边电流关断值;驱动信号生成电路,用于将获取的下一采样周期的原边采样电流与所述原边电流关断值比较,生成功率管关断信号并发送到所述功率管驱动电路模块。
- 根据权利要求6所述的反激式转换器恒流控制电路,其特征在于,所述驱动信号生成电路还用于根据接收的时钟信号,生成功率管导通信号,并发送到所述功率管驱动电路模块。
- 根据权利要求8所述的反激式转换器恒流控制电路,其特征在于,所述功率管驱动模块包括:驱动电路场效应管,其源端与反激式转换器的采样电阻连接,用于将反激式转换器功率管的密勒平台电流引入原边电流采样电路中。
- 根据权利要求9所述的反激式转换器恒流控制电路,其特征在于,在所述驱动电路场效应管的栅端与所述控制模块之间接入电阻,用于滤除电流尖刺。
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Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN114167771A (zh) * | 2021-11-19 | 2022-03-11 | 瀚昕微电子(无锡)有限公司 | 用于ac-dc控制器的输出驱动控制电路 |
US20230034590A1 (en) * | 2021-07-28 | 2023-02-02 | Shanghai Bright Power Semiconductor Co., Ltd. | Control circuit for constant-current drive circuit and constant-current drive circuit |
CN117240408A (zh) * | 2023-11-10 | 2023-12-15 | 深圳市芯茂微电子有限公司 | 一种应用于隔离电源的通信方法及装置 |
Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN103066869A (zh) * | 2012-12-24 | 2013-04-24 | 泉芯电子技术(深圳)有限公司 | 一种基于三极管的去磁时间检测电路 |
US8593841B2 (en) * | 2010-11-04 | 2013-11-26 | Chengdu Monolithic Power Systems Co., Ltd. | Compensation circuit for constant current regulation of power supply and method thereof |
CN103728578A (zh) * | 2014-01-10 | 2014-04-16 | 美芯晟科技(北京)有限公司 | 退磁检测方法、退磁检测电路及应用该电路的恒流驱动器 |
CN105636303A (zh) * | 2014-11-03 | 2016-06-01 | 华润矽威科技(上海)有限公司 | 一种恒流控制电路及方法 |
CN106992684A (zh) * | 2017-04-25 | 2017-07-28 | 昂宝电子(上海)有限公司 | 反激式电源***及其控制方法 |
-
2019
- 2019-12-24 WO PCT/CN2019/127739 patent/WO2021127957A1/zh active Application Filing
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US8593841B2 (en) * | 2010-11-04 | 2013-11-26 | Chengdu Monolithic Power Systems Co., Ltd. | Compensation circuit for constant current regulation of power supply and method thereof |
CN103066869A (zh) * | 2012-12-24 | 2013-04-24 | 泉芯电子技术(深圳)有限公司 | 一种基于三极管的去磁时间检测电路 |
CN103728578A (zh) * | 2014-01-10 | 2014-04-16 | 美芯晟科技(北京)有限公司 | 退磁检测方法、退磁检测电路及应用该电路的恒流驱动器 |
CN105636303A (zh) * | 2014-11-03 | 2016-06-01 | 华润矽威科技(上海)有限公司 | 一种恒流控制电路及方法 |
CN106992684A (zh) * | 2017-04-25 | 2017-07-28 | 昂宝电子(上海)有限公司 | 反激式电源***及其控制方法 |
Non-Patent Citations (1)
Title |
---|
WU QIANG: "Research of Integrated Method of PSR Flyback Converter with High Precision Constant Current Adaptive Valley Switching and Synchronous Rectifier", CHINESE DOCTORAL DISSERTATIONS FULL-TEXT DATABASE, UNIVERSITY OF CHINESE ACADEMY OF SCIENCES, CN, 1 January 2019 (2019-01-01), CN, XP055827324, ISSN: 1674-022X * |
Cited By (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20230034590A1 (en) * | 2021-07-28 | 2023-02-02 | Shanghai Bright Power Semiconductor Co., Ltd. | Control circuit for constant-current drive circuit and constant-current drive circuit |
US11839002B2 (en) * | 2021-07-28 | 2023-12-05 | Shanghai Bright Power Semiconductor Co., Ltd. | Control circuit for constant-current drive circuit and constant-current drive circuit |
CN114167771A (zh) * | 2021-11-19 | 2022-03-11 | 瀚昕微电子(无锡)有限公司 | 用于ac-dc控制器的输出驱动控制电路 |
CN117240408A (zh) * | 2023-11-10 | 2023-12-15 | 深圳市芯茂微电子有限公司 | 一种应用于隔离电源的通信方法及装置 |
CN117240408B (zh) * | 2023-11-10 | 2024-04-09 | 深圳市芯茂微电子有限公司 | 一种应用于隔离电源的通信方法及装置 |
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