WO2019227863A1 - 永磁同步牵引传动***控制***和方法 - Google Patents

永磁同步牵引传动***控制***和方法 Download PDF

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Publication number
WO2019227863A1
WO2019227863A1 PCT/CN2018/115118 CN2018115118W WO2019227863A1 WO 2019227863 A1 WO2019227863 A1 WO 2019227863A1 CN 2018115118 W CN2018115118 W CN 2018115118W WO 2019227863 A1 WO2019227863 A1 WO 2019227863A1
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Prior art keywords
target
current value
permanent magnet
torque
value
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PCT/CN2018/115118
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English (en)
French (fr)
Inventor
毕京斌
夏猛
曹虎
曾凡飞
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中车青岛四方车辆研究所有限公司
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Application filed by 中车青岛四方车辆研究所有限公司 filed Critical 中车青岛四方车辆研究所有限公司
Priority to JP2020553498A priority Critical patent/JP6964794B2/ja
Priority to EP18920211.2A priority patent/EP3758216B1/en
Priority to RU2020133196A priority patent/RU2740000C1/ru
Publication of WO2019227863A1 publication Critical patent/WO2019227863A1/zh
Priority to US17/027,596 priority patent/US10897218B1/en

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/022—Synchronous motors
    • H02P25/024—Synchronous motors controlled by supply frequency
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/22—Current control, e.g. using a current control loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/0085—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for high speeds, e.g. above nominal speed
    • H02P21/0089—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for high speeds, e.g. above nominal speed using field weakening
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/022—Synchronous motors
    • H02P25/024—Synchronous motors controlled by supply frequency
    • H02P25/026—Synchronous motors controlled by supply frequency thereby detecting the rotor position
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/022—Synchronous motors
    • H02P25/03—Synchronous motors with brushless excitation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H02P27/12—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation pulsing by guiding the flux vector, current vector or voltage vector on a circle or a closed curve, e.g. for direct torque control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H02P27/14—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation with three or more levels of voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2207/00—Indexing scheme relating to controlling arrangements characterised by the type of motor
    • H02P2207/05—Synchronous machines, e.g. with permanent magnets or DC excitation

Definitions

  • the present application relates to the field of traction transmission control, and in particular, to a control system and a control method suitable for a permanent magnet synchronous traction transmission system.
  • the traction drive system is the power system of the train. It consists of two parts: the converter and the motor.
  • the motor completes the conversion from electrical energy to mechanical energy to drive the train.
  • the permanent magnet synchronous traction drive system uses permanent magnet synchronous motors. Compared with asynchronous motors, permanent magnet synchronous motors have the characteristics of high power factor, low heat generation, low noise, and high reliability.
  • the application of urban rail permanent magnet synchronous motors in the traction drive system of rail transit is still in its infancy.
  • In terms of traction motor and traction converter control although there are similarities with asynchronous traction drive system control, there are also many practical problems unique to permanent magnet synchronous motors.
  • the present application addresses the problems of complicated algorithms and low control accuracy of the permanent magnet synchronous motor control in the prior art, and proposes a new type of permanent magnet synchronous traction drive system control method and method.
  • the specific technical solutions are as follows:
  • a control system for a permanent magnet synchronous traction drive system which is used for controlling the permanent magnet synchronous traction drive system.
  • the control system includes a sampling unit and a controller;
  • the sampling unit is connected to a permanent magnet synchronous motor, and includes a current sensor for collecting a running excitation current and a running torque current of the permanent magnet synchronous motor, a voltage sensor for collecting a supporting capacitor voltage of the permanent magnet synchronous motor, and a collecting permanent magnet.
  • Rotary transformer for initial position of rotor and frequency of synchronous motor;
  • the controller includes:
  • Command acquisition unit used to acquire a target torque command issued to the traction drive system
  • MTPA calculation unit used to calculate the target excitation current value and target torque current value according to the target torque command;
  • Adjustment unit including an excitation adjustment unit and a torque adjustment unit, the excitation adjustment unit is configured to generate an excitation current adjustment value according to a target excitation current value and a running excitation current value; and the torque adjustment unit is used to generate a excitation current adjustment value according to a target torque current value And running torque current value to generate torque current adjustment value;
  • Decoupling control unit used to generate the target modulation ratio and modulation frequency according to the excitation current adjustment value and the torque current adjustment value output by the adjustment unit;
  • Segmented synchronous modulation unit According to the target modulation ratio and modulation frequency generated by the decoupling control unit, it outputs a PWM modulation wave control signal to the permanent magnet synchronous motor.
  • the controller further includes a field weakening compensation unit: a compensation signal for generating a target excitation current value and a target torque current value to compensate for both.
  • a field weakening compensation unit a compensation signal for generating a target excitation current value and a target torque current value to compensate for both.
  • the controller further includes an accurate current calculation unit: configured to convert the target excitation current value and the target torque current value into an accurate excitation current value and an accurate torque current value; the excitation adjustment unit adjusts according to the accurate excitation current value Generate an excitation current adjustment value; the torque adjustment unit generates a torque current adjustment value according to the precise torque current adjustment.
  • an accurate current calculation unit configured to convert the target excitation current value and the target torque current value into an accurate excitation current value and an accurate torque current value
  • the excitation adjustment unit adjusts according to the accurate excitation current value Generate an excitation current adjustment value
  • the torque adjustment unit generates a torque current adjustment value according to the precise torque current adjustment.
  • the controller further includes a voltage feedforward unit: acquiring output data of the current accurate calculation unit, and generating target torque compensation data.
  • the application also provides a control method of a permanent magnet synchronous traction drive system, including the following steps:
  • the target modulation ratio and modulation frequency are used to control the permanent magnet synchronous traction motor.
  • the method of converting the target torque command of the traction drive system into the target excitation current value and the target torque current value of the permanent magnet synchronous motor is:
  • T e is the target torque
  • L q is the q-axis equivalent inductance
  • L d is the d-axis equivalent inductance
  • i q is the target torque current value
  • i d is the target excitation current value
  • i s is the target phase current
  • ⁇ f is the motor flux linkage
  • P n is the number of motor pole pairs
  • ⁇ is the motor voltage and current angle difference.
  • the method further includes the following steps: converting the supporting capacitor voltage according to the set target modulation ratio, comparing the supporting capacitor voltage obtained with the sampling, and adjusting the generated torque current compensation amount i q_crr and the excitation current compensation amount i d_crr , respectively, and After the target excitation current value and the target torque current value are synthesized, they are used for subsequent calculations.
  • the method further includes the following steps: performing accurate calculations on the target excitation current value and the target torque current value to obtain the precise motor excitation current value i dtarget and the precise torque current value i qtarget :
  • i dtarget i d + i d_ccr (4)
  • the obtained accurate excitation current value i dtarget and the accurate torque current value i qtarget are used for adjustment calculation.
  • the method further comprises the steps of calculating a voltage compensation value by using an accurate excitation current value i dtarget and an accurate torque current value i qtarget for the calculation of the target modulation ratio:
  • R s is the rotor resistance
  • U d is the d-axis control voltage component
  • U q is the q-axis control voltage component
  • the method for generating the target modulation ratio M is:
  • Fc is the supporting capacitor voltage
  • PID.I dout is the excitation current adjustment output value
  • the method of generating the modulation frequency Fs_out is:
  • PID.I qout is the torque current adjustment output value
  • Fs is the rotor frequency
  • This application proposes a new type of field weakening control algorithm in the control algorithm. By fitting the output voltage and comparing it with the input voltage, the system can operate stably in the field weakening area while improving the field weakening efficiency.
  • the present application proposes an accurate current calculation method.
  • the control accuracy of the field weakening can be improved, and the system performance can be improved under the condition that the inverter capacity is unchanged.
  • Figure 1 is a schematic structural diagram of a permanent magnet synchronous traction drive system
  • FIG. 2 is a simplified structure diagram of the control system described in this application.
  • FIG. 3 is a schematic structural diagram of a control system according to an embodiment of the present application.
  • FIG. 4 is a schematic structural diagram of a control system according to another embodiment of the present application.
  • FIG. 6 is a schematic diagram of decoupling control of the present application.
  • Figure 7 is a schematic diagram of asynchronous SVPWM modulation
  • FIG. 8 is an angular distribution diagram of the synchronous SVPWM switching in the present application 11.
  • 1-sampling unit 101- current sensor; 102- voltage sensor; 103- resolver; 2- controller; 21- instruction acquisition unit; 22- MTPA calculation unit; 23- regulation unit; 231- excitation regulation unit 232-torque adjustment unit; 24-decoupling control unit; 25-segment synchronous modulation unit; 26-accurate current calculation unit; 27-weak field compensation unit; 28-voltage feedforward unit; 3-permanent magnet synchronous motor ; 4-traction converter; 41-IGBT converter module; 42-chopper module; 43-precharge module; 5-three-phase controllable contactor.
  • This application provides a control system for a permanent magnet synchronous traction drive system, which can be used in a train traction system using a permanent magnet synchronous motor as a power, that is, for a permanent magnet synchronous traction drive system (hereinafter referred to as a traction drive system).
  • the main topology of the permanent magnet synchronous traction drive system is shown in Figure 1. It includes traction converter 4 and permanent magnet synchronous motor 3 (PMSM, Permanent Magnet Synchronous Motor).
  • the internal circuit of traction converter 4 includes IGBT converter module 41. , Chopper module 42 and pre-charging module 43, the output end of traction converter 4 is connected to permanent magnet synchronous motor 3 via three-phase controllable contactor 5.
  • the control system includes a sampling unit 1 and a controller 2.
  • FIG. 2 is a simplified schematic diagram of the structure of the control system. In the figure, the traction converter 4 is simplified with a symbol.
  • the control system controls the permanent magnet synchronous traction drive system by controlling the switching pulses of the IGBT converter module 41 in the traction converter 4.
  • the sampling unit 1 is connected to the permanent magnet synchronous motor 3 and includes a current sensor 101 for collecting a running excitation current i d_fed and a running torque current i q_fed of the permanent magnet synchronous motor 3, and a permanent magnet synchronous motor.
  • the current sensor 101, the voltage sensor 102 and the resolver 103 are all connected to the controller 2.
  • the data collected by the sampling unit 1 can be stored therein. When other units need to perform calculations, the corresponding data will be extracted from the collection unit 1. It should be noted that, for the convenience of illustration in FIG. 3 and FIG. 4, only the data reading process of the sampling unit 1 and one of the units is shown, but it is understandable that when other units need to perform calculations, the The corresponding data is extracted in unit 1.
  • FIG. 3 is a schematic structural diagram of the control system, which shows a structural composition of the controller 2.
  • the controller 2 includes:
  • the instruction obtaining unit 21 is used to obtain a target torque instruction issued to the traction drive system;
  • the target torque instruction is an operation instruction to the entire traction drive system, and the control target of the control system is to make the traction drive system stable according to the target torque instruction run;
  • MTPA Maximum Torque Per Ampere calculation unit 22: used to calculate the target excitation current value i d and the target torque current value i q according to the target torque command; the MTPA calculation unit converts the target torque command into a value that can be used by the control system i d and i q current signals, the control system will perform control according to the target current (i d , i q ) and the feedback current (i d_fed , i q_fed ) collected by the sampling unit;
  • the adjustment unit 23 includes an excitation adjustment unit 231 and a torque adjustment unit 232.
  • the excitation adjustment unit 231 is configured to generate an excitation current adjustment value according to the target excitation current value i d and the running excitation current value i d_fed ;
  • the torque adjustment unit 232 is configured to The target torque current value i q and the running torque current value i q_fed generate a torque current adjustment value;
  • the decoupling control unit 24 is configured to generate a target modulation ratio M and a modulation frequency Fs_out according to the excitation current adjustment value and the torque current adjustment value output by the adjustment unit 23.
  • Segmented synchronous modulation unit 25 outputs a PWM (Pulse Width Modulation) modulation wave control signal for the permanent magnet synchronous motor 3 based on the target modulation ratio M and the modulation frequency Fs_out generated by the decoupling control unit 24.
  • PWM Pulse Width Modulation
  • control system can complete a tracking control of the permanent magnet synchronous motor 3 according to the torque command.
  • the controller 2 further includes a current accurate calculation unit 26: for converting the target excitation current value i d and the target torque current value i q generated by the MTPA calculation unit 22 into accurate values Excitation current value and precise torque current value; the current is calibrated through accurate current calculation, which can further improve the control accuracy.
  • the excitation adjustment unit 231 adjusts and generates the excitation current adjustment value according to the precise excitation current value; the torque adjustment unit 232 adjusts and generates the torque current adjustment value according to the accurate torque current value.
  • the controller 2 further includes a field weakening compensation unit 27: for generating a compensation signal of the target excitation current value i d and the target torque current value i q to compensate the two.
  • the field weakening compensation unit 27 receives the signal output from the decoupling control unit 24 and the support capacitor voltage Fc signal, generates a current compensation value, and transmits it to the output of the MTPA calculation unit 22.
  • the current accurate calculation unit 26 will calculate the output value of the MTPA calculation unit 22
  • the combination with the compensation value fed back by the field weakening compensation unit 27 is used for accurate current calculation.
  • the accurate current calculation unit 26 and the field weakening compensation unit 27 cooperate with each other to realize an accurate calculation of the current. That is, the field weakening compensation unit 27 receives the signal output from the decoupling control unit 24 and the support capacitor voltage Fc collected by the acquisition unit 1 to generate compensation values of the target exciting current value current i d and the target torque current value i q , respectively. Further, the compensation value is passed to the current accurate calculation unit 26, and the current accurate calculation unit 26 will perform accurate current calculation based on i d and i q output from the MTPA calculation unit 22 and the compensation value output from the field weakening compensation unit 27.
  • the controller further includes a voltage feedforward unit 28: acquiring output data of the current accurate calculation unit 26, and generating target torque compensation data. The compensation data is fed back to the decoupling control unit 24 for calculation of the modulation ratio.
  • the present application also provides a control method of a permanent magnet synchronous traction drive system, which is divided into the following two embodiments according to whether or not accurate calculation of current is performed.
  • the target torque command of the traction drive system is converted into a target exciting current value i d and a target torque current value i q .
  • the command obtained by the traction drive system is a target torque command, which is converted by the MTPA calculation unit 22 into a target excitation current value i d and a target torque current value i q of the permanent magnet synchronous motor 3, and the specific conversion method is:
  • T e is the target torque
  • L q is the q-axis equivalent inductance
  • L d is the d-axis equivalent inductance
  • i d is the target exciting current value
  • i q is the target torque current value
  • i s is the target phase current
  • ⁇ f is the motor flux linkage
  • P n is the number of motor pole pairs
  • ⁇ is the motor voltage and current angle difference.
  • the target excitation current value i d and the target torque current value i q obtained by the MTPA calculation unit 22 are transferred to the adjustment unit 23 for current adjustment calculation.
  • the excitation adjustment unit 231 generates an excitation current adjustment value PID.I dout according to the target excitation current value i d and the running excitation current value i d_fed ; the torque adjustment unit generates a rotation according to the target torque current value i q and the running torque current value i q_fed Torque current adjustment value PID.I qout .
  • the excitation current adjustment value and the torque current adjustment value will be used for decoupling control to generate the target modulation ratio and modulation frequency.
  • the adjustment unit 23 adopts a PID (Proportion Integration Integration) adjustment calculation method, which is a well-known calculation method, and is not described herein again.
  • PID Proportion Integration Integration
  • the target excitation current value i d and the target torque current value i q are transmitted to the voltage pre-feedback unit 28 to calculate a voltage compensation value, that is, the aforementioned target torque compensation data.
  • the specific calculation method is as follows:
  • R s is the rotor resistance
  • U d is the d-axis control voltage component
  • U q is the q-axis control voltage component
  • the voltage feedforward unit 28 outputs U d and U q to the decoupling control unit 24, and the adjustment unit 23 outputs the generated excitation current adjustment value PID.I dout and the torque current adjustment value PID.I qout to the solution.
  • the decoupling control unit 24 generates a target modulation ratio M and a modulation frequency Fs_out by the decoupling control unit 24.
  • the method of generating the target modulation ratio M is:
  • Fc is a supporting capacitor voltage
  • PID.I dout is an excitation current adjustment output value, which is generated by the torque adjustment unit 232.
  • the method of generating the modulation frequency Fs_out is:
  • PID.I qout is a torque current adjustment output value, which is generated by the excitation adjustment unit 231, and Fs is a rotor frequency collected by the sampling unit 1.
  • the decoupling control unit 24 finally completes the combination of the modulation ratio M and the modulation frequency Fs_out.
  • the segmented synchronous modulation unit generates a PWM modulation wave according to the target modulation ratio M and the modulation frequency Fs_out, and is used for the control of the permanent magnet synchronous traction motor 3.
  • the asynchronous SVPWM modulation program receives M and Fs_out information, and generates a three-phase (u, v, w) pulse by determining the sector where the voltage vector is located.
  • the target modulation ratio used in this embodiment is 0.906, and the modulation of the synchronous 11-division SVPWM (Basic Boundary Clamping Strategy) segment modulation module is switched to 11 pulses after the modulation degree is greater than 0.906.
  • the 4 pulses disappear symmetrically and become 7 pulses; the modulation degree further increases, and the two pulses disappearing symmetrically become 5 pulses; when the modulation degree is greater than 1, it becomes a square wave single pulse.
  • 30Hz-40Hz is the 11th-frequency synchronous modulation I, and each modulation cycle enters 30 interrupts; above 40Hz until the square wave is the 11th-frequency synchronous modulation II, each modulation cycle enters 15 interruptions; enter After passing through the modulation area, the number of pulses decreases symmetrically as the modulation degree increases. When the modulation degree is greater than 1, it becomes a square wave single pulse.
  • the pulse width can be derived throughout the cycle, and then the IGBT converter module is turned on and off.
  • the angle calculation formula is as follows:
  • the control method of the permanent magnet synchronous traction drive system of this embodiment includes accurate current calculation, and specifically includes the following steps:
  • step (1) Control the conversion of target quantity. Same as step (1) in the first embodiment.
  • the support capacitor voltage F c1 is converted according to the set target modulation ratio Mt, and after comparing with the support capacitor voltage Fc obtained by sampling, the generated torque current compensation amount i q_crr and the excitation current compensation amount i d_crr are adjusted respectively with the target.
  • the torque current value i q and the target exciting current value i d are added and combined for accurate current calculation.
  • the principle of the field weakening control of the field weakening compensation unit 27 is shown in FIG. 5.
  • the field weakening control unit 27 uses an accurate voltage compensation amount, with the modulation ratio as the final control target, and generates a compensation amount corresponding to the compensation amounts of i d and i q .
  • Mt is the target modulation ratio for the field weakening control (it can be understood as the modulation ratio expected from the output of the system to the segment synchronous modulation unit 25.
  • the feedback formula F c1 is calculated as:
  • U q and U d are the output results of the voltage feedforward unit
  • PID.Idout is the d-axis PID adjustment output result, that is, the result output by the torque modulation unit 232.
  • F c1 is calculated using the set target modulation ratio Mt.
  • the method of accurate current calculation is:
  • the target excitation current value i d and the target torque current value i q are accurately calculated to obtain the motor's precise excitation current value i dtarget and the precise torque current value i qtarget :
  • i dtarget i d + i d_ccr (4)
  • the decoupling control unit 24 outputs the calculated Us and PID.Idout to the field weakening compensation control unit 27.
  • the field weakening compensation control unit 27 converts the supporting capacitor voltage F c1 according to the set target modulation ratio Mt After comparing with the support capacitor voltage Fc obtained by sampling, the generated torque current compensation amount i q_crr and the excitation current compensation amount i d_crr are adjusted and output to the current accurate calculation unit 26, which are respectively calculated and generated by the MTPA calculation unit 22 The moment current value i q and the target excitation current value i d are added and combined for accurate current calculation.
  • the adjustment calculation method of the torque current compensation amount i q_crr and the excitation current compensation amount i d_crr may adopt a PID adjustment calculation method, and details are not described herein again.
  • the obtained precise excitation current value i dtarget and accurate torque current value i qtarget of the motor are used for adjustment calculation.
  • a PID adjustment method is adopted.
  • the excitation adjustment unit 231 generates the excitation current adjustment value PID.I dout according to the precise excitation current value i dtarget and the running excitation current value i d_fed ; the torque adjustment unit 232 generates the accurate torque current value i qtarget and the running torque current value i q_fed The torque current adjustment value PID.I qout ; the excitation current adjustment value PID.I dout and the torque current adjustment value PID.I qout will be used for decoupling control to generate the target modulation ratio and modulation frequency.
  • the target excitation current value and the target torque current value are decoupled, a target modulation ratio is generated according to the target excitation current value, and a modulation frequency is generated according to the target torque current value.
  • this embodiment uses the precise excitation current value i dtarget and the precise torque current value i qtarget to calculate the voltage compensation value, which is used for the compensation calculation of the target modulation ratio:
  • R s is the rotor resistance
  • U d is the d-axis control voltage component
  • U q is the q-axis control voltage component
  • the method for generating the target modulation ratio and the modulation frequency is the same as step (3.2) in Embodiment 1, and is not repeated here.
  • this embodiment uses accurate current calculation. At the most initial time, that is, the starting time, each data is basically 0. After starting, the initial target exciting current value i d and the target rotation are obtained by calculating the torque command. The moment current value i q , because there is no running data at this time, accurate calculation cannot be performed. Therefore, the target excitation current value i d and the target torque current value i q are decoupled and calculated by the adjustment unit to output a PWM signal to start the traction drive system. Then, after the acquisition unit 1 collects the corresponding operating data, the entire control system starts to operate normally to achieve precise control.
  • the switching frequency of the system can be reduced, the system efficiency can be improved, and the dynamic response speed and stability of the system can be improved.

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Abstract

一种永磁同步牵引传动***控制***和方法。控制***包括采样单元和控制器；采样单元采集永磁同步电机运行励磁电流和运行转矩电流、支撑电容电压及转子频率的旋转变压器；控制器获取对牵引传动***下达的目标转矩指令，计算目标励磁电流值和目标转矩电流值，生成励磁电流调节值和转矩电流调节值；转矩调节单元用于根据目标转矩电流值和运行转矩电流值生成转矩电流调节值，并根据调节单元输出的励磁电流调节值和转矩电流调节值生成目标调制比与调制频率，最终输出对永磁同步电机的PWM调制波控制信号。该控制方法，采用新型SVPWM脉冲控制方法，来进一步降低开关频率，提高***效率，并实现在较低开关频率***中的稳定运行。

Description

永磁同步牵引传动***控制***和方法 技术领域
本申请涉及牵引传动控制领域，尤其涉及一种适用于永磁同步牵引传动***的控制***和控制方法。
背景技术
牵引传动***是列车的动力***，由变流器和电机两大部分组成，电机完成电能到机械能的转变，带动列车行驶。
永磁同步牵引传动***采用的为永磁同步电机，永磁同步电机较异步电机相比，具有功率因数高、发热小、噪声小、可靠性高等特点。城轨永磁同步电机在轨道交通牵引传动***中的应用尚处于起步阶段。永磁同步牵引传动***的控制中存在大量技术问题需要进一步研究。在牵引电机与牵引变流器控制方面，虽与异步牵引传动***控制有相通之处，但也存在许多永磁同步电机特有的实际问题。
目前现有的城轨永磁同步电机控制算法，其多采用异步SVPWM(Space Vector Pulse Width Modulation)运行，其在高转速情况下，为满足输出电流谐波要求，其IGBT(Insulated Gate Bipolar Transistor)开关频率大大增加，输出损耗提高，同时为满足散热要求造成硬件成本增加。
由于永磁同步电机是永磁体励磁，弱磁范围较窄，弱磁难度较大。较好的弱磁控制技术可在逆变器容量不变的情况下大幅提高***性能。目前众多弱磁方案，其算法复杂，同时弱磁效率低，效果差。
发明内容
本申请针对现有技术中，永磁同步电机控制存在的算法复杂、控制精度低等问题，提出一种新型的永磁同步牵引传动***的控制***和方法。具体技术方案如下：
一种永磁同步牵引传动***控制***，用于永磁同步牵引传动***的控制，所述控制***包括采样单元和控制器；
所述采样单元与永磁同步电机连接，包括用于采集永磁同步电机运行励磁电流和运行转矩电流的电流传感器、用于采集永磁同步电机支撑电容电压的电压传感器、用于采集永磁同步电机转子初始位置及转子频率的旋转变压器；
所述控制器包括：
指令获取单元：用于获取对牵引传动***下达的目标转矩指令；
MTPA计算单元：用于根据目标转矩指令，计算目标励磁电流值和目标转矩电流值；
调节单元：包括励磁调节单元和转矩调节单元，所述励磁调节单元用于根据目标励磁电流值和运行励磁电流值生成励磁电流调节值；所述转矩调节单元用于根据目标转矩电流值和运行转矩电流值生成转矩电流调节值；
解耦控制单元：用于根据调节单元输出的励磁电流调节值和转矩电流调节值生成目标调制比与调制频率；
分段同步调制单元：根据解耦控制单元生成的目标调制比和调制频率，输出对永磁同步电机的PWM调制波控制信号。
优选的是，所述控制器进一步包括弱磁补偿单元：用于生成目标励磁电流值和目标转矩电流值的补偿信号以对二者进行补偿。
优选的是，控制器进一步包括电流精确计算单元：用于将目标励磁电流值和目标转矩电流值换算为精确励磁电流值和精确转矩电流值；所述励磁调节单元根据精确励磁电流值调节生成励磁电流调节值；所述转矩调节单元根据精确转矩电流值调节生成转矩电流调节值。
优选的是，控制器进一步包括电压前馈单元：获取电流精确计算单元的输出数据，并生成目标转矩补偿数据。
本申请还提供了一种永磁同步牵引传动***控制方法，包括以下步骤：
将牵引传动***的目标转矩指令转化为目标励磁电流值和目标转矩电流值；
将目标励磁电流值和目标转矩电流值进行调节计算；
将目标励磁电流值和目标转矩电流值进行解耦，根据目标励磁电流值生成目标调制比，根据目标转矩电流值生成调制频率；
将目标调制比和调制频率用于永磁同步牵引电机的控制。
优选的是，将牵引传动***的目标转矩指令转化为永磁同步电机的目标励磁电流值和目标转矩电流值的方法为：
根据：
Figure PCTCN2018115118-appb-000001
Figure PCTCN2018115118-appb-000002
将以上两式联立，求解目标励磁电流值和目标转矩电流值；
其中T e为目标转矩，L q为q轴等效电感，L d为d轴等效电感，i q为目标转矩电流值，i d为目标励磁电流值，i s为目标相电流，ψ f为电机磁链，P n为电机极对数，φ为电机电压电流角度差。
优选的是，进一步包括以下步骤：根据设定目标调制比折算支撑电容电压，与采样获得的支撑电容电压进行比较后，调节生成转矩电流补偿量i q_crr和励磁电流补偿量i d_crr，分别与目标励磁电流值和目标转矩电流值合成后，用于后续计算。
优选的是，进一步包括以下步骤：对目标励磁电流值和目标转矩电流值进行精确计算，以获得电机精确励磁电流值i dtarget和精确转矩电流值i qtarget：
Figure PCTCN2018115118-appb-000003
i dtarget＝i d+i d_ccr  (4)
将获得的精确励磁电流值i dtarget和精确转矩电流值i qtarget用于调节计算。
优选的是，进一步包括以下步骤，采用精确励磁电流值i dtarget和精确转矩电流值i qtarget计算电压补偿值，用于目标调制比的补偿计算：
Figure PCTCN2018115118-appb-000004
其中R s为转子电阻，ω r角速度,U d为d轴控制电压分量，U q为q轴控制电压分量。
优选的是，生成目标调制比M的方法为：
Figure PCTCN2018115118-appb-000005
Figure PCTCN2018115118-appb-000006
其中，Fc为支撑电容电压，PID.I dout为励磁电流调节输出值；
生成调制频率Fs_out的方法为：
Fs_out＝(1+PID.I qout)*F s  (8)
其中，PID.I qout为转矩电流调节输出值，Fs为转子频率。
与现有技术相比，本申请的优点和积极效果在于：
(1)本申请提供的永磁同步牵引传动***的控制方法，通过对永磁同步电机输出特性及反电动势的进一步研究，采用新型SVPWM脉冲控制方法，来进一步降低开关频率，降低变流器的开关损耗，提高***效率，并实现在较低开关频率***中的稳定运行。
(2)本申请在控制算法中提出了一种新型的弱磁控制算法，通过拟合输出电压，并与输入电压进行比较，使***在弱磁区域稳定运行同时提高弱磁效率。
(3)本申请提出了电流精确计算方法，通过精确电流单元及弱磁单元配合，可以提高弱磁的控制精度，并在逆变器容量不变的情况系下，提高***性能。
附图说明
图1为永磁同步牵引传动***结构示意图；
图2为本申请所述控制***的结构简化示意图
图3为本申请一种实施方式所述控制***的结构示意图；
图4为本申请另一种实施方式所述控制***的结构示意图；
图5为本申请弱磁控制原理图；
图6为本申请解耦控制原理图；
图7为异步SVPWM调制原理图；
图8为本申请11分配同步SVPWM开关角分布图。
图中：1-采样单元；101-电流传感器；102-电压传感器；103-旋转变压器；2-控制器；21-指令获取单元；22-MTPA计算单元；23-调节单元；231-励磁调节单元；232-转矩调节单元；24-解耦控制单元；25-分段同步调制单元；26-电流精确计算单元；27-弱磁补偿单元；28-电压前馈单元；3-永磁同步电机；4-牵引变流器；41-IGBT变流模块；42-斩波模块；43-预充电模块；5-三相可控接触器。
具体实施方式
以下，结合附图对本申请的具体实施方式进行进一步的描述。
本申请提供了一种永磁同步牵引传动***的控制***，可以用于采用永磁同步电机作为动力的列车牵引***，即用于永磁同步牵引传动***(以下简称牵引传动***)。
永磁同步牵引传动***的主拓扑结构如图1所示，包括牵引变流器4及永磁同步电机3(PMSM,Permanent Magnet Synchronous Motor)，牵引变流器4内部电路包括IGBT变流模块41、斩波模块42和预充电模块43，牵引变流器4的输出端经三相可控接触器5与永磁同步电机3连接。
所述控制***包括采样单元1和控制器2。图2为所述控制***的结构简化示意图。图中牵引变流器4用符号简化表示。控制***通过控制牵引变流器4中IGBT变流模块41的开关脉冲，实现对永磁同步牵引传动***的控制。
如图2所示，采样单元1与永磁同步电机3连接，包括用于采集永磁同步电机3运行励磁电流i d_fed和运行转矩电流i q_fed的电流传感器101、用于采集永 磁同步电机3支撑电容电压Fc的电压传感器102、用于采集永磁同步电机3转子初始位置Theta及转子频率Fs的旋转变压器103；采样单元采集的以上数据将被传递至控制器2。
所述电流传感器101、电压传感器102及旋转变压器103均与控制器2连接。
采样单元1所采集的数据可保存于其中，当其它单元需要进行计算时，会从采集单元1中提取相应的数据。需要说明的是，图3、图4中为了便于表示，仅示出采样单元1与其中一个单元的数据读取过程，但可以理解的是，当其它单元需要进行计算时，同样也可以从采样单元1中提取相应的数据。
图3为所述控制***的结构示意图，其示出了所述控制器2的结构组成。所述控制器2包括：
指令获取单元21：用于获取对牵引传动***下达的目标转矩指令；目标转矩指令是对整个牵引传动***的运行指令，控制***的控制目标是使牵引传动***可按目标转矩指令稳定运行；
MTPA(Maximum Torque Per Ampere)计算单元22：用于根据目标转矩指令，计算目标励磁电流值i d和目标转矩电流值i q；MTPA计算单元将目标转矩指令转化为控制***可以使用的i d和i q电流信号，控制***将根据目标电流(i d、i q)和采样单元采集的反馈电流(i d_fed、i q_fed)执行控制；
调节单元23：包括励磁调节单元231和转矩调节单元232，励磁调节单元231用于根据目标励磁电流值i d和运行励磁电流值i d_fed生成励磁电流调节值；转矩调节单元232用于根据目标转矩电流值i q和运行转矩电流值i q_fed生成转矩电流调节值；
解耦控制单元24：用于根据调节单元23输出的励磁电流调节值和转矩电流调节值生成目标调制比M与调制频率Fs_out。
分段同步调制单元25：根据解耦控制单元24生成的目标调制比M和调制频率Fs_out，输出对永磁同步电机3的PWM(Pulse Width Modulation)调制 波控制信号。
基于以上结构，控制***可完成对永磁同步电机3根据转矩指令的一个跟踪控制。
作为控制***结构的进一步优化，参考图4，控制器2进一步包括电流精确计算单元26：用于将MTPA计算单元22计算生成的目标励磁电流值i d和目标转矩电流值i q换算为精确励磁电流值和精确转矩电流值；通过电流精确计算对电流进行校准，进而可进一步提高控制的精度。此时，励磁调节单元231根据精确励磁电流值调节生成励磁电流调节值；转矩调节单元232根据精确转矩电流值调节生成转矩电流调节值。
作为控制***的进一步优化，参考图4，控制器2进一步包括弱磁补偿单元27：用于生成目标励磁电流值i d和目标转矩电流值i q的补偿信号以对二者进行补偿。弱磁补偿单元27接收解耦控制单元24输出的信号以及支撑电容电压Fc信号，生成电流补偿值，传递至MTPA计算单元22的输出端，电流精确计算单元26将根据MTPA计算单元22的输出值和弱磁补偿单元27反馈的补偿值的结合，用于电流精确计算。
可以理解的是，电流精确计算单元26与弱磁补偿单元27相互配合实现电流的精确计算。也就是说，弱磁补偿单元27接收解耦控制单元24输出的信号以及采集单元1采集的支撑电容电压Fc，分别生成目标励磁电流值电流i d和目标转矩电流值i q的补偿值，进一步地，将补偿值传递至电流精确计算单元26，电流精确计算单元26将根据MTPA计算单元22输出的i d和i q以及弱磁补偿单元27输出的补偿值，进行电流的精确计算。
作为控制***的进一步优化，控制器进一步包括电压前馈单元28：获取电流精确计算单元26的输出数据，并生成目标转矩补偿数据。该补偿数据将反馈至解耦控制单元24，用于调制比的计算。
本申请还提供了一种永磁同步牵引传动***控制方法，根据是否进行电流精确计算，分为以下两种实施方式。
实施例1
本实施例的永磁同步牵引传动***控制方法，包括以下步骤：
(1)控制目标量的转化。
将牵引传动***的目标转矩指令转化为目标励磁电流值i d和目标转矩电流值i q。
牵引传动***获得的指令为目标转矩指令，该指令经MTPA计算单元22换算成为永磁同步电机3的目标励磁电流值i d和目标转矩电流值i q，具体的换算方法为：
根据：
Figure PCTCN2018115118-appb-000007
Figure PCTCN2018115118-appb-000008
将以上两式联立，求解目标励磁电流值i d和目标转矩电流值i q；
其中T e为目标转矩，L q为q轴等效电感，L d为d轴等效电感，i d为目标励磁电流值，i q为目标转矩电流值，i s为目标相电流，ψ f为电机磁链，P n为电机极对数，φ为电机电压电流角度差。
(2)将目标励磁电流值和目标转矩电流值进行调节计算
将MTPA计算单元22计算获得的目标励磁电流值i d和目标转矩电流值i q传递到调节单元23进行电流的调节计算。励磁调节单元231根据目标励磁电流值i d和运行励磁电流值i d_fed生成励磁电流调节值PID.I dout；转矩调节单元根据目标转矩电流值i q和运行转矩电流值i q_fed生成转矩电流调节值PID.I qout。励磁电流调节值和转矩电流调节值将用于解耦控制，生成目标调制比和调制频率。
本实施例中调节单元23采用的是PID(Proportion Integration Differentiation)调节计算方法，其为公知的计算方法，此处不再赘述。
(3)将目标励磁电流值和目标转矩电流值进行解耦，根据目标励磁电流值生成目标调制比，根据目标转矩电流值生成调制频率。
(3.1)计算电压补偿值
将目标励磁电流值i d和目标转矩电流值i q传递到电压前反馈单元28计算电压补偿值，即前述目标转矩补偿数据。具体计算方法如下：
Figure PCTCN2018115118-appb-000009
其中R s为转子电阻，ω r角速度,U d为d轴控制电压分量，U q为q轴控制电压分量。
(3.2)生成目标调制比和调制频率
参见图6，电压前馈单元28将U d和U q输出到解耦控制单元24，调节单元23将生成的励磁电流调节值PID.I dout和转矩电流调节值PID.I qout输出到解耦控制单元24，由解耦控制单元24生成目标调制比M和调制频率Fs_out。
生成目标调制比M的方法为：
Figure PCTCN2018115118-appb-000010
Figure PCTCN2018115118-appb-000011
其中，Fc为支撑电容电压，PID.I dout为励磁电流调节输出值，由所述转矩调节单元232生成。
生成调制频率Fs_out的方法为：
F s_out＝(1+PID.I qout)*F s  (8)
其中，PID.I qout为转矩电流调节输出值，由所述励磁调节单元231生成，Fs为采样单元1采集的转子频率。
解耦控制单元24最终完成调制比M与调制频率Fs_out的合成。
(4)分段同步调制。
分段同步调制单元根据目标调制比M和调制频率Fs_out生成PWM调制波，用于永磁同步牵引电机3的控制。
异步SVPWM调制程序接收M、Fs_out信息，通过判断电压矢量所在扇区来产生三相(u,v,w)脉冲。
参考图7，本实施例采用的目标调制比为0.906，同步11分频SVPWM调制(Basic Boundary Clamping Strategy策略)分段调制模块的调制切换为当调制度大于0.906进入过调制区后，11脉冲中的4个脉冲对称消失，变为7脉冲；调制度进一步增大，对称消失两个脉冲变为5脉冲；当调制度大于1则变为方波单脉冲。
如上图所示，其中30Hz-40Hz为11分频同步调制I，每个调制周期进入30次中断；40Hz以上一直到方波为11分频同步调制II，每个调制周期进入15次中断；进入过调制区后，脉冲数随调制度增大而对称减小，当调制度大于1则变为方波单脉冲。
如图8所示，采用30中断时11分频同步SVPWM的A相脉冲，我们可以根据每个扇区对应的比较值推导出在1/4周期内的五个开关角α1、α2、α3、α4、α5。
根据同步SVPWM的特性(1/2周期对称，1/4周期反对称)可以推导出整个周期内脉冲宽度，进而控制IGBT变流模块的开通和切断。其中角度计算公式如下：
Figure PCTCN2018115118-appb-000012
实施例2
本实施例的永磁同步牵引传动***控制方法，包括电流精确计算，具体包括以下步骤：
(1)控制目标量的转化。同实施例1中第(1)步。
(2)电流精确计算。
更进一步的，根据设定目标调制比Mt折算支撑电容电压F c1，与采样获得的支撑电容电压Fc进行比较后，调节生成转矩电流补偿量i q_crr和励磁电流补偿量i d_crr，分别与目标转矩电流值i q和目标励磁电流值i d相加合成后，用于电流精确计算。
弱磁补偿单元27的弱磁控制的原理如图5所示。弱磁控制单元27使用精确电压补偿量，以调制比作为最终控制目标，生成i d,i q的补偿量对应的补偿量。
其中Mt为弱磁控制设定目标调制比(可以理解为本***期望的输出到分段同步调制单元25的调制比，这个单元目的是为了让解耦控制单元24最终的输出M＝Mt)，其取值范围为0-1，经验取值范围为0.88-0.91.其中反馈量F c1计算公式为：
Figure PCTCN2018115118-appb-000013
其中U q，U d为电压前馈单元的输出结果，PID.Idout为d轴PID调节输出结果，即转矩调制单元232输出的结果。采用设定的目标调制比Mt进行F c1的计算。
电流精确计算的方法为：
对目标励磁电流值i d和目标转矩电流值i q进行精确计算，以获得电机精确励磁电流值i dtarget和精确转矩电流值i qtarget：
Figure PCTCN2018115118-appb-000014
i dtarget＝i d+i d_ccr  (4)
以上过程可以理解的是，解耦控制单元24将计算获得的Us及PID.Idout输出到弱磁补偿控制单元27，弱磁补偿控制单元27根据设定的目标调制比Mt折算支撑电容电压F c1，与采样获得的支撑电容电压Fc进行比较后，调节生成转矩电流补偿量i q_crr和励磁电流补偿量i d_crr，并且输出到电流精确计算单元26， 分别与MTPA计算单元22计算生成的目标转矩电流值i q和目标励磁电流值i d相加合成后，用于电流精确计算。
其中，转矩电流补偿量i q_crr和励磁电流补偿量i d_crr的调节计算方法可采用PID调节计算方法，此处不再赘述。
(3)将精确励磁电流值和精确转矩电流值的调节计算。
将获得的电机精确励磁电流值i dtarget和精确转矩电流值i qtarget用于调节计算。本实施例中，采用的为PID调节方法。
励磁调节单元231根据精确励磁电流值i dtarget和运行励磁电流值i d_fed生成励磁电流调节值PID.I dout；转矩调节单元232根据精确转矩电流值i qtarget和运行转矩电流值i q_fed生成转矩电流调节值PID.I qout；励磁电流调节值PID.I dout和转矩电流调节值PID.I qout将用于解耦控制，生成目标调制比和调制频率。
(4)生成目标调制比和调制频率。
参考图6，将目标励磁电流值和目标转矩电流值进行解耦，根据目标励磁电流值生成目标调制比，根据目标转矩电流值生成调制频率。
为了进一步提高调制比的计算精度，本实施例采用精确励磁电流值i dtarget和精确转矩电流值i qtarget计算电压补偿值，用于目标调制比的补偿计算：
Figure PCTCN2018115118-appb-000015
其中R s为转子电阻，ω r角速度,U d为d轴控制电压分量，U q为q轴控制电压分量。
目标调制比和调制频率的生成方法同实施例1中步骤(3.2)，此处不再赘述。
(5)分段同步调制。同实施例1步骤(4)，此处不再赘述。
需要说明的是，本实施例采用电流精确计算，在最初始时刻，即启动时刻，各数据基本都是0，启动后通过对转矩指令的计算获得初始的目标励磁电流值 i d和目标转矩电流值i q，由于此时还不存在运行数据，无法进行精确计算，因此目标励磁电流值i d和目标转矩电流值i q经过调节单元进行解耦计算后输出PWM信号启动牵引传动***，随后采集单元1采集到相应的运行数据后，整个控制***开始正常运转，实现精准控制。
采用本申请所述的方法用于永磁牵引传动***的控制，可以降低***开关频率，提高***效率，提高***动态响应速度和稳定性。
以上所述，仅是本申请的较佳实施例而已，并非是对本申请作其它形式的限制，任何熟悉本专业的技术人员可能利用上述揭示的技术内容加以变更或改型为等同变化的等效实施例应用于其它领域，但是凡是未脱离本申请技术方案内容，依据本申请的技术实质对以上实施例所作的任何简单修改、等同变化与改型，仍属于本申请技术方案的保护范围。

Claims (10)

  1. 一种永磁同步牵引传动***控制***，用于永磁同步牵引传动***的控制，其特征在于，所述控制***包括采样单元和控制器；
    所述采样单元与永磁同步电机连接，包括用于采集永磁同步电机运行励磁电流和运行转矩电流的电流传感器、用于采集永磁同步电机支撑电容电压的电压传感器、用于采集永磁同步电机转子初始位置及转子频率的旋转变压器；
    所述控制器包括：
    指令获取单元：用于获取对牵引传动***下达的目标转矩指令；
    MTPA(Maximum Torque Per Ampere)计算单元：用于根据目标转矩指令，计算目标励磁电流值和目标转矩电流值；
    调节单元：包括励磁调节单元和转矩调节单元，所述励磁调节单元用于根据目标励磁电流值和运行励磁电流值生成励磁电流调节值；所述转矩调节单元用于根据目标转矩电流值和运行转矩电流值生成转矩电流调节值；
    解耦控制单元：用于根据调节单元输出的励磁电流调节值和转矩电流调节值生成目标调制比与调制频率；
    分段同步调制单元：根据解耦控制单元生成的目标调制比和调制频率，输出对永磁同步电机的PWM(Pulse Width Modulation)调制波控制信号。
  2. 如权利要求1所述的永磁同步牵引传动***控制***，其特征在于：所述控制器进一步包括弱磁补偿单元：用于生成目标励磁电流值和目标转矩电流值的补偿信号以对二者进行补偿。
  3. 如权利要求1或2所述的永磁同步牵引传动***控制***，其特征在于：所述控制器进一步包括电流精确计算单元：用于将目标励磁电流值和目标转矩电流值换算为精确励磁电流值和精确转矩电流值；所述励磁调节单元根据精确励磁电流值调节生成励磁电流调节值；所述转矩调节单元根据精确转矩电流值调节生成转矩电流调节值。
  4. 如权利要求3所述的永磁同步牵引传动***控制***，其特征在于： 所述控制器进一步包括电压前馈单元：获取电流精确计算单元的输出数据，并生成目标转矩补偿数据。
  5. 一种永磁同步牵引传动***控制方法，其特征在于，包括以下步骤：
    将牵引传动***的目标转矩指令转化为目标励磁电流值和目标转矩电流值；
    将目标励磁电流值和目标转矩电流值进行调节计算；
    将目标励磁电流值和目标转矩电流值进行解耦，根据目标励磁电流值生成目标调制比，根据目标转矩电流值生成调制频率；
    将目标调制比和调制频率用于永磁同步牵引电机的控制。
  6. 如权利要求5所述的永磁同步牵引传动***控制方法，其特征在于：将牵引传动***的目标转矩指令转化为永磁同步电机的目标励磁电流值和目标转矩电流值的方法为：
    根据：
    Figure PCTCN2018115118-appb-100001
    Figure PCTCN2018115118-appb-100002
    将以上两式联立，求解目标励磁电流值和目标转矩电流值；
    其中T e为目标转矩，L q为q轴等效电感，L d为d轴等效电感，i q为目标转矩电流值，i d为目标励磁电流值，i s为目标相电流，ψ f为电机磁链，P n为电机极对数，φ为电机电压电流角度差。
  7. 如权利要求6所述的永磁同步牵引传动***控制方法，其特征在于，进一步包括以下步骤：根据设定目标调制比折算支撑电容电压，与采样获得的支撑电容电压进行比较后，调节生成转矩电流补偿量i q_crr和励磁电流补偿量i d_crr，分别与目标转矩电流值和目标励磁电流值合成后，用于后续计算。
  8. 如权利要求7所述的永磁同步牵引传动***控制方法，其特征在于，进一步包括以下步骤：对目标励磁电流值和目标转矩电流值进行精确计算，以获得电机精确励磁电流值i dtarget和精确转矩电流值i qtarget：
    Figure PCTCN2018115118-appb-100003
    i dtarget＝i d+i d_ccr                  (4)
    将获得的精确励磁电流值i dtarget和精确转矩电流值i qtarget用于调节计算。
  9. 如权利要求7所述的永磁同步牵引传动***控制方法，其特征在于，进一步包括以下步骤，采用精确励磁电流值i dtarget和精确转矩电流值i qtarget计算电压补偿值，用于目标调制比的补偿计算：
    Figure PCTCN2018115118-appb-100004
    其中R s为转子电阻，ω r角速度,U d为d轴控制电压分量，U q为q轴控制电压分量。
  10. 如权利要求9所述的永磁同步牵引传动***控制方法，其特征在于：
    生成目标调制比M的方法为：
    Figure PCTCN2018115118-appb-100005
    Figure PCTCN2018115118-appb-100006
    其中，Fc为支撑电容电压，PID.I dout为励磁电流调节输出值；
    生成调制频率Fs_out的方法为：
    Fs_out＝(1+PID.I qout)*Fs               (8)
    其中，PID.I qout为转矩电流调节输出值，Fs为转子频率。
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