WO2016180058A1 - Lte-a dual-codebook precoding selection method based on beam operation and group mean - Google Patents

Lte-a dual-codebook precoding selection method based on beam operation and group mean Download PDF

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WO2016180058A1
WO2016180058A1 PCT/CN2016/073259 CN2016073259W WO2016180058A1 WO 2016180058 A1 WO2016180058 A1 WO 2016180058A1 CN 2016073259 W CN2016073259 W CN 2016073259W WO 2016180058 A1 WO2016180058 A1 WO 2016180058A1
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channel
phase modulation
mutual information
subcarriers
matrix
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衡伟
胡津铭
朱云帆
陈雪倩
张清华
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东南大学
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H04B7/0478—Special codebook structures directed to feedback optimisation

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  • the invention belongs to the field of wireless communication technologies, and relates to an LTE-A 8 antenna spatial multiplexing dual codebook precoding selection algorithm, in particular to a LTE-A dual codebook precoding selection method based on beam operation and packet averaging.
  • the 3GPP LTE-A (LTE-Advanced) project is an evolution of LTE (Long Term Evolution), corresponding to LTE Release 10 and later.
  • Carrier aggregation technology in LTE-A supports a maximum bandwidth of 100 MHz, a downlink peak rate of 1 Gbit/s, and a peak spectrum efficiency of 30 bits/s/Hz.
  • LTE-A downlink supports up to 8 transmit antennas for data transmission, supports up to 8 layers of spatial multiplexing mode, and uses a dual codebook precoding scheme.
  • codebook 1 has 16 matrices, each matrix consists of 4 beam vectors, and codebook 2 consists of angled selection vectors, which have 16 matrices, so there are 256 precodings.
  • matrix For layer 3 and layer 4, codebook 1 has 4 matrices, each matrix consists of 8 beam vectors, codebook 2 consists of angled selection vectors, layer 3 has 16 matrices, and layer 4 has 8 The matrix, so layer 3 and layer 4 have 64 and 32 precoding matrices, respectively.
  • the gain of precoding is not obvious, so the number of bits of PMI is correspondingly reduced.
  • the dual codebook design brings a huge amount of codebook, which increases the complexity of the codebook selection.
  • the spatial multiplexing mode needs to select an appropriate precoding matrix according to the channel, and the mutual information maximization criterion can be used to select a suitable precoding matrix.
  • the mutual information amount of subcarrier k is represented by I k and is expressed by the following equation, where L represents the number of transmission layers:
  • the precoding matrix W selected from the codebook needs to maximize the sum of the mutual information amounts of the respective subcarriers.
  • This method needs to calculate the mutual information amount on all subcarriers of the entire bandwidth, so it is called a full bandwidth mutual information criterion.
  • MI-SC Mutual Information Selection Criterion
  • the LTE system supports multiple bandwidth configurations (1.4 MHz to 20 MHz), which means that the number of RBs is 1 to 100, and each RB has 12 subcarriers. For each precoding matrix, a minimum of 12 times and a maximum of 1200 are required. Secondary mutual information.
  • the present invention provides a LTE-A dual codebook precoding selection method based on beam operation and packet averaging, which achieves the consistency of the precoding effect and greatly Reduce the computational complexity.
  • the LTE-A dual codebook precoding selection method based on beam operation and packet averaging includes the following steps:
  • K is the number of subcarriers for the entire bandwidth and c is a constant. Indicates that an integer is taken;
  • step (3) For each channel, traverse all the number of packets M i calculated in step (2), select the maximum number of packets as the number of packets of the channel, and select the maximum number of packets under all channels in the entire bandwidth as the entire bandwidth.
  • phase modulation channel in step (5) The expression is as follows:
  • Phase modulation parameter Related to the number of transmission layers, when the number of transmission layers is 1 or 2, the phase modulation parameters The value is ⁇ 1, -1, j, -j ⁇ ; when the number of transmission layers is 3, the phase modulation parameter The value is ⁇ 1, -1 ⁇ ; when the number of transmission layers is 4, the phase modulation parameter The value is ⁇ 1, -1, j, -j ⁇ .
  • step (6) the expression of the beam vector b q corresponding to the number of transmission layers is 1-4:
  • the expression of the mutual information amount I j in the step (7) is:
  • the signal-to-noise ratio SINR j,l on the jth channel of the first layer is related to the channel estimation mode.
  • W is a precoding matrix
  • I L is an L-order identity matrix
  • the precoding selection algorithm of the present invention can be applied to the dual codebook precoding selection of LTE-A 8 antenna spatial multiplexing, and is optimized for the transport layer 1 to 4 layers, and the original mutual information maximization criterion Compared with the precoding algorithm, the consistency of the precoding effect is maintained, and the computational complexity is greatly reduced.
  • 1 is a flowchart of a LTE-A dual codebook precoding selection method based on beam operation and packet averaging;
  • 3 is a multiplication number required for calculating the mutual information amount of the transport layer 1 to 4 layers when the receiving antenna is 4;
  • 4 is a number of additions required for calculating the mutual information amount of the transport layer 1 to 4 layers when the receiving antenna is 4;
  • 5 is a matrix inverse number required for calculating the mutual information amount of the transport layer 1 to 4 layers when the receiving antenna is 4;
  • FIG. 6 is a comparison diagram of packet numbers in different bandwidth configurations and channels according to the present invention.
  • the air interface model applied to the heterogeneous network convergence of WLAN and LTE includes the following steps:
  • step (3) traversing the number of all the packets calculated in step (2), selecting the maximum number of packets as the number of packets of the channel, and then selecting the maximum number of packets under all channels in the entire bandwidth as the number of packets M of the entire bandwidth;
  • the beam-based channel information calculation process for all channels is divided into 2 steps:
  • the average channel matrix H j is divided into two channel matrices of the same four columns, and the phase modulation parameters of the 1 to 4 layers are calculated. They are:
  • the beam vector b q to be calculated when the number of transmission layers is 1 to 4 is respectively selected from the corresponding beam vector matrix B:
  • W is a precoding matrix
  • I L is an L-order identity matrix
  • the precoding matrix W uses a dual codebook design for the cross-polarized 8 antenna according to the adaptive precoding technique, using the beam vector b q and the phase modulation parameter Expressed as:
  • b q2 can select q 1 , q 1 +1, q 1 +3, 3 kinds of vectors;
  • b q2 can select q 1 , q 1 +1, q 1 +2, 3 vectors.
  • b m1 , b m2 , b m3 have the following four combinations:
  • the codebook 1 and the codebook 2 are no longer traversed, and the traversal beam and the phase modulation parameters are replaced. After the beam and the phase modulation parameters are determined, the value of the HW can be obtained by checking the first step. The table is obtained.
  • 3 to 5 are comparison results of the multiplication, addition, matrix inverse and full-band mutual information criterion calculations required to calculate the mutual information of one channel for all codebooks.
  • the results show that the number of multiplications and additions are significantly reduced.
  • the number of matrix inverses is reduced.
  • Figure 6 is a comparison of the number of channels required to calculate the present invention and the full bandwidth MI-SC under the extended pedestrian channel model EPA, extended typical urban channel model ETU, extended vehicle channel model EVA with bandwidth of 1.4, 5, 10, 20 MHz. The results show that the number of calculated channels required by the present invention is much smaller than the full bandwidth MI-SC.

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Abstract

Disclosed in the present invention is an LTE-A dual-codebook precoding selection method based on beam operation and group means. The method is directed to dual-codebook precoding employed for LTE-A eight-antenna spatial multiplexing having 1-4 transmission layers, and is based on the criterion of mutual information maximization. By traversing beam vectors and phase modulation parameters and storing dot products of phase modulation channels and beams, mutual information calculation can be achieved by table look-up, thus addressing intensive and repetitive computation of precoding matrix selection in the prior art. The present invention employs group means to group subcarriers in the full bandwidth, and the mutual information is calculated by using the mean of each channel group to greatly reduce the number of channels requiring computation. The amounts of multiplication and addition of complex numbers and matrix inversion computation are significantly reduced without compromising the precoding performance, thus lowering computation complexity.

Description

一种基于波束运算和分组平均的LTE-A双码本预编码选择方法LTE-A dual codebook precoding selection method based on beam operation and packet averaging 技术领域Technical field
本发明属于无线通信技术领域，涉及LTE-A 8天线空间复用双码本预编码选择算法，尤其涉及一种基于波束运算和分组平均的LTE-A双码本预编码选择方法。The invention belongs to the field of wireless communication technologies, and relates to an LTE-A 8 antenna spatial multiplexing dual codebook precoding selection algorithm, in particular to a LTE-A dual codebook precoding selection method based on beam operation and packet averaging.
背景技术Background technique
3GPP LTE-A(LTE-Advanced)项目是LTE(Long Term Evolution)的演进，对应LTE Release 10以及以后的版本。LTE-A中通过载波聚合技术，最大支持带宽100MHz，下行峰值速率可到1Gbit/s，峰值频谱效率可达到30bit/s/Hz。The 3GPP LTE-A (LTE-Advanced) project is an evolution of LTE (Long Term Evolution), corresponding to LTE Release 10 and later. Carrier aggregation technology in LTE-A supports a maximum bandwidth of 100 MHz, a downlink peak rate of 1 Gbit/s, and a peak spectrum efficiency of 30 bits/s/Hz.
为达到峰值频谱效率，LTE-A下行支持多达8个发射天线进行数据传输，支持多达8层的空间复用模式，并采用了双码本的预编码方案。对于层1和层2来说，码本1共有16个矩阵，每个矩阵由4个波束向量组成，码本2由经过调角的选择向量组成，共有16个矩阵，因此共有256个预编码矩阵。对于层3和层4来说，码本1共有4个矩阵，每个矩阵由8个波束向量组成，码本2由经过调角的选择向量组成，层3有16个矩阵，层4有8个矩阵，因此层3和层4分别有64和32个预编码矩阵。对于层5～8，预编码的增益并不明显，因此PMI的比特数相应减少，5～7层时只有4个预编码矩阵，而8层的预编码则是固定的。对于1～4层来说，双码本设计带来了巨大的码本量，提高了码本选择的复杂度。To achieve peak spectral efficiency, LTE-A downlink supports up to 8 transmit antennas for data transmission, supports up to 8 layers of spatial multiplexing mode, and uses a dual codebook precoding scheme. For layer 1 and layer 2, codebook 1 has 16 matrices, each matrix consists of 4 beam vectors, and codebook 2 consists of angled selection vectors, which have 16 matrices, so there are 256 precodings. matrix. For layer 3 and layer 4, codebook 1 has 4 matrices, each matrix consists of 8 beam vectors, codebook 2 consists of angled selection vectors, layer 3 has 16 matrices, and layer 4 has 8 The matrix, so layer 3 and layer 4 have 64 and 32 precoding matrices, respectively. For layers 5-8, the gain of precoding is not obvious, so the number of bits of PMI is correspondingly reduced. There are only 4 precoding matrices in 5-7 layers, and the precoding of 8 layers is fixed. For the 1 to 4 layers, the dual codebook design brings a huge amount of codebook, which increases the complexity of the codebook selection.
空间复用模式需要根据信道选择合适的预编码矩阵，使用互信息量最大化准则可以很好的选择合适的预编码矩阵。The spatial multiplexing mode needs to select an appropriate precoding matrix according to the channel, and the mutual information maximization criterion can be used to select a suitable precoding matrix.
用Ik表示子载波k的互信息量，由下式表示，式中L表示传输层数：The mutual information amount of subcarrier k is represented by I k and is expressed by the following equation, where L represents the number of transmission layers:
Figure PCTCN2016073259-appb-000001
Figure PCTCN2016073259-appb-000001
从码本中选择的预编码矩阵W需要使各个子载波互信息量之和最大化，这种方法需要计算整个带宽所有子载波上的互信息量，因此称之为全带宽互信息量准则。The precoding matrix W selected from the codebook needs to maximize the sum of the mutual information amounts of the respective subcarriers. This method needs to calculate the mutual information amount on all subcarriers of the entire bandwidth, so it is called a full bandwidth mutual information criterion.
Figure PCTCN2016073259-appb-000002
Figure PCTCN2016073259-appb-000002
采用全带宽互信息量准则(Mutual Information Selection Criterion,MI-SC)选择预编码矩阵的缺点在于计算复杂度非常高。其计算复杂度来源于两个方面：1)首先，为了确定合适的预编码矩阵，需要遍历码本中每个预编码矩阵。8天线双码本设计中，可选的预编码矩阵量较大，预编码矩阵量的增加将增大计算复杂度，对于1～4层，1和2层的 矩阵数为256个，3层、4层分别为64和32个。2)另一方面，其计算复杂度随着带宽增大，子载波数目的增多而增大。LTE***支持多种带宽配置(1.4MHz～20MHz)，这意味着RB个数为1～100个，每个RB有12个子载波，则对于每一个预编码矩阵，需要计算最少12次，最多1200次互信息量。The disadvantage of using the Mutual Information Selection Criterion (MI-SC) to select the precoding matrix is that the computational complexity is very high. The computational complexity comes from two aspects: 1) First, in order to determine a suitable precoding matrix, it is necessary to traverse each precoding matrix in the codebook. In the 8-antenna dual-codebook design, the amount of optional precoding matrix is large, and the increase of the precoding matrix amount will increase the computational complexity for 1 to 4 layers, 1 and 2 layers. The number of matrices is 256, and the 3 and 4 layers are 64 and 32 respectively. 2) On the other hand, its computational complexity increases as the bandwidth increases and the number of subcarriers increases. The LTE system supports multiple bandwidth configurations (1.4 MHz to 20 MHz), which means that the number of RBs is 1 to 100, and each RB has 12 subcarriers. For each precoding matrix, a minimum of 12 times and a maximum of 1200 are required. Secondary mutual information.
发明内容Summary of the invention
发明目的：为了克服现有技术中存在的不足，本发明提供一种基于波束运算和分组平均的LTE-A双码本预编码选择方法，达到既保持预编码效果的一致性的同时，又大幅降低了计算复杂度的效果。OBJECT OF THE INVENTION In order to overcome the deficiencies in the prior art, the present invention provides a LTE-A dual codebook precoding selection method based on beam operation and packet averaging, which achieves the consistency of the precoding effect and greatly Reduce the computational complexity.
技术方案：为实现上述目的，本发明提供的基于波束运算和分组平均的LTE-A双码本预编码选择方法，包括如下步骤：Technical Solution: To achieve the above object, the LTE-A dual codebook precoding selection method based on beam operation and packet averaging provided by the present invention includes the following steps:
(1)在频域中针对整个带宽上的任意信道，遍历寻找所有子载波所对应的信道频率响应幅值中的所有极大、极小值，计算两相邻极大、极小值之间的差并取绝对值，记为ΔHi，并计算两相邻极大、极小值之间的子载波数Δki，i＝0,1,…,N-2，N为极值的个数；(1) traversing all the maximal and minimum values in the channel frequency response amplitude corresponding to all subcarriers in the frequency domain for any channel on the entire bandwidth, and calculating between two adjacent maxima and minima The difference is taken as the absolute value, denoted as ΔH i , and the number of subcarriers Δk i , i=0,1,...,N-2,N between the two adjacent maxima and minima is calculated. number;
(2)根据每一个ΔHi计算该信道下整个带宽所需的分组数Mi，Mi的表达式如下：(2) Calculate the number of packets M i , M i required to calculate the entire bandwidth of the channel according to each ΔH i as follows:
Figure PCTCN2016073259-appb-000003
Figure PCTCN2016073259-appb-000003
式中，K为整个带宽的子载波数，c为一个常数，
Figure PCTCN2016073259-appb-000004
表示取上整数；Where K is the number of subcarriers for the entire bandwidth and c is a constant.
Figure PCTCN2016073259-appb-000004
Indicates that an integer is taken;
(3)针对每个信道，遍历步骤(2)中所计算的所有分组数Mi，选取最大分组数作为该信道的分组数，再选择整个带宽内所有信道下最大的分组数作为整个带宽的分组数M；(3) For each channel, traverse all the number of packets M i calculated in step (2), select the maximum number of packets as the number of packets of the channel, and select the maximum number of packets under all channels in the entire bandwidth as the entire bandwidth. Number of groups M;
(4)将整个带宽的所有子载波分成M组，前M‐1组，每组包含子载波数
Figure PCTCN2016073259-appb-000005
第M组包含子载波数
Figure PCTCN2016073259-appb-000006
表示取下整数，并对每组内的信道矩阵求平均值，称作平均信道矩阵Hj，j＝0,1,…,M-1；(4) Divide all subcarriers of the entire bandwidth into M groups, the first M-1 group, and each group contains the number of subcarriers.
Figure PCTCN2016073259-appb-000005
Group M contains the number of subcarriers
Figure PCTCN2016073259-appb-000006
Indicates that the integer is removed and the channel matrix in each group is averaged, called the average channel matrix H j , j=0, 1, ..., M-1;
(5)根据传输层数L，遍历每层分别对应的所有调相参数
Figure PCTCN2016073259-appb-000007
针对每个平均信道矩阵Hj，将其按列平均分割为子信道矩阵
Figure PCTCN2016073259-appb-000008
和
Figure PCTCN2016073259-appb-000009
并计算各个调相参数下的调相信道
Figure PCTCN2016073259-appb-000010
(5) traverse all the phase modulation parameters corresponding to each layer according to the number of transmission layers L
Figure PCTCN2016073259-appb-000007
For each average channel matrix H j , it is divided into subchannel matrices by column average
Figure PCTCN2016073259-appb-000008
with
Figure PCTCN2016073259-appb-000009
And calculate the phase modulation channel under each phase modulation parameter
Figure PCTCN2016073259-appb-000010
(6)根据传输层数L，遍历每层分别对应的所有波束向量bq，计算每个调相信道
Figure PCTCN2016073259-appb-000011
和每个波束向量bq的乘积
Figure PCTCN2016073259-appb-000012
并存储在查找表中；(6) Calculate each phase-modulated channel by traversing all beam vectors b q corresponding to each layer according to the number of transmission layers L
Figure PCTCN2016073259-appb-000011
Product of each beam vector b q
Figure PCTCN2016073259-appb-000012
And stored in a lookup table;
(7)遍历波束向量bq和调相参数
Figure PCTCN2016073259-appb-000013
利用所述查找表中所存储的调相信道和波束的乘积
Figure PCTCN2016073259-appb-000014
计算各个平均信道Hj的互信息量Ij，并进行累加得到所有信道互信息量之和；(7) traversing the beam vector b q and phase modulation parameters
Figure PCTCN2016073259-appb-000013
Utilizing the product of the phase modulation channel and the beam stored in the lookup table
Figure PCTCN2016073259-appb-000014
Calculating the mutual information amount I j of each average channel H j and performing accumulation to obtain the sum of the mutual information amounts of all channels;
(8)选择使得互信息量之和最大的波束向量和调相参数组合作为最终选择的预编码矩阵。(8) Selecting a combination of a beam vector and a phase modulation parameter that maximize the sum of mutual information amounts as a final selected precoding matrix.
其中，步骤(5)中所述调相信道
Figure PCTCN2016073259-appb-000015
的表达式如下：Wherein the phase modulation channel in step (5)
Figure PCTCN2016073259-appb-000015
The expression is as follows:
Figure PCTCN2016073259-appb-000016
Figure PCTCN2016073259-appb-000016
式中，调相参数
Figure PCTCN2016073259-appb-000017
与传输层数有关，当传输层数为1或2时，调相参数
Figure PCTCN2016073259-appb-000018
的取值为{1,-1,j,-j}；当传输层数为3时，调相参数
Figure PCTCN2016073259-appb-000019
的取值为{1,-1}；当传输层数为4时，调相参数
Figure PCTCN2016073259-appb-000020
的取值为{1,-1,j,-j}。Phase modulation parameter
Figure PCTCN2016073259-appb-000017
Related to the number of transmission layers, when the number of transmission layers is 1 or 2, the phase modulation parameters
Figure PCTCN2016073259-appb-000018
The value is {1, -1, j, -j}; when the number of transmission layers is 3, the phase modulation parameter
Figure PCTCN2016073259-appb-000019
The value is {1, -1}; when the number of transmission layers is 4, the phase modulation parameter
Figure PCTCN2016073259-appb-000020
The value is {1, -1, j, -j}.
其中，步骤(6)中传输层数为1～4时分别对应的波束向量bq的表达式如下：Wherein, in step (6), the expression of the beam vector b q corresponding to the number of transmission layers is 1-4:
1层和2层：
Figure PCTCN2016073259-appb-000021
bq∈B＝[b0b1 … b31]，其中，bi(i＝0,2,...,31)是一个4×1的列向量；1st and 2nd floors:
Figure PCTCN2016073259-appb-000021
 b q ∈ B = [b 0 b 1 ... b 31 ], where b i (i = 0, 2, ..., 31) is a 4 × 1 column vector;
3层和4层：
Figure PCTCN2016073259-appb-000022
bq∈B＝[b0b1 … b15]，其中，bi(i＝0,2,...,15)是一个4×1的列向量。3 and 4 layers:
Figure PCTCN2016073259-appb-000022
 b q ∈ B = [b 0 b 1 ... b 15 ], where b i (i = 0, 2, ..., 15) is a 4 × 1 column vector.
其中，步骤(7)中所述互信息量Ij的表达式为：Wherein, the expression of the mutual information amount I j in the step (7) is:
Figure PCTCN2016073259-appb-000023
Figure PCTCN2016073259-appb-000023
第l层第j个信道上的信噪比SINRj,l与信道估计方式有关，The signal-to-noise ratio SINR j,l on the jth channel of the first layer is related to the channel estimation mode.
对于MMSE检测：
Figure PCTCN2016073259-appb-000024
 For MMSE testing:
Figure PCTCN2016073259-appb-000024
对于ZF检测： For ZF detection:
式中，
Figure PCTCN2016073259-appb-000026
为噪声功率，W为预编码矩阵，IL为L阶单位矩阵。 In the formula,
Figure PCTCN2016073259-appb-000026
For noise power, W is a precoding matrix, and I L is an L-order identity matrix.
有益效果：本发明的预编码选择算法能应用于LTE-A 8天线空间复用的双码本预编码选择，针对传输层为1～4层进行了优化，与原始的互信息量最大化准则选择预编码算法相比，保持了预编码效果的一致性的同时，大幅降低了计算复杂度。Advantageous Effects: The precoding selection algorithm of the present invention can be applied to the dual codebook precoding selection of LTE-A 8 antenna spatial multiplexing, and is optimized for the transport layer 1 to 4 layers, and the original mutual information maximization criterion Compared with the precoding algorithm, the consistency of the precoding effect is maintained, and the computational complexity is greatly reduced.
附图说明DRAWINGS
图1为基于波束运算和分组平均的LTE-A双码本预编码选择方法的流程图；1 is a flowchart of a LTE-A dual codebook precoding selection method based on beam operation and packet averaging;
图2为本发明中调相信道和波束乘积存储流程图；2 is a flow chart of phase modulation channel and beam product storage in the present invention;
图3为本发明在接收天线为4时，传输层1～4层计算互信息量所需的乘法次数；3 is a multiplication number required for calculating the mutual information amount of the transport layer 1 to 4 layers when the receiving antenna is 4;
图4为本发明在接收天线为4时，传输层1～4层计算互信息量所需的加法次数；4 is a number of additions required for calculating the mutual information amount of the transport layer 1 to 4 layers when the receiving antenna is 4;
图5为本发明在接收天线为4时，传输层1～4层计算互信息量所需的矩阵逆次数；5 is a matrix inverse number required for calculating the mutual information amount of the transport layer 1 to 4 layers when the receiving antenna is 4;
图6为本发明在不同带宽配置和各信道下的分组数比较图。FIG. 6 is a comparison diagram of packet numbers in different bandwidth configurations and channels according to the present invention.
具体实施方式detailed description
下面结合实施例对本发明作更进一步的说明。The present invention will be further described below in conjunction with the embodiments.
图1中，针对LTE-A 8天线空间复用传输模式下传输层1～4层的双码本预编码，本发明的基于波束运算和分组平均的LTE-A双码本预编码选择方法，应用于WLAN与LTE的异构网融合的空中接口模型中，包括以下步骤：In FIG. 1, for the dual codebook precoding of the transport layer 1 to 4 layers in the LTE-A 8 antenna spatial multiplexing transmission mode, the beam computing and packet averaging based LTE-A dual codebook precoding selection method of the present invention, The air interface model applied to the heterogeneous network convergence of WLAN and LTE includes the following steps:
(1)在频域中针对整个带宽上的任意信道，遍历寻找所有子载波所对应的信道频率响应幅值中的所有极大、极小值(极大、极小值间隔出现)，计算两相邻极大、极小值之间的差并取绝对值，记为ΔHi，并计算两相邻极大、极小值之间的子载波数Δki，i＝0,1,…,N-2，N为极值的个数；(1) traversing all the maximal and minimum values in the channel frequency response amplitude corresponding to all subcarriers in the frequency domain for any channel on the entire bandwidth (maximum, minimum interval occurs), calculating two The difference between adjacent maxima and minima is taken as an absolute value, denoted as ΔH i , and the number of subcarriers Δk i , i=0,1,... between two adjacent maxima and minima is calculated. N-2, N is the number of extreme values;
(2)根据每一个ΔHi计算该信道下整个带宽所需的分组数Mi，
Figure PCTCN2016073259-appb-000027
其中K为整个带宽的子载波数，c为一个常数，本发明中取1.25，
Figure PCTCN2016073259-appb-000028
表示取上整数；(2) Calculate the number of packets required for the entire bandwidth of this channel M i according to each of ΔH i,
Figure PCTCN2016073259-appb-000027
Where K is the number of subcarriers of the entire bandwidth, and c is a constant, which is 1.25 in the present invention.
Figure PCTCN2016073259-appb-000028
Indicates that an integer is taken;
(3)遍历步骤(2)中所计算的所有分组数，选取最大分组数作为该信道的分组数，再选择整个带宽内所有信道下最大的分组数作为整个带宽的分组数M；(3) traversing the number of all the packets calculated in step (2), selecting the maximum number of packets as the number of packets of the channel, and then selecting the maximum number of packets under all channels in the entire bandwidth as the number of packets M of the entire bandwidth;
(4)将整个带宽的所有子载波分成M组，前M‐1组，每组包含子载波数
Figure PCTCN2016073259-appb-000029
第M组包含子载波数
Figure PCTCN2016073259-appb-000030
表示取下整数，并对每组内的信道矩阵求平均值，称作平均信道矩阵Hj，j＝0,1,…,M-1；(4) Divide all subcarriers of the entire bandwidth into M groups, the first M-1 group, and each group contains the number of subcarriers.
Figure PCTCN2016073259-appb-000029
Group M contains the number of subcarriers
Figure PCTCN2016073259-appb-000030
Indicates that the integer is removed and the channel matrix in each group is averaged, called the average channel matrix H j , j=0, 1, ..., M-1;
(5)根据传输层数L，遍历每层分别对应的所有调相参数
Figure PCTCN2016073259-appb-000031
针对每个平均信道矩阵Hj计算各个调相参数下的调相信道
Figure PCTCN2016073259-appb-000032
(5) traverse all the phase modulation parameters corresponding to each layer according to the number of transmission layers L
Figure PCTCN2016073259-appb-000031
Calculating the phase modulation channel under each phase modulation parameter for each average channel matrix H j
Figure PCTCN2016073259-appb-000032
(6)根据传输层数L，遍历每层分别对应的所有波束向量bq，计算每个调相信道
Figure PCTCN2016073259-appb-000033
和每个波束向量bq的乘积
Figure PCTCN2016073259-appb-000034
并存储在查找表中；(6) Calculate each phase-modulated channel by traversing all beam vectors b q corresponding to each layer according to the number of transmission layers L
Figure PCTCN2016073259-appb-000033
Product of each beam vector b q
Figure PCTCN2016073259-appb-000034
And stored in a lookup table;
(7)遍历波束向量bq和调相参数
Figure PCTCN2016073259-appb-000035
计算各个平均信道Hj的互信息量
Figure PCTCN2016073259-appb-000036
计算过程中所需调相信道和波束的乘积
Figure PCTCN2016073259-appb-000037
可以通过查表获得，并计算所有信道互信息量之和；(7) traversing the beam vector b q and phase modulation parameters
Figure PCTCN2016073259-appb-000035
Calculate the amount of mutual information of each average channel H j
Figure PCTCN2016073259-appb-000036
The product of the phase modulation channel and beam required in the calculation process
Figure PCTCN2016073259-appb-000037
It can be obtained by looking up the table and calculating the sum of mutual information of all channels;
(8)选择使得所述所有信道互信息量之和最大的波束向量和调相参数组合作为最终选择的预编码矩阵。(8) Selecting a combination of the beam vector and the phase modulation parameter that maximizes the sum of the mutual information amounts of all the channels as the final selected precoding matrix.
基于波束的所有信道互信息量计算过程分为2步：The beam-based channel information calculation process for all channels is divided into 2 steps:
(1)计算调相信道和波束的乘积，存入查找表中，过程如图2所示：(1) Calculate the product of the phase-modulated channel and the beam and store it in the look-up table. The process is shown in Figure 2:
对于第任意j组信道矩阵Hj，先按列分割成2个大小为NR×4的信道子矩阵
Figure PCTCN2016073259-appb-000038
和
Figure PCTCN2016073259-appb-000039
For the arbitrary j-group channel matrix H j , it is first divided into two channel sub-matrices of size N R ×4 by column.
Figure PCTCN2016073259-appb-000038
with
Figure PCTCN2016073259-appb-000039
然后，遍历该层对应的所有调相参数，对每一个调相参数，计算调相信道
Figure PCTCN2016073259-appb-000040
Then, traversing all the phase modulation parameters corresponding to the layer, and calculating the phase modulation channel for each phase modulation parameter
Figure PCTCN2016073259-appb-000040
Figure PCTCN2016073259-appb-000041
Figure PCTCN2016073259-appb-000041
式中，
Figure PCTCN2016073259-appb-000042
和
Figure PCTCN2016073259-appb-000043
为平均信道矩阵Hj按列平均分割后2个同为4列的信道矩阵，1到4层所需计算的调相参数
Figure PCTCN2016073259-appb-000044
分别为：In the formula,
Figure PCTCN2016073259-appb-000042
with
Figure PCTCN2016073259-appb-000043
For the average channel matrix H j , the average is divided into two channel matrices of the same four columns, and the phase modulation parameters of the 1 to 4 layers are calculated.
Figure PCTCN2016073259-appb-000044
They are:
Figure PCTCN2016073259-appb-000045
Figure PCTCN2016073259-appb-000045
接着，遍历该层对应的所有波束向量bq，计算每个调相信道
Figure PCTCN2016073259-appb-000046
与波束bq的乘积
Figure PCTCN2016073259-appb-000047
存入查找表中。Then, traversing all the beam vectors b q corresponding to the layer, and calculating each phase modulation channel
Figure PCTCN2016073259-appb-000046
Product with beam b q
Figure PCTCN2016073259-appb-000047
Save in the lookup table.
传输层数为1～4时所需计算的波束向量bq分别从相应的波束向量矩阵B中选取：The beam vector b q to be calculated when the number of transmission layers is 1 to 4 is respectively selected from the corresponding beam vector matrix B:
1层和2层：
Figure PCTCN2016073259-appb-000048
bq∈B＝[b0b1 … b31]；其中，bi(i＝0,1,...,31)是一个4×1的列向量。1st and 2nd floors:
Figure PCTCN2016073259-appb-000048
 b q ∈ B = [b 0 b 1 ... b 31 ]; where b i (i = 0, 1, ..., 31) is a 4 × 1 column vector.
3层和4层：
Figure PCTCN2016073259-appb-000049
bq∈B＝[b0b1 … b15]其中， bi(i＝0,1,...,15)是一个4×1的列向量。3 and 4 layers:
Figure PCTCN2016073259-appb-000049
 b q ∈ B = [b 0 b 1 ... b 15 ] where b i (i = 0, 1, ..., 15) is a 4 × 1 column vector.
(2)遍历调相参数
Figure PCTCN2016073259-appb-000050
和波束bq，通过查表计算互信息量。计算互信息量的表达式为：(2) traversing the phase modulation parameters
Figure PCTCN2016073259-appb-000050
And the beam b q , the mutual information is calculated by looking up the table. The expression for calculating mutual information is:
Figure PCTCN2016073259-appb-000051
Figure PCTCN2016073259-appb-000051
针对不同的检测方式，信噪比SINRj,l的计算公式不同，For different detection methods, the calculation formula of signal-to-noise ratio SINR j,l is different.
对于MMSE检测：
Figure PCTCN2016073259-appb-000052
 For MMSE testing:
Figure PCTCN2016073259-appb-000052
对于ZF检测：
Figure PCTCN2016073259-appb-000053
 For ZF detection:
Figure PCTCN2016073259-appb-000053
其中，
Figure PCTCN2016073259-appb-000054
为噪声功率，W为预编码矩阵，IL为L阶单位矩阵。among them,
Figure PCTCN2016073259-appb-000054
For noise power, W is a precoding matrix, and I L is an L-order identity matrix.
预编码矩阵W根据自适应预编码技术，针对交叉极化8天线采用双码本设计，用波束向量bq和调相参数
Figure PCTCN2016073259-appb-000055
表示为：The precoding matrix W uses a dual codebook design for the cross-polarized 8 antenna according to the adaptive precoding technique, using the beam vector b q and the phase modulation parameter
Figure PCTCN2016073259-appb-000055
Expressed as:
层1：
Figure PCTCN2016073259-appb-000056
Layer 1:
Figure PCTCN2016073259-appb-000056
层2：
Figure PCTCN2016073259-appb-000057
Layer 2:
Figure PCTCN2016073259-appb-000057
对于选定波束向量bq1，q1＝{0,1,…,31}：For the selected beam vector b q1 , q 1 ={0,1,...,31}:
如果其下标值q1为偶数，则bq2可以选q1、q1+1、q1+3，3种向量；If its subscript value q 1 is an even number, then b q2 can select q 1 , q 1 +1, q 1 +3, 3 kinds of vectors;
如果其下标值q1为奇数，则bq2可以选q1、q1+1、q1+2，3种向量。If the subscript value q 1 is an odd number, b q2 can select q 1 , q 1 +1, q 1 +2, 3 vectors.
层3：
Figure PCTCN2016073259-appb-000058
 Layer 3:
Figure PCTCN2016073259-appb-000058
其中，q1＝{0,1,…,15},q2＝(q1+4)mod16。Where q 1 = {0, 1, ..., 15}, q 2 = (q 1 + 4) mod16.
层4：Layer 4:
Figure PCTCN2016073259-appb-000059
Figure PCTCN2016073259-appb-000059
其中，q1＝{0,1,L,15},q2＝(q1+4)mod16，
Figure PCTCN2016073259-appb-000060
Where q 1 = {0, 1, L, 15}, q 2 = (q 1 + 4) mod16,
Figure PCTCN2016073259-appb-000060
计算所需的中间变量HjW的具体计算公式为：The specific calculation formula for the intermediate variable H j W required for the calculation is:
层1：
Figure PCTCN2016073259-appb-000061
Layer 1:
Figure PCTCN2016073259-appb-000061
层2：
Figure PCTCN2016073259-appb-000062
Layer 2:
Figure PCTCN2016073259-appb-000062
层3：
Figure PCTCN2016073259-appb-000063
Layer 3:
Figure PCTCN2016073259-appb-000063
bm1、bm2、bm3有如下4种组合：b m1 , b m2 , b m3 have the following four combinations:
{bq1,bq1,bq2},{bq2,bq1,bq2},{bq1,bq2,bq2},{bq2,bq1,bq1}{b q1 , b q1 , b q2 }, {b q2 , b q1 , b q2 }, {b q1 , b q2 , b q2 }, {b q2 , b q1 , b q1 }
其中，q1＝{0,1,…,15},q2＝(q1+4)mod16。Where q 1 = {0, 1, ..., 15}, q 2 = (q 1 + 4) mod16.
层4：Layer 4:
Figure PCTCN2016073259-appb-000064
Figure PCTCN2016073259-appb-000064
其中，q1＝{0,1,…,15},q2＝(q1+4)mod16，
Figure PCTCN2016073259-appb-000065
Where q 1 ={0,1,...,15},q 2 =(q 1 +4)mod16,
Figure PCTCN2016073259-appb-000065
在计算互信息量时，不再遍历码本1和码本2，取而代之的是遍历波束和调相参数，同时波束和调相参数确定以后，HW的值可以通过查第一步中产生的
Figure PCTCN2016073259-appb-000066
表获得。When calculating the mutual information amount, the codebook 1 and the codebook 2 are no longer traversed, and the traversal beam and the phase modulation parameters are replaced. After the beam and the phase modulation parameters are determined, the value of the HW can be obtained by checking the first step.
Figure PCTCN2016073259-appb-000066
The table is obtained.
图3～5为本发明遍历所***本计算一个信道的互信息量所需的乘法、加法、矩阵逆次数与全带宽互信息量准则计算的对比结果。结果显示乘法和加法次数都有显著下降，在层1和层2时，矩阵逆次数有所减少。3 to 5 are comparison results of the multiplication, addition, matrix inverse and full-band mutual information criterion calculations required to calculate the mutual information of one channel for all codebooks. The results show that the number of multiplications and additions are significantly reduced. At layer 1 and layer 2, the number of matrix inverses is reduced.
图6为带宽为1.4、5、10、20MHz配置在扩展步行者信道模型EPA、扩展典型城市信道模型ETU、扩展车辆信道模型EVA下本发明和全带宽MI-SC所需计算的信道个数对比，结果显示，本发明所需的计算的信道数目远远小于全带宽MI-SC。 Figure 6 is a comparison of the number of channels required to calculate the present invention and the full bandwidth MI-SC under the extended pedestrian channel model EPA, extended typical urban channel model ETU, extended vehicle channel model EVA with bandwidth of 1.4, 5, 10, 20 MHz. The results show that the number of calculated channels required by the present invention is much smaller than the full bandwidth MI-SC.

Claims (5)

  1. 一种基于波束运算和分组平均的LTE-A双码本预编码选择方法，其特征在于，该方法包括如下步骤：An LTE-A dual codebook precoding selection method based on beam operation and packet averaging, characterized in that the method comprises the following steps:
    (1)在频域中针对整个带宽上的任意信道，遍历寻找所有子载波所对应的信道频率响应幅值中的所有极大、极小值，计算两相邻极大、极小值之间的差并取绝对值，记为ΔHi，并计算两相邻极大、极小值之间的子载波数Δki，i＝0,1,…,N-2，N为极值的个数；(1) traversing all the maximal and minimum values in the channel frequency response amplitude corresponding to all subcarriers in the frequency domain for any channel on the entire bandwidth, and calculating between two adjacent maxima and minima The difference is taken as the absolute value, denoted as ΔH i , and the number of subcarriers Δk i , i=0,1,...,N-2,N between the two adjacent maxima and minima is calculated. number;
    (2)根据每一个ΔHi计算该信道下整个带宽所需的分组数Mi，Mi的表达式如下：(2) Calculate the number of packets M i , M i required to calculate the entire bandwidth of the channel according to each ΔH i as follows:
    Figure PCTCN2016073259-appb-100001
    Figure PCTCN2016073259-appb-100001
    式中，K为整个带宽的子载波数，c为一个常数，
    Figure PCTCN2016073259-appb-100002
    表示取上整数；    Where K is the number of subcarriers for the entire bandwidth and c is a constant.
    Figure PCTCN2016073259-appb-100002
    Indicates that an integer is taken;
    (3)针对每个信道，遍历步骤(2)中所计算的所有分组数Mi，选取最大分组数作为该信道的分组数，再选择整个带宽内所有信道下最大的分组数作为整个带宽的分组数M；(3) For each channel, traverse all the number of packets M i calculated in step (2), select the maximum number of packets as the number of packets of the channel, and select the maximum number of packets under all channels in the entire bandwidth as the entire bandwidth. Number of groups M;
    (4)将整个带宽的所有子载波分成M组，前M‐1组，每组包含子载波数
    Figure PCTCN2016073259-appb-100003
    第M组包含子载波数
    Figure PCTCN2016073259-appb-100004
    Figure PCTCN2016073259-appb-100005
    表示取下整数，并对每组内的信道矩阵求平均值，称作平均信道矩阵Hj，j＝0,1,…,M-1；    (4) Divide all subcarriers of the entire bandwidth into M groups, the first M-1 group, and each group contains the number of subcarriers.
    Figure PCTCN2016073259-appb-100003
    Group M contains the number of subcarriers
    Figure PCTCN2016073259-appb-100004
    Figure PCTCN2016073259-appb-100005
    Indicates that the integer is removed and the channel matrix in each group is averaged, called the average channel matrix H j , j=0, 1, ..., M-1;
    (5)根据传输层数L，遍历每层分别对应的所有调相参数
    Figure PCTCN2016073259-appb-100006
    针对每个平均信道矩阵Hj，将其按列平均分割为子信道矩阵
    Figure PCTCN2016073259-appb-100007
    和
    Figure PCTCN2016073259-appb-100008
    并计算各个调相参数下的调相信道
    Figure PCTCN2016073259-appb-100009
    (5) traverse all the phase modulation parameters corresponding to each layer according to the number of transmission layers L
    Figure PCTCN2016073259-appb-100006
    For each average channel matrix H j , it is divided into subchannel matrices by column average
    Figure PCTCN2016073259-appb-100007
    with
    Figure PCTCN2016073259-appb-100008
    And calculate the phase modulation channel under each phase modulation parameter
    Figure PCTCN2016073259-appb-100009
    (6)根据传输层数L，遍历每层分别对应的所有波束向量bq，计算每个调相信道
    Figure PCTCN2016073259-appb-100010
    和每个波束向量bq的乘积
    Figure PCTCN2016073259-appb-100011
    并存储在查找表中；    (6) Calculate each phase-modulated channel by traversing all beam vectors b q corresponding to each layer according to the number of transmission layers L
    Figure PCTCN2016073259-appb-100010
    Product of each beam vector b q
    Figure PCTCN2016073259-appb-100011
    And stored in a lookup table;
    (7)遍历波束向量bq和调相参数
    Figure PCTCN2016073259-appb-100012
    利用所述查找表中所存储的调相信道和波束的乘积
    Figure PCTCN2016073259-appb-100013
    计算各个平均信道Hj的互信息量Ij，并进行累加得到所有信道互信息量之和；    (7) traversing the beam vector b q and phase modulation parameters
    Figure PCTCN2016073259-appb-100012
    Utilizing the product of the phase modulation channel and the beam stored in the lookup table
    Figure PCTCN2016073259-appb-100013
    Calculating the mutual information amount I j of each average channel H j and performing accumulation to obtain the sum of the mutual information amounts of all channels;
    (8)选择使得互信息量之和最大的波束向量和调相参数组合作为最终选择的预编码矩阵。(8) Selecting a combination of a beam vector and a phase modulation parameter that maximize the sum of mutual information amounts as a final selected precoding matrix.
  2. 根据权利要求1中所述的双码本预编码选择方法，其特征在于，步骤(5)中所述 调相信道
    Figure PCTCN2016073259-appb-100014
    的表达式如下：    A dual codebook precoding selection method according to claim 1, wherein said phase modulation channel in step (5)
    Figure PCTCN2016073259-appb-100014
    The expression is as follows:
    Figure PCTCN2016073259-appb-100015
    Figure PCTCN2016073259-appb-100015
    式中，调相参数
    Figure PCTCN2016073259-appb-100016
    与传输层数有关，当传输层数为1或2时，调相参数
    Figure PCTCN2016073259-appb-100017
    的取值为{1,-1,j,-j}；当传输层数为3时，调相参数
    Figure PCTCN2016073259-appb-100018
    的取值为{1,-1}；当传输层数为4时，调相参数
    Figure PCTCN2016073259-appb-100019
    的取值为{1,-1,j,-j}。    Phase modulation parameter
    Figure PCTCN2016073259-appb-100016
    Related to the number of transmission layers, when the number of transmission layers is 1 or 2, the phase modulation parameters
    Figure PCTCN2016073259-appb-100017
    The value is {1, -1, j, -j}; when the number of transmission layers is 3, the phase modulation parameter
    Figure PCTCN2016073259-appb-100018
    The value is {1, -1}; when the number of transmission layers is 4, the phase modulation parameter
    Figure PCTCN2016073259-appb-100019
    The value is {1, -1, j, -j}.
  3. 根据权利要求1中所述的双码本预编码选择方法，其特征在于，步骤(6)中传输层数为1～4时分别对应的波束向量bq的表达式如下：The dual codebook precoding selection method according to claim 1, wherein the expression of the beam vector b q corresponding to the number of transmission layers in the step (6) is 1-4:
    1层和2层：
    Figure PCTCN2016073259-appb-100020
    m＝0,1,2,3,n＝0,1,…,31，bq∈B＝[b0 b1 … b31]，其中，bi(i＝0,2,...,31)是一个4×1的列向量；    1st and 2nd floors:
    Figure PCTCN2016073259-appb-100020
    m = 0, 1, 2, 3, n = 0, 1, ..., 31, b q ∈ B = [b 0 b 1 ... b 31 ], where b i (i = 0, 2, ..., 31) is a 4 × 1 column vector;
    3层和4层：
    Figure PCTCN2016073259-appb-100021
    m＝0,1,2,3,n＝0,1,…,15，bq∈B＝[b0 b1 … b15]，其中，bi(i＝0,2,...,15)是一个4×1的列向量。    3 and 4 layers:
    Figure PCTCN2016073259-appb-100021
    m=0,1,2,3,n=0,1,...,15,b q ∈B=[b 0 b 1 ... b 15 ], where b i (i=0,2,..., 15) is a 4 × 1 column vector.
  4. 根据权利要求1中所述的双码本预编码选择方法，其特征在于，步骤(7)中所述互信息量Ij的表达式为：The dual codebook precoding selection method according to claim 1, wherein the expression of the mutual information amount I j in the step (7) is:
    Figure PCTCN2016073259-appb-100022
    Figure PCTCN2016073259-appb-100022
    第l层第j个信道上的信噪比SINRj,l与信道估计方式有关，The signal-to-noise ratio SINR j,l on the jth channel of the first layer is related to the channel estimation mode.
    对于MMSE检测：
    Figure PCTCN2016073259-appb-100023
         For MMSE testing:
    Figure PCTCN2016073259-appb-100023
    对于ZF检测：
    Figure PCTCN2016073259-appb-100024
         For ZF detection:
    Figure PCTCN2016073259-appb-100024
    式中，
    Figure PCTCN2016073259-appb-100025
    为噪声功率，W为预编码矩阵，IL为L阶单位矩阵。    In the formula,
    Figure PCTCN2016073259-appb-100025
    For noise power, W is a precoding matrix, and I L is an L-order identity matrix.
  5. 根据权利要求1中所述的双码本预编码选择方法，其特征在于，步骤(2)中常数c的取值为1.25。 The dual codebook precoding selection method according to claim 1, wherein the value of the constant c in the step (2) is 1.25.
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