WO2012092751A1

WO2012092751A1 - Method and system for neighboring cell interference detection

Info

Publication number: WO2012092751A1
Application number: PCT/CN2011/075605
Authority: WO
Inventors: 宁迪浩; 朱登魁; 肖华华; 鲁照华
Original assignee: 中兴通讯股份有限公司
Priority date: 2011-01-05
Filing date: 2011-06-10
Publication date: 2012-07-12
Also published as: CN102594737B; CN102594737A

Abstract

The present invention discloses a method and system for neighboring cell interference detection. The method is applied to a reception end of an Orthogonal Frequency Division Multiplexing (OFDM) or Orthogonal Frequency Division Multiple Access (OFDMA) system. When performing interference and noise detection for a beared data flow within an interference suppression area, the method includes: for each data sub-carrier corresponding to the data flow, after calculating and obtaining the interference and noise covariance matrix of the data sub-carrier location, performing numerical analysis for the interference and noise covariance matrix of the data sub-carrier location, and obtaining an interference and noise power ratio, wherein the interference suppression area is a time-frequency two-dimension resource block in the reception data bearing area. According to the method and system, the size of the interference component can be detected without using a silent frame and a specialized interference measurement signal. Therefore the calculation complexity and operation labor are lower.

Description

一种邻区干扰检测方法及*** Neighborhood interference detection method and system

技术领域 Technical field

本发明涉及邻区干扰检测技术，具体涉及一种邻区干扰检测方法及***。 The invention relates to a neighboring area interference detecting technology, in particular to a neighboring area interference detecting method and system.

背景技术 Background technique

无线通信***总是受到各种各样的干扰，对于第 4代以正交频分多址接入 ( OFDMA, Orthogonal Frequency Division Multiple Access )技术为基础的通信***而言（ 4G, Wimax, LTE ) ,始终受到较严重的正交频分复用（ OFDM, Orthogonal Frequency Division Multiplexing ) 同道干扰 ( CCI , Co-Channel Interference ) 。在蜂窝网络中，由于频谱复用的关系，此种干扰表现为邻区干扰。 Wireless communication systems are always subject to various types of interference, for the fourth generation of communication systems based on OFDMA (Orthogonal Frequency Division Multiple Access) technology (4G, Wimax, LTE) It is always subject to more severe Orthogonal Frequency Division Multiplexing (OFDM) and Co-Channel Interference (CCI). In cellular networks, due to the spectrum multiplexing, such interference appears as neighbor interference.

目前，邻区干扰检测、抑制和消除问题是一个热门的研究问题，也是 4G 通信***同频组网必须要解决的问题。主动式的手段通常表现为功率控制、动态的频率复用、邻区的波束和调度协作以及正在讨论中的协同多点传输 ( CoMP ) 中的联合传输，这些技术在标准制定时就需要做较详细的讨论，需要网络结构和信令支持。而在被动式的干扰消除技术则不依赖于信令的交互，通常由接收机完成，可以广泛适用于各种网络中。 At present, the problem of neighboring area interference detection, suppression and elimination is a hot research issue, and it is also a problem that the 4G communication system must solve in the same frequency network. Proactive approaches typically manifest as power control, dynamic frequency reuse, neighboring beam and scheduling cooperation, and joint transmission in CoMP, which is under discussion. These techniques need to be compared when standards are developed. A detailed discussion requires network structure and signaling support. Passive interference cancellation technology does not rely on the interworking of signaling, usually by the receiver, and can be widely applied to various networks.

在接收侧完成的被动式的干扰消除，相对于非干扰消除接收机来说，复杂度会有相当程度的增加，同时在没有邻区干扰或者邻区干扰较弱时，性能上并不能获得提升，如果能从接收信号中检测出干扰信号的强度，从而选择合适的接收算法，可实现最优化的性能与复杂度的折中。同时，邻区干扰水平这一参数可以广泛的应用于各种主动式的干扰控制和抑制技术，作为这些技术的参考指标。 The passive interference cancellation performed on the receiving side has a considerable increase in complexity compared to the non-interference cancellation receiver. At the same time, when there is no adjacent area interference or the neighboring area interference is weak, the performance cannot be improved. If the intensity of the interfering signal can be detected from the received signal, and an appropriate receiving algorithm is selected, a compromise between optimized performance and complexity can be achieved. At the same time, the neighboring interference level can be widely applied to various active interference control and suppression technologies as a reference indicator for these technologies.

现有的干扰检测手段大致分为两种：一种是在射频接收模块处完成，通过检测信号的峰值功率与均值功率的比值，判断是否存在干扰，此种方法存在的问题一是不能针对某些具体的载波，判断其上是否存在干扰，二是无法具体给出干扰信号的功率大小；另一种是通过在网络上使用静默帧的方式来测量干扰大小，此种方式显然会对网络资源造成浪费，而且由于干扰的时变特性，也无法保证检测出的干扰的有效性。 The existing interference detection methods are roughly divided into two types: one is completed at the RF receiving module, and the ratio of the peak power to the mean power of the detected signal is used to determine whether there is interference. The problem of this method is that it cannot be targeted to a certain Some specific carriers determine whether there is interference on the second, and the second is that the power level of the interference signal cannot be specified; the other is by using a silent frame on the network. Measuring the size of the interference is obviously a waste of network resources, and the effectiveness of the detected interference cannot be guaranteed due to the time-varying characteristics of the interference.

发明内容 Summary of the invention

本发明要解决的技术问题是提供一种邻区干扰检测方法及***，无需利用静默帧，无需专门的干扰测量信号，即可检测出干扰分量的大小，计算复杂度和运算量较低。 The technical problem to be solved by the present invention is to provide a neighboring area interference detecting method and system, which does not need to utilize a silent frame, and can detect the size of the interference component without special interference measurement signal, and the calculation complexity and the calculation amount are low.

为解决上述技术问题，本发明提供了一种邻区干扰检测方法，用于正交频分复用 OFDM或正交频分多址 OFDMA***的接收端 ,在一干扰抑制区域内，对其中承载的一数据流进行干扰噪声检测时，该方法包括： In order to solve the above technical problem, the present invention provides a neighboring area interference detecting method, which is used in a receiving end of an Orthogonal Frequency Division Multiplexing (OFDM) or Orthogonal Frequency Division Multiple Access (OFDMA) system, and carries it in an interference suppression area. When a data stream is subjected to interference noise detection, the method includes:

对所述数据流对应的一数据子载波，在计算得到所述数据子载波所在位置的干扰噪声协方差矩阵后，对所述干扰噪声协方差矩阵进行数值分析，得到干扰噪声功率比值； After calculating an interference noise covariance matrix of the data subcarrier corresponding to the data subcarrier, performing numerical analysis on the interference noise covariance matrix to obtain an interference noise power ratio;

其中，所述干扰抑制区域为接收数据承载区域中的一时频二维资源块。其中，对所述干扰噪声协方差矩阵进行数值分析的步骤包括：釆用特征值分解法或釆用对角线元素法对所述数据子载波所在位置的干扰噪声协方差矩阵进行数值分析。 The interference suppression area is a time-frequency two-dimensional resource block in the received data bearer area. The step of performing numerical analysis on the interference noise covariance matrix comprises: performing eigenvalue decomposition method or using a diagonal element method to perform numerical analysis on an interference noise covariance matrix of a position of the data subcarrier.

其中，釆用特征值分解法对所述数据子载波所在位置的干扰噪声协方差矩阵进行数值分析，得到干扰噪声功率比值的步骤包括： Wherein, the eigenvalue decomposition method is used to perform numerical analysis on the interference noise covariance matrix of the position of the data subcarrier, and the step of obtaining the interference noise power ratio includes:

对所述干扰噪声协方差矩阵进行特征值分解或者奇异值分解，获得所述干扰噪声协方差矩阵的 S个特征值； Performing eigenvalue decomposition or singular value decomposition on the interference noise covariance matrix to obtain S eigenvalues of the interference noise covariance matrix;

从 S个所述特征值中选取最小的非零特征值： _n = 公式计算所述干扰噪声功率比值 I/N:

° 其中，釆用对角线元素法对所述数据子载波所在位置的干扰噪声协方差矩阵进行数值分析，得到干扰噪声功率比值的步骤包括： The smallest non-zero eigenvalue is selected from the S eigenvalues: _n = the formula calculates the interference noise power ratio I/N:

°, wherein the diagonal noise element method is used to numerically analyze the interference noise covariance matrix of the position of the data subcarrier, and the step of obtaining the interference noise power ratio includes:

计算所述干扰噪声协方差矩阵的对角线元素乘积 Prod ^；计算所述干扰噪声协方差矩阵的反对角线元素乘积^^(« - /)；根据所述对角线元素乘积和所述反对角线元素乘积计算干扰噪声度量因 Calculating a diagonal element product Prod ^ of the interference noise covariance matrix; Calculating an anti-angle element product of the interference noise covariance matrix ^^(« - /); calculating an interference noise metric according to the product of the diagonal element and the product of the anti-angle elements

Prod(NI) Prod(NI)

子 IR: IR = Sub IR: IR =

Prod(NI) - Prod(anti - NI) Prod(NI) - Prod(anti - NI)

根据所述干扰噪声度量因子计算所述干扰噪声功率比值 I/N： Calculating the interference noise power ratio I/N according to the interference noise metric:

Ι ΙΝ = 其中， Z为所述干扰噪声协方差矩阵的阶数。Ι ΙΝ = where Z is the order of the interference noise covariance matrix.

本发明还提供了一种邻区干扰检测***，用于正交频分复用 OFDM或正交频分多址 OFDMA***的接收端，在一干扰抑制区域内对其中承载的一数据流进行干扰噪声检测，所述干扰抑制区域为接收数据承载区域中的一时频二维资源块，该***包括，第一装置及第二装置，其中： The present invention also provides a neighboring area interference detecting system, which is used for receiving a data stream carried in an interference suppression area in a receiving end of an Orthogonal Frequency Division Multiplexing (OFDM) or Orthogonal Frequency Division Multiple Access (OFDMA) system. Noise detection, the interference suppression area is a time-frequency two-dimensional resource block in the received data bearer area, the system includes: a first device and a second device, where:

所述第一装置设置成：对所述数据流对应的一数据子载波，计算得到所述数据子载波所在位置的干扰噪声协方差矩阵； The first device is configured to: calculate, according to a data subcarrier corresponding to the data stream, an interference noise covariance matrix of a location of the data subcarrier;

所述第二装置设置成：对所述数据子载波所在位置的所述干扰噪声协方差矩阵进行数值分析，得到干扰噪声功率比值。 The second device is configured to perform a numerical analysis on the interference noise covariance matrix of the location of the data subcarrier to obtain an interference noise power ratio.

其中，所述第二装置是设置成以如下方式对所述数据子载波所在位置的所述干扰噪声协方差矩阵进行的数值分析的：釆用特征值分解法或釆用对角线元素法。 The second device is configured to perform numerical analysis on the interference noise covariance matrix of the location of the data subcarrier in the following manner: using an eigenvalue decomposition method or a diagonal element method.

其中，所述第二装置包括：第一单元、第二单元及第三单元，其中：所述第一单元设置成：对所述干扰噪声协方差矩阵进行特征值分解或者奇异值分解，获得所述干扰噪声协方差矩阵的 S个特征值； The second device includes: a first unit, a second unit, and a third unit, where: the first unit is configured to: perform eigenvalue decomposition or singular value decomposition on the interference noise covariance matrix, and obtain S eigenvalues of the interference noise covariance matrix;

所述第二单元设置成：从 S 个所述特征值中选取最小的非零特征值： mm■ ― j■ ' The second unit is configured to: select a minimum non-zero feature value from the S feature values: mm■ ― j■ '

所述第三单元设置成：釆用如下公式计算所述干扰噪声功率比值 I/N:

The third unit is configured to: 计算 calculate the interference noise power ratio I/N by the following formula:

其中，所述第二装置包括： A单元、 B单元、 C单元及 D单元，其中：所述 A单元设置成：计算所述干扰噪声协方差矩阵的对角线元素乘积 Prod(NI)；所述 B单元设置成：计算所述干扰噪声协方差矩阵的反对角线元素乘积 Prod(anti - NI)；所述 C单元设置成：根据所述对角线元素乘积和所述反对角线元素乘积计算干扰噪声度量因子 IR: IR = P∑^{NI) The second device includes: an A unit, a B unit, a C unit, and a D unit, where: the A unit is configured to: calculate a diagonal element product of the interference noise covariance matrix Prod(NI); the B unit is configured to: calculate an anti-corner element product Prod(anti - NI) of the interference noise covariance matrix; the C unit is set to: according to the diagonal element product sum Calculate the interference noise metric IR by the product of the anti-angle elements: IR = P∑^{NI)

Prod(NI) - Prod(anti - NI) Prod(NI) - Prod(anti - NI)

所述 D单元设置成：根据所述干扰噪声度量因子计算所述干扰噪声功率比值 I/N: IIN 其中， Z为所述干扰噪声协方差矩阵的阶数。 The D unit is configured to: calculate the interference noise power ratio I/N according to the interference noise metric: IIN where Z is an order of the interference noise covariance matrix.

本发明实施例的方法和***不依赖于静默帧或者其他干扰测量手段，在基带接收信号中检测出干扰分量的大小。利用现有的基带检测算法的信道估计参数，计算干扰与噪声的二阶统计协方差矩阵，通过计算该矩阵的数值特征，求出干扰功率与噪声功率的比值干扰功率与噪声功率的比值信息可以作为干扰消除算法使用的依据，也可以对调度、功率控制、干扰协调与避免等技术手段提供参考依据。 The method and system of the embodiments of the present invention do not rely on a silence frame or other interference measurement means to detect the magnitude of the interference component in the baseband received signal. Using the channel estimation parameters of the existing baseband detection algorithm, the second-order statistical covariance matrix of interference and noise is calculated. By calculating the numerical characteristics of the matrix, the ratio of the interference power to the noise power is obtained, and the ratio of the interference power to the noise power can be obtained. As the basis for the use of the interference cancellation algorithm, it can also provide reference for technical means such as scheduling, power control, interference coordination and avoidance.

本发明提出的干扰检测算法和***，是在接收机的基带处理单元完成的，易于与现有的基带接收装置结合，可以充分利用现有基带接收处理单元中的某些中间变量，可以具体检测出某些载波上的干扰水平，给出量化值。算法无需利用静默帧，无需专门的干扰测量信号，从普通的接收信号中即可判断干扰分量的大小，算法实时性好，每部分接收符号，均可给出相应的干扰功率水平，同时每部分相邻载波，均可给出相应的干扰功率水平。由于充分利用了现有基带处理单元中的某些中间变量，算法复杂度和运算量都非常低。 The interference detection algorithm and system proposed by the invention are completed in the baseband processing unit of the receiver, and are easy to be combined with the existing baseband receiving device, and can fully utilize some intermediate variables in the existing baseband receiving processing unit, and can specifically detect The interference level on some carriers is given and the quantized value is given. The algorithm does not need to use the silence frame, and does not need special interference measurement signals. The interference component can be judged from the ordinary received signal. The real-time performance of the algorithm is good. Each part receives the symbol, and the corresponding interference power level can be given. The adjacent carrier can give the corresponding interference power level. Due to the full use of some of the intermediate variables in the existing baseband processing unit, the algorithm complexity and computational complexity are very low.

附图概述 BRIEF abstract

图 1为本发明实施例干扰检测流程图。 FIG. 1 is a flowchart of interference detection according to an embodiment of the present invention.

本发明的较佳实施方式 Preferred embodiment of the invention

为使本发明的目的、技术方案和优点更加清楚明白，下文中将结合附图对本发明的实施例进行详细说明。需要说明的是，在不冲突的情况下，本申请中的实施例及实施例中的特征可以相互任意组合。 In order to make the objects, technical solutions and advantages of the present invention more clear, the following will be combined with the accompanying drawings. The embodiments of the present invention will be described in detail. It should be noted that, in the case of no conflict, the features in the embodiments and the embodiments in the present application may be arbitrarily combined with each other.

本文中的邻区干扰检测方法应用于 OFDM/OFDMA***。文中的发送端可以是基站、中继站等控制设备，也可以是手机、笔记本电脑、手持电脑等终端设备。接收端用于接收发送端的数据信号，类似地，接收端可以是基站，中继站等控制设备，也可以是手机、笔记本电脑、手持电脑等终端设备。 The neighbor interference detection method in this paper is applied to OFDM/OFDMA systems. The transmitting end in the text may be a control device such as a base station or a relay station, or may be a terminal device such as a mobile phone, a notebook computer, or a handheld computer. The receiving end is configured to receive the data signal of the transmitting end. Similarly, the receiving end may be a control device such as a base station or a relay station, or may be a terminal device such as a mobile phone, a notebook computer, or a handheld computer.

接收端将接收数据承载区域划分为一个或多个干扰抑制区域，每一干扰抑制区域为帧 /半帧结构中的一个时频二维资源块，即每一个干扰抑制区域在时间上包含多个连续的 OFDM/OFDMA符号，在频域上包含多个连续的子载波。接收数据承载区域可能包括一个时频二维资源块，也可能包括多个分离的时频二维资源块。在本实施例中，将其中的每一个独立的时频二维资源块作为一个干扰抑制区域。当然，在其他实施例中，接收数据承载区域中的相对独立的各个时频二维资源块也可以被进一步划分为多个干扰抑制区域。 The receiving end divides the received data bearer area into one or more interference suppression areas, and each interference suppression area is a time-frequency two-dimensional resource block in the frame/field structure, that is, each interference suppression area includes multiple times in time. A continuous OFDM/OFDMA symbol comprising a plurality of consecutive subcarriers in the frequency domain. The received data bearer area may include a time-frequency two-dimensional resource block, and may also include a plurality of separate time-frequency two-dimensional resource blocks. In this embodiment, each of the independent time-frequency two-dimensional resource blocks is used as an interference suppression area. Of course, in other embodiments, the relatively independent time-frequency two-dimensional resource blocks in the received data bearer region may be further divided into multiple interference suppression regions.

在 OFDM/OFDMA***中，上述干扰抑制区域可以承载一个或多个数据流，每一数据流对应一个或多个数据子载波和导频子载波，不同数据流对应的导频子载波不同。 In an OFDM/OFDMA system, the interference suppression region may carry one or more data streams, and each data stream corresponds to one or more data subcarriers and pilot subcarriers, and different data streams correspond to different pilot subcarriers.

如图 1所示，在一个干扰抑制区域内，按本实施例方法对其中承载的一个数据流进行邻区干扰检测时，包括： As shown in FIG. 1, when an adjacent interference detection is performed on a data stream carried by the method in this embodiment, the method includes:

步骤 10, 对该数据流对应的每一导频子载波，根据发送端在该导频子载波上发送的导频信号、该导频子载波上的接收信号和该导频子载波所在位置的信道系数估计值,计算得到该导频子载波所在位置的干扰噪声协方差矩阵；用 PsC(z)表示该干扰抑制区域中该数据流对应的第 I 个导频子载波， = 1, · · · , / , 则 PsC(i)所在位置的干扰噪声协方差矩阵 _Ρ(0按下式得到： I-P ) = (y_P {ή - {i) p {i)) (y_P { ~ Κ {ή ρ {ή)^Η ( l ) 其中， / )为发送端在 PsC(z)上发送的导频信号。 W为 ^PsC(0上的接收信号，具体地，为所有接收天线在第 i个导频子载波的接收信号构成的列矢量。为 PsC(i)所在位置的信道系数估计值，具体地，为所有接收天线在第 i个导频子载波所在位置的信道系数估计值构成的列矢量。 /为该干扰抑制区域中该数据流对应的导频子载波的个数。 ( {i)-h_p ( ) p {i))^H表示矩阵Step 10: For each pilot subcarrier corresponding to the data stream, according to a pilot signal sent by the transmitting end on the pilot subcarrier, a received signal on the pilot subcarrier, and a location of the pilot subcarrier. Estimating the channel coefficient, calculating the interference noise covariance matrix of the location of the pilot subcarrier; using PsC(z) to indicate the first pilot subcarrier corresponding to the data stream in the interference suppression region, = 1, · *, /, the interference noise covariance matrix _Ρ location of (i) PsC (0 to give the following _{formula: IP) = (y P {} ή - {i) p {i)) (y P {~ Κ {ή ρ {ή) ^Η ( l ) where / ) is the pilot signal transmitted by the transmitting end on PsC(z). W is the received signal of ^PsC (0, specifically, the column vector formed by the received signals of all receiving antennas on the i-th pilot subcarrier. The estimated value of the channel coefficient at the position where PsC(i) is located, specifically, The column vector formed by the estimated channel coefficients of all receiving antennas at the position of the i-th pilot subcarrier. The number of pilot subcarriers corresponding to the data stream in the region. ( {i)-h _p ( ) p {i)) ^H denotes a matrix

(y_p {i)-h_p (; ())的共轭转置。文中的干扰噪声协方差矩阵是一估计值。步骤 20, 对该数据流对应的每一数据子载波，将计算得到的各导频子载波所在位置的干扰噪声协方差矩阵的加权平均，作为该数据子载波所在位置的干扰噪声协方差矩阵； Conjugate transposition of (y _p {i)-h _p (; ()). The interference noise covariance matrix in this paper is an estimate. Step 20: For each data subcarrier corresponding to the data stream, calculate a weighted average of the interference noise covariance matrix of the location of each pilot subcarrier as the interference noise covariance matrix of the location of the data subcarrier;

用 DsC()表示该干扰抑制区域中该数据流对应的第 j 个数据子载波， 7 = 1,··· J , 则 DsCG)所在位置的干扰噪声协方差矩阵按下式得到：

The DsC() is used to represent the jth data subcarrier corresponding to the data stream in the interference suppression region, and the interference noise covariance matrix at the location of 7 = 1,··· J , then DsCG) is obtained by:

其中， ^为计算 DsCG)所在位置的时，赋予^— _ρ(0的权值， ∑β,=ι, 部分权值可以为 0; J为该干扰抑制区域中的数据子载波的个数。通过以上两步，接收端已经完成了对该干扰抑制区域的邻区干扰噪声估计。对数据承载区域内的各干扰抑制区域均按上述方法计算后，就完成了对该数据承载区域的邻区干扰噪声估计。 Wherein ^ is calculated location DSCG), giving ^ - ρ ₍₀ weight, Σβ, = ι, part of the weight value may be 0; J number of interference suppression for data subcarriers in the region. Through the above two steps, the receiving end has completed the neighboring area interference noise estimation for the interference suppression area. After calculating the interference suppression areas in the data bearer area according to the above method, the neighboring area of the data bearer area is completed. Interference noise estimation.

步骤 30, 对该数据流对应的每一数据子载波，对该数据子载波所在位置的干扰噪声协方差矩阵进行数值分析 , 得到干扰噪声功率比值； Step 30: Perform numerical analysis on the interference noise covariance matrix of the data subcarrier corresponding to each data subcarrier corresponding to the data stream, and obtain an interference noise power ratio;

上述数值分析可釆用特征值分解法和对角线元素法其中之一： The above numerical analysis can use one of the eigenvalue decomposition method and the diagonal element method:

I, 釆用特征值分解法进行数值分析时，步骤 30包括以下步骤： I. When performing numerical analysis using the eigenvalue decomposition method, step 30 includes the following steps:

1 )对干扰噪声协方差矩阵进行特征值分解或者奇异值分解，获得干扰噪声协方差矩阵的 s个特征值： ≥ /1₂ ≥—≥4≥ 0；干扰噪声协方差矩阵为厄尔米特矩阵，因此特征值分解和奇异值分解这两种分解方法等价，因而后文仅以特征值分解为例进行说明。 1) Perform eigenvalue decomposition or singular value decomposition on the interference noise covariance matrix to obtain s eigenvalues of the interference noise covariance matrix: ≥ /1 ₂ ≥−≥4≥ 0; the interference noise covariance matrix is Hermit Matrix, so the two decomposition methods of eigenvalue decomposition and singular value decomposition are equivalent, so the following is only an example of eigenvalue decomposition.

2)从 S个特征值中选取最小的非零特征值： „^ = '= min {λ_;}； 2) Select the smallest non-zero eigenvalue from the S eigenvalues: „^ = '= min {λ _; };

3 公式计算干扰噪声功率比值 Ι/Ν:

3 Formula calculates the interference noise power ratio Ι/Ν:

^{1 y} min ^{1 y} min

II, 釆用对角线元素法进行数值分析时，步骤 30包括以下步骤： 1 )分别计算干扰噪声协方差矩阵的对角线元素乘积和反对角线元素乘对角线元素乘积定义为： Prod _NI—_D =

II. When performing numerical analysis using the diagonal element method, step 30 includes the following steps: 1) Calculate the product of the diagonal element of the interference noise covariance matrix and the product of the diagonal element multiplication diagonal elements, respectively: Prod _NI — _D =

反对角线元素乘积定义为： Ρπχ^αηίί— _ΝΙ—^ )= [ R_NI__D(j)_xy 干扰噪声协方差矩阵为 Z阶矩阵，即 Z*Z维的矩阵。上述公式中， X表示干扰噪声协方差矩阵中元素的行数， y表示干扰噪声协方差矩阵中元素的列数。 The product of the anti-corner element is defined as: Ρπχ^αηίί— _ΝΙ —^ )= [ R _NI _ _D (j) _{xy The} interference noise covariance matrix is a Z-order matrix, that is, a matrix of Z*Z dimensions. In the above formula, X represents the number of rows of elements in the interference noise covariance matrix, and y represents the number of columns of elements in the interference noise covariance matrix.

2)使用如下公式，计算干扰噪声度量因子 IR: 2) Calculate the interference noise metric IR using the following formula:

Prod(R_N1__D(j)) Prod(R _N1 _ _D (j))

Prod R_NI__D (j))― Prodicmti Prod R _NI _ _D (j))― Prodicmti

3)使用如下公式，计算干扰噪声功率比值 I/N:

3) Calculate the interference noise power ratio I/N using the following formula:

本实施例中，上述宽带同频干扰噪声估计和干扰抑制方法的步骤中用到的导频子载波和数据子载波所在位置的信道系数估计值 ^ 及 ( ，可以通过以下方式计算得到： In this embodiment, the channel coefficient estimates ^ and ( ) of the pilot subcarrier and the data subcarrier used in the steps of the wideband co-channel interference noise estimation and interference suppression method are calculated by:

步骤一，对该干扰抑制区域中该数据流对应的每一导频子载波，接收端将该导频子载波上的接收信号与发送端在该导频子载波上发送的导频信号的共轭相乘，得到该导频子载波所在位置的信道系数估计值； Step 1: For each pilot subcarrier corresponding to the data stream in the interference suppression area, the receiving end shares the received signal on the pilot subcarrier with the pilot signal sent by the transmitting end on the pilot subcarrier. Multiplying the yoke to obtain an estimated channel coefficient of the location of the pilot subcarrier;

该干扰抑制区域中该数据流对应的第 I个导频子载波 PsC(i)所在位置的信道系数估计值 ^ ()由下式得到： h_P(i) = y_p(i)p*(i) = --- (6) 其中，（为接收端在第 ,个导频子载波上的接收信号，为发送端在第 ,个导频子载波上发送的导频信号（两端可以约定），表示对取共轭；其他参数含义如上文所述。因为相邻小区在同一导频子载波上的导频信号相关性比较低，通过上述运算，可以滤除导频子载波上相邻小区导频带来的干扰信号，得到较为准确的信道系数估计值。进而，基于各导频子载波所在位置的信道系数估计值的加权平均得到的数据子载波所在位置的信道系数估计值也较为准确。 The channel coefficient estimate ^() at the position of the first pilot subcarrier PsC(i) corresponding to the data stream in the interference suppression region is obtained by: h _P (i) = y _p (i)p*( i) = --- (6) where (the received signal on the first pilot subcarrier of the receiving end is the pilot signal transmitted by the transmitting end on the first pilot subcarrier (both ends can be agreed ), indicating that the pair is conjugated; other parameters have the meanings as described above. Because the correlation of pilot signals on the same pilot subcarrier is relatively low, the interference signal of the adjacent cell pilot band on the pilot subcarrier can be filtered out by the above operation, and a relatively accurate channel coefficient estimation value is obtained. . Furthermore, the channel coefficient estimation value of the position of the data subcarrier obtained based on the weighted average of the channel coefficient estimation values of the positions of the pilot subcarriers is also relatively accurate.

步骤二，对该数据流对应的每一数据子载波，将该数据流对应的各导频子载波所在位置的信道系数估计值的加权平均，作为该数据子载波所在位置的信道系数估计值； Step 2: for each data subcarrier corresponding to the data stream, weighted average of the channel coefficient estimation values of the locations of the pilot subcarriers corresponding to the data stream, as the channel coefficient estimation value of the location of the data subcarrier;

将该干扰抑制区域中该数据流对应的第 j 个数据子载波记为 DsCG), DsCG)所在位置的信道系数估计值 ^( 按下式得到：

其中，《为计算 DsCG)所在位置的^ (7·)时，赋予的权值， ∑a_l} =\ , i=l 部分的权值可以为 0, 其他参数含义如上文所述。接收端可以将该干扰抑制区域再划分为 f个时频二维资源块， =1,2,...; 每一时频二维资源块作为一个信道估计单元，每一信道估计单元中包括至少一个导频子载波和一个数据子载波。 The j-th data sub-carrier corresponding to the data stream in the interference suppression region is recorded as the channel coefficient estimation value of the position where DsCG), DsCG) is located.

Where ^ (7·) of the position of “DsCG” is calculated, the weight given, ∑a _l} =\ , the weight of the i=l part can be 0, and the meanings of other parameters are as described above. The receiving end may further divide the interference suppression area into f time-frequency two-dimensional resource blocks, =1, 2, . . .; each time-frequency two-dimensional resource block is used as a channel estimation unit, and each channel estimation unit includes at least One pilot subcarrier and one data subcarrier.

在进行信道估计单元划分的一实施例中，在按公式 (7)计算某个数据子载波所在位置的信道系数估计值时，为同一信道估计单元中各个导频子载波所在位置的信道系数估计值赋予的权值相同。 In an embodiment in which the channel estimation unit partitioning is performed, when calculating the channel coefficient estimation value of the location of a certain data subcarrier according to formula (7), the channel coefficient estimation of the location of each pilot subcarrier in the same channel estimation unit is used. Values are given the same weight.

在进行信道估计单元划分的另一实施例中，在按公式 (7)计算同一信道估计单元中各个数据子载波所在位置的信道系数估计值时，取一组相同的权值 α,, = 1,···,/， 7 = 1,···, J , 得到的各数据子载波所在位置的信道系数估计值相同。 In another embodiment in which the channel estimation unit partitioning is performed, when the channel coefficient estimation value of the position of each data subcarrier in the same channel estimation unit is calculated according to formula (7), a set of the same weight α, = 1 is taken. ,···, /, 7 = 1,···, J , The estimated channel coefficient of each data subcarrier is the same.

在进行信道估计单元划分的又一实施例，可以结合上述两个实施例的方式。如下： In still another embodiment of performing channel estimation unit division, the manner of the above two embodiments may be combined. as follows:

定义第 k个信道估计单元包含的导频子载波的索引构成的集合为 A, k = \,2,'-、K；第 k个信道估计单元中该数据流对应的每一数据子载波所在位置的信道系数估计值相等，记为 , 接收端按下式来计算该 : Defining a set of indices of pilot subcarriers included in the kth channel estimation unit is A, k = \, 2, '-, K; where each data subcarrier corresponding to the data stream in the kth channel estimation unit is located Location channel The coefficient estimates are equal, which is recorded as: The receiver calculates this by following the formula:

_Λ Κ Λ _Λ Κ Λ

=Σ 1=1 iΣeQi^ (^Ζ·) ( 8 ) 其中， /为一循环变量， / = 1,2,·· ·, ; ¾为计算时，赋予第 /个信道估计单元中各导频子载波所在位置的信道系数估计值的权值，因为是加权平均， κ =Σ 1=1 iΣeQi^ ( ^Ζ ·) ( 8 ) where / is a cyclic variable, / = 1,2,··· ·, ; 3⁄4 is the calculation, assigning the pilots in the channel estimation unit The weight of the channel coefficient estimate at the location of the carrier, because it is a weighted average, κ

a_kl要满足条件∑ I = 1, 0≤ ≤ 1 , 其中 ^ a _kl should satisfy the condition ∑ I = 1, 0 ≤ ≤ 1 , where ^

/=1 I表示导频索引集合包含的导频子载波的个数。在时频上，与某个数据子载波所在位置越近的导频子载波，信道相关性就越强。因此较佳地，在计算釆用的权值 ,中，大于等于其他的权值， i

。可以看出，本实施例在按公式 (7)计算某个数据子载波所在位置的信道系数估计值时，对于同一信道估计单元中各导频子载波所在位置的信道系数估计值，取相同的权值，且计算同一信道估计单元中各数据子载波所在位置的信道系数估计值时，通过取相同的一组权值，使得得到的各数据子载波所在位置的信道系数估计值相同。 /=1 I indicates the number of pilot subcarriers included in the pilot index set. In the time-frequency, the closer the pilot subcarriers are to the location of a certain data subcarrier, the stronger the channel correlation. Therefore, preferably, in calculating the weights used, the weights are greater than or equal to other weights, i

. It can be seen that, when calculating the channel coefficient estimation value of the location of a certain data subcarrier according to the formula (7), the channel coefficient estimation value of the location of each pilot subcarrier in the same channel estimation unit is the same. The weight value, and when calculating the channel coefficient estimation value of the location of each data subcarrier in the same channel estimation unit, the same set of weights is obtained, so that the obtained channel coefficient estimation values of the positions of the data subcarriers are the same.

釆用上述基于信道估计单元的方式可以简化计算。 The above calculation based on the channel estimation unit can simplify the calculation.

上述宽带同频干扰噪声估计和干扰抑制方法中，步骤 20的加权平均可以基于干扰噪声估计单元来进行。接收端将干扰抑制区域再划分为个时频二维资源块， Λ/=1,2,... ; 每个时频二维资源块作为一个干扰噪声估计单元，每一干扰噪声估计单元中包括至少一个导频子载波。同一干扰抑制区域中信道估计单元和干扰噪声估计单元的划分可以相同，也可以不同。 In the above wideband co-channel interference noise estimation and interference suppression method, the weighted average of step 20 can be performed based on the interference noise estimation unit. The receiving end subdivides the interference suppression area into time-frequency two-dimensional resource blocks, Λ/=1, 2,... ; each time-frequency two-dimensional resource block acts as an interference noise estimation unit, and each interference noise estimation unit At least one pilot subcarrier is included. The division of the channel estimation unit and the interference noise estimation unit in the same interference suppression area may be the same or different.

在进行干扰噪声估计单元划分的一实施例中，按公式 (2)计算某个数据子载波所在位置的干扰噪声协方差矩阵时，为同一干扰噪声估计单元中各个导频子载波所在位置的干扰噪声协方差矩阵赋予的权值相同。 In an embodiment in which the interference noise estimation unit is divided, when the interference noise covariance matrix of a certain data subcarrier is calculated according to formula (2), the interference of each pilot subcarrier in the same interference noise estimation unit is The noise covariance matrix gives the same weight.

在进行干扰噪声估计单元划分的另一实施例，按公式 (2)计算同一干扰噪声估计单元中各个数据子载波所在位置的干扰噪声协方差矩阵时，取相同的一组权值 = 1,- -,/ , 7 = 1,·· ·, J , 得到相同的干扰噪声协方差矩阵。在进行干扰噪声估计单元划分的又一实施例，可以结合上述两个实施例的方式。 ^下： In another embodiment in which the interference noise estimation unit partitioning is performed, when the interference noise covariance matrix of the position of each data subcarrier in the same interference noise estimation unit is calculated according to formula (2), the same set of weights = 1, - -, / , 7 = 1,·· ·, J , get the same interference noise covariance matrix. In still another embodiment of performing interference noise estimation unit division, the manner of the above two embodiments may be combined. ^Under:

定义第个干扰噪声估计单元包含的导频子载波的索引构成的集合为 m = \,2 ,M。第 w个干扰噪声估计单元中该数据流对应的每一数据子载波所在位置的干扰噪声协方差矩阵相等，记为 — ^接收端按下式来计算：

The set of indices formed by the pilot subcarriers included in the first interference noise estimation unit is defined as m = \, 2, M. The interference noise covariance matrix of the position of each data subcarrier corresponding to the data stream in the w interference noise estimation unit is equal, and is recorded as: - the receiving end calculates according to the following formula:

其中， /为一循环变量， / = 1,2,···,Μ ; 为计算 ¾— 时，赋予第 /个干扰噪声估计单元中各导频子载波对应的 _NI—_P (/)的权值，因为是加权平均， Where / is a loop variable, / = 1,2,···,Μ; for calculating 3⁄4—, the weight of _NI — _P (/) corresponding to each pilot subcarrier in the first/interference noise estimation unit is assigned Value, because it is a weighted average,

M M

β_η1要满足条件∑| ,| = ι,ο≤ ,≤ i , 其中表示导频索引集合包含 β _η1 satisfies the condition ∑| , | = ι, ο ≤ , ≤ i , where the pilot index set contains

/=1 /=1

的导频子载波的个数。 The number of pilot subcarriers.

可以看出，本实施例在按公式 (2)计算某个数据子载波所在位置的干扰噪声协方差矩阵时，对于同一干扰噪声估计单元中各导频子载波所在位置的干扰噪声协方差矩阵，取相同的权值；且在计算同一干扰噪声估计单元中各数据子载波所在位置的干扰噪声协方差矩阵时，通过取相同的一组权值，使得各数据子载波所在位置的干扰噪声协方差矩阵相同。 It can be seen that, in the embodiment, when calculating the interference noise covariance matrix of the location of a certain data subcarrier according to formula (2), the interference noise covariance matrix of the location of each pilot subcarrier in the same interference noise estimation unit, Taking the same weight; and when calculating the interference noise covariance matrix of each data subcarrier in the same interference noise estimation unit, by taking the same set of weights, the interference noise covariance of each data subcarrier is located The matrix is the same.

时频区域内，与某个数据子载波所在位置越近的导频子载波，信道相关性越强。因此较佳地，计算 ¾^釆用的权值 ,中， / = 1,2,···,Μ , 大于等于其他的权值。 In the time-frequency region, the closer the pilot subcarriers are to the location of a certain data subcarrier, the stronger the channel correlation. Therefore, it is preferable to calculate the weight used for 3⁄4^, where / = 1, 2, ···, Μ , greater than or equal to other weights.

釆用上述基于干扰噪声估计单元的方式可以简化计算。 The above calculation based on the interference noise estimation unit can simplify the calculation.

相应地，本文还提供了一种邻区干扰检测***，用于 OFDM或 OFDMA ***的接收端，在一干扰抑制区域内对其中承载的一数据流进行干扰噪声检测，所述干扰抑制区域为接收数据承载区域中的一时频二维资源块，该*** 包括，第一装置及第二装置，其中： Correspondingly, the present invention also provides a neighboring area interference detecting system for receiving end of an OFDM or OFDMA system, performing interference noise detection on a data stream carried therein in an interference suppression area, and the interference suppression area is receiving a time-frequency two-dimensional resource block in the data bearer area, the system comprising: a first device and a second device, wherein:

所述第一装置设置成：对所述数据流对应的一数据子载波，计算得到所述数据子载波所在位置的干扰噪声协方差矩阵；所述第二装置设置成：对该数据子载波所在位置的干扰噪声协方差矩阵进行数值分析，得到干扰噪声功率比值。 The first device is configured to: calculate, according to a data subcarrier corresponding to the data stream, an interference noise covariance matrix of a location of the data subcarrier; The second device is configured to perform numerical analysis on the interference noise covariance matrix of the location of the data subcarrier to obtain an interference noise power ratio.

其中，所述第二装置是设置成以如下方式对所述数据子载波所在位置的干扰噪声协方差矩阵进行的数值分析的：釆用特征值分解法或釆用对角线元素法。 The second device is configured to perform numerical analysis on the interference noise covariance matrix of the location of the data subcarrier in the following manner: using an eigenvalue decomposition method or a diagonal element method.

其中，当釆用特征值分解法对所述数据子载波所在位置的干扰噪声协方差矩阵进行数值分析时，所述第二装置包括，第一单元、第二单元及第三单元，其中： Wherein, when the eigenvalue decomposition method is used to perform numerical analysis on the interference noise covariance matrix of the location of the data subcarrier, the second device includes: a first unit, a second unit, and a third unit, where:

所述第一单元设置成：对所述干扰噪声协方差矩阵进行特征值分解或者奇异值分解，获得所述干扰噪声协方差矩阵的 S个特征值； The first unit is configured to: perform eigenvalue decomposition or singular value decomposition on the interference noise covariance matrix to obtain S eigenvalues of the interference noise covariance matrix;

所述第二单元设置成：从 s 个所述特征值中选取最小的非零特征值： mm■ ― j■ ' The second unit is configured to: select a minimum non-zero feature value from the s of the feature values: mm■ ― j■ '

述三单元设置成：釆用如下公式计算所述干扰噪声功率比值 I/N:

The three units are set to: 计算 Calculate the interference noise power ratio I/N using the following formula:

其中，当釆用对角线元素法对所述数据子载波所在位置的干扰噪声协方差矩阵进行数值分析时，所述第二装置包括， Α单元、 B单元、 C单元及 D 单元，其中： Wherein, when the diagonal noise element method is used to perform numerical analysis on the interference noise covariance matrix of the location of the data subcarrier, the second device includes: a unit, a B unit, a C unit, and a D unit, where:

所述 A单元设置成：计算所述干扰噪声协方差矩阵的对角线元素乘积 Prod(NI)；所述 B单元设置成：计算所述干扰噪声协方差矩阵的反对角线元素乘积 Prod(anti - NI)；所述 C单元设置成：根据所述对角线元素乘积和所述反对角线元素乘积计算干扰噪声度量因子 IR: IR = P∑^{NI) The A unit is configured to: calculate a diagonal element product Prod(NI) of the interference noise covariance matrix; the B unit is configured to: calculate an anti-corner element product Prod (anti) of the interference noise covariance matrix - NI); the C unit is configured to: calculate an interference noise metric IR according to the product of the diagonal element and the product of the diagonal elements: IR = P∑^{NI)

Prod(NI) - Prod(anti - NI) Prod(NI) - Prod(anti - NI)

所述 D单元设置成：根据干扰噪声度量因子计算干扰噪声功率比值 I/N: The D unit is configured to calculate an interference noise power ratio I/N according to an interference noise metric:

Ι ΙΝ = , ¹ 其中， Z为所述干扰噪声协方差矩阵的阶数。 Ι ΙΝ = , ¹ where Z is the order of the interference noise covariance matrix.

IR _Λ IR _Λ

1 1

v/R-i 下面用一些应用示例对本发明进行进一步说明，在以下示例中，各参数的含义与上述实施例方案相同，且假定接收端已经获得每个导频子载波上的信道系数估计值，并根据公式 (1)计算出每个导频子载波上的干扰噪声协方差矩阵，示例中主要说明在不同的接收天线数和导频数量以及在使用不同的数值分析方法时 , 如何计算得到数据子载波所在位置的干扰噪声协方差矩阵，以及干扰噪声功率比值。 v/Ri The present invention is further illustrated by some application examples. In the following examples, the meanings of the parameters are the same as those of the foregoing embodiment, and it is assumed that the receiving end has obtained the channel coefficient estimation value on each pilot subcarrier, and according to the formula ( 1) Calculate the interference noise covariance matrix on each pilot subcarrier. The example mainly shows how to calculate the data subcarrier position when using different number of receiving antennas and pilots and when using different numerical analysis methods. The interference noise covariance matrix, as well as the interference noise power ratio.

下面结合具体的应用场景，说明本发明所描述的邻区干扰检测算法。实施例 1 The neighboring area interference detection algorithm described in the present invention will be described below in conjunction with a specific application scenario. Example 1

本实施例为釆用特征值分解法计算干扰噪声功率比值的实施例。 This embodiment is an embodiment in which the interference noise power ratio is calculated by the eigenvalue decomposition method.

某通信***，接收天线数为 4, 选择的干扰抑制区域内包含的导频子载波数量为 20。 In a communication system, the number of receiving antennas is 4, and the number of pilot subcarriers included in the selected interference suppression area is 20.

计算得到的各导频子载波所在位置的干扰噪声协方差矩阵为 ,u , 对其进行加权平均得到该数据子载波所在位置的干扰噪声协方差矩阵 N/ = l£N/i ; 对 NI 矩阵进行特征值分解，获得 NI 矩阵的 4 个特征值， λ₁≥λ₂ > λ3 > λ₄ > 0 , 其最小非零特征值为 λ₄。 The calculated interference noise covariance matrix of each pilot subcarrier is u, and weighted and averaged to obtain the interference noise covariance matrix N/= l£N/i of the position of the data subcarrier; for the NI matrix The eigenvalue decomposition is performed to obtain four eigenvalues of the NI matrix, λ ₁ ≥ λ ₂ > λ3 > λ ₄ > 0 , and the minimum non-zero eigenvalue is λ ₄ .

根据公式计算 Ι/Ν , ΙΙΝ =

(λ,. - λ₄) / λ₄。输出 Ι/Ν作为当前干扰抑制区域的干扰功率估计，同时选择另一待处理干扰抑制区域，重复上述步骤，直至完成所有干扰抑制区域的检测。 Calculate Ι/Ν according to the formula, ΙΙΝ =

(λ,. - λ ₄ ) / λ ₄ . The output Ι/Ν is used as the interference power estimation of the current interference suppression area, while another interference suppression area to be processed is selected, and the above steps are repeated until the detection of all interference suppression areas is completed.

实施例 2 Example 2

某通信***，接收天线数为 8, 选择的干扰抑制区域内包含的导频子载波数量为 20。 In a communication system, the number of receiving antennas is 8, and the number of pilot subcarriers included in the selected interference suppression area is 20.

计算得到的各导频子载波所在位置的干扰噪声协方差矩阵为 ,u , 对其进行加权平均得到该数据子载波所在位置的干扰噪声协方差矩阵The calculated interference noise covariance matrix of each pilot subcarrier is located as u, and weighted and averaged to obtain the interference noise association of the location of the data subcarrier. Variance matrix

对 NI 矩阵进行特征值分解，获得 NI 矩阵的 8 个特征值， ≥ λ₂≥ ...≥ λ₈〉 0 , 其最小非零特征值为 λ₈。 The eigenvalue decomposition of the NI matrix is performed to obtain eight eigenvalues of the NI matrix, ≥ λ ₂ ≥ ... ≥ λ ₈ 〉 0 , and the minimum non-zero eigenvalue is λ ₈ .

根据公式计算 Ι/Ν, 〃W = 5^_{l 2}，，₇(λ「λ₈)/λ₈ 。输出 Ι/Ν作为当前干扰抑制区域的干扰功率估计，同时选择另一待处理干扰抑制区域，重复上述步骤，直至完成所有干扰抑制区域的检测。 Calculate Ι/Ν according to the formula, 〃W = 5^ _{l 2} , , ₇ (λ“λ ₈ )/λ ₈ . Output Ι/Ν is used as the interference power estimation of the current interference suppression region, and another interference suppression region to be processed is selected at the same time. Repeat the above steps until the detection of all interference suppression areas is completed.

实施例 3 Example 3

某通信***，接收天线数为 4, 选择的干扰抑制区域内包含的导频子载波数量为 12。 In a communication system, the number of receiving antennas is 4, and the number of pilot subcarriers included in the selected interference suppression area is 12.

计算得到的各导频子载波所在位置的干扰噪声协方差矩阵为 NI_h NI₂, -NIn ,对其进行加权平均得到该数据子载波所在位置的干扰噪声协方差矩阵 = ^ 对 NI 矩阵进行特征值分解，获得 NI 矩阵的 4 个特征值， λ₁≥λ₂ > λ3 > λ₄ > 0 , 其最小非零特征值为 λ₄。 The calculated interference noise covariance matrix of each pilot subcarrier is NI _h NI ₂ , -NIn , and weighted average is obtained to obtain the interference noise covariance matrix of the position of the data subcarrier = ^ Characterization of the NI matrix The value is decomposed to obtain four eigenvalues of the NI matrix, λ ₁ ≥ λ ₂ > λ3 > λ ₄ > 0 , and the minimum non-zero eigenvalue is λ ₄ .

根据公式计算 Ι/Ν , Ι Ι Ν = (λ,. - λ₄) / λ₄。输出 Ι/Ν作为当前干扰抑制区域的干扰功率估计，同时选择另一待处理干扰抑制区域，重复上述步骤，直至完成所有干扰抑制区域的检测。 Calculate Ι/Ν according to the formula, Ι Ι Ν = (λ,. - λ ₄ ) / λ ₄ . The output Ι/Ν is used as the interference power estimation of the current interference suppression area, while another interference suppression area to be processed is selected, and the above steps are repeated until the detection of all interference suppression areas is completed.

实施例 4 Example 4

本实施例为釆用对角线元素法计算干扰噪声功率比值的实施例。 This embodiment is an embodiment in which the interference noise power ratio is calculated by the diagonal element method.

计算得到的各导频子载波所在位置的干扰噪声协方差矩阵为 N ,Nh, -NI₂₀ , 对其进行加权平均得到该数据子载波所在位置的干扰噪声协方差矩阵 N/=l£N/i; The calculated interference noise covariance matrix of each pilot subcarrier is N, Nh, -NI ₂₀ , and weighted average is obtained to obtain the interference noise association of the data subcarrier. Variance matrix N/=l£N/i;

20 =ι 20 =ι

分别计算 NI矩阵的对角线的乘积与反对角线元素的乘积： Calculate the product of the product of the diagonal of the NI matrix and the element of the diagonal, respectively:

4 4

Prod(NI) = l ΝΙ_Χ,_Χ Prod(NI) = l ΝΙ _Χ , _Χ

4 4

Prod(anti - NI) = [ NI_x,_y 其中， x表示干扰噪声协方差矩阵中元素的行数， y表示干扰噪声协方差矩阵中元素的列数。 Prod(anti - NI) = [ NI _x , _y where x represents the number of rows of elements in the interference noise covariance matrix and y represents the number of columns of elements in the interference noise covariance matrix.

使用如下公式，计算干扰噪声度量因子 IR: Calculate the interference noise metric IR using the following formula:

_IR_ ProdjNI) _IR _ ProdjNI)

Prod(NI) - Prod(anti - NI) Prod(NI) - Prod(anti - NI)

使用如下公式，计算 I/N: Calculate I/N using the following formula:

IIN= , 1 ~ IIN= , 1 ~

IR _Λ IR _Λ

4 1 4 1

V/R-1 V/R-1

输出 Ι/Ν作为当前干扰抑制区域的干扰功率估计，同时选择另一待处理干扰抑制区域，重复上述步骤，直至完成所有干扰抑制区域的检测。 The output Ι/Ν is used as the interference power estimation of the current interference suppression area, while another interference suppression area to be processed is selected, and the above steps are repeated until the detection of all interference suppression areas is completed.

实施例 5 Example 5

计算得到的各导频子载波所在位置的干扰噪声协方差矩阵为 ,u , 对其进行加权平均得到该数据子载波所在位置的干扰噪声协方差矩阵 N/=l£N/i; 对角线的乘积与反对角线元素的乘积

Prod anti - NI) = NI_x,_y 使用如下公式，计算干扰噪声度量因子 IR: The calculated interference noise covariance matrix of each pilot subcarrier is located, u, weighted and averaged to obtain the interference noise covariance matrix of the location of the data subcarrier N/=l£N/i; diagonal Product of the product of the diagonal element

Prod anti - NI) = NI _x , _y Calculate the interference noise metric IR using the following formula:

_IR _ ProdjNI) _IR _ ProdjNI)

Prod(NI) - Prod(anti - NI) Prod(NI) - Prod(anti - NI)

使用如下公式，计算 I/N: Calculate I/N using the following formula:

I IN = , 1 ~ I IN = , 1 ~

IR _Λ IR _Λ

\\ 1 \\ 1

V /R-1 V /R-1

实施例 6 Example 6

某通信***，接收天线数为 4 , 选择的干扰抑制区域内包含的导频子载波数量为 12。 In a communication system, the number of receiving antennas is 4, and the number of pilot subcarriers included in the selected interference suppression area is 12.

计算得到的各导频子载波所在位置的干扰噪声协方差矩阵为 NI_h NI₂, -NIn ,对其进行加权平均得到该数据子载波所在位置的干扰噪声协方差矩阵 = ^ 对角线的乘积与反对角线元素的乘积：

The calculated interference noise covariance matrix of each pilot subcarrier is located as NI _h NI ₂ , -NIn , and weighted averaged to obtain the product of the interference noise covariance matrix = ^ diagonal of the position of the data subcarrier Product with anti-corner elements:

4 4

Prod(anti - NI) = [ NI_x,_y 使用如下公式，计算干扰噪声度量因子 IR: Prod(anti - NI) = [ NI _x , _y uses the following formula to calculate the interference noise metric IR:

_IR _ ProdjNI) _IR _ ProdjNI)

Prod(NI) - Prod(anti - NI) Prod(NI) - Prod(anti - NI)

使用如下公式，计算 I/N:

Calculate the I/N using the following formula:

输出 I/N作为当前干扰抑制区域的干扰功率估计，同时选择另一待处理干扰抑制区域，重复上述步骤，直至完成所有干扰抑制区域的检测。 The output I/N is used as the interference power estimation of the current interference suppression area, and another interference suppression area to be processed is selected at the same time, and the above steps are repeated until the detection of all the interference suppression areas is completed.

上述实施例中，实施例 2和实施例 5是较优实施例。 In the above embodiments, Embodiment 2 and Embodiment 5 are preferred embodiments.

实际***中，可能包含本发明所描述的全部流程步骤，也可能只包含其中部分流程步骤，同时不限于本发明所描述的流程步骤。 In the actual system, all the process steps described in the present invention may be included, and only some of the process steps may be included, and are not limited to the process steps described in the present invention.

本领域普通技术人员可以理解上述方法中的全部或部分步骤可通过程序来指令相关硬件完成，所述程序可以存储于计算机可读存储介质中，如只读存储器、磁盘或光盘等。可选地，上述实施例的全部或部分步骤也可以使用一个或多个集成电路来实现。相应地，上述实施例中的各模块 /单元可以釆用硬件的形式实现，也可以釆用软件功能模块的形式实现。本发明不限制于任何特定形式的硬件和软件的结合。 One of ordinary skill in the art will appreciate that all or a portion of the above steps may be accomplished by a program instructing the associated hardware, such as a read-only memory, a magnetic disk, or an optical disk. Alternatively, all or part of the steps of the above embodiments may also be implemented using one or more integrated circuits. Correspondingly, each module/unit in the above embodiment may be implemented in the form of hardware or in the form of a software function module. The invention is not limited to any specific form of combination of hardware and software.

当然，本发明还可有其他多种实施例，在不背离本发明精神及其实质的但这些相应的改变和变形都应属于本发明所附的权利要求的保护范围。 It is a matter of course that the invention may be embodied in various other forms and modifications without departing from the spirit and scope of the invention.

工业实用性本发明实施例方法和***不依赖于静默帧或者其他干扰测量手段，在基带接收信号中检测出干扰分量的大小。利用现有的基带检测算法的信道估计参数，计算干扰与噪声的二阶统计协方差矩阵，通过计算该矩阵的数值特征，求出干扰功率与噪声功率的比值干扰功率与噪声功率的比值信息可以作为干扰消除算法使用的依据，也可以对调度、功率控制、干扰协调与避免等技术手段提供参考依据。因此具有极强的工业实用性。 Industrial Applicability The method and system of the embodiments of the present invention do not rely on a silence frame or other interference measurement means to detect the magnitude of the interference component in the baseband received signal. Using the channel estimation parameters of the existing baseband detection algorithm, the second-order statistical covariance matrix of interference and noise is calculated. By calculating the numerical characteristics of the matrix, the ratio of the interference power to the noise power and the ratio of the interference power to the noise power can be obtained. As the basis for the use of the interference cancellation algorithm, it can also provide reference for technical means such as scheduling, power control, interference coordination and avoidance. Therefore, it has extremely strong industrial applicability.

Claims

权利要求书 Claim

1、一种邻区干 4尤检测方法，用于正交频分复用 OFDM或正交频分多址 OFDMA***的接收端，在一干扰抑制区域内，对其中承载的一数据流进行干扰噪声检测时，该方法包括： A method for detecting a neighboring area 4 for detecting a data stream carried by an OFDM or an orthogonal frequency division multiple access OFDMA system in an interference suppression area When noise is detected, the method includes:

其中，所述干扰抑制区域为接收数据承载区域中的一时频二维资源块。 The interference suppression area is a time-frequency two-dimensional resource block in the received data bearer area.

2、如权利要求 1所述的邻区干扰检测方法，其中，对所述干扰噪声协方差矩阵进行数值分析的步骤包括：釆用特征值分解法或釆用对角线元素法对所述数据子载波所在位置的干扰噪声协方差矩阵进行数值分析。 2. The neighboring area interference detecting method according to claim 1, wherein the step of performing numerical analysis on the interference noise covariance matrix comprises: using an eigenvalue decomposition method or using a diagonal element method to compare the data The interference noise covariance matrix at the location of the subcarrier is numerically analyzed.

3、如权利要求 2所述的邻区干扰检测方法，其中，釆用特征值分解法对所述数据子载波所在位置的干扰噪声协方差矩阵进行数值分析，得到干扰噪声功率比值的步骤包括： The neighboring area interference detecting method according to claim 2, wherein the method for analyzing the interference noise covariance matrix of the position of the data subcarrier by using the eigenvalue decomposition method, and obtaining the interference noise power ratio value comprises:

从 S个所述特征值中选取最小的非零特征值： _n = The smallest non-zero eigenvalue is selected from the S eigenvalues: _n =

如下公式计算所述干扰噪声功率比值 I/N:

° The interference noise power ratio I/N is calculated by the following formula:

°

4、如权利要求 2所述的邻区干扰检测方法，其中，釆用对角线元素法对所述数据子载波所在位置的干扰噪声协方差矩阵进行数值分析，得到干扰噪声功率比值的步骤包括： The neighboring area interference detecting method according to claim 2, wherein the diagonal noise element method performs numerical analysis on the interference noise covariance matrix of the position of the data subcarrier, and the step of obtaining the interference noise power ratio includes :

计算所述干扰噪声协方差矩阵的对角线元素乘积 Pro舉、； Calculating a diagonal element product of the interference noise covariance matrix

计算所述干扰噪声协方差矩阵的反对角线元素乘积^^(« - /)；根据所述对角线元素乘积和所述反对角线元素乘积计算干扰噪声度量因 Calculating an anti-angle element product of the interference noise covariance matrix ^^(« - /); calculating an interference noise metric according to the product of the diagonal element and the product of the anti-angle elements

Prod(NI) Prod(NI)

子 IR: IR = Sub IR: IR =

Prod(NI) - Prod(anti - NI) 根据所述干扰噪声度量因子计算所述干扰噪声功率比值 I/N： ΙΙΝ = , 其中， Z为所述干扰噪声协方差矩阵的阶数。Prod(NI) - Prod(anti - NI) Calculating the interference noise power ratio I/N according to the interference noise metric: ΙΙΝ = , where Z is the order of the interference noise covariance matrix.

5、一种邻区干 4尤检测***，用于正交频分复用 OFDM或正交频分多址 OFDMA***的接收端，在一干扰抑制区域内对其中承载的一数据流进行干扰噪声检测，所述干扰抑制区域为接收数据承载区域中的一时频二维资源块，该***包括，第一装置及第二装置，其中： 5. A neighboring cell 4 detection system, which is used for receiving end of an orthogonal frequency division multiplexing OFDM or orthogonal frequency division multiple access OFDMA system, and performing interference noise on a data stream carried therein in an interference suppression region Detecting that the interference suppression area is a time-frequency two-dimensional resource block in the received data bearer area, the system includes: a first device and a second device, where:

6、如权利要求 5所述的邻区干扰检测***，其中，所述第二装置是设置成以如下方式对所述数据子载波所在位置的所述干扰噪声协方差矩阵进行的数值分析的：釆用特征值分解法或釆用对角线元素法。 The neighboring interference detecting system according to claim 5, wherein the second device is configured to perform numerical analysis on the interference noise covariance matrix of the location of the data subcarrier in the following manner: Use the eigenvalue decomposition method or the diagonal element method.

7、如权利要求 6所述的邻区干扰检测***，其中，所述第二装置包括：第一单元、第二单元及第三单元，其中： 7. The neighboring area interference detecting system according to claim 6, wherein the second device comprises: a first unit, a second unit, and a third unit, wherein:

所述第二单元设置成：从 S 个所述特征值中选取最小的非零特征值：所述第三单元设置成：釆用如下公式计算所述干扰噪声功率比值 I/N: The second unit is configured to: select a minimum non-zero feature value from the S feature values: the third unit is configured to: 计算 calculate the interference noise power ratio I/N by using the following formula:

^{1 y} min ^{1 y} min

8、如权利要求 6所述的邻区干扰检测***，其中，所述第二装置包括： A单元、 B单元、 C单元及 D单元，其中： The neighboring area interference detecting system according to claim 6, wherein the second device comprises: an A unit, a B unit, a C unit, and a D unit, where:

所述 A单元设置成：计算所述干扰噪声协方差矩阵的对角线元素乘积 Prod(NI)； The A unit is configured to: calculate a diagonal element product Prod(NI) of the interference noise covariance matrix;

所述 B单元设置成：计算所述干扰噪声协方差矩阵的反对角线元素乘积 Prod{anti - NI)；所述 c单元设置成：根据所述对角线元素乘积和所述反对角线元素乘积计算干扰噪声度量因子 IR: IR = P∑^{NI) The B unit is configured to: calculate an anti-corner element product of the interference noise covariance matrix Prod{anti - NI); the c unit is configured to: calculate an interference noise metric IR according to the product of the diagonal element and the product of the anti-angle elements: IR = P∑^{NI)

Prod(NI) - Prod(anti - NI) Prod(NI) - Prod(anti - NI)

所述 D单元设置成：根据所述干扰噪声度量因子计算所述干扰噪声功率比值 I/N: IIN = . ¹ , 其中， Z为所述干扰噪声协方差矩阵的阶数。 The D unit is configured to: calculate the interference noise power ratio I/N according to the interference noise metric: IIN = . ¹ , where Z is an order of the interference noise covariance matrix.

IR _Λ IR _Λ

？ 1 ? 1