WO2011108429A1 - チャネル推定回路、チャネル推定方法および受信機 - Google Patents
チャネル推定回路、チャネル推定方法および受信機 Download PDFInfo
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- WO2011108429A1 WO2011108429A1 PCT/JP2011/054090 JP2011054090W WO2011108429A1 WO 2011108429 A1 WO2011108429 A1 WO 2011108429A1 JP 2011054090 W JP2011054090 W JP 2011054090W WO 2011108429 A1 WO2011108429 A1 WO 2011108429A1
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/0202—Channel estimation
- H04L25/0204—Channel estimation of multiple channels
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04J—MULTIPLEX COMMUNICATION
- H04J11/00—Orthogonal multiplex systems, e.g. using WALSH codes
- H04J11/0023—Interference mitigation or co-ordination
- H04J11/0063—Interference mitigation or co-ordination of multipath interference, e.g. Rake receivers
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/0202—Channel estimation
- H04L25/0224—Channel estimation using sounding signals
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2647—Arrangements specific to the receiver only
Definitions
- the present invention relates to a channel estimation circuit, a channel estimation method, and a receiving apparatus of an Orthogonal Frequency Division Multiplexing (OFDM) communication system.
- OFDM Orthogonal Frequency Division Multiplexing
- OFDM Long Term Evolution
- 3GPP 3rd Generation Partnership Project
- OFDM is a scheme in which a band to be used is divided into a plurality of subcarriers and each data symbol is assigned to each subcarrier for transmission, and the subcarriers are arranged so as to be orthogonal to each other on the frequency axis. Excellent frequency utilization efficiency.
- each subcarrier since each subcarrier has a narrow band, the influence of multipath interference can be suppressed, and high-speed and large-capacity communication can be realized.
- Patent Document 1 and Non-Patent Document 1 the IFFT (Inverse Fast Fourier Transform) process is performed on the channel estimation value of each subcarrier estimated from the reference signal to create a delay profile, and components below a predetermined threshold are regarded as noise.
- a channel estimation technique is disclosed that suppresses the influence of noise in the time domain by regarding and replacing with “0”. It is known that an accurate channel estimation value can be obtained by using such a channel estimation technique.
- FIG. 9 is a block diagram illustrating a conventional configuration example of a channel estimation circuit that obtains a channel estimation value of each subcarrier from a reception signal of each subcarrier.
- FIG. 10 is a flowchart showing the flow of processing by the channel estimation circuit shown in FIG.
- the conventional channel estimation circuit shown in FIG. 9 includes a pattern cancellation unit 41, a virtual waveform addition unit 42, an IFFT processing unit 43, a noise suppression unit 44, and an FFT processing unit 45.
- the pattern cancellation unit 41 cancels the pattern of the reference signal multiplexed and transmitted with the data symbol, and obtains the channel estimation value of each subcarrier (FIG. 10, step S20).
- the virtual waveform adding unit 42 adds a waveform so that the number of samples is a power of 2 to the channel estimation value estimated from the reference signal (step S21 in FIG. 10).
- the IFFT processing unit 43 converts the channel estimation value to which the waveform is added from a frequency component into a complex delay profile in the time domain (FIG. 10, step S22).
- the noise suppression unit 44 obtains a power delay profile from the complex delay profile, regards a sample whose power delay profile is equal to or less than a predetermined threshold as noise, and replaces the sample of the complex delay profile with “0” (FIG. 10, step S23). ).
- the FFT processing unit 45 converts the complex delay profile after the noise suppression processing into frequency components again, and obtains a channel estimation value in which noise is suppressed (step S24 in FIG. 10).
- Patent Document 2 discloses a channel estimation technique for performing mask processing for multiplying a rectangular wave on the time axis. With this technique, a noise component having a large delay time can be removed, so that a large noise component can also be removed.
- the process of multiplying the rectangular wave on the time axis has a problem of causing signal distortion at the waveform end after the noise removal process.
- the noise removal effect is greater than the influence of waveform edge distortion, and as a result, channel estimation accuracy is improved.
- the influence of waveform edge distortion cannot be ignored, and there is a problem in that the channel estimation accuracy decreases.
- the present invention relates to a channel estimation circuit, a channel estimation method, and a receiver capable of effectively removing noise components in the time domain and realizing accurate channel estimation in channel estimation of a wireless communication system using OFDM.
- the purpose is to provide.
- a known reference signal multiplexed with a data symbol and transmitted is used.
- Estimating means for obtaining a channel estimated value of each subcarrier; first converting means for converting the channel estimated value into a complex delay profile in the time domain; and noise suppressing means for suppressing noise by processing the complex delay profile;
- the complex delay profile processed by the noise suppression means is converted into the frequency domain, and the second conversion means for outputting the channel estimation value in which the noise is suppressed, and the state of the channel estimated by the estimation means are determined.
- Determining means, and the noise suppressing means is adapted to determine the complex delay profile according to the channel status determined by the determining means.
- Channel estimation circuit is provided which is characterized in that part to masking processing.
- Is used to calculate the channel estimation value of each subcarrier convert the channel estimation value into a complex delay profile in the time domain, process the complex delay profile to suppress noise, and suppress the noise.
- the channel estimation method for converting the channel frequency into the frequency domain and outputting the channel estimation value in which noise is suppressed the channel condition is determined when obtaining the channel estimation value of each subcarrier, and the determination is performed when noise is suppressed.
- a channel characterized by masking a part of the complex delay profile according to the channel conditions Constant method is provided.
- a processing unit that converts a signal wave that has been orthogonal frequency division multiplexed transmission into a frequency domain, and a channel estimation value of each subcarrier from a reception signal of each subcarrier obtained by this processing unit.
- a demodulator that demodulates the signal, and a channel estimator according to the first aspect is provided as a channel estimator.
- noise components can be effectively removed in the time domain, and accurate channel estimation can be realized.
- FIG. 10 It is a block diagram which shows the conventional structural example of the channel estimation circuit which calculates
- 10 is a flowchart showing a flow of processing by the channel estimation circuit shown in FIG. 9. It is a figure which shows an example of the complex delay profile in which the noise component exceeding a threshold value exists.
- LTE Long Term Evolution
- 3GPP 3rd Generation Partnership Project
- FIG. 1 is a block configuration diagram of a transmitter of a wireless communication system using OFDM according to an embodiment of the present invention.
- the transmitter 10 includes a channel encoding unit 11, a channel modulation unit 12, an IFFT processing unit 13, a CP (Cyclic Prefix) adding unit 14, a D / A (Digital / Analog) conversion unit 15, and a transmission antenna 16.
- FIG. 2 is a block configuration diagram of a receiver of a wireless communication system using OFDM according to an embodiment of the present invention, and shows a configuration of an LTE receiver.
- the receiver 20 includes a receiving antenna 21, an A / D (Analog / Digital) conversion unit 22, an FFT (Fast Fourier Transform) timing detection unit 23, a CP removal unit 24, an FFT processing unit 25, a channel estimation unit 26, a channel, and the like.
- FIG. 3 is a block diagram of a channel estimation circuit used as the channel estimation unit 26 shown in FIG.
- the channel estimation unit 26 includes a pattern cancellation unit 31, a virtual waveform addition unit 32, an IFFT processing unit 33, a noise suppression unit 34, an FFT processing unit 35, an SNR estimation unit 36, and a control unit 37.
- the channel encoder 11 performs error detection coding / error correction coding on the transmission data.
- the data channel modulation unit 12 maps transmission data subjected to error detection coding / error correction coding to an I component and a Q component.
- the IFFT processing unit 13 converts transmission data mapped to the I component and the Q component into a time-domain signal wave.
- CP adding section 14 adds a CP to the head of the OFDM symbol in order to prevent the influence of intersymbol interference due to multipath.
- the D / A conversion unit 15 converts the OFDM symbol to which the CP is added from a digital signal to an analog signal.
- the OFDM symbol converted into the analog signal is transmitted from the transmission antenna 16.
- the reception signal received by the reception antenna 21 is input to the A / D conversion unit 22.
- the A / D conversion unit 22 converts the received signal from an analog signal to a digital signal, and outputs the signal to the FFT timing detection unit 23 and the CP removal unit 24.
- the FFT timing detection unit 23 detects FFT timing information from the received signal converted into a digital signal.
- the CP removing unit 24 removes the CP added to the head from the OFDM symbol based on the detected FFT timing information.
- the FFT processing unit 25 converts the time-domain signal wave from which the CP is removed into each subcarrier component.
- the channel estimation unit 26 obtains a channel estimation value of each subcarrier from the reception signal of each subcarrier obtained by the FFT processing unit 25 using a known reference signal multiplexed and transmitted with the data symbol.
- the channel equalizer 27 multiplies the received signal of each subcarrier by the complex conjugate of the channel estimation value obtained by the channel estimator 26 to compensate for the distortion of the signal received on the channel (channel equalization).
- the channel demodulator 28 converts the received signal of each subcarrier whose channel influence is compensated from the I component and the Q component into likelihood information.
- the channel decoding unit 29 performs error correction decoding / error detection on the likelihood information obtained by the channel demodulation unit 28 to obtain received data.
- the pattern canceling unit 31 and the virtual waveform adding unit 32 of the channel estimation unit 26 are multiplexed with data symbols and transmitted from the received signal of each subcarrier obtained by converting the OFDM-transmitted signal wave into the frequency domain. It operates as an estimation means for obtaining a channel estimation value of each subcarrier using a known reference signal.
- the IFFT processing unit 33 operates as a first conversion unit that converts the channel estimation value into a complex delay profile in the time domain.
- the noise suppression unit 34 operates as a noise suppression unit that suppresses noise by processing the complex delay profile.
- the FFT processing unit 35 operates as a second conversion unit that converts the complex delay profile processed by the noise suppression unit 34 into the frequency domain and obtains a channel estimation value in which noise is suppressed.
- the SNR estimation unit 36 and the control unit 37 operate as a determination unit that determines the channel status estimated in the pattern cancellation unit 31 and the virtual waveform addition unit 32.
- FIG. 4 is a flowchart showing a flow of processing by the channel estimation unit 26 shown in FIG. The channel estimation operation will be described with reference to FIGS.
- the pattern cancel unit 31 cancels the reference signal pattern multiplexed and transmitted with the data symbol, and obtains the channel estimation value of each subcarrier (FIG. 4, step S10).
- the channel estimation value estimated from the reference signal is input to the SNR estimation unit 36 and the virtual waveform addition unit 32.
- the SNR estimation unit 36 estimates the SNR of the channel and notifies the control unit 37 of the estimation result (step S11 in FIG. 4).
- the virtual waveform adding unit 32 adds a waveform so that the number of samples is a power of 2 (FIG. 4, step S12).
- the channel estimation value with the added waveform is input to the IFFT processing unit 33.
- the IFFT processing unit 33 converts the frequency component of the channel estimation value into a complex delay profile in the time domain (FIG. 4, step S13).
- the noise suppression unit 34 obtains a power delay profile from the complex delay profile, regards a sample whose power delay profile is equal to or less than a threshold value as noise, and replaces the sample in the complex delay profile with “0” (FIG. 4, step S14).
- the control unit 37 refers to the SNR estimated value notified from the SNR estimation unit 36 and determines whether the environment is a low SNR environment or a high SNR environment (step S15 in FIG. 4).
- the noise suppression unit 34 does not perform any processing in the case of a high SNR environment, but in the case of a low SNR environment, a mask process for replacing a part of the complex delay profile with “0” (details will be described later). (Step S16 in FIG. 4).
- the FFT processing unit 35 converts the complex delay profile after the noise suppression processing into frequency components again, and obtains a channel estimation value in which noise is suppressed (step S17 in FIG. 4).
- FIG. 5 is a diagram for explaining the effect of the mask process on the complex delay profile.
- Masking of the complex delay profile is performed for a noise component having a large delay time in the power delay profile.
- noise components that could not be removed by the noise suppression process using the threshold value are removed by performing the mask process (shaded portion).
- mask processing is performed according to the channel conditions. This is because when the mask processing is performed in a high SNR environment, the accuracy of the band edge channel estimation value deteriorates. The reason will be described below.
- FIG. 6 is a diagram for explaining the relationship between the delay profile in the time domain and the channel estimation value in the frequency domain.
- description will be made using a power delay profile instead of a complex delay profile.
- this processing means convolution integration of the original channel estimation value and a sinc function that is a frequency waveform of a rectangular wave, as shown in FIG.
- the influence of noise is removed due to the smoothing effect, but signal distortion occurs at the waveform end.
- the noise suppression process using the normal threshold and the mask process are used together, but it is not always necessary to use them together.
- the noise suppression unit 34 may be configured only with mask processing.
- FIG. 7 is a diagram for explaining another embodiment of the mask process.
- a low SNR environment and a high SNR environment are divided into two based on the SNR estimation value, and a mask process is performed in a low SNR environment and a mask process is not performed in a high SNR environment. did.
- the present invention is not necessarily limited to this.
- the mask processing range is changed according to the SNR value, and the mask processing range is increased as the SNR is decreased, and the mask processing range is decreased as the SNR is increased. good.
- the mask process in the medium range is performed as shown in (b).
- the SNR environment a relatively wide range of mask processing is performed as shown in FIG.
- FIG. 7 shows an example in which the mask processing range is divided into three stages. It may be divided more finely than this, or may be configured to smoothly change the mask processing range in accordance with the SNR change.
- FIG. 8 is a diagram for explaining still another embodiment of mask processing.
- the process of multiplying the corresponding part of the delay profile by “0” is described as an example. In this case, not performing the mask process can be considered as a process of multiplying the delay profile by “1”.
- this coefficient may be changed according to the SNR, and the coefficient may be made smaller in the low SNR environment and larger in the high SNR environment.
- a delay profile shown in the figure shows a power delay profile for the sake of simplicity
- the delay profile is multiplied by a coefficient of 0.5
- the delay profile is multiplied by a coefficient of 0.0 as shown in (c).
- FIG. 8 shows an example in which the coefficient applied to the delay profile is divided into three stages. The coefficients may be divided more finely, and the coefficient may be changed smoothly according to the change in SNR.
- the configuration for determining whether to perform mask processing using the SNR estimated value has been described as an example, but the present invention is not necessarily limited to this.
- the channel estimation accuracy at the band edge decreases, but the band center portion is not significantly affected. Therefore, instead of SNR, it is also possible to determine whether to perform mask processing based on scheduling information indicating where in the band the data addressed to itself is mapped. That is, the mask processing may be performed when the data addressed to itself is mapped only to the center portion of the band, and the mask processing may not be performed when data is also present at the band edge.
- the mask processing can be controlled using both scheduling information and SNR.
- the LTE discussed in 3GPP has been described as an example, but the present invention is not necessarily limited to this.
- the present invention can be similarly implemented in a system using other OFDM transmission schemes and other wireless communication systems.
- the present invention can be widely used in a mobile phone, a data communication card, a PHS (Personal Handyphone System), a PDA (Personal Data Assistance, Personal Digital Assistant), a receiver of a communication device such as a radio base station.
- a mobile phone a data communication card
- a PHS Personal Handyphone System
- a PDA Personal Data Assistance, Personal Digital Assistant
- a receiver of a communication device such as a radio base station.
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Abstract
Description
図1は、本発明の実施の形態に係るOFDMを用いた無線通信システムの送信機のブロック構成図である。この送信機10は、チャネル符号化部11、チャネル変調部12、IFFT処理部13、CP(Cyclic Prefix)付加部14、D/A(Digital/Analog)変換部15、および送信アンテナ16を備える。
まず、図1に示す送信機10の動作を説明する。送信機10には、各ユーザ宛の送信データが入力される。チャネル符号化部11は、この送信データに、誤り検出符号化・誤り訂正符号化を施す。データチャネル変調部12は、誤り検出符号化・誤り訂正符号化が施された送信データを、I成分およびQ成分にマッピングする。IFFT処理部13は、I成分およびQ成分にマッピングされた送信データを、時間領域の信号波へ変換する。CP付加部14は、マルチパスによるシンボル間干渉の影響を防ぐために、OFDMシンボルの先頭にCPを付加する。D/A変換部15は、CPが付加されたOFDMシンボルを、デジタル信号からアナログ信号へ変換する。アナログ信号に変換されたOFDMシンボルは、送信アンテナ16から送信される。
図4は、図3に示すチャネル推定部26による処理の流れを示すフローチャートである。図3および図4を参照して、チャネル推定の動作について説明する。
図5は、複素遅延プロファイルに対するマスク処理の効果を説明する図である。電力遅延プロファイルのうち遅延時間の大きい雑音成分について、複素遅延プロファイルのマスク処理を行う。これにより、閾値を用いた雑音抑圧処理では除去しきれなかった雑音成分が、マスク処理(網掛け部分)を行うことによって除去される。
以上の実施の形態では、通常の閾値を用いた雑音抑圧処理とマスク処理を併用しているが、必ずしも併用する必要は無い。雑音抑圧部34は、マスク処理のみの構成であってもよい。
11 チャネル符号化部
12 チャネル変調部
13 IFFT処理部
14 CP付加部
15 D/A変換部
16 送信アンテナ
20 受信機
21 受信アンテナ
22 A/D変換部
23 FFTタイミング検出部
24 CP除去部
25 FFT処理部
26 チャネル推定部
27 チャネル等化部
28 チャネル復調部
29 チャネル復号部
31、41 パターンキャンセル部(推定手段の一部)
32、42 仮想波形追加部(推定手段の一部)
33、43 IFFT処理部(第1の変換手段)
34、44 雑音抑圧部(雑音抑圧手段)
35、45 FFT処理部(第2の変換手段)
36 SNR推定部(判断手段の一部)
37 制御部(判断手段の一部)
Claims (11)
- 直交周波数分割多重伝送された信号波を周波数領域に変換して得られた各サブキャリアの受信信号から、データシンボルと共に多重されて伝送された既知のリファレンスシグナルを用いて、上記各サブキャリアのチャネル推定値を求める推定手段と、
上記チャネル推定値を時間領域の複素遅延プロファイルに変換する第1の変換手段と、
上記複素遅延プロファイルを処理することにより雑音を抑圧する雑音抑圧手段と、
この雑音抑圧手段により処理された上記複素遅延プロファイルを周波数領域に変換して、雑音が抑圧されたチャネル推定値を得る第2の変換手段と、
上記推定手段において推定されるチャネルの状況を判断する判断手段と
を有し、
上記雑音抑圧手段は、上記判断手段の判断したチャネルの状況に応じて、上記複素遅延プロファイルの一部をマスク処理する
ことを特徴とするチャネル推定回路。 - 請求項1記載のチャネル推定回路において、前記判断手段は、信号対雑音比を判断基準として、チャネルの状況を判断することを特徴とするチャネル推定回路。
- 請求項2記載のチャネル推定回路において、前記雑音抑圧手段は、信号対雑音比が所定の値より低い場合に、前記マスク処理を行うことを特徴とするチャネル推定回路。
- 請求項1から3のいずれか1項記載のチャネル推定回路において、前記判断手段は、データが帯域のどこにマッピングされるかというスケジューリング情報を判断基準として、チャネルの状況を判断することを特徴とするチャネル推定回路。
- 請求項4記載のチャネル推定回路において、前記雑音抑圧手段は、帯域中央部分のみにデータがスケジューリングされる場合に前記マスク処理を行うことを特徴とするチャネル推定回路。
- 請求項1から5のいずれか1項記載のチャネル推定回路において、前記雑音抑圧手段は、前記判断手段の判断したチャネルの状況に応じて、前記マスク処理を行う範囲を変化させることを特徴とするチャネル推定回路。
- 請求項6記載のチャネル推定回路において、信号対雑音比が低いほど前記マスク処理を行う範囲を広くすることを特徴とするチャネル推定回路。
- 請求項1から7のいずれか1項記載のチャネル推定回路において、前記雑音抑圧手段は、前記判断手段の判断したチャネルの状況に応じて前記複素遅延プロファイルに掛ける係数を調節することによって、前記マスク処理を実現することを特徴とするチャネル推定回路。
- 請求項8記載のチャネル推定回路において、前記雑音抑圧手段は、信号対雑音比が所定の値より低いほど、前記係数を小さくすることを特徴とするチャネル推定回路。
- 直交周波数分割多重伝送された信号波を周波数領域に変換して得られた各サブキャリアの受信信号から、データシンボルと共に多重されて伝送された既知のリファレンスシグナルを用いて、上記各サブキャリアのチャネル推定値を求め、
上記チャネル推定値を時間領域の複素遅延プロファイルに変換し、
上記複素遅延プロファイルを処理することにより雑音を抑圧し、
雑音が抑圧された複素遅延プロファイルを周波数領域に変換して、雑音が抑圧されたチャネル推定値を出力する
チャネル推定方法において、
上記各サブキャリアのチャネル推定値を求める際にチャネルの状況を判断し、
上記雑音を抑圧するときに、判断されたチャネルの状況に応じて、上記複素遅延プロファイルの一部をマスク処理する
ことを特徴とするチャネル推定方法。 - 直交周波数分割多重伝送された信号波を周波数領域に変換する処理部と、
この処理部により得られた各サブキャリアの受信信号から各サブキャリアのチャネル推定値を求めるチャネル推定部と、
上記各サブキャリアの受信信号に上記チャネル推定値の複素共役を乗算してチャネル等化するチャネル等化部と、
このチャネル等化部によりチャネル等化された各サブキャリアの受信信号を復調する復調部と
を有し、
上記チャネル推定部として、請求項1記載のチャネル推定回路を有する
ことを特徴とする受信機。
Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
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JP2012503089A JPWO2011108429A1 (ja) | 2010-03-05 | 2011-02-24 | チャネル推定回路、チャネル推定方法および受信機 |
EP11750539.6A EP2544391A4 (en) | 2010-03-05 | 2011-02-24 | CHANNEL ESTIMATION SWITCHING, CHANNEL ESTIMATION PROCESS AND RECEIVER |
US13/582,697 US20120328055A1 (en) | 2010-03-05 | 2011-02-24 | Channel estimation circuit, channel estimation method, and receiver |
CN2011800124403A CN102792617A (zh) | 2010-03-05 | 2011-02-24 | 信道估计电路、信道估计方法和接收机 |
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PCT/JP2011/054090 WO2011108429A1 (ja) | 2010-03-05 | 2011-02-24 | チャネル推定回路、チャネル推定方法および受信機 |
Country Status (6)
Country | Link |
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US (1) | US20120328055A1 (ja) |
EP (1) | EP2544391A4 (ja) |
JP (1) | JPWO2011108429A1 (ja) |
CN (1) | CN102792617A (ja) |
TW (1) | TW201212597A (ja) |
WO (1) | WO2011108429A1 (ja) |
Cited By (5)
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JP2013168853A (ja) * | 2012-02-16 | 2013-08-29 | Sharp Corp | 受信装置、受信方法および受信プログラム |
CN106330797A (zh) * | 2015-07-10 | 2017-01-11 | 晨星半导体股份有限公司 | 通道效应消除装置及通道效应消除方法 |
JP2018007240A (ja) * | 2016-06-27 | 2018-01-11 | レジック・アイデントシステムズ・アクチェンゲゼルシャフト | Rfid受信装置および無線信号に符合化されたデータビットを抽出する方法 |
CN109691046A (zh) * | 2016-09-15 | 2019-04-26 | 索尼半导体解决方案公司 | 发送装置和*** |
JP2019114878A (ja) * | 2017-12-21 | 2019-07-11 | 日本電信電話株式会社 | 広帯域無線通信システムのチャネル推定装置およびチャネル推定方法 |
Families Citing this family (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP5601330B2 (ja) * | 2010-02-01 | 2014-10-08 | 日本電気株式会社 | チャネル推定値補間回路及び方法 |
US10057021B2 (en) * | 2015-04-24 | 2018-08-21 | Ubiquiti Networks, Inc. | Resource allocation in a wireless communication system |
US10651912B2 (en) | 2018-02-07 | 2020-05-12 | At&T Intellectual Property I, L.P. | Reciprocity based channel state information acquisition for frequency division duplex system |
US11411779B2 (en) * | 2020-03-31 | 2022-08-09 | XCOM Labs, Inc. | Reference signal channel estimation |
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- 2011-02-24 WO PCT/JP2011/054090 patent/WO2011108429A1/ja active Application Filing
- 2011-02-24 EP EP11750539.6A patent/EP2544391A4/en not_active Withdrawn
- 2011-02-24 CN CN2011800124403A patent/CN102792617A/zh active Pending
- 2011-02-24 JP JP2012503089A patent/JPWO2011108429A1/ja active Pending
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JP2013168853A (ja) * | 2012-02-16 | 2013-08-29 | Sharp Corp | 受信装置、受信方法および受信プログラム |
CN106330797A (zh) * | 2015-07-10 | 2017-01-11 | 晨星半导体股份有限公司 | 通道效应消除装置及通道效应消除方法 |
JP2018007240A (ja) * | 2016-06-27 | 2018-01-11 | レジック・アイデントシステムズ・アクチェンゲゼルシャフト | Rfid受信装置および無線信号に符合化されたデータビットを抽出する方法 |
CN109691046A (zh) * | 2016-09-15 | 2019-04-26 | 索尼半导体解决方案公司 | 发送装置和*** |
JP2019114878A (ja) * | 2017-12-21 | 2019-07-11 | 日本電信電話株式会社 | 広帯域無線通信システムのチャネル推定装置およびチャネル推定方法 |
Also Published As
Publication number | Publication date |
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JPWO2011108429A1 (ja) | 2013-06-27 |
US20120328055A1 (en) | 2012-12-27 |
TW201212597A (en) | 2012-03-16 |
CN102792617A (zh) | 2012-11-21 |
EP2544391A4 (en) | 2014-01-15 |
EP2544391A1 (en) | 2013-01-09 |
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