WO2005034333A1 - Procede permettant de faire fonctionner une machine a champ tournant, et convertisseur utilise a cet effet - Google Patents

Procede permettant de faire fonctionner une machine a champ tournant, et convertisseur utilise a cet effet Download PDF

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Publication number
WO2005034333A1
WO2005034333A1 PCT/EP2004/011048 EP2004011048W WO2005034333A1 WO 2005034333 A1 WO2005034333 A1 WO 2005034333A1 EP 2004011048 W EP2004011048 W EP 2004011048W WO 2005034333 A1 WO2005034333 A1 WO 2005034333A1
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WO
WIPO (PCT)
Prior art keywords
phase
current
machine
sll
intermediate circuit
Prior art date
Application number
PCT/EP2004/011048
Other languages
German (de)
English (en)
Inventor
Thomas Treichl
Andreas Szajek
Michael Hackner
Andreas Albrecht
Ulrich Herb
Hans-Georg Hornung
Original Assignee
Sensor-Technik Wiedemann Gmbh
Agco Gmbh & Co. Ohg
Salwit Agrarenergie Gmbh
Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Sensor-Technik Wiedemann Gmbh, Agco Gmbh & Co. Ohg, Salwit Agrarenergie Gmbh, Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. filed Critical Sensor-Technik Wiedemann Gmbh
Publication of WO2005034333A1 publication Critical patent/WO2005034333A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/493—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode the static converters being arranged for operation in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/16—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the circuit arrangement or by the kind of wiring
    • H02P25/22—Multiple windings; Windings for more than three phases
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H02P27/12—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation pulsing by guiding the flux vector, current vector or voltage vector on a circle or a closed curve, e.g. for direct torque control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0043—Converters switched with a phase shift, i.e. interleaved

Definitions

  • FIG. 1 schematically shows such an inverter and a three-phase machine with three phases each.
  • the three windings of the machine, each corresponding to one phase, have terminals Ul, U2, VI, V2, Wl, W2.
  • the terminals U2, V2, W2 are interconnected to a star point; VI is with switches Sll, S12 of a first strand, Ul with switches S21, S22 of a second strand and Wl with switches S31 ,.
  • a control circuit of the inverter opens and closes the switches of the individual strings in accordance with a predetermined time pattern in order to energize the individual phases of the induction machine in such a way that a rotating magnetic field is generated in the machine which causes a rotation of a Rotors drives.
  • the drive voltages applied to the individual terminals Ul, VI, Wl or phases are ideal usually sine waves offset against each other by a third period.
  • a conventional inverter cannot easily generate these continuously variable voltage values; they are approximated by the control circuit operating cyclically with a cycle period that is many times shorter than the rotation period of the field, and in each cycle opening or closing the individual switches of the inverter with a pulse duty factor that is proportional to the voltage value currently to be generated ,
  • the magnetic field generated in the rotating field machine is modeled using so-called space vectors, the direction of which indicates the phase of rotation of the rotating magnetic field and the length of which corresponds to the strength of the magnetic field.
  • a three-strand inverter as shown in FIG. 1 can assume eight different switching states, denoted uO, ul, ..., u7, to which a room pointer can be assigned in each case.
  • the switching states of the switches S12, S22, S32 are each opposite to those of the switches S11, S21, S31.
  • the switching states uO u7 and all terminals are Ul, VI, Wl of the induction machine at the same potential, and it flows '' no current from the intermediate circuit by the inverter to the machine.
  • a current flows through the switch S11 into the terminal Ul, and two currents, each with half the current, flow out of the machine via the terminals VI, Wl and the switches S22, S32.
  • the magnetic fields generated by the three windings overlap in the direction designated ul in FIG. 1.
  • the switches Sll, S21, S32 are open, equally strong currents flow into the terminals Ul, VI of the machine and the sum of these currents via the terminal Wl the, and the magnetic fields generated overlap in the direction u2.
  • FIG. 2 is a diagram showing the space pointers corresponding to the switching states; the space pointers uO and u7 are of vanishing length.
  • the switching states corresponding to the neighboring base space pointers u x , u 2 are set within time cycles in each case, which is proportional to the length of the projection of u '(t) onto the relevant basic space vector Ux or u 2 .
  • An exemplary switching pattern is shown in FIG. 3.
  • the top three curves show the switching states of switches Sll to S32, the curves labeled IS11, IS21 and IS31 show the strengths of currents flowing through switches Sll, S21 and S31, and Id the strength of a resulting intermediate circuit current.
  • a first phase I of the working cycle the switches S11, S21, S31 are open and the other switches are closed, corresponding to the switching state uO.
  • the streams JS11, IS21, IS31 are 0, and as a result the intermediate circuit current Id is 0.
  • a current with a current intensity I determined by the design of the inverter and the induction machine flows through the switch Sll and the terminal Ul and is distributed to the terminal VI and the switch S22 or the terminal Wl and the switch S32.
  • the intermediate circuit current Id is equal to IS11.
  • the inverter changes to the switching state u2 by opening the switch S21 and closing the switch S22.
  • the terminals U1, VI are now connected in parallel to the positive terminal of the intermediate circuit, and the sum of the currents flowing into the machine via them flows out via the terminal W1.
  • the current flowing through Sll in phase II is now distributed to switches Sll, S21, the intermediate circuit current Id remains the same.
  • the switching pattern considered here alternates two periods in which an intermediate circuit current flows with periods without an intermediate circuit current flow in the course of each cycle.
  • This fluctuating current requirement causes the intermediate circuit voltage to fluctuate.
  • phases in the operating cycle of the inverter in which less intermediate circuit voltage is available than in others, while the durations of the individual phases are calculated assuming a constant intermediate circuit voltage.
  • the general aim is to make the cycle period of the inverter as short as possible.
  • losses occur at the switches of the inverter.
  • they have a power loss that increases with the cycle frequency of the inverter and imposes an upper limit on the cycle frequency for current IGBT or MOSFET power switches of a few kHz.
  • Smooth capacitors with large capacitance and high dielectric strength are therefore still required for the operation of powerful machines, the costs of which are considerable.
  • the object of the invention is therefore to provide a method for operating an inverter and an inverter suitable for carrying out the method, which make it possible to keep the fluctuations in the intermediate circuit current or the intermediate circuit voltage low and thereby make it possible to use smaller and less expensive smoothing capacitors to use.
  • the object is achieved on the one hand by a method having the features of claim 1.
  • Each of which complements a first i-phase machine can be carried out using any method known for i-phase machines.
  • the same or different methods can be used to determine the switching sequences for the i-phase and the j -phase machine.
  • a suitable selection of a phase offset between the two switching sequences ensures that the two groups of strands load the intermediate circuit at different times, so that the DC link part of the current drawn from the intermediate circuit is larger and the oscillating component can be made smaller than in a single machine with i or j phases.
  • i + j n; i.e. the i-phase and the j -phase machine complement each other to form a complete n-phase induction machine.
  • phase offsets between the groups can be determined so that the DC component of the intermediate current is large and the AC component is low.
  • the phase shift can generally be set such that whenever one of the groups has no current draws, at least one of the other groups draws current, so that the intermediate circuit current never disappears completely.
  • the oscillating component of the intermediate circuit current is considerably reduced in comparison to a conventional i- or j-phase machine designed for the same output, especially if i and j have small values such as 2 or 3.
  • phase difference between the switching sequences of the groups can expediently be set to 180 ° divided by the number of groups.
  • the object is achieved by an inverter with n strings fed from a DC intermediate circuit (n> 4), a smoothing capacitor parallel to the strings and a control circuit for actuating switches of the n strings, in which the control circuit is set up, a method as above to be defined.
  • 4A shows a three-phase machine and an inverter, each with six phases
  • 5A is a timing diagram of a non-out-of-phase switching sequence for a six-phase inverter
  • FIG. 5B, C are time diagrams of phase-shifted switching sequences according to the invention.
  • FIG. 6A shows a phase-shifted switching sequence for the six-phase inverter at low power;
  • 6B shows a phase-shifted switching sequence for the six-phase inverter at high power
  • 7 shows a cutting sequence which is determined according to different methods for the two three-phase machines which complement one another for the six-phase machine
  • FIG. 9 space pointers to be generated in the four-phase machine of FIG. 8, analogous to FIG. 2;
  • FIG. 10 shows a time diagram of a non-phase-shifted switching sequence for the four-phase inverter from FIG. 8; 11 shows a time diagram of a phase-shifted switching sequence according to the invention.
  • FIG. 12 is an illustration of the mode of operation of the invention when a three-phase machine is divided into three sub-machines which are driven out of phase.
  • FIG. 4A shows a block diagram of a six-phase inverter and a six-phase induction machine connected to it.
  • the six-phase induction machine can be understood as a combination of two three-phase machines acting on a common shaft, whereby the connecting terminals of the first three-phase machine with Ul, U2, VI, V2, Wl, W2 and those of the second machine with the same symbols, each with an additional apostrophe.
  • the terminals U2, V2, W2, U2 ', V2', W2 'of both machines are connected to a common star point; however, this is not important for the functioning of the machine.
  • the terminals U2, V2, W2 of the first three-phase machine and those of the second three-phase machine could also each be interconnected to a star point.
  • a combination of two three-phase machines in a delta connection as shown in FIG. 4B can also be considered.
  • a structure as shown in FIG. 4C is also possible, in which six windings are connected in series to form a hexagon and each winding has both a phase of the first three-phase machine with terminals U1, VI, Wl and the second machine with the Terminals Ul ', VI', Wl 'is to be attributed.
  • the inverter is fed via an intermediate circuit with a positive rail (+) and a negative rail (-) by a rectifier (not shown).
  • a smoothing capacitor C and six strings, each with two switches, are connected in parallel between the two rails +, -.
  • the switches connected to the terminals Ul, VI, Wl are designated Sll, S12, S21, S22, S31, S32, and the corresponding switches assigned to the second three-phase machine have the same symbols, each with an additional one Apostrophe. Since the windings of the second sub-machine are oriented opposite to those of the first, in order to generate a given space vector, they must each be supplied with a current whose sign is opposite to that which flows through the corresponding winding of the first sub-machine.
  • the switching states for generating a given basic space vector are in each case opposite for the switches Sll ', ..., S32' assigned to the second sub-machine to those of the switches Sll, ..., S32 assigned to the first sub-machine, as in the table below specified.
  • the switching sequence with which the switches of the second sub-machine have to be actuated in order to generate a given space pointer like the pointer u '(t) in FIG. 2 is the same as that used for the first sub-machine by one to generate 180 ° phase-shifted space pointer -u '(t).
  • 5A specifically shows an example of such a switching sequence.
  • the switches S11 to S32 of the first sub-machine this switching sequence is identical to that of FIG. 3.
  • phases I to VIII of the switching sequence they generate the basic space pointers uO, ul, u2, u7, u7, u2, ul, uO one after the other ,
  • the first sub-machine loads the intermediate circuit with the current Id.
  • the states of the switches Sll 'to S32' correspond to those of the switches Sll to S32. opposite; in phases I to VIII, they generate the basic spatial pointer u7, u2, ul, uO, uO, u7, u2, ul.
  • the second sub-machine draws the intermediate circuit current Id 'in the phases II, III, VI, VII.
  • the transition time between the phases II and III or V and VI is not for both sub-machines - in contrast to the figure simplifying in this regard the same.
  • the currents Id, Id 'overlap in phase with Id, dead. A comparison of the power consumption in comparison to the three-phase machine of FIG. 1 is not yet associated with this.
  • any phase shift between the switching sequences of the two sub-machines leads to an equalization of the intermediate current and thus to a reduction in the voltage fluctuations in the intermediate circuit.
  • the duration of the neutral switching states uO, u7 will be less than or greater than half the cycle time.
  • the duration of the neutral states is greater than half a cycle duration, and phases alternate, in each of which one of the sub-machines has current pulls and phases in which no current is drawn draw each other.
  • phases in which one of the sub-machines draw current alternate with phases in which both draw current.
  • the intermediate circuit currents Id or Id 'caused by the sub-machine have a period that is half as long as the duty cycle of the inverter. Therefore, a phase shift of the switching sequences of the sub-machines against each other of 90 ° ensures a good equalization of the total intermediate circuit current Id, tot.
  • the period of the intermediate circuit currents can also match the cycle time of the inverter, for. B.
  • phases IV, V which correspond to switching state u7
  • phases I, VIII which correspond to the switching state uO
  • FIG. 8 shows a three-phase machine and an inverter, each with four phases.
  • the windings of the induction machine corresponding to the individual phases are each arranged at 90 ° to each other and have input terminals Ul, VI, Ul ', VI', each of which is connected to a switch Sll, S12 or S21, S22 or Sll ', S12' or S21 ', S22' are connected to the string of the inverter, and output terminals U2, V2, U2 ', V2' connected to a star point.
  • Switching states of the inverter in which the switches Sll, S21, Sll ', S21' are all open or all closed, and the corresponding, disappearing space pointers are denoted by uO.
  • a space vector u '(t) which rotates evenly on a circle K must be generated.
  • the respective base space pointer is generated during a time period corresponding to the projection of u '(t) onto the two adjacent base space pointers, here ul and u2, or when the time periods in which the base space pointers are generated , overlap, a space pointer is generated parallel to the bisector of the angle spanned by the base space pointer ul, u2.
  • FIG. 10 A switching sequence, not according to the invention, with which the control circuit CTL of the inverter from FIG. 8 can control its switch in order to generate the desired space vector u '(t) during a working cycle with phases I to X of the inverter, is shown in FIG. 10.
  • the switches of each string switched twice, the two switching times of each string being equidistant from a center point of the working cycle between phases V and VI.
  • the machine in the case of two strands which supply mutually opposite connections, for example Ul, Ul ', the machine
  • Switching times of the switches Sll, S12 of one strand are just as far from the beginning or end of the switching cycle as the switching times of the switches Sll ', S12' of the other strand from the middle of the switching cycle. There are therefore two time intervals per switching cycle in which the
  • the intermediate circuit current IdU of the inverter which is due to the current flow between the connections Ul and Ul ', is different from zero, and these two time periods are each centered in the first and second half of the switching cycle.
  • the six-phase induction machine already described above can also be understood as a combination of three two-phase machines, each of which corresponds to the terminal pairs Ul, Ul ', VI, VI' and Wl, Wl '.
  • the switching sequence not shown according to the invention shown in FIG. 5A it is easy to understand that there is a share in each of the two-phase machine formed by U1, U1 'and the machine formed by U1, U1' IdU or IdW on the intermediate circuit current with the same profile as Id in FIG.
  • FIG. 12 schematically shows the time course of the portions of the intermediate circuit current attributed to the individual two-phase machines on the assumption that, as in the switching sequence of FIG. 5A, each two-phase machine in each working cycle from tO to tl 1 the control circuit draws current twice, and that the times in which the individual machines draw current are each phase-shifted by 60 °.
  • the time intervals with a non-vanishing portion IdU, IdV, IdW of the intermediate circuit current are each shown as a vertical line with a dashed horizontal double arrow, which symbolizes the variable width of the current impulses u '(t) depending on the required machine power and the orientation of the space vector to be generated.
  • the current pulses attributed to the individual two-phase machines do not overlap, and the intermediate circuit current fluctuates between 0 and the maximum current consumed by a single two-phase machine Im. If the required power increases so that adjacent intervals of non-vanishing DC link current of the two-phase machines overlap, the current oscillates between Im and 21m, as shown for curve Id 'tot ' (2). If the required power increases again, so that neighboring intervals begin to overlap the next, the total intermediate circuit current Id, tot (3) fluctuates between 21m and 31m. In all cases, the alternating component of the total intermediate circuit current is effectively minimized.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Multiple Motors (AREA)
  • Inverter Devices (AREA)

Abstract

Une machine à champ tournant hexaphasée est considérée comme une combinaison de deux machines à champ tournant triphasées. Les deux machines à champ tournant sont alimentées par un convertisseur hexaphasé commun. Les commutateurs (S11, S12, S21, , S32') du convertisseur sont commandés par un circuit de commande (CTL), de manière à obtenir, à différents moments, du courant provenant dudit convertisseur.
PCT/EP2004/011048 2003-10-04 2004-10-04 Procede permettant de faire fonctionner une machine a champ tournant, et convertisseur utilise a cet effet WO2005034333A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE10346060A DE10346060A1 (de) 2003-10-04 2003-10-04 Verfahren zum Betreiben einer Drehfeldmaschine und Wechselrichter dafür
DE10346060.8 2003-10-04

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WO2005034333A1 true WO2005034333A1 (fr) 2005-04-14

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Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2007031058A1 (fr) * 2005-09-12 2007-03-22 Conti Temic Microelectronic Gmbh Procede pour faire fonctionner une machine electrique
WO2013007486A3 (fr) * 2011-07-08 2013-07-11 Robert Bosch Gmbh Procédé de commande d'une machine polyphasée
WO2013007623A3 (fr) * 2011-07-08 2013-10-10 Robert Bosch Gmbh Procédé de commande d'une machine polyphasée
CN103563233A (zh) * 2011-05-30 2014-02-05 罗伯特·博世有限公司 用于控制多相电机的方法
US9312802B2 (en) 2011-07-08 2016-04-12 Robert Bosch Gmbh Method for controlling a multiphase machine
DE102018201340B3 (de) 2018-01-30 2019-06-13 Bayerische Motoren Werke Aktiengesellschaft Verfahren zum Betreiben einer Drehfeldmaschine eines Kraftfahrzeugs, Übertragungsvorrichtung, Antriebseinheit sowie Kraftfahrzeug

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CN103887999B (zh) * 2012-12-20 2016-12-28 北京动力源科技股份有限公司 一种非隔离交错并联的控制方法及装置
DE102013223624A1 (de) * 2013-11-20 2015-05-21 Robert Bosch Gmbh Verfahren zum Ansteuern einer elektrischen Maschine
DE102014200337A1 (de) 2014-01-10 2015-07-16 Robert Bosch Gmbh Bestromen und Messen der Temperatur von Statorwicklungen einer zumindest motorisch betreibbaren elektrischen Drehfeldmaschine
DE102016223349A1 (de) 2016-11-24 2018-05-24 Brose Fahrzeugteile GmbH & Co. Kommanditgesellschaft, Würzburg Verfahren zum Betrieb eines bürstenlosen Elektromotors eines Kraftfahrzeugs

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US6392905B1 (en) * 2001-01-06 2002-05-21 Ford Global Technologies, Inc. Method and circuit for reducing battery ripple current in a multiple inverter system of an electrical machine

Patent Citations (1)

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US6392905B1 (en) * 2001-01-06 2002-05-21 Ford Global Technologies, Inc. Method and circuit for reducing battery ripple current in a multiple inverter system of an electrical machine

Cited By (15)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2007031058A1 (fr) * 2005-09-12 2007-03-22 Conti Temic Microelectronic Gmbh Procede pour faire fonctionner une machine electrique
US9608555B2 (en) 2011-05-30 2017-03-28 Robert Bosch Gmbh Method for actuating a polyphase machine
CN103563233A (zh) * 2011-05-30 2014-02-05 罗伯特·博世有限公司 用于控制多相电机的方法
WO2013007512A3 (fr) * 2011-07-08 2013-10-17 Robert Bosch Gmbh Procédé de commande d'une machine polyphasée
WO2013007623A3 (fr) * 2011-07-08 2013-10-10 Robert Bosch Gmbh Procédé de commande d'une machine polyphasée
CN103650324A (zh) * 2011-07-08 2014-03-19 罗伯特·博世有限公司 用于操控多相电机的方法
CN103650322A (zh) * 2011-07-08 2014-03-19 罗伯特·博世有限公司 用于操控多相电机的方法
US9203337B2 (en) 2011-07-08 2015-12-01 Robert Bosch Gmbh Method for controlling a multiphase machine
US9312802B2 (en) 2011-07-08 2016-04-12 Robert Bosch Gmbh Method for controlling a multiphase machine
WO2013007486A3 (fr) * 2011-07-08 2013-07-11 Robert Bosch Gmbh Procédé de commande d'une machine polyphasée
DE102018201340B3 (de) 2018-01-30 2019-06-13 Bayerische Motoren Werke Aktiengesellschaft Verfahren zum Betreiben einer Drehfeldmaschine eines Kraftfahrzeugs, Übertragungsvorrichtung, Antriebseinheit sowie Kraftfahrzeug
WO2019149502A1 (fr) 2018-01-30 2019-08-08 Bayerische Motoren Werke Aktiengesellschaft Procédé de fonctionnement d'un moteur à champ tournant d'un véhicule à moteur, dispositif de transmission, unité d'entraînement ainsi que véhicule à moteur
CN111295833A (zh) * 2018-01-30 2020-06-16 宝马股份公司 用于运行机动车的旋转场电机的方法传输设备、驱动单元以及机动车
US11271511B2 (en) 2018-01-30 2022-03-08 Bayerische Motoren Werke Aktiengesellschaft Method for operating a rotating field machine of a motor vehicle, transmission device, drive unit and motor vehicle
CN111295833B (zh) * 2018-01-30 2023-09-22 宝马股份公司 用于运行旋转场电机的方法传输设备、驱动单元和机动车

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