WO2001029987A1 - AN ADAPTIVE DIGITAL BEAMFORMING RECEIVER WITH π/2 PHASE SHIFT TO IMPROVE SIGNAL RECEPTION - Google Patents

AN ADAPTIVE DIGITAL BEAMFORMING RECEIVER WITH π/2 PHASE SHIFT TO IMPROVE SIGNAL RECEPTION Download PDF

Info

Publication number
WO2001029987A1
WO2001029987A1 PCT/EP2000/009761 EP0009761W WO0129987A1 WO 2001029987 A1 WO2001029987 A1 WO 2001029987A1 EP 0009761 W EP0009761 W EP 0009761W WO 0129987 A1 WO0129987 A1 WO 0129987A1
Authority
WO
WIPO (PCT)
Prior art keywords
signal
equalizer circuit
feedforward equalizer
feedforward
circuit
Prior art date
Application number
PCT/EP2000/009761
Other languages
French (fr)
Inventor
Joseph P. Meehan
Original Assignee
Koninklijke Philips Electronics N.V.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Koninklijke Philips Electronics N.V. filed Critical Koninklijke Philips Electronics N.V.
Priority to EP00972684A priority Critical patent/EP1142160A1/en
Priority to KR1020017007896A priority patent/KR20010086140A/en
Priority to JP2001531225A priority patent/JP2003512762A/en
Publication of WO2001029987A1 publication Critical patent/WO2001029987A1/en

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
    • H01Q3/2611—Means for null steering; Adaptive interference nulling
    • H01Q3/2617—Array of identical elements
    • H01Q3/2623—Array of identical elements composed of two antennas
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N7/00—Television systems
    • H04N7/015—High-definition television systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
    • H01Q3/2611—Means for null steering; Adaptive interference nulling
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/30—Time-delay networks
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/60—Receivers
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
    • H04B7/0842—Weighted combining
    • H04B7/0845—Weighted combining per branch equalization, e.g. by an FIR-filter or RAKE receiver per antenna branch
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
    • H04B7/0842—Weighted combining
    • H04B7/086—Weighted combining using weights depending on external parameters, e.g. direction of arrival [DOA], predetermined weights or beamforming
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03012—Arrangements for removing intersymbol interference operating in the time domain
    • H04L25/03019—Arrangements for removing intersymbol interference operating in the time domain adaptive, i.e. capable of adjustment during data reception
    • H04L25/03057—Arrangements for removing intersymbol interference operating in the time domain adaptive, i.e. capable of adjustment during data reception with a recursive structure
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N5/00—Details of television systems
    • H04N5/44—Receiver circuitry for the reception of television signals according to analogue transmission standards
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04Q—SELECTING
    • H04Q3/00—Selecting arrangements
    • H04Q3/18—Circuit arrangements for first stage of hunting switching
    • H04Q3/24—Circuit arrangements for first stage of hunting switching for line finders
    • H04Q3/26—Circuit arrangements for first stage of hunting switching for line finders comprising common calling and disconnecting circuit
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/16—Circuits
    • H04B1/26—Circuits for superheterodyne receivers
    • H04B1/28—Circuits for superheterodyne receivers the receiver comprising at least one semiconductor device having three or more electrodes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L2025/0335—Arrangements for removing intersymbol interference characterised by the type of transmission
    • H04L2025/03375—Passband transmission
    • H04L2025/03382—Single of vestigal sideband
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L2025/03433—Arrangements for removing intersymbol interference characterised by equaliser structure
    • H04L2025/03439—Fixed structures
    • H04L2025/03445—Time domain
    • H04L2025/03471—Tapped delay lines
    • H04L2025/03484—Tapped delay lines time-recursive
    • H04L2025/0349—Tapped delay lines time-recursive as a feedback filter
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L2025/03592—Adaptation methods
    • H04L2025/03598—Algorithms
    • H04L2025/03611—Iterative algorithms
    • H04L2025/03617—Time recursive algorithms
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N21/00—Selective content distribution, e.g. interactive television or video on demand [VOD]
    • H04N21/40—Client devices specifically adapted for the reception of or interaction with content, e.g. set-top-box [STB]; Operations thereof
    • H04N21/41—Structure of client; Structure of client peripherals
    • H04N21/426—Internal components of the client ; Characteristics thereof
    • H04N21/42607—Internal components of the client ; Characteristics thereof for processing the incoming bitstream
    • H04N21/4263—Internal components of the client ; Characteristics thereof for processing the incoming bitstream involving specific tuning arrangements, e.g. two tuners

Definitions

  • the present invention is directed, in general, to antenna systems and signal receivers and, more specifically, to an apparatus and method for improving the reception of signals such as digital television signals, e.g., ATSC 8-NSB signals.
  • signals such as digital television signals, e.g., ATSC 8-NSB signals.
  • Many digital television receivers have internal antennas or are connected to indoor antennas. In such digital television receivers there can be problems in receiving a good quality signal due to the presence of multiple signal echoes created by obstacles in the room.
  • the multiple signal echoes are inteferer signals that arrive late at the antenna (i.e., multipath delay).
  • the indoor antenna may be manually rotated or adjusted to maximize the main signal and minimize the unwanted signals created by the multiple signal echoes of the main signal.
  • the television receiver has an internal antenna that is not readily accessible, one must manually rotate or adjust the entire television receiver in order to make the desired adjustment.
  • a typical digital television signal is an ATSC 8-VSB signal.
  • ATSC refer to the Advanced Television Standards Committee.
  • 8-VSB refer to a television signal modulation format in which the television signal has eight vestigial sidebands.
  • a typical television signal carrier frequency is in the frequency range from 470 MHz to 800 MHz.
  • the present invention provides an apparatus and method for electronically modifying a television signal that is impaired by the presence of signal echoes of the main signal in order to minimize the signal echoes (i.e., null the interferers).
  • Such electronic modification of a signal is referred to as beamforming.
  • the invention comprises a beamforming circuit and a decision feedback equalizer circuit.
  • the beamforming circuit comprises (1) two circuit branches with each circuit branch having a radio frequency (RF) tuner capable of being coupled to an antenna, an intermediate frequency (IF) mixer, a ⁇ /2 phase shift circuit and two feedforward equalizer circuits and (2) a first adder circuit.
  • the beamforming circuit modifies the input signals to electronically form a beam in the direction of the desired signal and to electronically form a null in the direction of the interfering signal.
  • a first antenna receives a signal and sends the signal through a first radio frequency (RF) tuner, through a first intermediate frequency (IF) mixer, and through a first analog-to-digital converter to a first feedforward equalizer circuit.
  • the signal that goes through the first feedforward equalizer circuit is an "in-phase" component of the signal.
  • the signal is also passed through a first ⁇ /2 phase shifter and through a second feedforward equalizer circuit.
  • the signal that goes through the second feedforward equalizer circuit is a "quadrature" component of the signal.
  • the phase of the quadrature component of the signal has been shifted from the phase of the original signal by an amount equal to ⁇ /2 radians or ninety degrees (90°).
  • a second antenna receives a signal and sends the signal through a second RF tuner, through a second IF mixer, and through a second analog-to-digital converter to a third feedforward equalizer circuit.
  • the signal that goes through the third feedforward equalizer circuit is an "in-phase" component of the signal.
  • the signal is also passed through a second ⁇ /2 phase shifter and through a fourth feedforward equalizer circuit.
  • the signal that goes through the fourth feedforward equalizer circuit is a "quadrature" component of the signal.
  • the phase of the quadrature component of the signal has been shifted from the phase of the original signal by an amount equal to ⁇ /2 radians or ninety degrees (90°).
  • the output of the first feedforward equalizer circuit and the output of the second feedforward equalizer circuit and the output of the third feedforward equalizer circuit and the output of the fourth feedforward equalizer circuit are added together in a first adder circuit and are used as the input to the decision feedback equalizer circuit.
  • the beamforming circuit comprises the first circuit branch from the first RF tuner to the first and second feedforward equalizer circuits together with the second circuit branch from the second RF tuner to the third and fourth feedforward equalizer circuits together with the first adder circuit.
  • the decision feedback equalizer circuit comprises a second adder circuit, a decision device and a feedback equalizer circuit.
  • the second adder circuit is the first element of the decision feedback equalizer circuit.
  • the second adder circuit receives a signal from the first adder circuit of the beamforming circuit and combines that signal with a signal from the feedback equalizer circuit to create an input signal to the decision device.
  • the feedback equalizer circuit is connected to the output of the decision device to sample the output signal that leaves the decision device.
  • the feedback equalizer circuit feeds a modified form of that output signal back to the second adder circuit for use in creating an input signal to the decision device as described above.
  • the decision device calculates the error in the received signal that is due to an interfering signal arising from an echo of the main signal.
  • the decision device uses an adaptation algorithm to calculate corrections to the signal.
  • the decision device applies those corrections to the signal to electronically form a beam in the direction of the desired signal and to electronically form a null in the direction of the interfering signal.
  • the result is a significant improvement in the quality of signal reception.
  • the decision device also has control lines that are coupled to the first feedforward equalizer circuit and to the second feedforward equalizer circuit and to the third feedforward equalizer circuit and to the fourth feedforward equalizer circuit and to the feedback equalizer circuit.
  • the decision device can send control signals over the control lines to change any or all of the coefficients in these five equalizer circuits to modify the operating characteristics of the equalizer circuits.
  • the terms "include” and “comprise” and derivatives thereof mean inclusion without limitation;
  • the phrases “associated with” and “associated therewith,” as well as derivatives thereof, may mean to include, be included within, interconnect with, contain, be contained within, connect to or with, couple to or with, be communicable with, cooperate with, interleave, juxtapose, be proximate to, be bound to or with, have, have a property of, or the like;
  • the term “controller” means any device, system or part thereof that controls at least one operation, such a device may be implemented in hardware, firmware, or software, or some combination of at least two of the same.
  • FIGURE 1 is a block diagram of an adaptive digital beamforming receiver of the present invention
  • FIGURE 2 is a block diagram of a high definition television signal receiver in which the present invention may be embodied.
  • FIGURE 3 is a block diagram of an embodiment of the present invention in a signal receiver of a video device;
  • FIGURE 4 is a flow diagram illustrating the operation of an exemplary adaptive beamforming receiver in accordance with one embodiment of the present invention.
  • FIGURES 1 through 4 discussed below, and the various embodiments used to describe the principles of the present invention in this patent document are by way of illustration only and should not be construed in any way to limit the scope of the invention. Those skilled in the art will understand that the principles of the present invention may be implemented in any suitably arranged signal receiver.
  • FIGURE 1 illustrates an adaptive digital beamforming receiver 100, according to a preferred embodiment of the invention.
  • the invention comprises beamforming circuit 200 and decision feedback equalizer circuit 300.
  • Beamforming circuit 200 comprises two branches.
  • the first branch of beamforming circuit 200 comprises radio frequency (RF) tuner 222, which is capable of being coupled to antenna 220.
  • RF tuner 222 is coupled to intermediate frequency (IF) mixer 224.
  • IF mixer 224 down-convert the RF signal received from antenna 220 to an analog baseband signal.
  • IF mixer 224 is coupled to analog-to-digital converter 226, which converts the analog baseband signal to a digital baseband signal.
  • Analog-to-digital converter 226 is coupled to first feedforward equalizer circuit 228 and first B/2 phase shift circuit 230.
  • First B/2 phase shift circuit 230 is connected to second feedforward equalizer circuit 232.
  • First B/2 phase shift circuit 230 shifts by 90 degrees the digital baseband signal at the input of second feedforward equalizer 232 with respect to the baseband signal at the input of first feedforward equalizer 228.
  • first feedforward equalizer circuit 228 modifies the input signal to form a beam in the direction of the desired signal and to form a null in the direction of the interfering signal.
  • second feedforward equalizer circuit 232 modifies the B/2 phase shifted input signal to form a beam in the direction of the desired signal and to form a null in the direction of the interfering signal.
  • the second branch of beamforming circuit 200 comprises radio frequency (RF) tuner 242, which is capable of being coupled to antenna 240.
  • RF tuner 242 is coupled to intermediate frequency (IF) mixer 244. Together, RF tuner 242 and IF mixer 244 down- convert the RF signal received from antenna 240 to an analog baseband signal.
  • IF mixer 244 is coupled to analog-to-digital converter 246, which converts the analog baseband signal to a digital baseband signal.
  • Analog-to-digital converter 246 is coupled to third feedforward equalizer circuit 248 and second B/2 phase shift circuit 252.
  • Second B/2 phase shift circuit 252 is connected to fourth feedforward equalizer circuit 254.
  • Second B/2 phase shift circuit 230 shifts by 90 degrees the digital baseband signal at the input of fourth feedforward equalizer 254 with respect to the baseband signal at the input of third feedforward equalizer 252.
  • third feedforward equalizer circuit 248 modifies the input signal to form a beam in the direction of the desired signal and to form a null in the direction of the interfering signal.
  • fourth feedforward equalizer circuit 254 modifies the B/2 phase shifted input signal to form a beam in the direction of the desired signal and to form a null in the direction of the interfering signal.
  • first adder circuit 250 adds together the output signals from feedforward equalizer circuits 228, 232, 248 and 254.
  • the signal that results from the addition of the signals by first adder circuit 250 is an improved signal because it represents a combination of four separate signals, each of which has been modified to form a beam in the direction of the desired signal and modified to form a null in the direction of the interfering signal. Signal information that may have been missing from one of the signals (due to interference) may have been present in one of the other signals.
  • Antennas 220 and 240 may be vertical, single dipole, omni-directional antennas. Antennas 220 and 240 are spaced apart by a distance in the range from one- twentieth (1/20) of a wavelength of the received signal up to one (1) wavelength of the received signal. For example, in the case of a carrier frequency of 470 MHz, the maximum separation of antennas 220 and 240, would be approximately 0.63 meter or approximately 24.0 inches. Antennas 220 and 240 can be used as components of an internal antenna of a television receiver that uses the present invention.
  • First feedforward equalizer circuit 228 receives from first analog-to-digital converter 226 a digital form of the signal received by antenna 220.
  • First feedforward equalizer circuit 228 comprises circuitry (not shown) for operating a signal processing algorithm that is designed to compensate for the distortions in the amplitude and in the phase that a signal may acquire when that signal is transmitted through a dispersive channel. In this instance, the dispersive channel is the atmosphere.
  • a number of different types of prior art feedforward equalizer circuits are available that may be used as the first feedforward equalizer circuit 228 of the present invention.
  • One of the simplest types of equalizer circuits is the Linear Transversal Equalizer.
  • the Linear Transversal Equalizer samples values of the input signal in a tapped delay line having N tap points and multiplies those sampled values by N numerical coefficients and then sums the resultant values to form a representation of the signal.
  • the numerical coefficients are numbers that represent weight factors. The number of numerical coefficients can range from one coefficient up to, for example, one hundred coefficients or more.
  • the resultant signal is represented mathematically as follows:
  • third feedforward equalizer circuit 248 receives from second analog- to-digital converter 246 a digital form of the signal received by antenna 240.
  • Third feedforward equalizer circuit 248 may be identical in structure and function to the first feedforward equalizer circuit 228.
  • the output signal of the third feedforward equalizer circuit 248 is represented mathematically as follows:
  • Second feedforward equalizer circuit 232 receives from first B/2 phase shift circuit 230 a phase shifted digital form of the signal received by antenna 220.
  • Second feedforward equalizer circuit 232 is identical in structure and function to the first feedforward equalizer circuit 228. The only difference is that the signal has been phase shifted by B/2 radians. This shift is represented by the factor e* (B/2) .
  • the output signal of the second feedforward equalizer circuit 232 is represented mathematically as follows:
  • y n is the output
  • x l n is the n ⁇ sample of the input signal from the first antenna 220
  • a'j are the coefficients of second feedforward equalizer 232
  • N is the number of coefficients in the second feedforward equalizer 232.
  • the output signal of the fourth feedforward equalizer circuit 254 is represented mathematically as follows:
  • ⁇ 0 where y n is the output, x >n is the n ⁇ sample of the input signal from the second antenna 240, b' j are the coefficients of fourth feedforward equalizer 254, and N is the number of coefficients in the fourth feedforward equalizer 254.
  • Linear Transversal Equalizer in this description does not limit the invention to this particular type of equalizer. Other types of equalizers may be utilized to practice the invention.
  • the decision feedback equalizer circuit 300 of the invention comprises a second adder circuit 320, a decision device 330, and a feedback equalizer circuit 340.
  • the second adder circuit 320 of decision feedback equalizer circuit 300 is coupled to the first adder circuit 250 of beamforming circuit 200.
  • the second adder circuit 320 receives from the first adder circuit 250 a signal that is the sum of the output signal from first feedforward equalizer circuit 228 and the output signal from second feedforward equalizer circuit 232 and the output signal from third feedforward equalizer circuit 248 and the output signal from fourth feedforward equalizer circuit 254.
  • second adder circuit 320 also receives an input signal from feedback equalizer circuit 340.
  • Second adder circuit 320 is coupled to a decision device 330. Decision device
  • DSP digital signal processor
  • Decision device 330 performs two operations. The first operation is to make a decision as to which valid symbol the input symbol is closest to (in this case, the eight levels of the 8-VSB signal). This could be called a splicer. It is this valid symbol (i.e., the decision output) that is passed to the feedback equalizer circuit 340. The second operation of decision device 330 is based on the difference of the decision device input and the decision device output (i.e., the symbol error).
  • the symbol error is used in a decision directed adaptation algorithm (e.g., Least Mean Square Algorithm) or in a blind adaptation algorithm (e.g., Constant Modulus Algorithm) to update the equalizer coefficients so that the Mean Square Error (MSE) at the decision device input is reduced.
  • Decision device 330 may use any one of a number of equalizer adaptation algorithms well known in the prior art.
  • the equalizer adaptation algorithm used is the Least Mean Squares (LMS) method. It is referred to as the LMS algorithm.
  • Another equalizer adaptation algorithm available for use utilizes the Recursive Least Squares (RLS) method. It is referred to as the RLS algorithm.
  • RLS Recursive Least Squares
  • Other similar algorithms are also available for use. The description of the preferred embodiment of the invention is not intended to limit the type of algorithm that may be used in accordance with the concept of the invention.
  • the adaptation algorithm calculates the amount of error in the amplitude and phase of the signal.
  • the adaptation algorithm then calculates the amount of correction needed to correct the errors.
  • the decision device 330 then changes the values of the coefficients in first feedforward equalizer 228, second feedforward equalizer 232, third feedforward equalizer 248, fourth feedforward equalizer 254, and feedback equalizer 340. In this manner, decision device 330 modifies the signal to create an improved signal by electronically forming a beam in the direction of the desired signal and by electronically forming a null in the direction of the interfering signal.
  • Feedback equalizer circuit 340 is coupled to the output of decision device 330 for sampling the output signal of decision device 330.
  • Feedback equalizer circuit 340 also has an output coupled to an input of second adder circuit 320. This allows second adder circuit 320 to access the output signal of feedback equalizer circuit 340.
  • Second adder circuit 320 subtracts the output signal of feedback equalizer circuit 340 from the signal that is the sum of the output signal from first feedforward equalizer circuit 228 and the output signal from second feedforward equalizer circuit 248 and the output signal from third feedforward equalizer circuit 248 and the output signal from fourth feedforward equalizer circuit 254.
  • Feedback equalizer circuit 340 may also have the same form and structure of the first feedforward equalizer circuit 228 and the second feedforward equalizer circuit 248 and the third feedforward equalizer circuit 248 and the fourth feedforward equalizer circuit 254.
  • the output signal of feedback equalizer circuit 340 is represented mathematically as follows: where y n is the output, y n . k is the input signal from the decision device 330, C are the coefficients of feedback equalizer circuit 340, and M is the number of coefficients in feedback equalizer circuit 340. Therefore, the input signal to the decision device 330 is given by the mathematical expression:
  • y n ( c k y n _ k where y n is the estimated output, x ljn is the n ⁇ sample of the input signal from first antenna 220, x 2(self is the n ⁇ sample of the input signal from second antenna 240, and y n-k is the input signal from the decision device 330.
  • the values aj are the coefficients of the first feedforward equalizer circuit 228, the values a'; are the coefficients of the second feedforward equalizer circuit 248, the values b j are the coefficients of the third feedforward equalizer circuit 248, the values b' j are the coefficients of the fourth feedforward equalizer circuit 254, and the values c ⁇ _ are the coefficients of the feedback equalizer circuit 340.
  • the value N is the number of coefficients in feedforward equalizer circuit 228, feedforward equalizer circuit 232, feedforward equalizer circuit 248, and feedforward equalizer circuit 254.
  • the value M is the number of coefficients in the feedback equalizer circuit 340. This expression represents the input to the decision device 330.
  • Decision device 330 utilizes the above described input value for yford to sequentially set up and solve a set of linear equations to determine corrected values for the coefficients of each of the five equalizer circuits, that is, for the first feedforward equalizer circuit 228, and for the second feedforward equalizer circuit 232, and for the third feedforward equalizer circuit 248, and for the fourth feedforward equalizer circuit 254, for the feedback equalizer circuit 340.
  • the coefficients (also referred to as tap weights) of an equalizer can be adjusted to minimize the Mean Square Error (MSE), ⁇ k , according to:
  • a set of linear equations can be set up based on the orthogonality principle in mean-square estimation.
  • the equalizer coefficients, d J? are chosen such that the Mean Square
  • MSE Error
  • LMS Least Mean Square
  • Mean Square Error can be found and the opposite of this taken to update the tap values so that the MSE moves closer to the minimum.
  • the value ekX*(kT-nT) is an estimate of the gradient vector obtained from the data.
  • the LMS algorithm does not require knowledge of the signal's statistics or of the noise.
  • the new equalizer coefficient is deduced from the previous value of the coefficient minus an error function. The greater ⁇ is, the faster the convergence, and the smaller ⁇ is, the slower the convergence.
  • the LMS algorithm is easy to implement but slow to converge.
  • decision device 330 After decision device 330 has calculated the new equalizer coefficients for the equalizer circuits, decision device 330 sends a new equalizer coefficient to first feedforward equalizer circuit 228 via control line 331. Decision device 330 also sends a new equalizer coefficient to second feedforward equalizer circuit 232 via control line 333, sends a new equalizer coefficient to third feedforward equalizer circuit 248 via control line 335, sends a new equalizer coefficient to fourth feedforward equalizer circuit 254 via control line 337, and sends a new equalizer coefficient to feedback equalizer 340 via control line 339.
  • the decision device 330 creates an improved signal for signal receiver 400.
  • a video device will be briefly described.
  • the video device that will be described is a high resolution television signal receiver. It is to be borne in mind that the invention is not limited to use in a television signal receiver but may be used in any type of video device, including, without limitation, personal computer monitors, laptop computer monitors, handheld computer monitors, handheld video devices, and any type of device having the ability to display a video signal.
  • FIGURE 2 is a block diagram of a high definition television signal receiver, in which the present invention may be embodied.
  • the television signal is received by antenna 520 and sent to a RF tuner 522 and then to an IF mixer 524.
  • the signal is then sent to a demodulator and channel decoder circuit 526.
  • the signal is then sent to a transport demultiplexer and decryption circuit 530 where the audio, video and data portions of the signal are separated from each other.
  • the video portion of the signal is sent to a video decoder 540.
  • the audio portion of the signal is sent to an audio decoder 542.
  • the data portion of the signal is sent to a data decoder 544.
  • the video portion of the signal is sent to a video display circuit 550 and the audio portion of the signal is sent to an audio speaker unit 552.
  • FIGURE 3 is a block diagram of an embodiment of the present invention in a video device 600.
  • the video device 600 is a television signal receiver having a first antenna 520 and a second antenna 521.
  • the RF tuner 522 and the IF mixer 524 of the television signal receiver 500 have been replaced with the beamforming circuit 200 and with the decision feedback equalizer circuit 300 of the present invention.
  • FIGURE 3 is an exemplary adaptive digital beamforming receiver of the present invention.
  • the decision feedback equalizer circuit 300 sends the improved signal of the present invention to an MPEG-2 decoder 620.
  • the MPEG-2 decoder 620 is of a type well known in the prior art.
  • the video portion of the signal is sent to a video display unit 630.
  • the audio portion of the signal is sent to an audio speaker 640.
  • FIGURE 4 is a flow diagram illustrating the operation of an exemplary adaptive digital beamforming receiver in accordance with one embodiment of the present invention.
  • Step 700 comprises the step of demodulating a first analog signal from a first antenna.
  • Step 702 comprises the step of converting the first analog signal to a digital signal.
  • Step 704 comprises the step of modifying the first signal in a first feedforward equalizer to correct distortions in the first signal.
  • step 706 comprises the step of demodulating a second analog signal from a second antenna.
  • step 708 comprises the step of converting the second analog signal to a digital signal.
  • step 710 comprises the step of modifying the second signal in a second feedforward equalizer circuit to correct distortions in the second signal.
  • Step 712 comprises the step of adding the modified first signal and the modified second signal.
  • Step 714 comprises the step of adding to the sum of the modified first signal and the modified second signal a feedback signal from a feedback equalizer circuit to create an improved signal.
  • Step 716 comprises the step of modifying the improved signal in a decision device having an adaptive algorithm by adjusting the coefficients of the first feedforward equalizer circuit, and by adjusting the coefficients of the second feedforward equalizer circuit, and by adjusting the coefficients of the feedback equalizer circuit.

Landscapes

  • Engineering & Computer Science (AREA)
  • Signal Processing (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Multimedia (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Cable Transmission Systems, Equalization Of Radio And Reduction Of Echo (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)

Abstract

There is disclosed an apparatus and method for improving signal reception in a signal receiver. The apparatus comprises a beamforming circuit and a decision feedback equalizer circuit. The beamforming circuit comprises two circuit branches with each circuit branch having a radio frequency (RF) tuner capable of being coupled to an antenna, an intermediate frequency (IF) mixer, a B/2 phase shift circuit, and two feedforward equalizer circuits and an adder circuit. In the decision feedback equalizer circuit a decision device that is coupled to the output of said adder circuit modifies equalizer coefficients in said feedforward equalizer circuits to reduce an interfering signal by electronically forming a null in the direction of the interfering signal.

Description

An adaptive digital beamforming receiver with π 12 phase shift to improve signal reception.
The present invention is directed, in general, to antenna systems and signal receivers and, more specifically, to an apparatus and method for improving the reception of signals such as digital television signals, e.g., ATSC 8-NSB signals.
Many digital television receivers have internal antennas or are connected to indoor antennas. In such digital television receivers there can be problems in receiving a good quality signal due to the presence of multiple signal echoes created by obstacles in the room. The multiple signal echoes are inteferer signals that arrive late at the antenna (i.e., multipath delay). In cases where the television receiver is connected to a readily accessible indoor antenna, the indoor antenna may be manually rotated or adjusted to maximize the main signal and minimize the unwanted signals created by the multiple signal echoes of the main signal. In cases where the television receiver has an internal antenna that is not readily accessible, one must manually rotate or adjust the entire television receiver in order to make the desired adjustment.
There is therefore a need for improving the reception of a television signal in television receivers that have internal antennas and in television receivers that are connected to antennas that are located indoors. The desired system for improving the signal reception of such a television signal should not require the manual adjustment of either the antenna or the entire television receiver.
To address this problem, it is a primary object of the present invention to provide an apparatus and method for automatically adapting a television signal within a television receiver to minimize (or null) interferer signals of the television receiver that are caused by the presence of multiple signal echoes created by obstacles in the room in which the antenna of the television receiver is located.
It is important to realize that the apparatus and method of the present invention is not limited to improving only a television signal. Those skilled in the art will readily understand that the principles of the present invention may also be successfully applied to other types of signals. However, in the descriptions that follow, digital television signals are employed for illustration purposes.
A typical digital television signal is an ATSC 8-VSB signal. The letters ATSC refer to the Advanced Television Standards Committee. The number and letters 8-VSB refer to a television signal modulation format in which the television signal has eight vestigial sidebands. A typical television signal carrier frequency is in the frequency range from 470 MHz to 800 MHz.
The present invention provides an apparatus and method for electronically modifying a television signal that is impaired by the presence of signal echoes of the main signal in order to minimize the signal echoes (i.e., null the interferers). Such electronic modification of a signal is referred to as beamforming.
In the preferred embodiment of the invention, the invention comprises a beamforming circuit and a decision feedback equalizer circuit. The beamforming circuit comprises (1) two circuit branches with each circuit branch having a radio frequency (RF) tuner capable of being coupled to an antenna, an intermediate frequency (IF) mixer, a π/2 phase shift circuit and two feedforward equalizer circuits and (2) a first adder circuit. The beamforming circuit modifies the input signals to electronically form a beam in the direction of the desired signal and to electronically form a null in the direction of the interfering signal. A first antenna receives a signal and sends the signal through a first radio frequency (RF) tuner, through a first intermediate frequency (IF) mixer, and through a first analog-to-digital converter to a first feedforward equalizer circuit. The signal that goes through the first feedforward equalizer circuit is an "in-phase" component of the signal. The signal is also passed through a first π/2 phase shifter and through a second feedforward equalizer circuit. The signal that goes through the second feedforward equalizer circuit is a "quadrature" component of the signal. The phase of the quadrature component of the signal has been shifted from the phase of the original signal by an amount equal to π/2 radians or ninety degrees (90°).
Similarly, a second antenna receives a signal and sends the signal through a second RF tuner, through a second IF mixer, and through a second analog-to-digital converter to a third feedforward equalizer circuit. The signal that goes through the third feedforward equalizer circuit is an "in-phase" component of the signal. The signal is also passed through a second π/2 phase shifter and through a fourth feedforward equalizer circuit. The signal that goes through the fourth feedforward equalizer circuit is a "quadrature" component of the signal. The phase of the quadrature component of the signal has been shifted from the phase of the original signal by an amount equal to π/2 radians or ninety degrees (90°).
The output of the first feedforward equalizer circuit and the output of the second feedforward equalizer circuit and the output of the third feedforward equalizer circuit and the output of the fourth feedforward equalizer circuit are added together in a first adder circuit and are used as the input to the decision feedback equalizer circuit. The beamforming circuit comprises the first circuit branch from the first RF tuner to the first and second feedforward equalizer circuits together with the second circuit branch from the second RF tuner to the third and fourth feedforward equalizer circuits together with the first adder circuit. The decision feedback equalizer circuit comprises a second adder circuit, a decision device and a feedback equalizer circuit. The second adder circuit is the first element of the decision feedback equalizer circuit. The second adder circuit receives a signal from the first adder circuit of the beamforming circuit and combines that signal with a signal from the feedback equalizer circuit to create an input signal to the decision device. The feedback equalizer circuit is connected to the output of the decision device to sample the output signal that leaves the decision device. The feedback equalizer circuit feeds a modified form of that output signal back to the second adder circuit for use in creating an input signal to the decision device as described above.
The decision device calculates the error in the received signal that is due to an interfering signal arising from an echo of the main signal. The decision device uses an adaptation algorithm to calculate corrections to the signal. The decision device applies those corrections to the signal to electronically form a beam in the direction of the desired signal and to electronically form a null in the direction of the interfering signal. The result is a significant improvement in the quality of signal reception. The decision device also has control lines that are coupled to the first feedforward equalizer circuit and to the second feedforward equalizer circuit and to the third feedforward equalizer circuit and to the fourth feedforward equalizer circuit and to the feedback equalizer circuit. The decision device can send control signals over the control lines to change any or all of the coefficients in these five equalizer circuits to modify the operating characteristics of the equalizer circuits.
Although the present invention has been described in a form that utilizes two antennas, it is possible to use the present invention in a system that utilizes three or more antennas. The use of three or more antennas, however, causes the system to be more complex and expensive than the two antenna system. The foregoing has outlined rather broadly the features and technical advantages of the present invention so that those skilled in the art may better understand the detailed description of the invention that follows. Additional features and advantages of the invention will be described hereinafter that form the subject of the claims of the invention. Those skilled in the art should appreciate that they may readily use the conception and the specific embodiment disclosed as a basis for modifying or designing other structures for carrying out the same purposes of the present invention. Those skilled in the art should also realize that such equivalent constructions do not depart from the spirit and scope of the invention in its broadest form. Before undertaking the Detailed Description, it may be advantageous to set forth definitions of certain words and phrases used throughout this patent document: the terms "include" and "comprise" and derivatives thereof mean inclusion without limitation; the term "or," is inclusive, meaning and/or; the phrases "associated with" and "associated therewith," as well as derivatives thereof, may mean to include, be included within, interconnect with, contain, be contained within, connect to or with, couple to or with, be communicable with, cooperate with, interleave, juxtapose, be proximate to, be bound to or with, have, have a property of, or the like; and the term "controller" means any device, system or part thereof that controls at least one operation, such a device may be implemented in hardware, firmware, or software, or some combination of at least two of the same. It should be noted that the functionality associated with any particular controller may be centralized or distributed, whether locally or remotely. Definitions for certain words and phrases are provided throughout this patent document. Those of ordinary skill in the art should understand that in many, if not most, instances, such definitions apply to prior, as well as future uses of such defined words and phrases.
For a more complete understanding of the present invention, and the advantages thereof, reference is now made to the following descriptions taken in conjunction with the accompanying drawings, wherein like numbers designate like objects, and in which: FIGURE 1 is a block diagram of an adaptive digital beamforming receiver of the present invention;
FIGURE 2 is a block diagram of a high definition television signal receiver in which the present invention may be embodied. FIGURE 3 is a block diagram of an embodiment of the present invention in a signal receiver of a video device; and
FIGURE 4 is a flow diagram illustrating the operation of an exemplary adaptive beamforming receiver in accordance with one embodiment of the present invention.
FIGURES 1 through 4, discussed below, and the various embodiments used to describe the principles of the present invention in this patent document are by way of illustration only and should not be construed in any way to limit the scope of the invention. Those skilled in the art will understand that the principles of the present invention may be implemented in any suitably arranged signal receiver.
FIGURE 1 illustrates an adaptive digital beamforming receiver 100, according to a preferred embodiment of the invention. In this embodiment of the invention, the invention comprises beamforming circuit 200 and decision feedback equalizer circuit 300. Beamforming circuit 200 comprises two branches. The first branch of beamforming circuit 200 comprises radio frequency (RF) tuner 222, which is capable of being coupled to antenna 220. RF tuner 222 is coupled to intermediate frequency (IF) mixer 224. Together, RF tuner 222 and IF mixer 224 down-convert the RF signal received from antenna 220 to an analog baseband signal. IF mixer 224 is coupled to analog-to-digital converter 226, which converts the analog baseband signal to a digital baseband signal. Analog-to-digital converter 226 is coupled to first feedforward equalizer circuit 228 and first B/2 phase shift circuit 230. First B/2 phase shift circuit 230 is connected to second feedforward equalizer circuit 232. First B/2 phase shift circuit 230 shifts by 90 degrees the digital baseband signal at the input of second feedforward equalizer 232 with respect to the baseband signal at the input of first feedforward equalizer 228.
Under control of decision device 330, first feedforward equalizer circuit 228 modifies the input signal to form a beam in the direction of the desired signal and to form a null in the direction of the interfering signal. Similarly, under control of decision device 330, second feedforward equalizer circuit 232 modifies the B/2 phase shifted input signal to form a beam in the direction of the desired signal and to form a null in the direction of the interfering signal.
The second branch of beamforming circuit 200 comprises radio frequency (RF) tuner 242, which is capable of being coupled to antenna 240. RF tuner 242 is coupled to intermediate frequency (IF) mixer 244. Together, RF tuner 242 and IF mixer 244 down- convert the RF signal received from antenna 240 to an analog baseband signal. IF mixer 244 is coupled to analog-to-digital converter 246, which converts the analog baseband signal to a digital baseband signal. Analog-to-digital converter 246 is coupled to third feedforward equalizer circuit 248 and second B/2 phase shift circuit 252. Second B/2 phase shift circuit 252 is connected to fourth feedforward equalizer circuit 254. Second B/2 phase shift circuit 230 shifts by 90 degrees the digital baseband signal at the input of fourth feedforward equalizer 254 with respect to the baseband signal at the input of third feedforward equalizer 252.
Under control of decision device 330, third feedforward equalizer circuit 248 modifies the input signal to form a beam in the direction of the desired signal and to form a null in the direction of the interfering signal. Finally, under control of decision device 330, fourth feedforward equalizer circuit 254 modifies the B/2 phase shifted input signal to form a beam in the direction of the desired signal and to form a null in the direction of the interfering signal.
The output lines of first feedforward equalizer circuit 228, second feedforward equalizer 232, third feedforward equalizer circuit 248, and fourth feedforward equalizer circuit 254 are coupled to first adder circuit 250. First adder circuit 250 adds together the output signals from feedforward equalizer circuits 228, 232, 248 and 254. The signal that results from the addition of the signals by first adder circuit 250 is an improved signal because it represents a combination of four separate signals, each of which has been modified to form a beam in the direction of the desired signal and modified to form a null in the direction of the interfering signal. Signal information that may have been missing from one of the signals (due to interference) may have been present in one of the other signals. The additive combination of the four signals creates an improved signal that is less susceptible to interferer signals caused by multipath delays. Antennas 220 and 240 may be vertical, single dipole, omni-directional antennas. Antennas 220 and 240 are spaced apart by a distance in the range from one- twentieth (1/20) of a wavelength of the received signal up to one (1) wavelength of the received signal. For example, in the case of a carrier frequency of 470 MHz, the maximum separation of antennas 220 and 240, would be approximately 0.63 meter or approximately 24.0 inches. Antennas 220 and 240 can be used as components of an internal antenna of a television receiver that uses the present invention.
RF tuners 222 and 242, IF mixers 224 and 244, and analog-to-digital converters 226 and 246 are all conventional devices that are well known in the prior art. First feedforward equalizer circuit 228 receives from first analog-to-digital converter 226 a digital form of the signal received by antenna 220. First feedforward equalizer circuit 228 comprises circuitry (not shown) for operating a signal processing algorithm that is designed to compensate for the distortions in the amplitude and in the phase that a signal may acquire when that signal is transmitted through a dispersive channel. In this instance, the dispersive channel is the atmosphere.
A number of different types of prior art feedforward equalizer circuits are available that may be used as the first feedforward equalizer circuit 228 of the present invention. One of the simplest types of equalizer circuits is the Linear Transversal Equalizer. The Linear Transversal Equalizer samples values of the input signal in a tapped delay line having N tap points and multiplies those sampled values by N numerical coefficients and then sums the resultant values to form a representation of the signal. The numerical coefficients are numbers that represent weight factors. The number of numerical coefficients can range from one coefficient up to, for example, one hundred coefficients or more. The resultant signal is represented mathematically as follows:
Figure imgf000008_0001
where yn is the output, x1>n is the nΛ sample of the input signal from the first antenna 220, aj are the coefficients of first feedforward equalizer 228, and N is the number of coefficients in first feedforward equalizer 228. Similarly, third feedforward equalizer circuit 248 receives from second analog- to-digital converter 246 a digital form of the signal received by antenna 240. Third feedforward equalizer circuit 248 may be identical in structure and function to the first feedforward equalizer circuit 228. The output signal of the third feedforward equalizer circuit 248 is represented mathematically as follows:
Figure imgf000008_0002
where yn is the output, x ;„ is the nft sample of the input signal from the second antenna 240, bj are the coefficients of third feedforward equalizer 248, and N is the number of coefficients in the third feedforward equalizer 248.
Second feedforward equalizer circuit 232 receives from first B/2 phase shift circuit 230 a phase shifted digital form of the signal received by antenna 220. Second feedforward equalizer circuit 232 is identical in structure and function to the first feedforward equalizer circuit 228. The only difference is that the signal has been phase shifted by B/2 radians. This shift is represented by the factor e*(B/2). The output signal of the second feedforward equalizer circuit 232 is represented mathematically as follows:
λ = (∑β,V)« ,/J
/=0 where yn is the output, xl n is the nΛ sample of the input signal from the first antenna 220, a'j are the coefficients of second feedforward equalizer 232, and N is the number of coefficients in the second feedforward equalizer 232.
Similarly, the output signal of the fourth feedforward equalizer circuit 254 is represented mathematically as follows:
<=0 where yn is the output, x >n is the nΛ sample of the input signal from the second antenna 240, b'j are the coefficients of fourth feedforward equalizer 254, and N is the number of coefficients in the fourth feedforward equalizer 254.
It is understood that the use of the Linear Transversal Equalizer in this description does not limit the invention to this particular type of equalizer. Other types of equalizers may be utilized to practice the invention.
The decision feedback equalizer circuit 300 of the invention comprises a second adder circuit 320, a decision device 330, and a feedback equalizer circuit 340. The second adder circuit 320 of decision feedback equalizer circuit 300 is coupled to the first adder circuit 250 of beamforming circuit 200. The second adder circuit 320 receives from the first adder circuit 250 a signal that is the sum of the output signal from first feedforward equalizer circuit 228 and the output signal from second feedforward equalizer circuit 232 and the output signal from third feedforward equalizer circuit 248 and the output signal from fourth feedforward equalizer circuit 254. As will be described more fully below, second adder circuit 320 also receives an input signal from feedback equalizer circuit 340. Second adder circuit 320 is coupled to a decision device 330. Decision device
330 may be a digital signal processor (DSP) or other similar type of electronic controller device. Decision device 330 receives a signal from second adder circuit 320.
Decision device 330 performs two operations. The first operation is to make a decision as to which valid symbol the input symbol is closest to (in this case, the eight levels of the 8-VSB signal). This could be called a splicer. It is this valid symbol (i.e., the decision output) that is passed to the feedback equalizer circuit 340. The second operation of decision device 330 is based on the difference of the decision device input and the decision device output (i.e., the symbol error). The symbol error is used in a decision directed adaptation algorithm (e.g., Least Mean Square Algorithm) or in a blind adaptation algorithm (e.g., Constant Modulus Algorithm) to update the equalizer coefficients so that the Mean Square Error (MSE) at the decision device input is reduced. Decision device 330 may use any one of a number of equalizer adaptation algorithms well known in the prior art. In the preferred embodiment of the invention, the equalizer adaptation algorithm used is the Least Mean Squares (LMS) method. It is referred to as the LMS algorithm. Another equalizer adaptation algorithm available for use utilizes the Recursive Least Squares (RLS) method. It is referred to as the RLS algorithm. Other similar algorithms are also available for use. The description of the preferred embodiment of the invention is not intended to limit the type of algorithm that may be used in accordance with the concept of the invention.
The adaptation algorithm calculates the amount of error in the amplitude and phase of the signal. The adaptation algorithm then calculates the amount of correction needed to correct the errors. The decision device 330 then changes the values of the coefficients in first feedforward equalizer 228, second feedforward equalizer 232, third feedforward equalizer 248, fourth feedforward equalizer 254, and feedback equalizer 340. In this manner, decision device 330 modifies the signal to create an improved signal by electronically forming a beam in the direction of the desired signal and by electronically forming a null in the direction of the interfering signal.
Feedback equalizer circuit 340 is coupled to the output of decision device 330 for sampling the output signal of decision device 330. Feedback equalizer circuit 340 also has an output coupled to an input of second adder circuit 320. This allows second adder circuit 320 to access the output signal of feedback equalizer circuit 340. Second adder circuit 320 subtracts the output signal of feedback equalizer circuit 340 from the signal that is the sum of the output signal from first feedforward equalizer circuit 228 and the output signal from second feedforward equalizer circuit 248 and the output signal from third feedforward equalizer circuit 248 and the output signal from fourth feedforward equalizer circuit 254.
Feedback equalizer circuit 340 may also have the same form and structure of the first feedforward equalizer circuit 228 and the second feedforward equalizer circuit 248 and the third feedforward equalizer circuit 248 and the fourth feedforward equalizer circuit 254. The output signal of feedback equalizer circuit 340 is represented mathematically as follows:
Figure imgf000011_0001
where yn is the output, yn.k is the input signal from the decision device 330, C are the coefficients of feedback equalizer circuit 340, and M is the number of coefficients in feedback equalizer circuit 340. Therefore, the input signal to the decision device 330 is given by the mathematical expression:
yn = ( ckyn_k
Figure imgf000011_0002
where yn is the estimated output, xljn is the nΛ sample of the input signal from first antenna 220, x2(„ is the nΛ sample of the input signal from second antenna 240, and yn-k is the input signal from the decision device 330. The values aj are the coefficients of the first feedforward equalizer circuit 228, the values a'; are the coefficients of the second feedforward equalizer circuit 248, the values bj are the coefficients of the third feedforward equalizer circuit 248, the values b'j are the coefficients of the fourth feedforward equalizer circuit 254, and the values c\_ are the coefficients of the feedback equalizer circuit 340. The value N is the number of coefficients in feedforward equalizer circuit 228, feedforward equalizer circuit 232, feedforward equalizer circuit 248, and feedforward equalizer circuit 254. The value M is the number of coefficients in the feedback equalizer circuit 340. This expression represents the input to the decision device 330.
Decision device 330 utilizes the above described input value for y„ to sequentially set up and solve a set of linear equations to determine corrected values for the coefficients of each of the five equalizer circuits, that is, for the first feedforward equalizer circuit 228, and for the second feedforward equalizer circuit 232, and for the third feedforward equalizer circuit 248, and for the fourth feedforward equalizer circuit 254, for the feedback equalizer circuit 340. The coefficients (also referred to as tap weights) of an equalizer can be adjusted to minimize the Mean Square Error (MSE), εk , according to:
Sk ~ X ~ X where lk is the kft information symbol transmitted and lk is the estimate of the kΛ symbol at the output of the equalizer. The estimated symbol Ik is expressed as
Figure imgf000011_0003
j=-∞ where Xk is the sampled channel output and dj are the equalizer coefficients.
A set of linear equations can be set up based on the orthogonality principle in mean-square estimation. The equalizer coefficients, dJ? are chosen such that the Mean Square
Error (MSE), εk , is orthogonal to the complex conjugate of the transmitted symbol sequence, Xk , according to:
∑ dj Eixk-j x ι ) = £(?****-/ ) - ∞ < < ∞
J=—∞ where dj are the equalizer coefficients, Xj are the equalizer inputs, Xj* is the complex conjugate, E(X) is the expected value and yk is the estimated output of the equalizer. This equation involves the statistical autocorrelation function of the input signal and the cross correlation function between the input and predicted signal.
The above linear simultaneous equations have to be solved to find the optimum equalizer tap coefficients. This means that for an N tap equalizer, there are N linear simultaneous equations to be solved.
An adaptation algorithm such as the Least Mean Square (LMS) algorithm is used to solve the above equation. In the LMS algorithm an estimate of the gradient of the
Mean Square Error (MSE) can be found and the opposite of this taken to update the tap values so that the MSE moves closer to the minimum. The LMS algorithm is represented by the equation: d„(k+l) = dn(k) -Δekx*(kT-nT), n = 0,1,2,...,N-1 where dn(k) is the n* equalizer tap at time k, and T is the signaling interval, and ek is the error signal, and Δ is a variable adaptation constant (step size). The value ekX*(kT-nT) is an estimate of the gradient vector obtained from the data. The LMS algorithm does not require knowledge of the signal's statistics or of the noise. The new equalizer coefficient is deduced from the previous value of the coefficient minus an error function. The greater Δ is, the faster the convergence, and the smaller Δ is, the slower the convergence. The LMS algorithm is easy to implement but slow to converge.
After decision device 330 has calculated the new equalizer coefficients for the equalizer circuits, decision device 330 sends a new equalizer coefficient to first feedforward equalizer circuit 228 via control line 331. Decision device 330 also sends a new equalizer coefficient to second feedforward equalizer circuit 232 via control line 333, sends a new equalizer coefficient to third feedforward equalizer circuit 248 via control line 335, sends a new equalizer coefficient to fourth feedforward equalizer circuit 254 via control line 337, and sends a new equalizer coefficient to feedback equalizer 340 via control line 339.
The iterative process continues until the mean square error is minimized. In this manner the decision device 330 creates an improved signal for signal receiver 400. In order to clearly show how the present invention works in a video device, a video device will be briefly described. For purposes of illustration, the video device that will be described is a high resolution television signal receiver. It is to be borne in mind that the invention is not limited to use in a television signal receiver but may be used in any type of video device, including, without limitation, personal computer monitors, laptop computer monitors, handheld computer monitors, handheld video devices, and any type of device having the ability to display a video signal.
FIGURE 2 is a block diagram of a high definition television signal receiver, in which the present invention may be embodied. The television signal is received by antenna 520 and sent to a RF tuner 522 and then to an IF mixer 524. The signal is then sent to a demodulator and channel decoder circuit 526. The signal is then sent to a transport demultiplexer and decryption circuit 530 where the audio, video and data portions of the signal are separated from each other. The video portion of the signal is sent to a video decoder 540. The audio portion of the signal is sent to an audio decoder 542. The data portion of the signal is sent to a data decoder 544. The video portion of the signal is sent to a video display circuit 550 and the audio portion of the signal is sent to an audio speaker unit 552.
FIGURE 3 is a block diagram of an embodiment of the present invention in a video device 600. The video device 600 is a television signal receiver having a first antenna 520 and a second antenna 521. The RF tuner 522 and the IF mixer 524 of the television signal receiver 500 have been replaced with the beamforming circuit 200 and with the decision feedback equalizer circuit 300 of the present invention. The video device 600 shown in
FIGURE 3 is an exemplary adaptive digital beamforming receiver of the present invention.
In video device 600 the decision feedback equalizer circuit 300 sends the improved signal of the present invention to an MPEG-2 decoder 620. The MPEG-2 decoder 620 is of a type well known in the prior art. The video portion of the signal is sent to a video display unit 630. The audio portion of the signal is sent to an audio speaker 640.
FIGURE 4 is a flow diagram illustrating the operation of an exemplary adaptive digital beamforming receiver in accordance with one embodiment of the present invention. Step 700 comprises the step of demodulating a first analog signal from a first antenna. Step 702 comprises the step of converting the first analog signal to a digital signal. Step 704 comprises the step of modifying the first signal in a first feedforward equalizer to correct distortions in the first signal.
Similarly, step 706 comprises the step of demodulating a second analog signal from a second antenna. Step 708 comprises the step of converting the second analog signal to a digital signal. Step 710 comprises the step of modifying the second signal in a second feedforward equalizer circuit to correct distortions in the second signal.
Step 712 comprises the step of adding the modified first signal and the modified second signal. Step 714 comprises the step of adding to the sum of the modified first signal and the modified second signal a feedback signal from a feedback equalizer circuit to create an improved signal.
Step 716 comprises the step of modifying the improved signal in a decision device having an adaptive algorithm by adjusting the coefficients of the first feedforward equalizer circuit, and by adjusting the coefficients of the second feedforward equalizer circuit, and by adjusting the coefficients of the feedback equalizer circuit. Although the present invention has been described in detail, those skilled in the art should understand that they can make various changes, substitutions and alterations herein without departing from the spirit and scope of the invention in its broadest form.

Claims

CLAIMS:
1. An apparatus for improving signal reception in a signal receiver (100) having a first antenna (220) and a second antenna (240) comprising: a first feedforward equalizer circuit (228) capable of being coupled to said first antenna (220), said first feedforward equalizer circuit (228) comprising equalization circuitry capable of modifying a signal from said first antenna (220) to correct distortions in said signal; and second feedforward equalizer circuit (232) capable of being coupled to said first antenna (220) through a first B/2 phase shift circuit (230), said second feedforward equalizer circuit (232) comprising equalization circuitry capable of modifying a signal from said first antenna (220) to correct distortions in said signal; and third feedforward equalizer circuit (248) capable of being coupled to said second antenna (240), said second feedforward equalizer circuit (248) comprising equalization circuitry capable of modifying a signal from said second antenna (240) to correct distortions in said signal; and fourth feedforward equalizer circuit (254) capable of being coupled to said second antenna (240) through a second B/2 phase shift circuit (252), said fourth feedforward equalizer circuit (254) comprising equalization circuitry capable of modifying a signal from said second antenna (240) to correct distortions in said signal; an adder (250, 320) having a first input coupled to said first feedforward equalizer circuit (228), a second input coupled to said second feedforward equalizer circuit
(232), a third input coupled to said third feedforward equalizer circuit (248), and a fourth input coupled to said fourth feedforward equalizer circuit (254), wherein said adder (250, 320) is capable of adding said modified signal from said first feedforward equalizer circuit (228), said modified signal from said second feedforward equalizer circuit (232), said modified signal from said third feedforward equalizer circuit (248), and said modified signal from said fourth feedforward equalizer circuit (254); and a decision device (330) coupled to an output of said adder (250, 320) and capable of monitoring a signal on said adder (250, 320) output, wherein said decision device (330), in response to a value of said adder (250, 320) output signal, modifies equalizer coefficients in said first feedforward equalizer circuit (228) and said second feedforward equalizer circuit (232) and said third feedforward equalizer circuit (248) and said fourth feedforward equalizer circuit (254) to reduce interference signals from at least one of said first feedforward equalizer circuit (228) and said second feedforward equalizer circuit (232) and said third feedforward equalizer circuit (248) and said fourth feedforward equalizer circuit (254).
2. An apparatus as set forth in Claim 1 further comprising a feedback equalizer circuit (340) coupled to said decision device (330), said feedback equalizer circuit (340) comprising equalization circuitry modifying an output signal of said decision device (330), wherein a fifth input of said adder (250, 320) is coupled to an output of said feedback equalizer circuit (340).
3. An apparatus as set forth in Claim 1 wherein said decision device (330) comprises a microprocessor capable of executing an adaptation algorithm.
4. An apparatus as set forth in Claim 3 wherein said adaptation algorithm utilizes a least mean squares method.
5. An apparatus as set forth in Claim 3 wherein said microprocessor is capable of adjusting said equalizer coefficients in said first feedforward equalizer circuit (228), said second feedforward equalizer circuit (232), said third feedforward equalizer circuit (248), said fourth feedforward equalizer circuit (254), and said feedback equalizer circuit (340).
6. An apparatus as set forth in Claim 1 wherein at least one of said first feedforward equalizer circuit (228), said second feedforward equalizer circuit (232), said third feedforward equalizer circuit (248), said fourth feedforward equalizer circuit (254), and said feedback equalizer circuit (340) comprises a linear transversal equalizer.
7. An apparatus as set forth in Claim 1 wherein said first feedforward equalizer circuit (228) and said second feedforward equalizer circuit (232) are coupled to said first antenna (220) by first RF receiver circuitry (222, 224, 226) capable of receiving an RF signal from said first antenna (220) and converting said RF signal to a digital baseband signal.
8. An apparatus as set forth in Claim 1 wherein said third feedforward equalizer circuit (248) and said fourth feedforward equalizer circuit (254) are coupled to said second antenna (240) by second RF receiver circuitry (242, 244, 246) capable of receiving an RF signal from said second antenna (240) and converting said RF signal to a digital baseband signal.
9. A television receiver comprising: first RF receiver circuitry (222, 224, 226) capable of being coupled to a first antenna (220), receiving a first RF signal from said first antenna (220), and converting said first RF signal to a first digital baseband signal; and second RF receiver circuitry (242, 244, 246) capable of being coupled to a second antenna (240), receiving a second RF signal from said second antenna (240), and converting said second RF signal to a second digital baseband signal; and a first feedforward equalizer circuit (228) capable receiving said first digital baseband signal, said first feedforward equalizer circuit (228) comprising equalization circuitry capable of modifying said first digital baseband signal to minimize distortions therein; and a second feedforward equalizer circuit (232) capable receiving said first digital baseband signal through a first B/2 phase shift circuit (230), said second feedforward equalizer circuit (232) comprising equalization circuitry capable of modifying said first B/2 phase shifted digital baseband signal to minimize distortions therein; and a third feedforward equalizer circuit (248) capable of receiving said second digital baseband signal, said second feedforward equalizer circuit (248) comprising equalization circuitry capable of modifying said second digital baseband signal to minimize distortions therein; and a fourth feedforward equalizer circuit (254) capable receiving said second digital baseband signal through a second B/2 phase shift circuit (252), said second feedforward equalizer circuit (254) comprising equalization circuitry capable of modifying said second B/2 phase shifted digital baseband signal to minimize distortions therein; and an adder (250, 320) having a first input coupled to said first feedforward equalizer circuit (228), a second input coupled to said second feedforward equalizer circuit
(232), a third input coupled to said third feedforward equalizer circuit (248), and a fourth input coupled to said fourth feedforward equalzier circuit (254), wherein said adder (250, 320) is capable of adding said modified signal from said first feedforward equalizer circuit (228), said modified signal from said second feedforward equalizer circuit (232), said modified signal from said third feedforward equalizer circuit (248), and said modified signal from said fourth feedforward equalizer circuit (254); and a decision device (330) coupled to an output of said adder (250, 320) and capable of monitoring a signal on said adder (250, 320) output, wherein said decision device (330), in response to a value of said adder (250, 320) output signal, modifies equalizer coefficients in at least one of said first feedforward equalizer circuit (228) and said second feedforward equalizer circuit (232) and said third feedforward equalizer circuit (248) and said fourth feedforward equalizer circuit (254) to minimize distortions in at least one of said first feedforward equalizer circuit (228), said second feedforward equalizer circuit (232), said third feedforward equalizer circuit (248), and said fourth feedforward equalizer circuit (254); an MPEG-2 decoder (620) coupled to said decision device (330) capable of receiving and decoding an output signal from said decision device (330); and a video display unit (630) coupled to said MPEG-2 decoder (620) capable of receiving and displaying a decoded output signal from said MPEG-2 decoder (620).
10. A television receiver as set forth in Claim 9 further comprising a feedback equalizer circuit (340) coupled to said decision device (330), said feedback equalizer circuit (340) comprising equalization circuitry modifying an output signal of said decision device (330), wherein a fifth input of said adder (250, 320) is coupled to an output of said feedback equalizer circuit (340).
11. A television receiver as set forth in Claim 9 wherein said decision device (330) comprises a microprocessor capable of executing an adaptation algorithm.
12. A television receiver as set forth in Claim 11 wherein said adaptation algorithm utilizes a least mean squares method.
13. A television receiver as set forth in Claim 11 wherein said microprocessor is capable of adjusting said equalizer coefficients in said first feedforward equalizer circuit (228), said second feedforward equalizer circuit (232), said third feedforward equalizer circuit (248), said fourth feedforward equalizer circuit (254), and said feedback equalizer circuit (340).
14. A television receiver as set forth in Claim 9 wherein at least one of said first feedforward equalizer circuit (228), said second feedforward equalizer circuit (232), said third feedforward equalizer circuit (248), said fourth feedforward equalizer circuit (254), and said feedback equalizer circuit (340) comprises a linear transversal equalizer.
15. A method for improving signal reception in a signal receiver having a first antenna (220) and a second antenna (240) comprising the steps of: modifying a first signal from said first antenna (220) in a first feedforward equalizer circuit (228) to correct distortions in said first signal; phase shifting said unmodified first signal by a phase of B/2 radians; modifying said phase shifted first signal in a second feedforward equalizer (232) to correct distortions in said phase shifted first signal; modifying a second signal from said second antenna (240) in a third feedforward equalizer circuit (248) to correct distortions in said second signal; phase shifting said unmodified second signal by a phase of B/2 radians; modifying said phase shifted second signal in a fourth feedforward equalizer (254) to correct distortions in said phase shifted second signal; adding said modified first signal from said first feedforward equalizer circuit (228) and said modified phase shifted first signal from said second feedforward equalizer circuit (232) and said modified second signal from said third feedforward equalizer circuit (248) and said modified phase shifted second signal from said fourth feedforward equalizer circuit (254) to form a sum of said modified signals; monitoring in a decision device (330) said sum of said modified signals; and in response to a value of said sum of said modified signals, modifying equalizer coefficients in said first feedforward equalizer circuit (228) and said second feedforward equalizer circuit (232) and said third feedforward equalizer circuit (248) and said fourth feedforward equalizer circuit (254) to reduce interference signals from at least one of said first feedforward equalizer circuit (228) and said second feedforward equalizer circuit (232) and said third feedforward equalizer circuit (248) and said fourth feedforward equalizer circuit (254).
16. The method as set forth in Claim 15 wherein said step of modifying equalizer coefficients comprises the steps of: calculating corrections to said sum of said modified signals with an adaptation algorithm; and changing the values of portions of said sum of said modified signals using said calculated corrections.
17. The method as set forth in Claim 16 wherein the step of calculating corrections to said signal with an adaptation algorithm is carried out using an adaptation algorithm that utilizes a least mean squares method.
18. A method for improving signal reception in a signal receiver having a first antenna (220) and a second antenna (240) comprising the steps of: down-converting an RF signal received by said first antenna (220) to a first digital baseband signal; down-converting an RF signal received by said second antenna (240) to a second digital baseband signal; modifying said first digital baseband signal in a first feedforward equalizer circuit (228) to correct distortions in said first digital baseband signal; phase shifting said first digital baseband signal by a phase of B/2 radians; modifying said phase shifted first digital baseband signal in a second feedforward equalizer circuit (232) to correct distortions in said phase shifted first digital baseband signal; modifying said second digital baseband signal in a second feedforward equalizer circuit (248) to correct distortions in said second digital baseband signal; phase shifting said second digital baseband signal by a phase of B/2 radians; modifying said phase shifted second digital baseband signal in a fourth feedforward equahzer circuit (254) to correct distortions in said phase shifted second digital baseband signal; adding said first digital baseband signal and said phase shifted first digital baseband signal and said second digital baseband signal and said phase shifted second digital baseband signal to produce a composite baseband signal; monitoring in a decision device (330) said composite baseband signal; and in response to a value of said composite baseband signal, modifying equalizer coefficients in said first feedforward equalizer circuit (228) and said second feedforward equalizer circuit (232) and said third feedforward equalizer circuit (248) and said fourth feedforward equalizer circuit (254) to reduce interference signals in said composite baseband signal.
19. The method as set forth in Claim 18 wherein said step of modifying equalizer coefficients comprises the steps of: calculating corrections to said sum of said modified signals with an adaptation algorithm; and changing the values of portions of said sum of said modified signals using said calculated corrections.
20. The method as set forth in Claim 19 wherein the step of calculating corrections to said signal with an adaptation algorithm is carried out using an adaptation algorithm that utilizes a least mean squares method.
21. A method for improving signal reception in a signal receiver having a first antenna (220) and a second antenna (240) comprising the steps of: demodulating a first analog signal from a first antenna (220); converting said first analog signal to a digital signal; modifying said first signal in a first feedforward equalizer circuit (228) to correct distortions in said first signal; phase shifting said first signal by a phase of B/2 radians; modifying said phase shifted first signal in a second feedforward equalizer circuit (232) to correct distortions in said phase shifted first signal; demodulating a second analog signal from a second antenna (240); converting said second analog signal to a digital signal; modifying said second signal in a third feedforward equalizer circuit (248) to correct distortions in said second signal; phase shifting said second signal by a phase of B/2 radians; modifying said phase shifted second signal in a fourth feedforward equalizer circuit (254) to correct distortions in said phase shifted second signal; adding the modified first signal and the modified phase shifted first signal and the modified second signal and the modified phase shifted second signal; adding to the sum of said modified first signal and said modified phase shifted first signal and said modified second signal and said modified phase shifted second signal a feedback signal from a feedback equalizer circuit (340) to create a combined signal; and modifying the combined signal in a decision device (330) having an adaptive algorithm by adjusting the coefficients of said first feedforward equalizer circuit (228), by adjusting the coefficients of said second feedforward equalizer circuit (232), by adjusting the coefficients of said third feedforward equalizer circuit (248), by adjusting the coefficients of said fourth feedforward equalizer circuit (254), and by adjusting the coefficients of said feedback equalizer circuit (340).
PCT/EP2000/009761 1999-10-21 2000-10-05 AN ADAPTIVE DIGITAL BEAMFORMING RECEIVER WITH π/2 PHASE SHIFT TO IMPROVE SIGNAL RECEPTION WO2001029987A1 (en)

Priority Applications (3)

Application Number Priority Date Filing Date Title
EP00972684A EP1142160A1 (en) 1999-10-21 2000-10-05 AN ADAPTIVE DIGITAL BEAMFORMING RECEIVER WITH $g(p)/2 PHASE SHIFT TO IMPROVE SIGNAL RECEPTION
KR1020017007896A KR20010086140A (en) 1999-10-21 2000-10-05 An adaptive digital beamforming receiver with π/2 phase shift to improve signal reception
JP2001531225A JP2003512762A (en) 1999-10-21 2000-10-05 Adaptive digital beamforming receiver with π / 2 phase shift to improve signal reception quality

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
US09/422,734 US6115419A (en) 1999-10-21 1999-10-21 Adaptive digital beamforming receiver with π/2 phase shift to improve signal reception
US09/422,734 1999-10-21

Publications (1)

Publication Number Publication Date
WO2001029987A1 true WO2001029987A1 (en) 2001-04-26

Family

ID=23676135

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/EP2000/009761 WO2001029987A1 (en) 1999-10-21 2000-10-05 AN ADAPTIVE DIGITAL BEAMFORMING RECEIVER WITH π/2 PHASE SHIFT TO IMPROVE SIGNAL RECEPTION

Country Status (5)

Country Link
US (1) US6115419A (en)
EP (1) EP1142160A1 (en)
JP (1) JP2003512762A (en)
KR (1) KR20010086140A (en)
WO (1) WO2001029987A1 (en)

Families Citing this family (28)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2343815B (en) * 1998-11-12 2003-10-22 Sony Uk Ltd Digital receiver
US7292661B1 (en) * 2000-03-20 2007-11-06 Massachusetts Institute Of Technology Block-iterative equalizers for digital communication system
US7010029B1 (en) * 2000-04-13 2006-03-07 At&T Corp. Equalization of transmit diversity space-time coded signals
IT1317249B1 (en) * 2000-04-14 2003-05-27 Cit Alcatel METHOD AND APPARATUS FOR THE AUTOMATIC COMPENSATION OF THE DELAY FOR RADIO TRANSMISSIONS IN DIFFERENT SPACE.
US6650702B1 (en) * 2000-05-15 2003-11-18 Lockheed Martin Corp. Blind initialization of decision feedback equalizer using an antenna array
US6950477B2 (en) * 2001-01-16 2005-09-27 Joseph Meehan Blind dual error antenna diversity (DEAD) algorithm for beamforming antenna systems
US20020150185A1 (en) * 2001-03-29 2002-10-17 Joseph Meehan Diversity combiner for reception of digital television signals
US7034893B2 (en) * 2001-03-30 2006-04-25 Broadcom Corporation Method and apparatus for reception of terrestrial digital television signals
US6691181B2 (en) * 2001-10-09 2004-02-10 Phillip M. Adams Programmatic time-gap defect detection apparatus and method
ITMI20012631A1 (en) * 2001-12-13 2003-06-13 Marconi Comm Spa MEDIUM SQUARE ERROR-BASED METHOD FOR ADAPTIVE ADJUSTMENT OF PMD COMPENSATORS IN OPTICAL FIBER AND COMMUNICATION SYSTEMS
US6980614B2 (en) * 2002-01-14 2005-12-27 Raytheon Company System and method for subband beamforming using adaptive weight normalization
US20030228860A1 (en) * 2002-06-06 2003-12-11 Chewnpu Jou Integrated radio-frequency receiver
KR100911142B1 (en) * 2002-12-02 2009-08-06 삼성전자주식회사 Equalizer for high density optical disc reproducing apparatus and equalizing method therefor
US7103383B2 (en) * 2002-12-31 2006-09-05 Wirless Highways, Inc. Apparatus, system, method and computer program product for digital beamforming in the intermediate frequency domain
KR100510678B1 (en) * 2003-03-19 2005-08-31 엘지전자 주식회사 Smart antenna control system for digital TV
US20050129148A1 (en) * 2003-12-11 2005-06-16 Wideband Semiconductors, Inc. Control algorithm in QAM modems
US7526022B2 (en) * 2004-05-19 2009-04-28 Harris Corporation Low complexity equalizer
US7295618B2 (en) * 2004-06-16 2007-11-13 International Business Machines Corporation Automatic adaptive equalization method and system for high-speed serial transmission link
JP4405375B2 (en) * 2004-12-07 2010-01-27 三菱電機株式会社 Digital broadcast receiver
KR100836969B1 (en) * 2005-08-05 2008-06-10 세이코 엡슨 가부시키가이샤 Receiving device
KR100782820B1 (en) * 2005-09-30 2007-12-06 삼성전자주식회사 Printing apparatus having broadcast receiver and operating method thereof
US20080205563A1 (en) * 2007-02-09 2008-08-28 Simpson Richard D Digital Filter
US8902365B2 (en) * 2007-03-14 2014-12-02 Lance Greggain Interference avoidance in a television receiver
US8330873B2 (en) * 2007-03-14 2012-12-11 Larry Silver Signal demodulator with overmodulation protection
TWI367655B (en) * 2008-11-04 2012-07-01 Realtek Semiconductor Corp Equalizer and method applied thereto
US9036689B2 (en) * 2012-03-29 2015-05-19 Terasquare Co., Ltd. Variable-precision distributed arithmetic multi-input multi-output equalizer for power-and-area-efficient optical dual-polarization quadrature phase-shift-keying system
US10998627B2 (en) * 2017-10-23 2021-05-04 Nec Corporation Phase adjustment circuit and array antenna device
US10425256B2 (en) * 2018-02-06 2019-09-24 Huawei Technologies Canada Co., Ltd. Methods and systems for interference mitigation in a dual-polarized communication system

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5771439A (en) * 1996-05-20 1998-06-23 Raytheon E-Systems, Inc. Adaptive antenna system and method for cellular and personal communication systems
US5844951A (en) * 1994-06-10 1998-12-01 Northeastern University Method and apparatus for simultaneous beamforming and equalization
US5929811A (en) * 1995-03-28 1999-07-27 Rilling; Kenneth F. Adaptive array with automatic loop gain control

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4280128A (en) * 1980-03-24 1981-07-21 The United States Of America As Represented By The Secretary Of The Army Adaptive steerable null antenna processor
US4691205A (en) * 1985-06-06 1987-09-01 Rca Corporation Beam forming network for circularly polarized shaped beam antenna system
US5230007A (en) * 1991-06-28 1993-07-20 Motorola, Inc. Method for optimizing an adaptive filter update coefficient
US5274844A (en) * 1992-05-11 1993-12-28 Motorola, Inc. Beam pattern equalization method for an adaptive array
FR2705499A1 (en) * 1993-05-18 1994-11-25 Europ Agence Spatiale Adaptive signal processing system
EP0763307A2 (en) * 1994-06-03 1997-03-19 Telefonaktiebolaget Lm Ericsson Diversity combining for antennas

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5844951A (en) * 1994-06-10 1998-12-01 Northeastern University Method and apparatus for simultaneous beamforming and equalization
US5929811A (en) * 1995-03-28 1999-07-27 Rilling; Kenneth F. Adaptive array with automatic loop gain control
US5771439A (en) * 1996-05-20 1998-06-23 Raytheon E-Systems, Inc. Adaptive antenna system and method for cellular and personal communication systems

Also Published As

Publication number Publication date
KR20010086140A (en) 2001-09-07
JP2003512762A (en) 2003-04-02
US6115419A (en) 2000-09-05
EP1142160A1 (en) 2001-10-10

Similar Documents

Publication Publication Date Title
US6115419A (en) Adaptive digital beamforming receiver with π/2 phase shift to improve signal reception
JP4308870B2 (en) Interference rejection device with fast phase adaptation
US6366613B2 (en) High stability fast tracking adaptive equalizer for use with time varying communication channels
US6563868B1 (en) Method and apparatus for adaptive equalization in the presence of large multipath echoes
US7050491B2 (en) Adaptive equalization of digital modulating signal recovered from amplitude-modulated signal subject to multipath
US8194791B2 (en) Joint, adaptive control of equalization, synchronization, and gain in a digital communications receiver
US6526093B1 (en) Method and apparatus for equalizing a digital signal received via multiple transmission paths
US20050024540A1 (en) Method and apparatus for receiving digital television signals using space diversity and beam-forming
US7555080B2 (en) Digital broadcasting receiving system and equalizing method thereof
US20050261898A1 (en) Method and adaptive filter for processing a sequence of input data
EP1014477A2 (en) Directing an antenna to receive digital television signals
US6950477B2 (en) Blind dual error antenna diversity (DEAD) algorithm for beamforming antenna systems
US9042436B2 (en) Asymmetric multi-channel adaptive equalizer
US20090067483A1 (en) Efficient adaptive equalizer implementation
EP1145475A1 (en) An adaptive digital beamforming receiver to improve signal reception
WO2014188508A1 (en) Diversity-receiving device, diversity-receiving method, receiving program, and recording medium
EP1397880B1 (en) Joint timing recovery and equalization for an n-antennae system
JP5881453B2 (en) Equalizer, receiver, and equalization method
WO2014188578A1 (en) Diversity-receiving device, diversity-receiving method, receiving program, and recording medium
Lei et al. A Multiantenna Diversity System with Blind Equalisation for Mobile Video Signal Reception
Park et al. A selection beamforming algorithm combined with the spatial equalizer for the VSB DTV receiver system
KR20020061839A (en) Apparatus for of removing NTSC co-channel interference of digital TV

Legal Events

Date Code Title Description
AK Designated states

Kind code of ref document: A1

Designated state(s): JP KR

AL Designated countries for regional patents

Kind code of ref document: A1

Designated state(s): AT BE CH CY DE DK ES FI FR GB GR IE IT LU MC NL PT SE

WWE Wipo information: entry into national phase

Ref document number: 2000972684

Country of ref document: EP

121 Ep: the epo has been informed by wipo that ep was designated in this application
ENP Entry into the national phase

Ref country code: JP

Ref document number: 2001 531225

Kind code of ref document: A

Format of ref document f/p: F

WWE Wipo information: entry into national phase

Ref document number: 1020017007896

Country of ref document: KR

WWP Wipo information: published in national office

Ref document number: 1020017007896

Country of ref document: KR

WWP Wipo information: published in national office

Ref document number: 2000972684

Country of ref document: EP