WO1996018937A1 - Convertisseur bidirectionnel raccorde au secteur comprenant un decoupeur continu/continu a modulation d'impulsions en largeur et dispositif de stockage/alimentation d'energie - Google Patents

Convertisseur bidirectionnel raccorde au secteur comprenant un decoupeur continu/continu a modulation d'impulsions en largeur et dispositif de stockage/alimentation d'energie Download PDF

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Publication number
WO1996018937A1
WO1996018937A1 PCT/US1995/014505 US9514505W WO9618937A1 WO 1996018937 A1 WO1996018937 A1 WO 1996018937A1 US 9514505 W US9514505 W US 9514505W WO 9618937 A1 WO9618937 A1 WO 9618937A1
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WO
WIPO (PCT)
Prior art keywords
waveform
inverter
real
power
voltage
Prior art date
Application number
PCT/US1995/014505
Other languages
English (en)
Inventor
Michael R. Behnke
Xu Renjie
William L. Erdman
Raymond M. Hudson
Original Assignee
Kenetech Windpower, Inc.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Kenetech Windpower, Inc. filed Critical Kenetech Windpower, Inc.
Priority to AU41493/96A priority Critical patent/AU4149396A/en
Publication of WO1996018937A1 publication Critical patent/WO1996018937A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/04—Circuit arrangements for ac mains or ac distribution networks for connecting networks of the same frequency but supplied from different sources
    • H02J3/06—Controlling transfer of power between connected networks; Controlling sharing of load between connected networks
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
    • G05F1/70—Regulating power factor; Regulating reactive current or power
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/28—Arrangements for balancing of the load in a network by storage of energy
    • H02J3/32—Arrangements for balancing of the load in a network by storage of energy using batteries with converting means
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1582—Buck-boost converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/66—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal
    • H02M7/68—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters
    • H02M7/72—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/79—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/797—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E10/00—Energy generation through renewable energy sources
    • Y02E10/50—Photovoltaic [PV] energy
    • Y02E10/56—Power conversion systems, e.g. maximum power point trackers
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E70/00—Other energy conversion or management systems reducing GHG emissions
    • Y02E70/30—Systems combining energy storage with energy generation of non-fossil origin
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
    • Y02P90/00—Enabling technologies with a potential contribution to greenhouse gas [GHG] emissions mitigation
    • Y02P90/40—Fuel cell technologies in production processes

Definitions

  • This invention relates generally to conversion technologies for converting electrical energy between AC and DC.
  • the present invention is particularly useful for connecting an electrical utility to an apparatus that stores and /or produces DC electrical energy.
  • electrical energy can be stored in well-known and cost effective devices such as batteries or fuel cells. DC electrical energy can also be produced by photovoltaic cells. Energy storage technologies which produce or store electrical energy in DC form require a power inverter to exchange energy with an AC utility system.
  • a power inverter could include a power electronic AC-DC rectifier and /or DC- AC inverter coupled between the AC utility system and the energy storage device such as that described in Serial No. 07/986,798 cross-referenced above, which is a pulse-width-modulated (PWM) voltage-fed inverter that can transfer power bidirectionally.
  • PWM pulse-width-modulated
  • PWM power inverters include low harmonic distortion of output current, controllable line power factor, and the capability to operate satisfactorily over a wide range of utility source impedances.
  • the voltage on the DC side of the inverter must be greater than the peak-to-peak line-to-neutral voltage on the AC side of the inverter.
  • the present invention allows a DC-AC inverter to be used with a DC device having a lower voltage than that required by the DC side of the inverter.
  • the power conversion system includes a pulse-width modulated (PWM), voltage-fed inverter coupled to a utility AC source, a two-quadrant DC-DC chopper inverter coupled to the PWM inverter, and a DC device coupled to the DC-DC chopper.
  • PWM pulse-width modulated
  • the power conversion system bidirectionally controls the flow of power through the inverter and the DC-DC chopper. First, a real power flow is selected in direction and amount.
  • the current flow through the DC-DC chopper is controlled by pulse-width modulation techniques to provide the selected current, thereby controlling the real power flow.
  • the DC-AC converter is controlled by an inverter control unit, responsive to a sensed voltage on its DC side to maintain a predetermined voltage on said DC side.
  • the inverter control unit includes a DC bus voltage regulator that controls the DC voltage Vi on the DC side of the inverter by regulating the instantaneous current flow with pulse width modulation techniques to import or export power from the utility grid in an amount necessary to maintain a predetermined optimal voltage Vi*.
  • the inverter control unit also includes a reactive power controller to control reactive power flow between the inverter and the utility grid. Real power flow through the inverter is only controlled indirectly by controlling the real power flow through the DC-DC chopper to the DC device.
  • the DC-DC chopper includes a pair of transistors that are operated in complementary fashion with the appropriate duty cycle to provide an operator-specified DC current through a filter inductor and through the DC device in direction and amount.
  • a DC control unit controls real power by controlling the DC current flow through the DC- DC chopper to the DC device.
  • the DC bus voltage regulator controls the DC side of the DC-AC inverter at its optimal level and as a result, an AC output voltage may then be provided even with a relatively low DC voltage at the DC device because the DC voltage of the DC device is decoupled by the DC-DC chopper from the AC output voltage of the voltage-fed inverter.
  • the DC control unit uses the DC-DC chopper to control current flow with the DC device. For example, if a battery is used on the DC side, the DC-DC chopper is used to control the current flow to and from the battery, and the DC- AC inverter is unaffected by the state of charge of the battery, as long as a minimal voltage is provided.
  • the DC- AC inverter will be operable even at low DC voltages.
  • the inverter is useful for a DC electrical energy apparatus for an electrical grid, as well as for any other DC-AC coupler that has a high AC voltage relative to the DC device.
  • the maximum line-to-line RMS AC voltage required to produce sinusoidal current waveforms on the AC side of the inverter is [(V3 x Vj) + 2 ⁇ /2 ].
  • the maximum line-to-line RMS AC voltage required on the utility side to produce sinusoidal current waveforms on the AC side of the inverter to the utility is known to be [ (V3 x V Battery ) + 2 ⁇ /2 ]. Therefore, with the DC-DC chopper, the DC inverter voltage Vi is substituted for the battery voltage VDC an d sinusoidal current can be produced even though the battery voltage is lower than would otherwise be required.
  • the power flow control unit can operate the inverter to supply reactive power to the grid for compensation of reactive power loads.
  • the power flow control waveform may be shaped to provide a specific reactive power, either as a specific number of VARs (Volt- Ampere Reactive units), or as a power factor angle which defines the relation between the real and reactive power supplied to the grid.
  • VARs Volt- Ampere Reactive units
  • the reactive power supplied by the inverter helps the grid to compensate for the reactive loads commonly placed on the grid by consumers of electricity.
  • Fig. 1 is a block diagram illustrating a DC electrical energy apparatus including a DC device, a four-phase inverter, a utility grid, power generating facilities, and electrical power users.
  • Fig. 2 is a block diagram of a DC electrical energy apparatus including a two-quadrant DC-DC chopper.
  • Fig. 3 is a schematic diagram of a preferred embodiment of the DC electrical energy apparatus including a two-quadrant DC-DC chopper.
  • Fig. 4 is a flow chart illustrating formation of a power flow control waveform within the power flow control unit.
  • Fig. 5 is a diagrammatic illustration of a preferred embodiment of a power flow waveform generator.
  • Fig. 6 is a flow chart illustrating operation of a charge controller for the real power controller.
  • Fig. 7 is a block diagram of a real power controller that provides the DC device current control waveform for the chopper.
  • Fig. 8 is a block diagram of a delta modulator current controller for controlling inverter currents in accordance with the power flow control waveform.
  • Fig. 9 is a block diagram illustrating an inverter having its DC side coupled to a DC bus that is coupled to a first DC-DC chopper and a first DC device such as a battery, and also coupled to a second DC-DC chopper and a second DC device such as a photovoltaic cell.
  • FIGs. 1 through 9 of the drawings disclose various embodiments of the present invention for purposes of illustration only.
  • One skilled in the art will readily recognize alternative embodiments of the structures and methods illustrated herein that may be employed without departing from the principles of the invention.
  • Fig. 1 is a block diagram illustrating a DC electrical energy device 10 connected to an AC electric power grid 12.
  • the AC electric power grid 12 includes transmission lines and other electrical transmission circuits commonly provided by electrical utilities.
  • Power for the AC electric power grid 12 is supplied by power generating facilities 14, which may include any of a number of conventional generating facilities, for example coal-fired plants, nuclear plants, and hydroelectric plants.
  • the AC electric power grid 12 provides power to electrical power users 16.
  • the power users 16 include any of a wide range of consumers of electricity, for example a household or a large factory.
  • a four-phase inverter comprising a three-phase voltage fed inverter 20 and a two-quadrant DC-DC chopper 21 are coupled between the AC electric power grid 12 and a DC device 22.
  • the DC device 22 may comprise any DC device that stores or produces DC electrical energy.
  • the DC device 22 may comprise a battery that stores DC electrical energy at selected times and releases energy back at other times, in a manner as will be described.
  • the DC device 22 may comprise a DC energy generating device such as a photovoltaic cell array.
  • a DC control unit 23 is coupled to the DC-DC chopper 21 and the DC device 22 to control real power flow, as will be described.
  • the three-phase voltage-fed inverter 20 includes circuits for converting electrical energy from AC to DC, or from DC to AC (i.e., the inverter 20 is bidirectional).
  • An inverter control unit 24 controls the inverter 20 to control the flow of power therethrough.
  • the inverter control unit 24 receives inputs from sensors coupled to the AC electric power grid 12, including the voltage on the grid 12 and the instantaneous current flow between the inverter 20 and the grid 12.
  • the inverter control unit 24 also receives a voltage Vi on its DC side. Responsive thereto, the inverter control unit 24 controls the flow of power through the inverter 20. Furthermore, the inverter control unit 24 can control the inverter 20 to supply reactive power to the electric power grid 12.
  • Real power flow through the inverter 20 is bidirectional: the real power flow can be in either direction, including a charge direction from the AC electric power grid 12 to the DC device 22, or a discharge direction from the DC device 22 to the AC electric power grid 12.
  • the charge direction electrical energy on the AC electric power grid 12 will be stored in the DC device 22 which could occur when the power supplied by the generating facilities 14 exceeds the needs of the power users 16.
  • energy from the DC device 22 supplies power to the AC electrical power grid 12.
  • the discharge direction would be selected when the power needs of the AC electric power grid 12 exceed the supplies available from the power generating facilities 14, or if it is simply more economical to provide energy from the DC device 22 instead of the power generating facilities 14.
  • the AC electric power grid 12 may supply 3-phase power at 480 volts rms, which is typical of the utilities in the United States. However any other polyphase power supply or power grid may utilize the DC electrical energy apparatus 10.
  • the inverter 20 includes inverter inverter switching circuits 26, described in more detail with reference to Fig. 3.
  • the inverter switching circuits 26 are driven by conventional inverter drive circuits 28 selected to satisfy the requirements of the inverter switching circuits 26.
  • the inverter drive circuits 28 are controlled by current regulators 30 illustrated in the inverter control unit 24.
  • the current regulators 30 are described in more detail with reference to Fig. 9.
  • the inverter control unit 24 also includes a power flow waveform generator 32 described in further detail below, for example with reference to Figs. 3, 4, 5, 6, and 7.
  • the two quadrant DC-DC chopper 21 includes circuits described in more detail with reference to Fig. 3 that control DC current flow between the DC device 22 and the DC side of the inverter 20.
  • the chopper 21 includes chopper switching circuits 25 driven by conventional chopper drive circuits 27 selected to satisfy the requirements of the chopper switching circuits 25.
  • the chopper drive circuits 27 are controlled by chopper current regulators 29, which are described in more detail with reference to Fig. 9.
  • the DC device 22 is coupled between a +DC rail 33 and a -DC rail 34.
  • a voltage sensor 35 is coupled to sense the voltage VDC across the +DC rail 33 and the -DC rail 34.
  • the sensed voltage VDC typically varies with the charge stored in the DC device 22, and is useful to control storage of electrical energy.
  • An additional voltage sensor 36 is coupled to sense a inverter voltage Vj across a +rail 37 and a -rail 38 of the DC bus between the inverter switching circuits 26 of the inverter 20 and the DC-DC chopper inverter 21.
  • a current sensor 39 is coupled to measure a DC current flow IDC in direction and amount through the two-quadrant DC-DC chopper 21. The current IDC is useful for controlling the real power flow through the chopper 21, as will be described in more detail with reference to Figs. 5, 6, and 7.
  • a DC control unit 41 is coupled to the chopper current regulators to control the DC current between the DC device 22 and the inverter 20.
  • the inverter control unit 24 includes a DC bus voltage regulator 40 and a reactive power controller 42 described in more detail with reference to Figs. 5, 6, and 7 coupled to the power flow waveform generator 32 to control the direction and amount of power flow through the inverter 20.
  • the DC bus regulator 40 controls the DC bus voltage Vi by importing or exporting real power from the utility grid 12 in the amount necessary to maintain a constant DC bus voltage Vj.
  • the inverter control unit 24 also includes a reactive power controller 42 coupled to the power flow waveform generator 32 to supply a selected reactive power flow between the inverter 20 and the utility grid 12. The amount of reactive power flow is selected responsive to a reactive power measurement sensed by conventional reactive power sensing equipment 43 coupled to the utility grid 12.
  • the reactive power controller 42 is described in more detail below with reference to Fig. 5.
  • the voltage on each line of the utility grid 12 is sensed by grid voltage sensors 44, for example by voltage transformers, and supplied to the power flow waveform generator 32 as a voltage (reference) waveform. Additionally, current sensors 46 sense the instantaneous current flowing on each of the phase lines coupled between the inverter 20 and the utility grid 12. The instantaneous current amounts are supplied to the current regulators 30 to aid in controlling the current flow through each of the phase lines.
  • the DC-DC chopper 21 includes a first DC switch 47 and a filter inductor 48 coupled in series on the +rail 37 between the inverter 20 and the DC device 22.
  • the first DC switch 47 is coupled to one of the inverter drive circuits 28, to control its switching.
  • the inverter drive circuits 28 are in turn controlled by the power flow waveform generator 32.
  • the DC-DC chopper 21 also includes a second DC switch 49 coupled to a node 51 defined between the first DC switch 47 an the filter inductor 48. Specifically, the second DC switch 49 is coupled between the node 51 and the -DC rail 34.
  • the second switch 49 is driven by chopper inverter drive circuits 27, which is in turn controlled by the DC control unit 23.
  • the first DC switch 47 and the second DC switch 49 operate together as a pair. Specifically, these DC switches 47 and 49 are operated in complimentary fashion, i.e., only one of the DC switches will be open at any arbitrary point in time during operation.
  • the filter inductor 48 removes unwanted ripple current inherently by high speed modulation of switches 47 and 49. It should be noted that the filter inductor depicted is merely representative of a filter in general (a single inductor would be the simplest form of filter). Alternative embodiments of the filter could include a combination of several passive elements, for example.
  • the inverter 20 includes the inverter switching circuits 26 for a three-phase AC power supply.
  • the inverter inverter switching circuits 26 include three switch pairs, including a phase A switch pair 50a, a phase B switch pair 50b, and a phase C switch pair 50c.
  • Each switch pair 50a, 50b, 50c includes respectively an upper switch 52a, 52b, 52c, positioned between the +DC rail 37 and its respective phase line, and a lower switch 54a, 54b, 54c, connected between the -DC rail 38 and its respective phase line.
  • the AC switches 52, 54 are operated in complementary fashion; i.e., only one of the switches in a pair will be open at a point in time during operation of the switching circuit 26.
  • the AC switches 52 and 54 of the inverter 20 and the DC switches 47, 49 of the DC-DC chopper 21 may include any of a number of different types of active switches, including insulated gate bipolar transistors (IGBT's), bipolar junction transistors (BJT's), field effect transistors (FET's), or Darlington transistors.
  • IGBT's insulated gate bipolar transistors
  • BJT's bipolar junction transistors
  • FET's field effect transistors
  • Darlington transistors insulated gate bipolar transistors
  • Each switch 47, 49, 52, and 54 may include only a single transistor, or may include multiple transistors connected in parallel.
  • a freewheeling diode is connected in an inverse parallel relationship with each transistor.
  • the switches 47, 49, 52, and 54 are preferably IGBT's.
  • Each switch pair 50 is driven by the current regulators 30 and the conventional inverter drive circuits 28 using a power flow waveform for each phase.
  • a conventional filter 56 is provided to smooth the output of the inverter 20, which reduces the high frequency components inherent in high speed switching. Specifically, the filter 56 removes unwanted harmonic content introduced by high speed modulation of the switch pairs 50a, 50b, 50c.
  • the filter 56 may include reactors and capacitors and, preferably the inductance of the reactors is as large as possible. However, practical concerns such as cost and size usually limit the actual inductance in any installation.
  • the power flow waveform generator 32 generates AC control waveforms 59a-c, one for each AC phase of the output power.
  • the inputs to the power flow waveform generator 32 include a VAR multiplier Mi from the reactive power controller 42, a DC bus multiplier M 2 from the DC bus voltage regulator 40, a constant K (if appropriate), and the voltage waveform for each of the three AC phases.
  • the voltage on each of the phases is transformed to a low level by grid voltage transformers (shown as 44 in Fig. 2). Specifically, the voltage waveform on phase A is transformed to a reference waveform A, the voltage on phase B is transformed to a reference waveform B, and the voltage on phase C is transformed to a reference waveform C.
  • a control waveform 59 for each phase is generated by the power flow waveform generator 32 in accordance with the algorithms to be described with reference to Figs. 4 and 5 below. Specifically, a Phase A control waveform 59a is generated in the generator 32 and applied through the current regulator 30 and the drive circuit 28 to control the switch pair 50a. Likewise, a Phase B control waveform 59b is generated to control the switch pair 50b, and a Phase C control waveform 59c is generated to control the switch pair 50c.
  • the power flow control waveforms 59 are produced and applied digitally at a rate between 8 KHz and 16 KHz, which means that the sample period for the control waveforms 59 are between 125 and 62.5 microseconds.
  • Fig. 4 is a flowchart of operations within the power flow waveform generator 32 to provide the AC power flow control waveforms 59a-c.
  • the steps in the flowcharts could be implemented with software and a microprocessor. It should be apparent that other hardware or methods may be used to accomplish the steps described therein.
  • Fig. 4 shows only the operations on a single phase. It should be apparent to one skilled in the art that the operations in Fig. 4 occur in parallel for each phase of the output.
  • a box 60 a reference waveform is obtained. After the reference waveform has been obtained, as in the box 60, it is applied to form an imaginary waveform as illustrated in a box 62.
  • the imaginary waveform may be obtained by rotating the reference waveform by 90°.
  • the imaginary waveform is then multiplied, as illustrated in a box 64, by a multiplier Mi which is calculated in a manner to be described with reference to Fig. 5.
  • the multiplied imaginary waveform is then added in a box 66.
  • the reference waveform is applied to form the real waveform illustrated in a box 68.
  • the real waveform may be substantially similar to the reference waveform.
  • the real waveform is applied to a box 70, in which it is multiplied by a real multiplier M2 supplied from the DC bus regulation PI controller 40 discussed in detail below with reference to Figs. 5, 6, and 7.
  • the multiplied real waveform is then added to the multiplied imaginary waveform to obtain a power flow control waveform 59a-c to control the power flow through the inverter 20.
  • the reference current is obtained either directly from an operator interface, or by dividing a power-level input from the operator interface by the sensed battery voltage.
  • the switching circuit is controlled to provide a current through the DC device 22 that produces the desired power flow.
  • Fig. 5 is a more detailed illustration of the power flow waveform generator 32.
  • the 3-phase AC reference waveform is applied to a 3- to 2-phase converter 80.
  • the 3- to 2-phase converter 80 converts the 3 phases of the reference waveform to 2 phases in accordance with the following matrix equation: A 2 1 cos(2 ⁇ / 3) cos(4 ⁇ / 3) ' A B 2 0 sin(2 ⁇ / 3) sin(4 ⁇ / 3) B (1) 0 1 1 1 C
  • a 2 , B 2 are the 2-phase reference quantities and A, B, and C are the 3-phase reference quantities.
  • the outputs of the 3- to 2-phase converter 80 i.e., the two 2-phase reference waveforms, are provided to two separate processing lines, one that produces and processes an imaginary waveform and another one that produces and processes a real waveform.
  • the 2-phase reference waveform is applied to a box 82 in which each phase is multiplied by e* .
  • the 2-phase reference waveform is applied to a box 84 in which each phase is multiplied by eJ°° (or 1).
  • a box 84 a 2-phase real waveform
  • a 2- to 3-phase converter 88 to output a 3-phase real waveform.
  • the reference waveform illustrated as an input into the box 80 may be used to form the real waveform at the output of the box 88 without the need for 3- to 2-phase conversion and 2- to 3-phase conversion.
  • Each phase of the 3-phase imaginary waveform is then multiplied by a VAR multiplier Mi selected by the reactive power controller 42.
  • the VAR multiplier Mi has the same value for each phase.
  • the VAR multiplier Mi can be manually selected by an operator who observes the number of VARs at the output and compares them with the VARs desired by the grid 12. He then adjusts the multiplier Mi to produce the desired number of VARs. If the utility requires more VARs than the hardware in the line-side inverter 20 can produce, then the VAR multiplier Mi is limited to a maximum value, at which point it will supply all the VARs that it can. The maximum value is usually determined by the safe current carrying capability of the circuits in the line-side inverter 20. The maximum value may be implemented in software so that the multiplier Mi cannot exceed that value.
  • the VAR multiplier Mi can also be selected automatically by a hierarchical control loop such as a voltage regulator that can be operator controlled to provide a fixed terminal voltage VARs.
  • An error signal may be used in the control loop, to minimize the error between the measured voltage and the desired voltage.
  • a value K is selected to specify a predetermined power factor angle. Then, the value K is multiplied by M 2 , as illustrated in a box 87. This product is applied to the reactive power controller 42.
  • the imaginary multiplier Mi is proportional to the DC bus multiplier M2 supplied from the DC bus voltage regulator 40 described in detail below.
  • the DC bus voltage regulator 40 controls the DC bus voltage Vi by importing or exporting power from the utility grid in the amount necessary to maintain a constant predetermined voltage Vi*.
  • the DC bus voltage regulator 40 receives the actual inverter voltage Vi sensed by the voltage sensor 36 (Fig. 2) and the predetermined voltage Vi*.
  • the desired inverter voltage Vi* is a parameter predetermined by output requirements and device limitations.
  • the desired inverter voltage Vi* is selected to be above the maximum peak-to-peak voltage of the utility grid, but below the maximum voltage rating of the switching devices in the inverter.
  • one predetermined value for Vi* is 750 volts, which is above the 675 peak-to-peak AC voltage of a 480 volt (rms) utility source, but lower than the maximum voltage rating of commercially-available switching devices such as a 1400V insulated gate bipolar transistor (IGBT).
  • IGBT insulated gate bipolar transistor
  • the DC bus voltage regulator 40 supplies a DC bus multiplier M 2 having a value that maintains the DC side at the predetermined constant voltage Vi*.
  • the DC bus voltage regulator 40 includes a differencing unit 89 and a proportional plus integral controller 90.
  • the differencing unit 89 the desired inverter voltage Vi* is differenced with the actual inverter voltage Vi obtained from the voltage sensor 39. The resulting difference is applied to the proportional plus integral controller 90, whose output supplies the DC bus multiplier M2.
  • the DC bus multiplier M2 is applied to each of the three phase real waveforms from the 2-to-3 phase converter 88 to provide a multiplied real waveform for each phase. Then, the multiplied real waveform for each phase is added respectively to the corresponding phase of the multiplied imaginary waveforms from the upper arm of Fig. 5. The result of this addition operation is the control waveforms 59a, 59b, and 59c. Specifically, the multiplied real waveform for phase A is added to the multiplied imaginary waveform for phase A in order to obtain the control waveform 59a for phase A. Similarly for phase B and phase C, the multiplied real waveform is added to the multiplied imaginary waveform to yield a control waveform 59b and 59c. The control waveforms 59a, 59b, 59c are then applied to the current regulators 30 shown in Figs. 2 and 3, which control the inverter switching circuits 26 through the inverter drive circuits 28.
  • the DC control unit 41 includes a DC current controller 91 that controls the real power flow by controlling the DC current to and from the DC device 22 with a current control value M 3 .
  • a DC current controller 91 that controls the real power flow by controlling the DC current to and from the DC device 22 with a current control value M 3 .
  • One embodiment of the DC control unit 41 will be described with reference to Fig. 7.
  • the DC control unit 41 can be implemented digitally, utilizing a microprocessor to receive inputs, perform calculations, and output a result.
  • Fig. 7 is a block diagram of the DC control unit 41.
  • the DC current controller 91 receives an input from an operator interface 94, which receives input information from an operator who specifies a desired real power flow in any convenient measure such as watts.
  • the desired real power flow is converted in real time to a command current Idesire d that controls the current flow through the two-quadrant DC-DC chopper 21.
  • the sensed voltage across the DC device 72, VDO is used together with the desired real power to specify a desired current by the following relation:
  • the conversion unit 95 calculates the desired current from the relationship of Equation (3).
  • the operator could directly provide Idesired- W the operator input is in terms of desired current, then the conversion unit 95 simply passes this input on to the current controller 91. It will be apparent to one skilled in the art that control of DC current to and from the DC device 22 is equivalent to control of real power through the inverter 20.
  • the DC current controller 91 is designed to provide a current control value M 3 at its output that will produce the command current Idesired to or from the DC device 22.
  • the value for the command current I d esire d is passed directly through the DC current controller 91.
  • a charge /discharge controller 92 receives the current control value M 3 . Additional inputs into the charge /discharge controller include VDO (the voltage sensed across the DC device 22) and predetermined values for a high voltage VH and a low voltage VL- These predetermined values specify an operating range for the DC device 22.
  • VDO the voltage sensed across the DC device 22
  • VL the voltage voltage of the DC device 22
  • VH and VL are highly dependent upon the particular DC device 22 in a particular application.
  • the value V for instance, could be a voltage that determines when the DC device 22 is fully discharged so that it can no longer supply power.
  • the maximum voltage, VH is the voltage indicating that the DC device 22 is fully charged.
  • VH could be used for determining when to stop charging the DC device 22.
  • VDO me charge controller 92 adjusts the real power multiplier M 3 . For example, when a fully charged state is reached, the charge controller 92 can set M 3 to zero. Operation of one embodiment of the charge controller 92 is described further with reference to Fig. 6.
  • Fig. 6 illustrates one method of implementing the charge controller 92.
  • an operator inputs the mode and amount of either the DC current or the real power flow.
  • the amount of real power flow may be specified by the operator in watts, and then converted to the command current Ide s ired n a box 95 (Fig. 7) by dividing it by VDC
  • the mode is specified by a "positive" or "negative" designation.
  • a decision is made, dependent upon three conditions: whether the idle mode has been selected as illustrated in a decision 96, whether the charge mode has been selected as illustrated in a decision 98, or whether a discharge mode has been selected as illustrated in a decision 100. If the idle mode has been chosen, then, from the box 96, the operation moves to a decision 102 which continues the idle loop until the mode has changed to either a charge mode or a discharge mode.
  • operation exits from the box 98 into a charge loop.
  • the charge on the DC device 22 is measured, and a decision 104 is made based upon the charge of the DC device 22. If the DC device 22 is fully charged, then operation returns to the input box 94 to wait for another operator input. However if the DC device 22 is not fully charged then operation moves to an operation box 106 which supplies the desired current to charge the DC device 22.
  • a decision 108 allows the operator to exit the charge loop. Until the mode changes, operation loops through the charge loop including the charge decision 104, the operation box 106, and the mode decision 108. If the mode changes, then operation returns to the operator input box 94.
  • a supply mode may be chosen to supply energy to the utility grid 12. If the supply mode is chosen, then the supply loop is entered. The charge on the DC device 22 is monitored, and if the DC device 22 is fully discharged, then it can of course supply no further energy and operation returns to the input box 94. However if energy is available (i.e., if the DC device 22 has energy to be supplied) then operation moves to the box 112 in which the desired current is supplied to the utility grid 12. Next, as illustrated in the decision 114, when the mode changes then operation returns to the input 94. As long as the mode does not change then the supply loop continues to supply the desired current to the utility grid.
  • Fig. 6 illustrates only one embodiment of a charge controller 92. It will be apparent to one skilled in the art that other implementations of the charge controller may be developed to control charging the battery. For example, instead of allowing the full specified real power flow, another charge controller may increase or decrease the actual real power flow dependent upon V sen se d - It iH also be apparent to one skilled in the art that the controller may be adapted to DC sources of energy such as photovoltaic cells and fuel cells by eliminating the charge mode.
  • Fig. 8 is a delta modulator current regulator 118 that applies the 3-phase AC line currents i ., i ⁇ . ic specified by the control waveforms 59a, 59b, 59c and the DC current _ > •
  • the delta modulator current regulator 118 periodically compares each desired line current _A, i ⁇ , -c or DC device current io with the corresponding actual line current i A , i ⁇ , ic, and DC device current ioo sensed by the respective current sensors 120a, 120b, 120c, and 39 (Fig. 3).
  • the current sensors 120a-c are positioned to sense the line currents from each of the switch pairs 50a- c.
  • the current sensor 39 is positioned to sensor the current through the DC device 22.
  • a current comparison is accomplished using a compare device 122 for each of the lines.
  • current comparisons are performed at a rate between 8 and 16 KHz, which is equivalent to a sample period between 125 and 62.5 microseconds.
  • the respective upper switching device 52 or 47 is switched on and the lower switching device 54 or 49 switched off, otherwise, the upper device 52 or 47 is switched off and the lower device 54 or 49 is switched on.
  • the compare devices 122 provide PWM (Pulse Width
  • the inverter drive circuits 28 preferably include conventional transistors and additional circuitry necessary to drive the gates of the respective switches 47, 52, 49, and 54, which are IGBT's in the preferred embodiment, in response to the on or off signal specified by the PWM commutation signals. For each sample period, a switch state is specified by the PWM commutation signals. The switch state so selected remains in effect until the next sample period, at which time the comparisons are repeated with updated actual and desired values. In alternate embodiments, other conventional PWM methods can be used.
  • Fig. 9 is a block diagram illustrating two separate DC devices coupled to a common DC bus 200.
  • the common DC bus is coupled on the DC side to the inverter 20 and the AC electric power grid illustrated and discussed with reference to Fig. 1, for example.
  • the DC bus 200 is coupled to a battery 206 by a two quadrant DC-DC chopper 21a.
  • the DC bus 200 is also coupled to photovoltaic or fuel cells 210 through the two quadrant DC-DC chopper 21b.
  • the photovoltaic or fuel cells 210 may comprise any of a plurality of DC generating cells.
  • the two quadrant DC-DC choppers 21a-b are constructed and controlled in the matter described elsewhere, and the DC bus 200 may comprise a capacitor for short term energy storage across the bus.
  • any of a plurality of other DC devices could also be coupled to the DC bus 200.
  • additional batteries may be coupled to the DC bus 200 by an additional two quadrant DC-DC chopper.
  • the effect of the two quadrant DC-DC choppers is to isolate the DC bus 200 from the particular DC device, thereby allowing any of a plurality of DC devices with different output voltage characteristics to be coupled to the DC bus 200.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Automation & Control Theory (AREA)
  • Inverter Devices (AREA)

Abstract

Un convertisseur bidirectionnel (c.-à-d., redresseur et onduleur) permet de transférer une énergie électrique entre un réseau secteur (12) en courant alternatif haute tension et un dispositif de stockage/alimentation d'énergie en courant continu (22) (telle qu'une batterie ou une série de piles photovoltaïques ou électrochimiques). Le convertisseur comprend un circuit inverseur (20) à modulation d'impulsions en largeur couplé au secteur (12), et un découpeur continu-continu (21) couplé entre le circuit inverseur (20) à modulation d'impulsions en largeur et un dispositif de stockage/alimentation d'énergie en courant continu (22). Le circuit inverseur (20) à modulation d'impulsions en largeur comprend un circuit de commutation (26) à commutateurs électriques rapides montés par paires, ces paires étant couplées entre le bus d'alimentation en courant alternatif du réseau et le bus d'alimentation du découpeur continu-continu. Une unité de commande (24) du circuit inverseur comprend un régulateur (40) d'alimentation en courant continu du bus qui régule la tension du côté courant continu du circuit inverseur (20) à modulation d'impulsions en largeur, et un régulateur (42) de puissance de réaction. Une unité de commande (23) de courant continu comprend un régulateur (41) de puissance réelle qui contrôle le débit de puissance réelle en régulant le flux de courant du dispositif de stockage/alimentation d'énergie en courant continu (22). En fonction de la modulation des commutateurs à courant continu (25) du découpeur continu-continu (21), le courant continu se dirigeant vers le dispositif de stockage/alimentation d'énergie en courant continu (22) est régulé de façon à obtenir un débit désiré de puissance réelle dans le découpeur continu-continu (21), indépendamment de la tension (VDC) du dispositif de stockage/alimentation d'énergie en courant continu (22).
PCT/US1995/014505 1994-12-14 1995-11-09 Convertisseur bidirectionnel raccorde au secteur comprenant un decoupeur continu/continu a modulation d'impulsions en largeur et dispositif de stockage/alimentation d'energie WO1996018937A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AU41493/96A AU4149396A (en) 1994-12-14 1995-11-09 Grid connected bi-directional converter including a pwm, dc-dc chopper, and energy storage/supply device

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
US35644994A 1994-12-14 1994-12-14
US08/356,449 1994-12-14

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Cited By (34)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0940858A2 (fr) * 1998-03-03 1999-09-08 Canon Kabushiki Kaisha Système photovoltaique de génération d'énergie
EP0973248A2 (fr) * 1998-07-14 2000-01-19 ABB Ricerca SpA Méthode de commande pour un onduleur à fréquence fixe
WO2002011267A2 (fr) 2000-07-28 2002-02-07 International Power Systems, Inc. Convertisseur cc/cc et systeme de gestion de puissance
DE10127599A1 (de) * 2001-05-31 2002-12-12 Deutsch Zentr Luft & Raumfahrt Brennstoffzellensystem und Verfahren zur Inbetriebnahme/Außerbetriebnahme eines Brennstoffzellensystems
US6566764B2 (en) 2000-05-23 2003-05-20 Vestas Wind Systems A/S, R&D Variable speed wind turbine having a matrix converter
US6812587B2 (en) 2001-02-05 2004-11-02 Capstone Turbine Corporation Continuous power supply with back-up generation
US6856040B2 (en) 2002-02-11 2005-02-15 Vestas Wind Systems A/S Variable speed wind turbine having a passive grid side rectifier with scalar power control and dependent pitch control
WO2005036684A2 (fr) * 2003-10-10 2005-04-21 Nuvera Fuel Cells, Inc. Electronique d'alimentation pour systeme d'alimentation a piles a combustible
WO2005046019A1 (fr) * 2003-11-07 2005-05-19 Responsiveload Limited Sous-station de reseau de distribution d'electricite optimisee
US7105941B2 (en) * 2000-08-17 2006-09-12 Hongsun Hua Framework composition windmill
WO2006125410A1 (fr) * 2005-05-20 2006-11-30 Sma Technologie Ag Onduleur de batterie bidirectionnel
EP1748542A1 (fr) * 2005-07-29 2007-01-31 Siemens Aktiengesellschaft Procédé de commande pour un système de pile à combustible et système de pile à combustible
CN100379113C (zh) * 2003-09-11 2008-04-02 上海交通大学 同时实现并网发电和电网无功功率补偿的一体化方法
WO2009033506A1 (fr) * 2007-09-14 2009-03-19 Abb Technology Ag Système statcom destiné à fournir une énergie réactive et/ou active à un réseau d'alimentation électrique
FR2941824A1 (fr) * 2009-01-30 2010-08-06 Jacques Rene Claude Froidefond Procede d'alimentation d'un groupe de lampes utilisant les energies renouvelables ou le reseau 50 hz
EP2294494A1 (fr) * 2008-06-13 2011-03-16 Ceramic Fuel Cells Limited Système et procédé de stabilisation de pile à combustible
WO2011060823A1 (fr) * 2009-11-19 2011-05-26 Siemens Aktiengesellschaft Convertisseur et sous-module d'un convertisseur destiné à charger ou décharger un réservoir d'énergie
US7952232B2 (en) 2008-03-13 2011-05-31 General Electric Company Wind turbine energy storage and frequency control
WO2011077134A3 (fr) * 2009-12-24 2012-03-08 David Gordon Appareil de génération d'énergie électrique
US8253273B2 (en) 2007-07-26 2012-08-28 Utc Power Corporation Power system having AC and DC power sources
EP2506418A3 (fr) * 2011-03-29 2013-01-23 Sony Corporation Inverseur relié à une grille, système et procédé
FR2983365A1 (fr) * 2011-11-25 2013-05-31 Renault Sa Systeme de transfert d'energie electrique
EP2606550A2 (fr) * 2010-08-18 2013-06-26 Volterra Semiconductor Corporation Circuits de commutation pour extraire de l'énergie d'une source d'énergie électrique et procédés associés
WO2013120966A1 (fr) * 2012-02-17 2013-08-22 Alstom Technology Ltd Dispositif de conversion électrique ac/dc autorisant une récupération d'énergie et une gestion des courts-circuits côté continu
CN103368373A (zh) * 2012-03-27 2013-10-23 罗斯蒙特航天公司 使用电压至电流匹配的功率因子校正
US20130307342A1 (en) * 2011-11-07 2013-11-21 Fairchild Semiconductor Corporation Photovoltaic System Power Optimization
WO2014105625A1 (fr) * 2012-12-31 2014-07-03 Elwha Llc Équilibrage de paramètres de réseau électrique à l'aide d'une commande d'énergie distribuée
CN105790302A (zh) * 2016-04-11 2016-07-20 阳光电源股份有限公司 一种级联型光伏并网逆变器及其控制方法和控制装置
US20170133879A1 (en) * 2014-06-23 2017-05-11 Gridbridge, Inc. Versatile site energy router
US20170155253A1 (en) 2014-06-20 2017-06-01 General Electric Company System and method of power control for an energy storage charging station
ES2734585A1 (es) * 2019-10-31 2019-12-10 Real Energy Systems S L U Sistema de gestión de carga o limitación de potencia en instalaciones fotovoltaicas.
CN110855158A (zh) * 2018-08-20 2020-02-28 中车株洲电力机车研究所有限公司 变流器模块及变流器
US10707789B2 (en) 2017-05-12 2020-07-07 General Electric Company Adaptive current damping module for improved power converter control in wind turbine systems
EP2856598B1 (fr) * 2012-06-01 2023-07-19 The University of Hong Kong Convertisseurs de puissance bidirectionnels avec commande de tension alternative d'entrée

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5001619A (en) * 1987-12-07 1991-03-19 Kabushiki Kaisha Toshiba Harmonics suppression control circuit for a PWM inverter
US5187427A (en) * 1991-11-27 1993-02-16 U.S. Windpower, Inc. Static reactive power compensator
US5291388A (en) * 1992-04-16 1994-03-01 Westinghouse Electric Corp. Reconfigurable inverter apparatus for battery-powered vehicle drive
US5329222A (en) * 1992-11-30 1994-07-12 Westinghouse Electric Corporation Apparatus and method for dynamic voltage restoration of utility distribution networks
US5436540A (en) * 1994-05-16 1995-07-25 General Electric Company Protection circuit for a gate turn-off device in an electrical braking system for an electric traction motor vehicle

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5001619A (en) * 1987-12-07 1991-03-19 Kabushiki Kaisha Toshiba Harmonics suppression control circuit for a PWM inverter
US5187427A (en) * 1991-11-27 1993-02-16 U.S. Windpower, Inc. Static reactive power compensator
US5291388A (en) * 1992-04-16 1994-03-01 Westinghouse Electric Corp. Reconfigurable inverter apparatus for battery-powered vehicle drive
US5329222A (en) * 1992-11-30 1994-07-12 Westinghouse Electric Corporation Apparatus and method for dynamic voltage restoration of utility distribution networks
US5436540A (en) * 1994-05-16 1995-07-25 General Electric Company Protection circuit for a gate turn-off device in an electrical braking system for an electric traction motor vehicle

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* Cited by examiner, † Cited by third party
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EP0940858A2 (fr) * 1998-03-03 1999-09-08 Canon Kabushiki Kaisha Système photovoltaique de génération d'énergie
JPH11251615A (ja) * 1998-03-03 1999-09-17 Canon Inc 融雪機能付き太陽光発電システム
EP0940858A3 (fr) * 1998-03-03 2002-01-09 Canon Kabushiki Kaisha Système photovoltaique de génération d'énergie
EP0973248A2 (fr) * 1998-07-14 2000-01-19 ABB Ricerca SpA Méthode de commande pour un onduleur à fréquence fixe
EP0973248A3 (fr) * 1998-07-14 2000-04-19 ABB Ricerca SpA Méthode de commande pour un onduleur à fréquence fixe
US6856038B2 (en) 2000-05-23 2005-02-15 Vestas Wind Systems A/S Variable speed wind turbine having a matrix converter
US6566764B2 (en) 2000-05-23 2003-05-20 Vestas Wind Systems A/S, R&D Variable speed wind turbine having a matrix converter
WO2002011267A2 (fr) 2000-07-28 2002-02-07 International Power Systems, Inc. Convertisseur cc/cc et systeme de gestion de puissance
EP1433239B1 (fr) * 2000-07-28 2016-03-30 International Power Systems,Inc. Convertisseur cc/cc et système de gestion de puissance
US7105941B2 (en) * 2000-08-17 2006-09-12 Hongsun Hua Framework composition windmill
US6812587B2 (en) 2001-02-05 2004-11-02 Capstone Turbine Corporation Continuous power supply with back-up generation
DE10127599C2 (de) * 2001-05-31 2003-04-24 Deutsch Zentr Luft & Raumfahrt Brennstoffzellensystem und Verfahren zur Inbetriebnahme/Außerbetriebnahme eines Brennstoffzellensystems
DE10127599A1 (de) * 2001-05-31 2002-12-12 Deutsch Zentr Luft & Raumfahrt Brennstoffzellensystem und Verfahren zur Inbetriebnahme/Außerbetriebnahme eines Brennstoffzellensystems
US7015595B2 (en) 2002-02-11 2006-03-21 Vestas Wind Systems A/S Variable speed wind turbine having a passive grid side rectifier with scalar power control and dependent pitch control
US6933625B2 (en) 2002-02-11 2005-08-23 Vestas Wind Systems A/S Variable speed wind turbine having a passive grid side rectifier with scalar power control and dependent pitch control
US6856040B2 (en) 2002-02-11 2005-02-15 Vestas Wind Systems A/S Variable speed wind turbine having a passive grid side rectifier with scalar power control and dependent pitch control
CN100379113C (zh) * 2003-09-11 2008-04-02 上海交通大学 同时实现并网发电和电网无功功率补偿的一体化方法
WO2005036684A2 (fr) * 2003-10-10 2005-04-21 Nuvera Fuel Cells, Inc. Electronique d'alimentation pour systeme d'alimentation a piles a combustible
WO2005036684A3 (fr) * 2003-10-10 2005-06-30 Nuvera Fuel Cells Inc Electronique d'alimentation pour systeme d'alimentation a piles a combustible
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US7652394B2 (en) 2003-11-07 2010-01-26 Responsiveload Limited Responsive electricity grid substation
WO2005046019A1 (fr) * 2003-11-07 2005-05-19 Responsiveload Limited Sous-station de reseau de distribution d'electricite optimisee
WO2006125410A1 (fr) * 2005-05-20 2006-11-30 Sma Technologie Ag Onduleur de batterie bidirectionnel
AU2006251711B2 (en) * 2005-05-20 2009-12-24 Sma Solar Technology Ag Bi-directional battery power inverter
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USRE45069E1 (en) 2005-05-20 2014-08-12 Sma Solar Technology Ag Bidirectional battery power inverter
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US8253273B2 (en) 2007-07-26 2012-08-28 Utc Power Corporation Power system having AC and DC power sources
WO2009033506A1 (fr) * 2007-09-14 2009-03-19 Abb Technology Ag Système statcom destiné à fournir une énergie réactive et/ou active à un réseau d'alimentation électrique
CN101803139A (zh) * 2007-09-14 2010-08-11 Abb技术有限公司 用于向电力网提供无功和/或有功功率的statcom***
US8154896B2 (en) 2007-09-14 2012-04-10 Abb Technology Ag STATCOM system for providing reactive and/or active power to a power network
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US9515569B2 (en) 2012-02-17 2016-12-06 Alstom Technology Ltd. AC/DC electrical conversion device permitting energy recovery and management of DC-side short-circuits
FR2987181A1 (fr) * 2012-02-17 2013-08-23 Alstom Technology Ltd Dispositif de conversion electrique ac/dc autorisant une recuperation d'energie et une gestion des courts-circuits cote continu
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EP2856598B1 (fr) * 2012-06-01 2023-07-19 The University of Hong Kong Convertisseurs de puissance bidirectionnels avec commande de tension alternative d'entrée
US9819184B2 (en) 2012-12-31 2017-11-14 Elwha Llc Balancing power grid parameters using distributed energy control
WO2014105625A1 (fr) * 2012-12-31 2014-07-03 Elwha Llc Équilibrage de paramètres de réseau électrique à l'aide d'une commande d'énergie distribuée
US20170155253A1 (en) 2014-06-20 2017-06-01 General Electric Company System and method of power control for an energy storage charging station
US10520966B2 (en) 2014-06-20 2019-12-31 General Electric Company System and method of power control for an energy storage charging station
US20170133879A1 (en) * 2014-06-23 2017-05-11 Gridbridge, Inc. Versatile site energy router
US11757304B2 (en) * 2014-06-23 2023-09-12 Gridbridge, Inc. Versatile site energy router
CN105790302A (zh) * 2016-04-11 2016-07-20 阳光电源股份有限公司 一种级联型光伏并网逆变器及其控制方法和控制装置
CN105790302B (zh) * 2016-04-11 2018-02-23 阳光电源股份有限公司 一种级联型光伏并网逆变器及其控制方法和控制装置
CN105790302B9 (zh) * 2016-04-11 2018-08-07 阳光电源股份有限公司 一种级联型光伏并网逆变器及其控制方法和控制装置
US10680550B2 (en) 2016-04-11 2020-06-09 Sungrow Power Supply Co., Ltd. Cascaded photovoltaic grid-connected inverter, control method and control device for the same
US10707789B2 (en) 2017-05-12 2020-07-07 General Electric Company Adaptive current damping module for improved power converter control in wind turbine systems
CN110855158A (zh) * 2018-08-20 2020-02-28 中车株洲电力机车研究所有限公司 变流器模块及变流器
ES2734585A1 (es) * 2019-10-31 2019-12-10 Real Energy Systems S L U Sistema de gestión de carga o limitación de potencia en instalaciones fotovoltaicas.

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