US4031453A - Triggered transistor switching regulator - Google Patents

Triggered transistor switching regulator Download PDF

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Publication number
US4031453A
US4031453A US05/631,736 US63173675A US4031453A US 4031453 A US4031453 A US 4031453A US 63173675 A US63173675 A US 63173675A US 4031453 A US4031453 A US 4031453A
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United States
Prior art keywords
voltage
transistor
resistor
driver stage
diode
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Expired - Lifetime
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US05/631,736
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English (en)
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Dirk Johan Adriaan Teuling
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US Philips Corp
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US Philips Corp
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters

Definitions

  • the invention relates to a switched-mode power supply for converting an input voltage into a substantially constant output D.C. voltage wherein a driver stage supplys a periodic pulse shaped control signal to a switch to render it conducting during a first part of the period and to block it during the remaining, second part of the period, with a control of the duration of said parts of the period, and output electrode of the switch being connected to a terminal of the input voltage source through a self-inductance.
  • This undesired oscillation can be damped by means of a clipping circuit, in which circuit a rectifier conducts only when the voltage across the switch would otherwise rise to a value above its value at the end of the second part of the period. Because the dissipation in the resistor is considerable it must be able to withstand a high permissible power and consequently it is a costly component.
  • a further problem is supplying the driver stage.
  • This stage cannot be supplied by the output voltage as the circuit could not start when first switched on. It is therefore normal practice to choose the input voltage source as a power supply for the driver stage, for which a resistor is also used.
  • the input voltage is not stabilized, the current through the driver stage and consequently also the control current of the switch may vary. If the input voltage varies in the controlled state, then also the conduction time of the switch varies and it appears that the variation of the current through the driver stage may be too large for a proper operation of the circuit and/or exceeds the permissible variation specified by the manufacturer of the transistor. Because the control energy of the switch is considerable, this resistor also must have a high permissible power.
  • the circuit according to the invention is characterized in that an electrode of a rectifier is coupled to said self-inductance while a smoothing capacitor and a supply resistor for the driver stage are connected to another electrode thereof.
  • the circuit for clipping the undesired oscillation has a second function, namely generating a supply voltage for the driver stage.
  • this supply voltage is now the sum of the input and of the output voltage or of a voltage derived therefrom and is consequently more constant than in the case where this supply voltage was the input voltage, so that the variation of the current through the driver stage is smaller.
  • Another advantage of the measure according to the invention is that the supply voltage of the driver stage is comparatively low during starting after switch-on, so that the control current of the switch is small for the time that the duration of the first part of the period is short, which is favourable for achieving a gradual increase of the output voltage.
  • FIG. 1 is a circuit useful for explaining the invention
  • FIG. 2 shows wave forms of the voltages produced therein
  • FIG. 3 shows an embodiment of the circuit according to the invention
  • FIG. 4 shows an embodiment of the circuit according to the invention which embodiment is a part of a television receiver.
  • reference numeral 1 represents a transistor of the n-p-n type which functions as a switch. Its collector is connected through a winding 2 to the positive terminal 3 of an input voltage source, whereas its emitter is connected to the negative terminal of the source, which terminal may be connected to ground.
  • Winding 2 is the primary winding of a transformer 4, a secondary winding 5 of which is connected between ground and the anode of a diode 6.
  • the winding senses of windings 2 and 5 have been chosen such that diode 6 conducts when transistor 1 is blocked and vice versa, which is indicated by means of polarity dots.
  • a capacitor 7 is connected between the cathode of diode 6 and ground. This cathode forms a terminal 8 at which the output voltage V o of the circuit appears and to which a load 9 is connected.
  • Transistor 1 conducts during a first part ⁇ T of the period T of a pulse-shaped control signal fed to its base. Its collector current flows through winding 2 in which energy derived from the voltage source is stored. At the moment at which transistor 1 is blocked this energy produces a current through winding 5 and diode 6.
  • the control signal for transistor 1 is supplied by a driver transistor 10.
  • An oscillator not shown in FIG. 1, generates a signal, which, through a modulator 11 and possibly an amplifier, drives the base of transistor 10.
  • the collector of this transistor is connected through a primary winding 12 of a driver transformer 13 and a resistor 14 to terminal 3, and its emitter is connected to ground.
  • the junction point of resistor 14 and winding 12 is connected to ground through a smoothing capacitor 15.
  • a secondary winding 16 of transformer 13 drives the base of transistor 1.
  • transistor 1 the non-simultaneous drive of transistor 1 has been opted for, i.e. transistor 1 conducts when transistor 10 is blocked and vice versa. This is obtained by the choice of the winding senses of windings 12 and 16, which is indicated in FIG. 1 by polarity dots.
  • Modulator 11 comprises a comparison stage in which the voltage V o is compared with a reference voltage, whereby in known manner control of the duration ⁇ T of the conduction time of transistor 1 is obtained to substantially keep voltage V o constant in spite of possible variations of the input voltage V B at terminal 3 and/or of load 9.
  • FIG. 2a the voltage at the anode of diode 6 and in FIG. 2b the voltage at the collector of transistor 1 has been plotted.
  • the first mentioned voltage in the first part ⁇ T of the period takes the value -nV B and in the second part the value V o
  • the voltage of FIG. 2b is zero in the time ⁇ T and thereafter takes the value V B + (V o /n), 1:n being the ratio between the number of turns of windings 2 and 5.
  • V B + (V o /n) 1:n being the ratio between the number of turns of windings 2 and 5.
  • the current flowing in the leakage inductance of transformer 4 can not be immediately blocked.
  • a high frequency oscillation of decreasing amplitude is produced which is determined by the leakage inductance and the parasitic capacitances. This oscillation causes an increase in the collector voltage and a radiation into the apparatus (not shown) which is supplied with the supply voltage by the circuit of FIG. 1.
  • a clipping circuit which consists of a diode 18, a capacitor 19 and a resistor 20.
  • the anode of diode 18 is connected to the collector of transistor 1, while the parallel circuit consisting of capacitor 19 and resistor 20 is connected between the cathode of diode 18 and terminal 3. If the value of resistor 20 is low enough, the energy of the oscillation is then dissipated in this resistor so that the voltage at the collector remains, during the entire second part of the period, substantially equal to its final value V B + (V o /n).
  • FIG. 2c shows diagrammatically the variation of this voltage. At the cathode of diode 18 a d.c.
  • FIG. 3 shows the circuit according to the invention.
  • resistors 14 and 20 of FIG. 1 are replaced by one resistor 14' which is connected between junction point D of diode 18 and capacitor 19 and junction point A of winding 12 and capacitor 15.
  • a resistor 21 of a small value (approximately 100 ⁇ ) is connected between the anode of diode 18 and the collector of transistor 1 and limits the peak current through the diode.
  • the circuit of FIG. 3 also has other advantages, which will be discussed below.
  • transistor 1 Because transistor 1 must be suitable for very high powers, the storage time of the charge carriers in its base layer is very large if the transistor is saturated so that the collector current will be turned off later than the base current. This implies a variation of ⁇ by leaps and bounds in the beginning. As, however, the initial value of V D is smaller, due to the measure according to the invention, than it is in the stationary operation, the base current is small so that at first the transistor is not driven full on, so that the collector current does substantially not flow longer than the base current and ⁇ increases gradually. In proportion as V o is built up, transistor 1 becomes increasingly saturated.
  • a self-inductance 22, included in the base lead of this transistor ensures, in known manner, that turning off of the collector current, which in normal operation is indeed delayed with respect to that of the base current, is effected rapidly. For simplicity this delay has not been discussed hereinbefore.
  • the detrimental influence of the leakage inductance of transformer 4 can also be removed by means of a capacitor which is connected between two suitable points of windings 2 and 5. Thanks to the measure according to the invention this capacitor can be dispensed with.
  • FIG. 4 shows an embodiment in which the circuit is the combination of a power supply circuit and of a line deflection circuit in a television receiver. Such a circuit was discussed in the publication "IEEE transactions on Broadcast and Television Receivers" of August 1972, volume BTR-18, Number 3, pp 177 to 182.
  • the deflection current flows alternatively through a parallel diode 23 and through transistor 1 and a diode 24 and through a linearity control 25 and a line deflection coil 26.
  • Reference 27 indicates a trace and reference 28 a retrace capacitor.
  • a plurality of windings across which supply voltages are produced are applied around the core of transformer 4. One of them, winding 29, is shown in FIG. 4.
  • Elements 6, 23, 24, 25 and 28 are connected to various points of a further winding 30 of transformer 4.
  • Winding 30 is connected to ground through a capacitor 31.
  • the voltage produced across the capacitor 31 is used to control the ratio ⁇ in modulator 11.
  • the circuit is described in more detail in the above mentioned publication and in U.S. patent application Ser. No. 473,771, filed May 28, 1974, now abandoned and refiled on Mar. 26, 1976 as Ser. No. 670,875 and U.S. Pat. No. 3,950,674.
  • the emitter of driver transistor 10 is not connected to ground but a low voltage is developed there which is stabilized by means of a zener diode 32, by means of which voltage the line oscillator (not shown) and modulator 11 are supplied with power.
  • a zener diode 32 by means of which voltage the line oscillator (not shown) and modulator 11 are supplied with power.
  • Modulator 11 controls an amplifier 33 which supplies a control current to the base of transistor 10 and which is fed by the same supply voltage at point D as transistor 10. It is obvious that other parts of the receiver may be supplied by this voltage or by that at the emitter of transistor 10.
  • a diode 34 prevents the voltage at point A from becoming negative when transistor 10 fails. Otherwise the base of transistor 1 would continue to get a positive control voltage. Any disturbing oscillations are damped by an RC-network 35 connected parallel to winding 12 and a further RC-network 36 between the base of transistor 1 and ground.
  • the transistors in the circuit of FIG. 4 are the following Philips types: the transistor of amplifier 33:BC 548; transistor 10: BD 232; transistor 1: BU 208.
  • Diode 18 is a BY 207, capacitor 19 has a capacitance of approximately 100 nF, while resistor 14' has a value of approximately 33k ⁇ and a permissible power of 5.5W.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
US05/631,736 1974-12-02 1975-11-13 Triggered transistor switching regulator Expired - Lifetime US4031453A (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
NL7415666A NL7415666A (nl) 1974-12-02 1974-12-02 Geschakelde voedingsspanningsschakeling.
NL7415666 1974-12-02

Publications (1)

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US4031453A true US4031453A (en) 1977-06-21

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US05/631,736 Expired - Lifetime US4031453A (en) 1974-12-02 1975-11-13 Triggered transistor switching regulator

Country Status (6)

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US (1) US4031453A (fr)
JP (1) JPS5177818A (fr)
DE (1) DE2554058C3 (fr)
FR (1) FR2293738A1 (fr)
GB (1) GB1532809A (fr)
NL (1) NL7415666A (fr)

Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4115725A (en) * 1975-12-30 1978-09-19 Hitachi, Ltd. Horizontal deflection circuit
US4121282A (en) * 1976-01-21 1978-10-17 Sony Corporation Power supply circuit
US4276586A (en) * 1978-04-06 1981-06-30 U.S. Philips Corporation Tuned switched-mode power supply
US4276587A (en) * 1976-01-23 1981-06-30 Sony Corporation DC to DC Converter
US4290101A (en) * 1977-12-29 1981-09-15 Burroughs Corporation N Phase digital inverter
US4318168A (en) * 1980-06-27 1982-03-02 Raytheon Company Over stress sense circuit for flyback power supply
US4323957A (en) * 1980-05-16 1982-04-06 Sperry Corporation Voltage supression circuit for a voltage converter circuit
US4370701A (en) * 1981-04-24 1983-01-25 Rockwell International Corporation Energy conserving drive circuit for switched mode converter utilizing current snubber apparatus
US4377842A (en) * 1980-10-06 1983-03-22 International Business Machines Corporation Flyback voltage control
US4523265A (en) * 1983-06-29 1985-06-11 Compagnie De Signaux Et D'entreprises Electriques Process and device for eliminating the disturbances related to the fluctuations of the load in chopped power supplies
US4635176A (en) * 1984-04-15 1987-01-06 Victor Company Of Japan, Ltd. High voltage DC generator with reduced ringing and voltage fluctuation
US5563780A (en) * 1993-12-08 1996-10-08 International Power Systems, Inc. Power conversion array applying small sequentially switched converters in parallel
US5745353A (en) * 1992-09-24 1998-04-28 Kabushiki Kaisha Toshiba Snubber circuit that suppresses surge and rush current flowing to a switching element of a self excitation-type flyback power supply
US20050146310A1 (en) * 2003-12-24 2005-07-07 Ray Orr DC converters having buck or boost configurations

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0420997B1 (fr) * 1989-09-29 1994-05-04 Siemens Aktiengesellschaft Disposition de circuit pour alimentation à découpage du type à récupération
DE58907009D1 (de) * 1989-09-29 1994-03-24 Siemens Ag Schaltungsanordnung für ein Sperrwandler-Schalnetzteil.

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3504263A (en) * 1967-12-04 1970-03-31 Technipower Inc Self-oscillating switching type power supply
US3697852A (en) * 1971-04-30 1972-10-10 Ibm Transistor switching regulator
US3831079A (en) * 1971-06-14 1974-08-20 West Electric Co Electronic photographic flash apparatus
US3859590A (en) * 1973-07-30 1975-01-07 Ibm Waveform averaging rc circuit

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3504263A (en) * 1967-12-04 1970-03-31 Technipower Inc Self-oscillating switching type power supply
US3697852A (en) * 1971-04-30 1972-10-10 Ibm Transistor switching regulator
US3831079A (en) * 1971-06-14 1974-08-20 West Electric Co Electronic photographic flash apparatus
US3859590A (en) * 1973-07-30 1975-01-07 Ibm Waveform averaging rc circuit

Cited By (15)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4115725A (en) * 1975-12-30 1978-09-19 Hitachi, Ltd. Horizontal deflection circuit
US4121282A (en) * 1976-01-21 1978-10-17 Sony Corporation Power supply circuit
US4276587A (en) * 1976-01-23 1981-06-30 Sony Corporation DC to DC Converter
US4290101A (en) * 1977-12-29 1981-09-15 Burroughs Corporation N Phase digital inverter
US4276586A (en) * 1978-04-06 1981-06-30 U.S. Philips Corporation Tuned switched-mode power supply
US4323957A (en) * 1980-05-16 1982-04-06 Sperry Corporation Voltage supression circuit for a voltage converter circuit
US4318168A (en) * 1980-06-27 1982-03-02 Raytheon Company Over stress sense circuit for flyback power supply
US4377842A (en) * 1980-10-06 1983-03-22 International Business Machines Corporation Flyback voltage control
US4370701A (en) * 1981-04-24 1983-01-25 Rockwell International Corporation Energy conserving drive circuit for switched mode converter utilizing current snubber apparatus
US4523265A (en) * 1983-06-29 1985-06-11 Compagnie De Signaux Et D'entreprises Electriques Process and device for eliminating the disturbances related to the fluctuations of the load in chopped power supplies
US4635176A (en) * 1984-04-15 1987-01-06 Victor Company Of Japan, Ltd. High voltage DC generator with reduced ringing and voltage fluctuation
US5745353A (en) * 1992-09-24 1998-04-28 Kabushiki Kaisha Toshiba Snubber circuit that suppresses surge and rush current flowing to a switching element of a self excitation-type flyback power supply
US5563780A (en) * 1993-12-08 1996-10-08 International Power Systems, Inc. Power conversion array applying small sequentially switched converters in parallel
US20050146310A1 (en) * 2003-12-24 2005-07-07 Ray Orr DC converters having buck or boost configurations
US7193396B2 (en) * 2003-12-24 2007-03-20 Potentia Semiconductor Corporation DC converters having buck or boost configurations

Also Published As

Publication number Publication date
FR2293738B1 (fr) 1978-07-28
GB1532809A (en) 1978-11-22
NL7415666A (nl) 1976-06-04
FR2293738A1 (fr) 1976-07-02
DE2554058C3 (de) 1979-03-29
DE2554058A1 (de) 1976-08-12
DE2554058B2 (de) 1978-08-10
JPS5177818A (fr) 1976-07-06

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