US3737686A

US3737686A - Shielded balanced microwave analog multiplier

Info

Publication number: US3737686A
Application number: US00265933A
Authority: US
Inventors: J Swanekamp; J Malloy
Original assignee: US Department of Navy
Current assignee: US Department of Navy
Priority date: 1972-06-23
Filing date: 1972-06-23
Publication date: 1973-06-05
Anticipated expiration: 1990-06-05

Abstract

A passive, four quadrant, balanced analogue multiplier for use in the microwave and RF region, including four backward-wave, 3 db quadrature couplers. The couplers are interconnected whereby four output signals are supplied to four respective diodes of the mulitplier from the two input signals to be multiplied for parallel signal processing.

Description

EInited States Patent Swanekamp et al.

[ 51 ,iune5,1973

SHIELDED BALANCED MICROWAVE ANALOG MULTIPLIER [56] References Cited UNITED STATES PATENTS 3,513,398 5/1970 Bossard et al. ..325/446 3,621,400 l1/l97l Paciorek et a1 ..333/l1 X 3,634,768 1/1972 Carpenter et al ..32 l/69 X 3,681,697 8/1972 Moroney ..325/446 Primary Examiner-Joseph F. Ruggiero Attorney-R. S. Sciascia [57] ABSTRACT A passive, four quadrant, balanced analogue multiplier for use in the microwave and RF region, including four backward-wave, 3 db quadrature couplers. The couplers are interconnected whereby four output signals are supplied to four respective diodes of the mulitplier from the two input signals to be multiplied for parallel signal processing.

5 Claims, 2 Drawing Figures OUT PATENTED 73 SHEET 1 BF 2 SHIELDED BALANCED MICROWAVE ANALOG MULTIPLIER BACKGROUND OF THE INVENTION This invention relates generally to microwave signal processing apparatus and, more particularly, to a shielded, balanced microwave analogue multiplier.

In signal correlation systems, it is generally necessary to multiply two or more input signals to form an analogue signal representative of the product of the instantaneous amplitudes of the respective signals. When the input signals are in the microwave frequency range, special problems are posed and conventional audio frequency circuits are not operative.

Prior art attempts to provide signal multiplication at microwave frequencies include systems for heterodyning the signals down to a low frequency range and using a conventional ring modulator as a multiplier bridge. Heterodyning suffers from the disadvantage of not operating at the original microwave frequencies and, thus, requiring an excessive number of components, several of them active.

A passive multiplier, operating at the original microwave frequencies, is inherently unbalanced because the coaxial inputs short out one of the four diodes in the ring modulator, causing an undesirable dc. bias in the output. In addition, the device is not RF shielded beyond the coaxial inputs, thereby making possible pickup of undesired signals and causing deterioration of the signal-to-noise ratio. Also, this type of device does not provide for biasing the diodes to provide a balance adjustment and to insure operation in the desired squarelaw region of the diodes, which is required if the output is to be representative of the product of the instantaneous amplitudes of the applied microwave signals. Still furthermore, this type of device is not adaptable to planar design, that is, it has crossovers, thereby precluding certain construction techniques such as stripline, integrated RF circuitry, or the like.

Another prior art device is disclosed in US. Pat. No. 3,160,882 to John H. Malloy. This device utilized four diodes in a ring arrangement driven by a hybrid ring into which the two signals tobe multiplied were connected as inputs. The series signal processing in the diodes led to diode bias circuitry which was difficult to adjust for balanced operation. In addition, the use of the hybrid ring drive limited the frequency range over which a single correlator could be used to about 35 10. percent.

SUMMARY OF THE INVENTION Accordingly, one object of the invention is to provide an improved, passive, analogue multiplier particularly suitable for operation in the microwave frequency range.

Another object of the present invention is to provide a balanced, microwave, analogue signal multiplier.

A still further object of the present invention is to provide an analogue multiplier operable in the microwave frequency range having an improved signal-tonoise ratio.

Yet another object of the instant invention is to provide a microwave signal multiplier with total electromagnetic shielding.

Still another object of the present invention is to provide an analogue signal multiplier adaptable to miniature microwave planar construction.

A still further object of the present invention is to provide an analogue multiplier having a large usable frequency range.

Yet another object of the present invention is to provide a simpler diode biasing arrangement and better isolation in an analogue signal multiplier.

Briefly, in accordance with one embodiment of the invention, these and other objects are attained by providing a shielded, balanced, analogue signal multiplier operable at the microwave frequency range utilizing four backward-wave, 3 db, quadrature couplers connected in such a way as to take two input signals and provide four output signals. These four output signals from the coupler drive network are applied to four parallel diodes of the multiplier, each separately driven into their square law regions. Their output is then processed through integrating amplifiers and a differential amplifier whose output represents the product of the instantaneous amplitudes of the original input signals.

BRIEF DESCRIPTION OF THE DRAWINGS A more complete appreciation of the invention, and many of the attendant advantages thereof, will be readily appreciated as the same becomes better understood by reference to the following description, when considered in connection with the accompanying drawings wherein:

FIG. 1 is a schematic view of one embodiment of the analogue multiplier according to the present invention, and

FIG. 2 is a schematic view of an alternative embodiment of the analogue multiplier according to the present invention.

DESCRIPTION OF THE PREFFERED EMBODIMENT The operation of correlation is multiplication followed by time averaging. The correlation function is an even function with respect to the relative time delay between the two input signals to be correlated, with a maximum value at zero relative delay between two input signals, i.e., the correlator, when operating on two signal phasors, must perform the scalar, or dot product of the two input voltage phasors. Thus, with two sinusoidal input signals of the form E cos (0,! and E cos (n, (t r), the correct correlation multiplication must produce the product of the two signal magnitudes times the cosine of the phase angle between the two input signals, i.e., E, E cos w r.

Referring now to FIG. 1, sinusoidal input signal E cos m is applied to input port 10 of backward wave coupler l4 and sinusoidal input signal E cos co (2 r) is applied to input" port 12 of backward wave coupler 16. The isolated ports of couplers l4 and 16 are terminated in their characteristic impedances l8 and 20, respectively. The input power is split equally between the two output ports of each coupler whereby a voltage of E,/ \/7(cos w t appears at coupled output port 22 and a voltage of E,/\/ 2 cos m t appears at transmitted output port 24 of coupler 12. Similarly, a voltage of E 2 cos (m w r 90) appears at coupled output port 26 and a voltage of E lfi cos w, (t 1') appears at transmitted" output port 27 of coupler 16. These four output voltages are then coupled to the input and isolated

ports

32, 34, 36, and 38 of

couplers

28 and 30 in the following manner: Coupled port 22 connected to input port 36,

transmitted" port 24 connected to input port 32, coupled port 26 connected to isolated port 34, and transmitted port 27 connected to isolated port 38. For voltages connected to the

input ports

32 and 36, the output supplied is 1/\/ 2 times the input voltage with a phase shift at the transmitted output port, and a 90 phase shift at the coupled port, as was the case with

couplers

12 and 16. With voltages fed into the

isolated ports

34 and 38, the 0 phase shift is associated with the output voltage at the coupled port and 90 associated with the transmitted port. Superposition is then used to sum the voltage at the

output ports

40, 42, 44 and 46 due to voltage inputs at

ports

32, 34, 36 and 38. Thus, the outputs v (E /2) cos (m t 90) (E /2) cos (ant 01 1' v (E,/2) cos (0,: (E /2) cos ((0,: (0 1' 180) v (E /2) cos (m I80") (E /2) cos (m t +wyr) v =(E /2) cos (m,t 90) (E /2) cos (w t+m 'r 90) appear at

output ports

40, 42, 44 and 46, respectively.

While there are 4! (24) distinct possible ways or sets of connecting the four output voltages from

ouplers

14 and 16 to the four inputs of

couplers

28 and 30, there are three characteristic classes of eight output voltage sets from

couplers

28 and 30. Only one of these three classes contains the 0 and 180 relative phase relationship between the two input voltage terms appearing in each of the four output voltage v,, v v and v The interconnection shown in FIG. 1 and described hereinabove is only one of these eight possible combinations and should not be construed to be the only one possible.

Output voltages v v v and v, are then processed in

hot carrier diodes

48, 50, 52 and 54 respectively, each of these diodes operating in its square law (i Kv region, i.e., that the diode bias and its input signal voltage amplitude are such as to assure this operation. The functional relationship of the hot carrier diodes obeys Schottky theory almost exactly and may be expressed as where i is the current through the diode, v is the voltage across the diode, I, is the diode saturation current, and a is a diode constant. With the diode forwardly biased at a voltage v, and a current 1,, a small a.c. signal voltage v, applied around this bias point produces an output signal current of I, (I, 1 (e l) behaving like an ideal square law device.

Referring back to FIG. 1, an adjustable d.c. bias 56, S8, 60 and 62 is provided for each

diode

48, 50, 52 and 54, respectively, through

resistors

64, 66, 68 and 70, respectively. Reactive impedance elements, such as

chokes

72, 74, 76 and 78, provide d.c. return paths for

diodes

48, 50, 52 and 54, respectively. The outputs from

diodes

48, 50, 52 and 54, operating in their square law regions, are

RF shunt capacitors

80, 82, 84 and 86, at each

diode output

48, 50, 52 and 54, respectively, ground the RF signal component centered around frequencies in, and 2 (0,, so that e,,,, need include only the d.c. terms and quasi d.c. component centered around w= 0 (in the case of a dynamic system). As an example, consider the diode voltage v appearing at the input of diode 48 where v (12 /2) cos (ant 90) (E /2) cos (um w r v, (E /2) sin (0,: (E /Z) sin (w,t +w,'r) Substituting into the equation for e,,,,, e, Ka(E,/2) sin co t Ka(E /2) sin ((0,! al K04 (ER/8) sin (a t K0: (E2 /8) sin (ant am) Kat (E,E /4) sin (a l sin ((1),! 01 1') e Ka(E /2) sin (0 Ka(E /2) sin (cu t W) K11 (ER/l6) [1 cos 2mg] K0: (EX/l6) [l cos (2w t 210 7)] K0: (E E /8) [cos 0: 7 cos 2 0.51)].

After bypassing all (0,2 and 20),! components through shunt capacitor 80,

0! l [(E12/2) (E22/2) i z C05 1 Similarly, I

2 (X01 18) [ER/2) (E /2) E E cos (1) 7] and 03 02 and Thus, e e e and 2,, contain only d.c. and quasi LII d.c. terms remaining for further signal processing. The outputs from

diodes

48 and 50, e and 2 respectively, are supplied to the input of integrating amplifier 88, and the outputs of

diodes

52 and 54, e and e respectively, are supplied to the input of integrating amplifier 90. The outputs of integrating

amplifiers

88 and 90 then form the inputs of differential amplifier 92 whose output is readily seen to be out K 01 02) 03 04)] e K E E cos (0 1' e K R ('r), where R (1') E E cos cu 'rthe correlation function.

In an alternative embodiment, shown in FIG. 2, the multiplication process is performed identically with the four 3 db hybrid couplers and the four biased, hot carrier diodes previously illustrated and explained with respect to FIG. 1. The four output voltagese e e,,;,, and e from

diodes

48, 50, 52 and 54, respectively, are the same as before, but rather than supplying them to integrating and differential amplifiers, voltages e, and c are added in

resistors

94 and 96, respectively, and voltages e and e are added in

resistors

98 and 100, respectively. These two summing voltages are then supplied as the input to summing integrating amplifier 102, whose output e is also of the form K,,E,E cos 01,1.

It is to be particularly noted that the entire device,

except for the d.c. bias sources, is totally shielded from external electromagnetic radiation and stray RF signals. The ability 9f the instant invention to provide a completely shielded system is a distinct advantage over the prior art which, heretofore, has been unable to a significant increase in signal-to-noise ratio over prior art devices may be obtained.

It is readily apparent that any transmission line made may be utilized to fabricate the multiplier. Thus, coaxial cable, stripline, waveguide and miniature microwave planar fabrication may be utilized. Furthermore, any desired shielding may be used.

The four outputs from the coupler drive network en able the four diodes of the multiplier to be each separately driven, thereby utilizing parallel signal processing which permit better isolation of the diodes and a simple, easily adjustable biasing arrangement. In addition, the use of backward-wave couplers gives the coupler drive network an octave band frequency range capability, i.e., i 33.3 percent frequency range. This means that less correlators are required to cover a given broad frequency range, or a broader usable frequency range is available from each correlator. A continuously variable delay at one of the inputs can generate a complete correlation function.

Obviously, numerous modifications and variations of the present invention are possible in light of the above teachings. Thus, as an alternative to using backward wave couplers, 3 db line couplers may be used in the coupler drive network. Seven other combinations for interconnecting the couplers to implement the doubly balanced correlator concept will become obvious as other alternatives to the proposed embodiment. It is therefore to be understood that, within the scope of the appended claims, the invention may be practiced otherwise than as specifically described herein.

What is claimed as new and desired to be secured by Letters Patent of the United States is:

1. A shielded, balanced microwave analogue multiplier comprising in combination:

a first set of backward wave couplers having at least two ports for receiving two sinusoidal input signals;

a second set of backward wave couplers connected to the output ports of said first set of couplers, said second set of couplers having four output ports and producing four output signals;

a unilaterally conducting device connected to each of said output ports;

means for biasing said unilaterally conducting devices whereby they operate in their square law region, and

means coupled to said unilaterally conducting device for producing an output signal proportional to the product of the instantaneous amplitudes of said two input signals.

2. A shielded, balanced microwave analogue multiplier according to claim 1 wherein said unilaterally conducting devices comprise diodes,

and wherein said biasing means comprises a dc. bias course.

3. A shielded balanced microwave analogue multiplier according to claim 2 wherein each of said set of couplers comprises two backwardwave 3 db quadrature couplers.

4. A shielded balanced microwave analogue multiplier according to claim 3 wherein said producing means comprises:

an integrating amplifier coupled to two of said diodes;

a second integrating amplifier coupled to the other two of said diodes; and

a differential amplifier coupled to the outputs of said integrating amplifiers.

5. A shielded balanced microwave analogue multiplier according to claim 3 wherein said producing means comprises:

summing resistors coupled to each of said diode outputs and a summing integrating amplifier coupled to the other terminal of said summing resistors.

Claims

1. A shielded, balanced microwave analogue multiplier comprising in combination: a first set of backward wave couplers having at least two ports for receiving two sinusoidal input signals; a second set of backward wave couplers connected to the output ports of said first set of couplers, said second set of couplers having four output ports and producing four output signals; a unilaterally conducting device connected to each of said output ports; means for biasing said unilaterally conducting devices whereby they operate in their square law region, and means coupled to said unilaterally conducting device for producing an output signal proportional to the product of the instantaneous amplitudes of said two input signals.

2. A shielded, balanced microwave analogue multiplier according to claim 1 wherein said unilaterally conducting devices comprise diodes, and wherein said biasing means comprises a d.c. bias course.

3. A shielded balanced microwave analogue multiplier according to claim 2 wherein each of said set of couplers comprises two backward-wave 3 db quadrature couplers.

4. A shielded balanced microwave analogue multiplier according to claim 3 wherein said producing means comprises: an integrating amplifier coupled to two of said diodes; a second integrating amplifier coupled to the other two of said diodes; and a differential amplifier coupled to the outputs of said integrating amplifiers.

5. A shielded balanced microwave analogue multiplier according to claim 3 wherein said producing means comprises: summing resistors coupled to each of said diode outputs and a summing integrating amplifier coupled to the othEr terminal of said summing resistors.