US2922961A - Finline coupler - Google Patents

Finline coupler Download PDF

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Publication number
US2922961A
US2922961A US485671A US48567155A US2922961A US 2922961 A US2922961 A US 2922961A US 485671 A US485671 A US 485671A US 48567155 A US48567155 A US 48567155A US 2922961 A US2922961 A US 2922961A
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United States
Prior art keywords
wave
finline
wave guide
path
along
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US485671A
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English (en)
Inventor
Sloan D Robertson
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AT&T Corp
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Bell Telephone Laboratories Inc
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Publication date
Priority to US2923901D priority Critical patent/US2923901A/en
Priority to NL202464D priority patent/NL202464A/xx
Priority to BE544910D priority patent/BE544910A/xx
Priority to NL107014D priority patent/NL107014C/xx
Priority to DEK161815D priority patent/DE749990C/de
Priority to CH226583D priority patent/CH226583A/de
Priority to CH226760D priority patent/CH226760A/de
Priority to FR883731D priority patent/FR883731A/fr
Priority to CH229859D priority patent/CH229859A/de
Priority to FR884313D priority patent/FR884313A/fr
Priority to FR884435D priority patent/FR884435A/fr
Application filed by Bell Telephone Laboratories Inc filed Critical Bell Telephone Laboratories Inc
Priority to US485671A priority patent/US2922961A/en
Priority to US485672A priority patent/US2921272A/en
Priority to FR1137621D priority patent/FR1137621A/fr
Priority to DEW17954A priority patent/DE1021913B/de
Priority to GB3066/56A priority patent/GB789639A/en
Application granted granted Critical
Publication of US2922961A publication Critical patent/US2922961A/en
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/16—Auxiliary devices for mode selection, e.g. mode suppression or mode promotion; for mode conversion
    • H01P1/161—Auxiliary devices for mode selection, e.g. mode suppression or mode promotion; for mode conversion sustaining two independent orthogonal modes, e.g. orthomode transducer
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/213—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies
    • H01P1/2138—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies using hollow waveguide filters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P3/00—Waveguides; Transmission lines of the waveguide type
    • H01P3/02—Waveguides; Transmission lines of the waveguide type with two longitudinal conductors
    • H01P3/023—Fin lines; Slot lines
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/08—Coupling devices of the waveguide type for linking dissimilar lines or devices
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01R—ELECTRICALLY-CONDUCTIVE CONNECTIONS; STRUCTURAL ASSOCIATIONS OF A PLURALITY OF MUTUALLY-INSULATED ELECTRICAL CONNECTING ELEMENTS; COUPLING DEVICES; CURRENT COLLECTORS
    • H01R39/00—Rotary current collectors, distributors or interrupters
    • H01R39/02—Details for dynamo electric machines
    • H01R39/04—Commutators
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
    • H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
    • H03B5/18—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising distributed inductance and capacitance
    • H03B5/1817—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising distributed inductance and capacitance the frequency-determining element being a cavity resonator
    • H03B5/1835—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising distributed inductance and capacitance the frequency-determining element being a cavity resonator the active element in the amplifier being a vacuum tube
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N1/00—Scanning, transmission or reproduction of documents or the like, e.g. facsimile transmission; Details thereof
    • H04N1/46—Colour picture communication systems
    • H04N1/56—Processing of colour picture signals
    • H04N1/60—Colour correction or control

Definitions

  • the present invention relates to extremely wide band coupling elements for use in Wave guiding channels, and more particularly to such coupling elements having polarization selective characteristics.
  • the amount of signal information which can be transmitted along a given wave path can be enhanced by transmitting simultaneously a plurality of separate signals of the same frequency range, each signal carrying a distinct message.
  • two separate messages can be transmitted simultaneously without intermodulation along a single hollow wave guide by launching the two signal waves to be transmitted so that their electric field vectors are mutually perpendicularly polarized. Then by selectively coupling on the basis of the direction of polarization of the electric vector to only one of the two signal waves, the message contained in this signal will be derived.
  • a coupling arrangement adapted for selecting a particular signal wave on the basis of the direction of polarization of its electric field vector shall be referred to as a polarization selective coupler. It is generally characteristic of prior art polarization selective couplers that they do not achieve sufficiently broad band operation.
  • a broad object of the invention is to increase the frequency range over which polarization selective coupling may be achieved.
  • a polarization selective coupler which comprises fin-like elements which are joined together at a predetermined point along their length. Wave energy is then coupled to these fins at a point which is a quarter wavelength at the operating frequency from the junction of the two fins.
  • the narrow band characteristics of couplers of this type may be advantageously utilized to provide frequency selectivity for wave energy passing into the hollow wave 2 7 guide.
  • couplers cannot be employed where extremely broad band coupling is required.
  • couplers are characterized by abrupt geometric discontinuities along the wave path provided through the coupler, which further precludes their use in broad band applications.
  • a feature of this first aspect of the invention is a coupling arrangement utilizing a pair of fins in a way to provide a smooth curved wave path which both eliminates any abrupt geometric discontinuities along the wave path and obviates the necessity for a quarter wavelength section along the finline wave path.
  • a further object of the present infashion is generally designated a hybrid coupler, or
  • hybrid junction and shall be so referred to herein. Cont1nued experience with the various hybrid junctions proposed heretofore has proved these devices to be generally narrow band devices capable of operating only over a very limited frequency bandwidth.
  • a further object of the present invention therefore is to provide a power dividing junction capable of operatlng over extremely broad frequency bands.
  • wave energy propagating along a hollow wave guide is coupled to a second wave guiding path by use of a finline structure which forms a continuous wave path between the wave guide and the second wave guiding path.
  • the finline structure includes two very thin metal fins spaced apart along their entire length for forming a continuous wave path along the interspace therebetween, the opposing surfaces of the two fins serving as the boundaries of the continuous Wave path.
  • the opposing surfaces are spaced to form two tapered sections of wave path and a narrow section of wave path intermediate the two tapered sections along the continuous wave path.
  • the tapered section at one end of the finline extends into the hollow wave guide and matches the characteristic impedance of the narrow section to the characteristic impedance of the hollow wave extends into the second wave guiding path and matches the characteristic impedance of the narrow section along the finline wave path to the characteristic impedance of the second wave guiding path.
  • the narrow section of wave path preferably extends through the boundary of the hollow wave guide.
  • a finline structure is utilized for coupling wave energy between a hollow conductive wave guide and a coaxial line.
  • the finline structure comprises two thin coplanar conductive fin elements spaced apart along their entire length and having their opposing surfaces serve as boundaries to form a continuous wave path between the hollow wave guide and the coaxial line.
  • the opposing surfaces are spaced to form first and second tapered sections of wave path and a narrow section of wave path intermediate the tapered sections along the continuous wave path.
  • the first tapered section extends along a longitudinal plane within the hollow wave guide and is tapered gradually from the transverse dimension of the hollow wave guide to the transverse dimension of the narrow section of wave path
  • the second tapered section extends into the coaxial line and is tapered gradually from the radial dimension between the inner and outer conductors of the coaxial line to the transverse dimension of the narrow section of wave path. It is especially important to have a smooth continuous wave path between the hollow wave guide and the coaxial line connector if broad band operation is desired. Furthermore, it is essential for broad band operation that the two fins forming the finline structure be spaced apart along their entire length.
  • a plurality of finline structures are combined to effect such a bend.
  • two finline structures each comprising two coplanar fins closely spaced over a portion of their length and tapered at one end for impedance matching, are positioned in substantially mutually perpendicular planes within a first wave guide and spaced apart along the wave guide axis.
  • the closely spaced region of each of the finline structures is coupled through a smooth wave path to separate coaxial transmission lines.
  • Each of the coaxial lines which is coupled at one end to a diiferent one of the first two finline structures, is coupled at the other end to a different one of a second pair of finline structures which are positioned within a second circular wave guide.
  • the second pair of finline structures is positioned in substantially mutually perpendicular planes within the second wave guide and spaced apart along the axis of this wave guide. It will be convenient for purposes of explanation to consider the finline structures as positioned in the horizontal and vertical planes of the first and second circular wave guides.
  • electromagnetic wave energy propagating along the first wave guide will be divided between the two finline structures associated therewith according to the polarity of the wave, that is, the hor izontal component of such a wave will be coupled to the horizontally positioned finline structure and the vertical component will be coupled to the vertically positioned finline structure.
  • the horizontal and vertical components of the wave are then transferred by way of the separate coaxial lines to the horizontally and vertically positioned finline structures in the second wave guide.
  • the energy propagating along the coaxial lines is made to follow any convenient path for effecting the desired bend, and after eifecting the desired bend the horizontal and vertical components of the wave are thereafter recombined in the second wave guide to form the original wave. It is important, however, in order to obtain the original wave undistorted, that the electrical length of the wave path used for executing the bend be the same for each of the two components of the wave.
  • Fig. 1 shows a longitudinal section of a wave guide to coaxial line finline coupler in accordance with the present invention
  • Fig. 1A is an end view taken from the right end of the finline coupler of Fig. 1;
  • Fig. 2 shows a longitudinal section of a second embodiment of the present invention forming a wave guide to coaxial line finline coupler
  • Fig. 2A is an end view taken from the right end of the finline coupler of Fig. 2;
  • Fig. 3 is a cut-away perspective view of an embodiment of the finline structure used to form a power dividing junction in accordance with the present invention.
  • Fig. 4 is a perspective view of an embodiment of the finline structure used to form a flexible connection between a pair of hollow wave guides, in accordance with another aspect of the present invention.
  • Figs. 1 and 1A illustrate an extremely broad band finline coupler for coupling electromagnetic wave energy between the circular hollow wave guide 10 and the coaxial line 12.
  • This coupler comprises two thin coplanar conductive fins 13 and 14 which are spaced apart along their entire length.
  • This arrangement of these two fins shall be referred to herein as a finline or finline structure and the wave path provided therealong shall be referred to as a finline wave path.
  • the two fins are closely spaced along a portion of their length to form along the interspace therebetween a narrow wave path 15 in this region.
  • Each of the fins is tapered away from the closely spaced region 15 to form an impedance matching section between this closely spaced region and the hollow wave guide.
  • the tapers 16 and 17 are preferably several wavelengths long at the lowest operating frequency, their optimum contour may be computed for any given set of operating conditions according to well known design formula.
  • the fins taper to merge smoothly with the walls of the wave guide.
  • the smooth tapered sections may be replaced by a succession of steps which form successive quarter wavelength matching sections, approaching the characteristics of the tapered section as the number of steps along the finline is increased.
  • Pins 13 and 14 project through an aperture in the wall of the wave guide 10 to connect with conductors 18 and 19, respectively, of coaxial line 12.
  • the closely spaced section 15 of finline 11 extends outside of the confines of wave guide It) and is terminated by a tapered section 23 wherein fin 13 is smoothly tapered outwardly toward the inner surface of conductor 18.
  • the energy propagating along the finline path is maintainedconfined in the extremely narrow path and is substantially unaffected by the discontinuity presented by the transition at the aperture in the wave guide.
  • the wave energy may be more closely confined to the closely spacedsection 15 by the insertion of dielectr1c material between the fins along this section.
  • the geometric discontinuity occasioned by this transition will tend not to excite spurious modes along the wave guide.
  • Mode killers such as thin plates 21 of lossy material may advantageously be provided on either side of the finline structure for further inhibiting the excitation of any spuriousmodes along the curved portion of the finline wave path.
  • mode killers such as the tapering of the hollow wave guide in the region of the finline to obtain a narrow guide dimension transverse to the plane of the finline adjacent the curved region of the finline wave path.
  • the tapered guide may be simulated by the insertion of wedge-shaped conductive elements to taper efiectively the inner surface of the hollow wave guide.
  • a finline structure may be utilized for coupling between a hollow wave guide and wave guiding means other than a coaxial transmission line, such as a twoconductor balanced line, a single wire helix, a bifilar helix, or a second hollow wave guide.
  • a wave guide to wave guide finline coupler is disclosed specifically in a copending patent application Serial No. 485,672 by H. T. Friis and S. D. Robertson.
  • finline coupler as used herein shall designate any coupling arrangement which includes a finline or finline structure.
  • each of the. figures shall be referred to as a finline coupler, the coupler of Fig. 1 utilizing only one finline, whereas the couplers shown in Figs. 2 and 3 utilize two finlines and the circular bend coupler of Fig. 4 utilizes four finlines.
  • a second embodiment of the present invention is the finline coupler shown in Figs. 2 and 2A.
  • two finline structures are positioned to be coextensive along a hollow wave guide.
  • a first finline 111 is positioned to extend along a longitudinal plane parallel to the axis of wave guide 110 but displaced to one side of the wave guide axis.
  • This finline comprises two fins 113 and 114 closely spaced along a portion of their length and tapered in a direction away from the closely spaced section 115 for matching the characteristic impedance of the closely spaced section to the characteristic impedance of the hollow wave guide.
  • Fins 113 and 114 are connected to conductors 118 and 119, respectively, of coaxial line 112 in the manner described above with reference to Fig. 1.
  • a second finline structure 211 of the same type is positioned parallel to finline 111 and coextensive therewith along wave guide 110 but on the other side of the wave guide axis.
  • the second finline is connected to a second
  • the coupling to any particular mode of propagation can be minimized.
  • the coupling to any particular mode can be maximized.
  • the output from each of the parallel finlines is then combined by any suitable means (not shown) for transmission to a utilization circuit.
  • the tapered sections of the finlines 111 and 211 of Fig. 2 may be oppositely directed so that one of the finlines couples to wave energy passing in one direction along the wave guide and the other finline couples to wave energy passing in the opposite direction along the wave guide.
  • Such a system is useful in measuring techniques where a portion of the energy passing along a main wave guide to a given load is coupled via one of the finlines to monitoring equipment, the remaining portion of the wave energy continuing on to the load. Thereafter, a portion of the wave energy reflected from the load, and therefore passing in the opposite direction along the main wave guide, is coupled via the second finline to additional monitoring equipment for measuring the amount of energy reflected. In this manner, the standing wave ratio and other characteristics of a transmission path can readily be determined.
  • two finlines are spaced apart along a hollow wave guide as shown in Fig. 3 to form a power dividing finline coupler.
  • a first finline 311, comprising fins 313 and 314 is positioned to extend along a longitudinal axial plane within a hollow wave guide 410, as explained with reference to Fig. 1.
  • a second finline 411, comprising fins 413 and 414, is spaced apart from finline 311 along the wave guide axis and is positioned to extend along a second longitudinal axial plane within wave guide 410, the plane of the second finline being rotated a predetermined angle 6 with respect to the plane of the first finline.
  • the angle 6' may be made either adjustable or fixed in accordance with the end to be effected.
  • the component parallel to the finline will be coupled via the finline to a second wave path whereas the perpendicular component, which is represented by vector E will pass substantially unaffected through the region of the finline and continue along the wave guide.
  • the finline serves as a 3 db coupler, coupling half the wave energy to the coaxial line and allowing half the wave energy to continue propagating along the hollow wave guide.
  • wave energy propagating from right to left along wave guide 410 and represented by vector E will be divided in two, half of the wave energy being coupled to coaxial line 312 as shown by vector E and half of the wave energy continuing along the wave guide, polarized as shown by vector E
  • wave energy introduced at the coaxial line terminals 312 as shown by E will be divided in half and propagate as IE and E
  • wave energy introduced at coaxial line 412 as shown by vector E will be divided in half and propagate as E and E
  • the circular wave guide 410 of Fig. 3 may be connected at each end to a section of rectangular Wave guide, the wide dimension of the rectangular wave guide being perpendicular to the electric vectors E and E, at the respective ends of wave guide 410.
  • a transition section may advantageously be interposed between the rectangular and the circular wave guide sections for smoothly changing from the rectangular mode propagation to the circular mode propagation along the power dividing coupler.
  • the finline structure of Fig. 1 may be embodied in a finline coupler for forming a flexible section which can be used for by-passing a bend in a hollow wave guide.
  • a finline coupler for forming a flexible section which can be used for by-passing a bend in a hollow wave guide.
  • a finline 512 of the type shown in Fig. l, is positioned to extend along a longitudinal axial plane within wave guide 510.
  • a second finline 516 is spaced apart longitudinally from finline 512 along the wave guide axis and positioned to extend along a Second longitudinal axial plane within the wave guide, the plane of finline 516 being substantially perpendicular to the plane of the finline 512.
  • the two finlines 512 and 516 are coupled via two coaxial lines 514 and 518, respectively, to a second pair of mutually perpendicular finlines 522 and 526, respectively.
  • the two finlines of the second pair are positioned to extend along wave guide 520 in two mutually perpendicular axial planes and are spaced apart longitudinally along the wave guide axis. For applications where space is a premium, it is feasible to telescope the two finlines in each of the wave guides to the point where they overlap a substantial amount.
  • Wave guides 510 and 520 are advantageously terminated by the tapered impedances 519 and 529, respectively, for preventing reflection of any wave energy from these terminals. However, such terminations usually can be omitted.
  • a wave propagating from left to right along wave guide 510 and polarized in the plane of finline 512 will be coupled to wave guide 520 via finline 512, coaxial line 514, and finline 522.
  • a wave propagating in the plane of finline 516 will be coupled to wave guide 520 via finline 516, coaxial line 518, and finline 526.
  • two distinct waves having mutually perpendicularly polarized electric vectors can be eifectively coupled simultaneously between two angularly disposed sections of circular hollow wave guide. In such a case, however, it is important that the electric vector of each of the two waves be closely aligned with the corresponding one of the mutually perpendicularly positioned finlines.
  • the finline coupler of Fig. 4 may also be used to couple a single wave whose electric field vector lies neither in the plane of finline 512 nor finline 516 but is somewhere between these two planes.
  • the component of the wave which lies in the plane of finline 512 is coupled to wave guide 520, via finline 512, coaxial line 514, and finline 522.
  • the component of the wave which lies in the plane perpendicular to finline 512, and therefore in the plane of finline 516 will be coupled to wave guide 520 via finline 516, coaxial line 518, and finline 526.
  • the two components are then recombined in wave guide 520 to form the original signal wave.
  • each of the wave paths for each of the components of the wave includes a section of hollow wave guide, two finlines, and a section of coaxial line.
  • this condition can be met, independent of frequency, if corresponding elements of the two wave paths be equal, that is, if the lengths of each of the finlines be made equal, the lengths of the section of coaxial line be made equal, and the lengths of the sections of hollow wave guide in the wave paths be made equal.
  • mode killers such as the resistive plates 21 of Fig. 1 may advantageously be utilized in the embodiments of both Figs. 3 and 4. In these embodiments the resistive plates will be positioned as shown in Fig. 1.
  • the embodiment of the finline coupler shown in Fig. 2 may advantageously be incorporated in the embodiments of Figs. 3 and 4.
  • the finline 311 of Fig. 3 may advantageously be replaced by a number of parallel coextensive finlines as shown by Fig. 2.
  • finline 411 of Fig. 3 may be replaced by a number of parallel coextensive finlines for minimizing coupling to spurious modes, the parallel planes of the finline replacing finline 411 being rotated a predetermined angle with respect to the parallel planes of the finlines replacing finline 311.
  • a number of parallel coextensive finlines as taught by Fig. 2, may advantageously replace one or more of the finlines of Fig. 4.
  • dielectric material may advantageously be positioned along the narrow section of finline Wave path in each of the embodiments disclosed for more effectively confining the a 9 a H V: electric field propagating along the finline, as discussed with reference to Fig. 1.
  • conductive bounding means defining a hollow wave guide and forming a first waveguiding path, a coaxial transmission line defining a second waveguiding path to be coupled to said first waveguiding path, said coaxial line comprising an inner and an outer conductor with a predetermined separation therebetween, said first and second waveguiding paths each having a spatial orientation and a transmission mode, at least one of the characteristics of said first path differing from the corresponding characteristic of said second path, and coupling means for forming a physically smooth and continuous wave path from within said hollow wave guide to the interior of said second waveguiding path comprising a pair of thin coplanar conductive fin elements extending axially along a portion of the hollow wave guide, the thickness of the two fin elements being no more than several percent of the cut-ofi wavelength of the wave guide, the two elements being spaced along their entire length and the interspace therebetween forming said smooth and continuous Wave path, the transverse dimension of said continuous wave path initially being equal to the transverse dimension of said
  • a hollow wave guide having a predetermined transverse dimension
  • inner and outer coaxially disposed conductive members forming a coaxial transmission line having a predetermined separation between said inner and outer conductive members
  • means for coupling wave energy between said hollow wave guide and said coaxial line comprising two thin coplanar conductive elements spaced apart along their entire length, the thickness of the two fin elements being no more than several percent of a wavelength atthe cut-off frequency of the wave guide, the spacing being dimensioned to form a physically smooth and continuous wave path having first and second tapered sections of Wave path and a uniformly narrow section ofwave path intermediate said tapered sections, the first tapered section of wave path extending in an axial plane within the hollow wave guide and tapered gradually from the transverse dimension of said hollow wave guide tothe transverse dimension of the narrow section of wave path, and the second tapered section of wave path extending into the coaxial transmission line andbeing tapered gradually from the separation between the inner and outer conductors of the coaxial line to the transverse dimension of the narrow section of wave path.
  • a hollow conductive wave guide, a coaxial transmission line, and means forming a physically smooth and continuous wave path for coupling wave energy between said hollow wave guide and said coaxial transmission line comprising two thin coplanar fin elements spaced apart along their entire length, the thickness of the two fin elements being no more than several percent of a wavelength at the cut-0E frequency of the Wave guide, the spacing being dimensioned to form a physically smooth and continuous wave path having first and second tapered sections of wave path and a narrow section of wave path intermediate said tapered sections, the first tapered section wave path extending in an axial plane within the conductive wave guide for matching the characteristic impedance of the hollow wave guide to the characteristic impedance of the narrow section of wave path, and the second tapered section of wave path extending in an axial plane of the coaxial transmission line for matching the characteristic impedance of the 1O coaxial transmission line to the characteristic impedance of the narrow section of wave path.
  • a hollow conductive wave guide having a predetermined transverse dimension forming a main waveguiding path, two coaxial transmission lines to be coupled with said hollow wave guide, and means for coupling wave energy between said hollow wave guide and said coaxial lines comprising two finlines positioned in parallel longitudinal planes along a portion of the length of the hollow wave guide, the two finlines being spaced apart approximately one-third the guide transverse dimension,'each of the finlines comprising two thin coplanar conductive elements spaced apart along their entire length and having their opposing surfaces form a physically smooth and continuous wave path of the interspace therebetween, the thickness of the two fin elements being no more than several percent of a wavelength at the cu -01f frequency of the wave guide, said opposing surfaces spaced to form first and second tapered sections of wave path and a narrow section of wave path intermediate said tapered sections, the first tapered section being positioned along the hollow wave guide for matching the characteristic impedance of the hollow wave guide to the characteristic impedance of the narrow section of wave path, and the second tapered section extending
  • a hollow conductive wave guide having a predetermined transverse dimension
  • means for coupling wave energy between said hollow conductive wave guide and said plurality of auxiliary paths comprising a like plurality of finlines positioned coextensively along parallel longitudinal planes of the hollow wave guide, each of the finlines extending to form a continuation of a separate one of the auxiliary waveguiding paths and comprising two thin coplanar conductive elements spaced apart along their entire length and having their opposing surfaces form a physically smooth and continuous wave path of the interspace therebetween, the thickness of the two fin elements being no more than several percent of a wavelength at the cut-off frequency of the waveguide, said continuous wave path having first and second tapered end sections and a narrow section intermediate said tapered sections, the first tapered section being positioned along the hollow wave guide and tapered gradually from the transverse dimension of the hollow Wave guide to
  • a hollow conductive wave guide having a predetermined transverse dimension, a plurality of coaxial transmission lines to be coupled with said hollow wave guide, and means for coupling wave energy between said hollow wave guide and said plurality of coaxial transmission lines-comprising a like plurality of finlines extending coextensively in parallel planes along a portion of the length of said hollow wave guide, each of the finlines comprising two thin coplanar conductive elements spaced apart along their entire length for forming a physically smooth and continuous waveguiding path of the interspace between said elements, the thickness of the two fin elements being no more than several percent of a wavelength at the cut-off frequency of the wave guide, said continuous waveguiding path having first and second tapered sections and a narrow section intermediate said tapered section, the first tapered section is positioned along 1 1 the hollow wave guide and the second tapered section extends to form a continuation of one of the coaxial transmission lines.
  • Apparatus forming a hybrid coupler comprising a main hollow wave guide, first and second coaxial transmission lines to be coupled with said main hollow wave guide, and first and second finlines 'for coupling energy between said main wave guide and said first and second coaxial lines respectively, the two planar finlines being spaced apart along the wave guide axis and the plane of the first finline being rotated an angle of 45 degrees about the wave guide axis with respect to the plane of the second finline, each of the finlines comprising two thin coplanar conductive elements spaced apart along their entire length for forming a physically smooth and continuous wave path along the interspace between their opposing surfaces, the thickness of the two fin elements being no more than several percent of a wave length at the cut-off frequency of the wave guide and the opposing surfaces of the conductive elements being spaced apart to form first and second tapered sections of wave path and a narrow section of wave path intermediate said tapered sections along said physically smooth and continuous wave path, the first tapered section being positioned axially along a portion of the hollow wave guide and
  • a main hollow wave guide means defining first and second auxiliary waveguiding paths in energy coupling relation with said main hollow wave guide, said auxiliary wave guiding paths each having a transverse dimension across which an electric field of electromagnetic wave energy can be supported, and first and second finlines for coupling energy between said main wave guide and said first and second waveguiding paths respectively, the two planar finlines being spaced apart along the wave guide axis and the plane of the first finline being rotated an angle of 45 degrees about the wave guide axis with respect to the plane of the second finline, each of said finline structures comprising two thin coplanar conductive elements spaced apart along their entire length, the thickness of the two fin elements being no more than several percent of a wavelength at the cut-off frequency of the wave guide, the spacing between the two thin conductive elements dimensioned to form a physically smooth and continuous wave path having first and second tapered end sections and a narrow section intermediate said tapered sections, the first tapered section being positioned axially along a portion
  • Apparatus forming a power dividing junction comprising a main hollow wave guide, means defining first and second auxiliary waveguiding paths in energy coupling relation with said main hollow wave guide, said auxiliary wave guiding paths each having a transverse dimension across which an electric field of electromagnetic wave energy can be supported, and first and second finlines for coupling wave energy between said main wave guide and said first and second waveguiding paths, respectively, each of said finline structures comprising two thin coplanar conductive elements spaced apart along their entire length, the thickness of the two fin elements being no more than several percent of a wavelength at the cut-ofi frequency of the wave guide, the two finlines extending within the main wave guide and being spaced apart along the wave guide axis and the plane of the first finline being rotated a predetermined angle about the wave guide axis with respect to the plane of the second finline, each of the finlines being characterized in that the opposing surfaces of its two conductive elements bound a physically smooth and continuous wave path having first and second tapered end sections and a narrow section intermediate said tapered

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  • Engineering & Computer Science (AREA)
  • Multimedia (AREA)
  • Signal Processing (AREA)
  • Waveguide Aerials (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
US485671A 1941-07-25 1955-02-02 Finline coupler Expired - Lifetime US2922961A (en)

Priority Applications (16)

Application Number Priority Date Filing Date Title
US2923901D US2923901A (en) 1941-07-25 robertson
NL202464D NL202464A (xx) 1941-07-25
BE544910D BE544910A (xx) 1941-07-25
NL107014D NL107014C (xx) 1941-07-25
DEK161815D DE749990C (de) 1941-07-25 1941-07-31 Zentrumsbuechse fuer Presskollektoren und aehnliche Pressstoffkoerper
CH226583D CH226583A (de) 1941-07-25 1942-06-22 Dezimeterwellensender.
CH226760D CH226760A (de) 1941-07-25 1942-06-30 Zentrumsbüchse, z. B. für Presskollektoren.
FR883731D FR883731A (fr) 1941-07-25 1942-07-02 Manchon central pour collecteurs de courant électrique et autres articles analogues en matière comprimée
CH229859D CH229859A (de) 1941-07-25 1942-07-11 Einrichtung zur Herstellung korrigierter Farbauszüge für die Zwecke der bildlichen Wiedergabe.
FR884313D FR884313A (fr) 1941-07-25 1942-07-21 Procédé et dispositif pour l'obtention de reproductions fidèles au point de vue des couleurs
FR884435D FR884435A (fr) 1941-07-25 1942-07-24 émetteur à ondes décimétriques
US485671A US2922961A (en) 1941-07-25 1955-02-02 Finline coupler
US485672A US2921272A (en) 1941-07-25 1955-02-02 Finline coupler
FR1137621D FR1137621A (fr) 1941-07-25 1955-10-11 Dispositif de couplage à ailettes
DEW17954A DE1021913B (de) 1941-07-25 1955-11-30 Kopplungsanordnung fuer breitbandigen Energieuebergang
GB3066/56A GB789639A (en) 1941-07-25 1956-01-31 Improvements in coupling arrangements for electromagnetic wave transmission paths

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE229859X 1941-07-25
US485671A US2922961A (en) 1941-07-25 1955-02-02 Finline coupler

Publications (1)

Publication Number Publication Date
US2922961A true US2922961A (en) 1960-01-26

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ID=25764481

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US2923901D Expired - Lifetime US2923901A (en) 1941-07-25 robertson
US485671A Expired - Lifetime US2922961A (en) 1941-07-25 1955-02-02 Finline coupler

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US2923901D Expired - Lifetime US2923901A (en) 1941-07-25 robertson

Country Status (7)

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US (2) US2922961A (xx)
BE (1) BE544910A (xx)
CH (3) CH226583A (xx)
DE (1) DE1021913B (xx)
FR (4) FR883731A (xx)
GB (1) GB789639A (xx)
NL (2) NL202464A (xx)

Cited By (7)

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US2981904A (en) * 1959-01-06 1961-04-25 Hughes Aircraft Co Microwave transition device
US3248601A (en) * 1957-10-30 1966-04-26 Raytheon Co Collinear input and output couplers, each using rectangular guide to ridge guide to transmission line conversion, for traveling wave tube
US3284725A (en) * 1962-01-15 1966-11-08 Airtron Division Of Prec Produ Microwave coupler for combining two orthogonally polarized waves utilizing a ridge-like impedance matching member
US3435380A (en) * 1965-03-09 1969-03-25 Thomson Houston Comp Francaise Polarization rotator for microwaves
FR2550892A1 (fr) * 1983-08-19 1985-02-22 Labo Electronique Physique Sortie d'antenne en guide d'onde pour une antenne plane hyperfrequence a reseau d'elements rayonnants ou recepteurs et systeme d'emission ou de reception de signaux hyperfrequences comprenant une antenne plane equipee d'une telle sortie d'antenne
FR2608835A1 (fr) * 1986-12-19 1988-06-24 Thomson Csf Dispositif de couplage a large bande entre la ligne a retard d'un tube a onde progressive et le circuit externe de transmission de l'energie du tube, et tube a onde progressive comportant un tel dispositif
CN104467708A (zh) * 2014-12-22 2015-03-25 中国电子科技集团公司第五十四研究所 一种c波段空间功率合成固态功率放大器

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* Cited by examiner, † Cited by third party
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DE1072479B (xx) * 1953-08-25 1959-12-31
BE562429A (xx) * 1956-12-19
DE1095334B (de) * 1959-06-30 1960-12-22 Siemens Ag UEbergang von einer Koaxialleitung auf einen Hohlleiter
US3066290A (en) * 1959-12-28 1962-11-27 Varian Associates Waveguide hybrid junctions
US4028650A (en) * 1972-05-23 1977-06-07 Nippon Hoso Kyokai Microwave circuits constructed inside a waveguide
JPS583401B2 (ja) * 1972-05-23 1983-01-21 日本放送協会 マイクロハカイロ
FR2560442B1 (fr) * 1984-02-24 1987-08-07 Thomson Csf Dispositif de commutation et de limitation a ligne a fente, fonctionnant en hyperfrequences
DE3406641A1 (de) * 1984-02-24 1985-08-29 ANT Nachrichtentechnik GmbH, 7150 Backnang Zweiband-polarisationsweiche
FR2565043B1 (fr) * 1984-05-24 1986-10-17 Mecanismes Comp Ind De Motoreducteur dont l'arbre filete d'induit traverse un collecteur taraude adapte pour cooperer avec le filetage de l'arbre
JP2897678B2 (ja) * 1995-03-22 1999-05-31 株式会社村田製作所 誘電体共振器及び高周波帯域通過フィルタ装置
CN108963407A (zh) * 2018-08-20 2018-12-07 中国科学院国家空间科学中心 一种三燕尾金属膜片正交模耦合器

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US2546840A (en) * 1945-04-26 1951-03-27 Bell Telephone Labor Inc Wave guide phase shifter
US2633493A (en) * 1946-04-02 1953-03-31 Seymour B Cohn Broad-band wave guide-to-coaxial line junction
US2660667A (en) * 1943-02-23 1953-11-24 Bell Telephone Labor Inc Ultrahigh frequency resonator
US2691731A (en) * 1951-02-21 1954-10-12 Westinghouse Electric Corp Feed horn
US2702366A (en) * 1950-03-22 1955-02-15 Univ Leland Stanford Junior High-frequency impedance measuring device
US2724090A (en) * 1951-05-02 1955-11-15 Litton Industries Inc Electron discharge device output coupler

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CA505234A (en) * 1954-08-17 Western Electric Company, Incorporated Wave guide phase shifter
US2567748A (en) * 1943-10-02 1951-09-11 Milton G White Control of wave length in wave guides
US2708236A (en) * 1950-03-18 1955-05-10 Bell Telephone Labor Inc Microwave amplifiers
US2683256A (en) * 1952-04-07 1954-07-06 Us Army Magnetron amplifier

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Publication number Priority date Publication date Assignee Title
US2660667A (en) * 1943-02-23 1953-11-24 Bell Telephone Labor Inc Ultrahigh frequency resonator
US2546840A (en) * 1945-04-26 1951-03-27 Bell Telephone Labor Inc Wave guide phase shifter
US2633493A (en) * 1946-04-02 1953-03-31 Seymour B Cohn Broad-band wave guide-to-coaxial line junction
US2702366A (en) * 1950-03-22 1955-02-15 Univ Leland Stanford Junior High-frequency impedance measuring device
US2691731A (en) * 1951-02-21 1954-10-12 Westinghouse Electric Corp Feed horn
US2724090A (en) * 1951-05-02 1955-11-15 Litton Industries Inc Electron discharge device output coupler

Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3248601A (en) * 1957-10-30 1966-04-26 Raytheon Co Collinear input and output couplers, each using rectangular guide to ridge guide to transmission line conversion, for traveling wave tube
US2981904A (en) * 1959-01-06 1961-04-25 Hughes Aircraft Co Microwave transition device
US3284725A (en) * 1962-01-15 1966-11-08 Airtron Division Of Prec Produ Microwave coupler for combining two orthogonally polarized waves utilizing a ridge-like impedance matching member
US3435380A (en) * 1965-03-09 1969-03-25 Thomson Houston Comp Francaise Polarization rotator for microwaves
FR2550892A1 (fr) * 1983-08-19 1985-02-22 Labo Electronique Physique Sortie d'antenne en guide d'onde pour une antenne plane hyperfrequence a reseau d'elements rayonnants ou recepteurs et systeme d'emission ou de reception de signaux hyperfrequences comprenant une antenne plane equipee d'une telle sortie d'antenne
EP0134611A1 (fr) * 1983-08-19 1985-03-20 Laboratoires D'electronique Et De Physique Appliquee L.E.P. Antenne plane hyperfréquence à réseau d'éléments rayonnants ou récepteurs et système d'émission ou de réception de signaux hyperfréquences comprenant une telle antenne plane
FR2608835A1 (fr) * 1986-12-19 1988-06-24 Thomson Csf Dispositif de couplage a large bande entre la ligne a retard d'un tube a onde progressive et le circuit externe de transmission de l'energie du tube, et tube a onde progressive comportant un tel dispositif
EP0274950A1 (fr) * 1986-12-19 1988-07-20 Thomson-Csf Dispositif de couplage à large bande entre la ligne à retard d'un tube à onde progressive et le circuit externe de transmission de l'énergie du tube, et tube à onde progressive comportant un tel dispositif
US4871950A (en) * 1986-12-19 1989-10-03 Thomson-Csf Wide band device for coupling between the delay line of a travelling wave tube and the external circuit transmitting the energy of the tube
CN104467708A (zh) * 2014-12-22 2015-03-25 中国电子科技集团公司第五十四研究所 一种c波段空间功率合成固态功率放大器

Also Published As

Publication number Publication date
FR1137621A (fr) 1957-05-31
GB789639A (en) 1958-01-22
FR883731A (fr) 1943-07-13
BE544910A (xx)
CH229859A (de) 1943-11-30
CH226760A (de) 1943-04-30
FR884313A (fr) 1943-08-10
FR884435A (fr) 1943-08-12
NL107014C (xx)
NL202464A (xx)
US2923901A (en) 1960-02-02
DE1021913B (de) 1958-01-02
CH226583A (de) 1943-04-15

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