US20120033754A1 - Ofdm channel estimation method and apparatus - Google Patents
Ofdm channel estimation method and apparatus Download PDFInfo
- Publication number
- US20120033754A1 US20120033754A1 US13/277,754 US201113277754A US2012033754A1 US 20120033754 A1 US20120033754 A1 US 20120033754A1 US 201113277754 A US201113277754 A US 201113277754A US 2012033754 A1 US2012033754 A1 US 2012033754A1
- Authority
- US
- United States
- Prior art keywords
- pilot symbols
- spaced
- regularly
- time
- subset
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Abandoned
Links
Images
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/003—Arrangements for allocating sub-channels of the transmission path
- H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/0202—Channel estimation
- H04L25/0224—Channel estimation using sounding signals
- H04L25/0226—Channel estimation using sounding signals sounding signals per se
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/0202—Channel estimation
- H04L25/0224—Channel estimation using sounding signals
- H04L25/0228—Channel estimation using sounding signals with direct estimation from sounding signals
- H04L25/023—Channel estimation using sounding signals with direct estimation from sounding signals with extension to other symbols
- H04L25/0232—Channel estimation using sounding signals with direct estimation from sounding signals with extension to other symbols by interpolation between sounding signals
Definitions
- the present invention generally relates to channel estimation, and more particularly relates to channel estimation for OFDM systems.
- the response of a wireless communication channel is estimated by a wireless receiver so that the receiver can coherently demodulate received data symbols.
- Channel estimation is typically performed using known symbols referred to as pilot symbols. Pilot symbols are transmitted in the time-frequency domain in OFDM (Orthogonal Frequency-Division Multiplexing) systems.
- the pilot symbols sample the time-frequency response of the OFDM channel which is a slow-varying, two-dimensional process.
- the response of an OFDM channel is conventionally estimated based on pilot symbols using minimum mean-square error estimation (MMSE), maximum-likelihood (ML) estimation or other approaches that are suboptimal such as interpolation.
- MMSE minimum mean-square error estimation
- ML maximum-likelihood
- MMSE channel estimation typically requires prior knowledge of channel statistics and tends to be highly complex because of the matrix inversion performed during the channel estimation process.
- the size of the matrix inversion performed by an MMSE estimator depends on the number of pilot symbol observations. In OFDM systems, pilot symbol density must be sufficiently large so that receiving devices can properly reconstruct an accurate representation of the time-frequency channel response. This in turn can dramatically increase the size of the matrix inversion performed by an MMSE channel estimator, significantly increasing MMSE estimation complexity.
- ML channel estimation also tends to be relatively complex, but not as complex as MMSE estimation. When pilot symbols are regularly spaced, ML estimation can be implemented using a two-dimensional FFT (fast-Fourier transform) process that yields the channel response in the delay-Doppler domain.
- FFT fast-Fourier transform
- the complexity of both MMSE and ML estimators tends to increase significantly when pilot symbol spacing is irregular.
- Many types of OFDM systems have high pilot symbol density and irregular pilot symbol spacing.
- IEEE the Institute of Electrical and Electronics Engineers
- 802 16e WiMAX
- Pilot spacing is also irregular, meaning that pilot symbols are transmitted at different time and frequency intervals.
- LTE Long Term Evolution
- 3GPP 3rd Generation Partnership Project
- the matrix inversion performed by a conventional MMSE estimator increases significantly when pilot symbol spacing is irregular.
- the complexity of a conventional ML estimator also increases when the estimator processes irregularly-spaced pilot symbols.
- An interpolation-based technique can be used to perform channel estimation when pilot symbol density is relatively high, but is sub-optimal and sacrifices accuracy for less complexity.
- the irregularly-spaced pilot symbols can be partitioned into at least two different groups of regularly-spaced pilot symbols in the time-frequency domain. Each group of regularly-spaced pilot symbols is individually processed with lower complexity and the results combined to generate an accurate time-frequency channel response estimate.
- a set of irregularly-spaced pilot symbols is transmitted over a time-frequency window.
- Channel response is estimated based on the pilot symbols by grouping the pilot symbols into subsets of regularly-spaced pilot symbols.
- An intermediate quantity is generated for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset.
- the channel response is estimated over the time-frequency window as a function of the intermediate quantities.
- FIG. 1 illustrates a block diagram of an embodiment of a wireless receiver.
- FIG. 2 illustrates an embodiment of a method for estimating channel response based on a set of irregularly-spaced pilot symbols transmitted over a time-frequency window.
- FIG. 3 illustrates a plot diagram of an embodiment of irregularly-spaced WiMAX pilot symbols grouped into subsets of regularly-spaced pilot symbols.
- FIG. 4 illustrates a plot diagram of an embodiment of irregularly-spaced LTE pilot symbols grouped into subsets of regularly-spaced pilot symbols.
- FIG. 5 illustrates an embodiment of a method for estimating channel response based on subsets of regularly-spaced pilot symbols.
- FIG. 6 illustrates another embodiment of a method for estimating channel response based on subsets of regularly-spaced pilot symbols.
- FIG. 1 illustrates an embodiment of a wireless receiver 100 such as a mobile phone or a wireless Local Area Network (LAN) adapter.
- the receiver 100 processes OFDM signals transmitted in the time-frequency domain, e.g., in accordance with LTE, WiMAX, etc. Irregularly-spaced pilot symbols are transmitted in the time-frequency domain to aid in channel estimation at the receiver 100 .
- the receiver 100 includes one or more antennas 110 , front end circuitry 120 , a baseband processor 130 and a post processor 140 .
- Each antenna 110 receives an OFDM signal transmitted over a multipath fading channel.
- Received signals are down-converted to corresponding baseband signals by the front end circuitry 120 such as one or more amplifiers, filters, mixers, digitizers, etc.
- the baseband processor 130 demodulates received data symbols based on an estimate of the channel.
- a channel estimator 132 included in or associated with the baseband processor 130 generates the channel estimate.
- a pilot symbol partition unit 134 included in or associated with the baseband processor 130 partitions the irregularly-spaced pilot symbols into at least two different groups of regularly-spaced pilot symbols in the time-frequency domain.
- the channel estimator 132 processes the smaller subsets of regularly-spaced pilot symbols to estimate the channel instead of a single larger set of irregularly-spaced pilot symbols, reducing channel estimation complexity while maintaining sufficient accuracy.
- the baseband processor 130 uses the channel estimate to obtain soft bit values from the demodulated data symbols, e.g., by weighting and combining various components of the baseband signal.
- the baseband processor 130 provides the soft bit values to the post processor 140 for subsequent processing such as error correction, etc.
- FIG. 2 illustrates an embodiment of program logic implemented by the baseband processor 130 for performing channel estimation.
- the program logic begins by the pilot symbol partition unit 134 grouping a set of irregularly-spaced pilot symbols into subsets of regularly-spaced pilot symbols in the time-frequency domain (Step 200 ).
- the channel estimator 132 generates an intermediate quantity for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset (Step 210 ).
- the channel estimator 132 also computes an estimate of the channel response as a function of the different intermediate quantities (Step 220 ).
- the baseband processor 130 uses the composite channel estimate obtained based on the pilot symbol groupings to demodulate received data symbols as is well known in the art.
- the irregularly-spaced pilot symbols are grouped into subsets of regularly-spaced pilot symbols based on a priori pilot spacing information.
- FIG. 3 shows an embodiment of how the pilot symbol partition unit 134 groups a set of irregularly-spaced pilot symbols based on a priori WiMAX pilot spacing information. Pilot symbols transmitted over a particular time-frequency window in accordance with WiMAX are irregularly spaced as shown in FIG. 3 .
- the pilot symbol partition unit 134 partitions the irregularly-spaced pilot symbol pattern into at least four subsets of regularly-spaced WiMAX pilot patterns and identifies the pilot symbols associated with each regularly-spaced pattern.
- the first regularly-spaced pattern has an initial frequency offset ( ⁇ ) of 0 and a time offset ( ⁇ ) of 4.
- the second regularly-spaced pattern has an initial frequency offset of 0 and a time offset of 8.
- the third regularly-spaced pattern has an initial frequency offset of 1 and a time offset of 0 and the fourth pattern has an initial frequency offset of 1 and a time offset of 12.
- FIG. 4 shows an embodiment of how the pilot symbol partition unit 134 groups a set of irregularly-spaced pilot symbols based on a priori LTE pilot spacing information.
- the pilot symbol partition unit 134 partitions the irregularly-spaced LTE pilot symbol pattern into at least two regularly-spaced pilot patterns over the time-frequency window.
- the first regularly-spaced pattern has an initial frequency offset ( ⁇ ) of 0 and a time offset ( ⁇ ) of 0.
- the second regularly-spaced pattern has an initial frequency offset of 4 and a time offset of 3.
- irregularly-spaced OFDM pilot symbols can be grouped into subsets of regularly-spaced pilot symbols by blindly detecting the communication mode used to transmit the pilot symbols.
- the baseband processor 130 and/or the pilot symbol partition unit 134 can determine if a pilot symbol pattern is irregular based on the communication mode, and if so, whether the irregular pattern can be partitioned into smaller, regularly-spaced patters.
- the communication mode may correspond to the transmission technology (e.g., WiMAX, LTE, etc.) or can be any other type of information relating to the communication of information over a wireless channel that can be used to determine pilot spacing.
- the pilot symbols are then grouped into subsets of regularly-spaced pilot symbols based on the communication mode.
- the channel estimator 132 generates a composite channel estimate based on the smaller subsets of regularly-spaced pilot symbols instead of a single larger set of irregularly-spaced pilot symbols.
- FIG. 5 illustrates one embodiment where the intermediate quantities derived by the channel estimator 132 for each subset of regularly-spaced pilot symbols are computed using an MMSE model.
- a discrete frequency domain received OFDM sample can be expressed as:
- the baseband processor 130 estimates the channel response H[t,f] based on known pilot symbols and uses the channel response H[t,f] to coherently demodulate received data symbols.
- the pilot observations X[t,f] can be concisely expressed in matrix form by arranging the observations into a column vector as given by:
- ⁇ 1 is a diagonal matrix containing the pilot symbols as diagonal elements and X 1 , H 1 and Z 1 are column vectors of the same size corresponding to the pilot observation, channel and noise, respectively.
- Equation (3) The column-vector form of equation (3) can be converted to matrix-form by introducing the subscript t as given by:
- the channel H[t, f] can be modeled as a two-dimensional, zero-mean White Sense Stationary (WSS) Gaussian random process having the following correlation:
- the channel correlation represented by equation (5) is typically known or can be estimated from past observation.
- the MMSE channel estimation can be formulated based on the channel statistics and the matrix representation of equation (4) as explained next.
- H denote the column vector containing the channel response at the locations to be estimated in the time-frequency domain.
- this can be any part of the 16 OFDM symbols by 56 frequency sub-carriers shown in the window area of FIG. 3 .
- the MMSE estimate of H is the mean of H conditioned on the observation X t as given by:
- H ⁇ ⁇ ( X t ) ⁇ E ⁇ ⁇ H
- ⁇ Ht E ⁇ H t H t H ⁇ denotes the auto covariance matrix of H t
- H HXt is the similarly defined covariance matrix between H and X t .
- the elements in the different covariance matrices can be derived using the channel correlation function of equation (5). Accordingly, the MMSE channel estimation process becomes a linear operation that transforms the pilot observation vector X t into a vector containing the channel estimates at the desired locations.
- the pilot symbol observations 500 corresponding to the i th regular pilot symbol pattern over the time-frequency window limited by the symbol range 0 ⁇ t ⁇ N SYM and the frequency sub-carrier range 0 ⁇ f ⁇ N SUB are given by:
- the intermediate quantity derived for each subset of regularly-spaced pilot symbols is an intermediate channel response estimate ⁇ i [t, f] 510 computed using equations (6) and (8) where the index i corresponds to the i th regularly-spaced pilot pattern 500 under consideration.
- each subset of regularly-spaced pilot symbols determined by the pilot symbol partition unit 134 is used to generate an intermediate MMSE channel estimate ⁇ i [t, f] 510 .
- a signal combiner 520 included in or associated with the channel estimator 132 combines the different intermediate MMSE channel estimates ⁇ i [t, f] to form a composite MMSE estimate of the channel as given by:
- FIG. 6 illustrates another embodiment where the intermediate quantities derived by the channel estimator 132 for each subset of regularly-spaced pilot symbols are computed using a delay-Doppler model.
- an intermediate delay-Doppler image 610 of the channel defined over the delay range 0 ⁇ K and the Doppler range 0 ⁇ v ⁇ Q and derived from the i th regular pilot pattern 600 is given by:
- Each intermediate delay-Doppler image I i [ ⁇ , v] 610 represents the two-dimensional DFT (discrete Fourier transform) of the observation 600 of size (Q,K) corresponding to the i th regular pilot symbol pattern. Patterns of different offsets ( ⁇ i , ⁇ i )are phase modulated by the leading term in equation (10).
- a signal combiner 620 included in or associated with the channel estimator 132 combines the different intermediate delay-Doppler images I i [ ⁇ ,v] 610 to obtain a composite delay-Doppler image as given by:
- the baseband processor 130 and/or the channel estimator 132 convert the composite delay-Doppler image I COMP [ ⁇ , v] from the delay-Doppler domain to the time-frequency domain to obtain a composite estimate ⁇ COMP of the channel.
- the composite delay-Doppler image is converted to the time-frequency domain by a two-dimensional inverse DFT (IDFT) function 630 of size(N SYM ,N SUB ).
- IDFT two-dimensional inverse DFT
- the composite delay-Doppler image I COMP [ ⁇ ,v] is filtered before conversion to the time-frequency domain.
- the two-dimensional IDFT function 630 is performed over the entire time-frequency window to yield the composite channel estimate ⁇ COMP as given by:
- W[ ⁇ ,v] is a windowing function for removing sampling artifacts.
- the windowing function W[ ⁇ ,v] is a two-dimensional brick-wall filter that eliminates non-zero elements of the composite delay-Doppler image outside the maximum delay-Doppler spread as given by:
Landscapes
- Engineering & Computer Science (AREA)
- Signal Processing (AREA)
- Computer Networks & Wireless Communication (AREA)
- Power Engineering (AREA)
- Mobile Radio Communication Systems (AREA)
Abstract
Smaller patterns of regularly-spaced pilot symbols are discerned from a larger pattern of irregularly-spaced pilot symbols transmitted in the time-frequency domain. Accordingly, the irregularly-spaced pilot symbols can be partitioned into at least two different groups of regularly-spaced pilot symbols in the time-frequency domain. Each group of regularly-spaced pilot symbols is individually processed with lower complexity and the results combined to generate an accurate time-frequency channel response estimate. According to an embodiment, a set of irregularly-spaced pilot symbols is transmitted over a time-frequency window. Channel response is estimated based on the pilot symbols by grouping the pilot symbols into subsets of regularly-spaced pilot symbols. An intermediate quantity is generated for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset. The channel response is estimated over the time-frequency window as a function of the intermediate quantities.
Description
- This application is a continuation of U.S. application Ser. No. 12/265,220, filed Nov. 5, 2008, now pending, the disclosure of which is incorporated herein by reference.
- The present invention generally relates to channel estimation, and more particularly relates to channel estimation for OFDM systems.
- The response of a wireless communication channel is estimated by a wireless receiver so that the receiver can coherently demodulate received data symbols. Channel estimation is typically performed using known symbols referred to as pilot symbols. Pilot symbols are transmitted in the time-frequency domain in OFDM (Orthogonal Frequency-Division Multiplexing) systems. The pilot symbols sample the time-frequency response of the OFDM channel which is a slow-varying, two-dimensional process. The response of an OFDM channel is conventionally estimated based on pilot symbols using minimum mean-square error estimation (MMSE), maximum-likelihood (ML) estimation or other approaches that are suboptimal such as interpolation.
- MMSE channel estimation typically requires prior knowledge of channel statistics and tends to be highly complex because of the matrix inversion performed during the channel estimation process. The size of the matrix inversion performed by an MMSE estimator depends on the number of pilot symbol observations. In OFDM systems, pilot symbol density must be sufficiently large so that receiving devices can properly reconstruct an accurate representation of the time-frequency channel response. This in turn can dramatically increase the size of the matrix inversion performed by an MMSE channel estimator, significantly increasing MMSE estimation complexity. ML channel estimation also tends to be relatively complex, but not as complex as MMSE estimation. When pilot symbols are regularly spaced, ML estimation can be implemented using a two-dimensional FFT (fast-Fourier transform) process that yields the channel response in the delay-Doppler domain.
- The complexity of both MMSE and ML estimators tends to increase significantly when pilot symbol spacing is irregular. Many types of OFDM systems have high pilot symbol density and irregular pilot symbol spacing. For example, the downlink specified in IEEE (the Institute of Electrical and Electronics Engineers) standard 802 16e (WiMAX) has 120 pilots for each OFDM symbol. Pilot spacing is also irregular, meaning that pilot symbols are transmitted at different time and frequency intervals. The Long Term Evolution (LTE) standard specified in
Release 8 of 3GPP (3rd Generation Partnership Project) also calls for irregular pilot symbol spacing. The matrix inversion performed by a conventional MMSE estimator increases significantly when pilot symbol spacing is irregular. The complexity of a conventional ML estimator also increases when the estimator processes irregularly-spaced pilot symbols. An interpolation-based technique can be used to perform channel estimation when pilot symbol density is relatively high, but is sub-optimal and sacrifices accuracy for less complexity. - SUMMARY
- Smaller patterns of regularly-spaced pilot symbols can be discerned from a larger pattern of irregularly-spaced pilot symbols transmitted in the time-frequency domain. Accordingly, the irregularly-spaced pilot symbols can be partitioned into at least two different groups of regularly-spaced pilot symbols in the time-frequency domain. Each group of regularly-spaced pilot symbols is individually processed with lower complexity and the results combined to generate an accurate time-frequency channel response estimate.
- According to an embodiment, a set of irregularly-spaced pilot symbols is transmitted over a time-frequency window. Channel response is estimated based on the pilot symbols by grouping the pilot symbols into subsets of regularly-spaced pilot symbols. An intermediate quantity is generated for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset. The channel response is estimated over the time-frequency window as a function of the intermediate quantities.
- Of course, the present invention is not limited to the above features and advantages. Those skilled in the art will recognize additional features and advantages upon reading the following detailed description, and upon viewing the accompanying drawings.
-
FIG. 1 illustrates a block diagram of an embodiment of a wireless receiver. -
FIG. 2 illustrates an embodiment of a method for estimating channel response based on a set of irregularly-spaced pilot symbols transmitted over a time-frequency window. -
FIG. 3 illustrates a plot diagram of an embodiment of irregularly-spaced WiMAX pilot symbols grouped into subsets of regularly-spaced pilot symbols. -
FIG. 4 illustrates a plot diagram of an embodiment of irregularly-spaced LTE pilot symbols grouped into subsets of regularly-spaced pilot symbols. -
FIG. 5 illustrates an embodiment of a method for estimating channel response based on subsets of regularly-spaced pilot symbols. -
FIG. 6 illustrates another embodiment of a method for estimating channel response based on subsets of regularly-spaced pilot symbols. -
FIG. 1 illustrates an embodiment of awireless receiver 100 such as a mobile phone or a wireless Local Area Network (LAN) adapter. Thereceiver 100 processes OFDM signals transmitted in the time-frequency domain, e.g., in accordance with LTE, WiMAX, etc. Irregularly-spaced pilot symbols are transmitted in the time-frequency domain to aid in channel estimation at thereceiver 100. Thereceiver 100 includes one ormore antennas 110,front end circuitry 120, abaseband processor 130 and apost processor 140. Eachantenna 110 receives an OFDM signal transmitted over a multipath fading channel. Received signals are down-converted to corresponding baseband signals by thefront end circuitry 120 such as one or more amplifiers, filters, mixers, digitizers, etc. Thebaseband processor 130 demodulates received data symbols based on an estimate of the channel. Achannel estimator 132 included in or associated with thebaseband processor 130 generates the channel estimate. A pilotsymbol partition unit 134 included in or associated with thebaseband processor 130 partitions the irregularly-spaced pilot symbols into at least two different groups of regularly-spaced pilot symbols in the time-frequency domain. Thechannel estimator 132 processes the smaller subsets of regularly-spaced pilot symbols to estimate the channel instead of a single larger set of irregularly-spaced pilot symbols, reducing channel estimation complexity while maintaining sufficient accuracy. Thebaseband processor 130 uses the channel estimate to obtain soft bit values from the demodulated data symbols, e.g., by weighting and combining various components of the baseband signal. Thebaseband processor 130 provides the soft bit values to thepost processor 140 for subsequent processing such as error correction, etc. -
FIG. 2 illustrates an embodiment of program logic implemented by thebaseband processor 130 for performing channel estimation. The program logic begins by the pilotsymbol partition unit 134 grouping a set of irregularly-spaced pilot symbols into subsets of regularly-spaced pilot symbols in the time-frequency domain (Step 200). Thechannel estimator 132 generates an intermediate quantity for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset (Step 210). Thechannel estimator 132 also computes an estimate of the channel response as a function of the different intermediate quantities (Step 220). Thebaseband processor 130 uses the composite channel estimate obtained based on the pilot symbol groupings to demodulate received data symbols as is well known in the art. According to one embodiment, the irregularly-spaced pilot symbols are grouped into subsets of regularly-spaced pilot symbols based on a priori pilot spacing information. -
FIG. 3 shows an embodiment of how the pilotsymbol partition unit 134 groups a set of irregularly-spaced pilot symbols based on a priori WiMAX pilot spacing information. Pilot symbols transmitted over a particular time-frequency window in accordance with WiMAX are irregularly spaced as shown inFIG. 3 . The pilotsymbol partition unit 134 partitions the irregularly-spaced pilot symbol pattern into at least four subsets of regularly-spaced WiMAX pilot patterns and identifies the pilot symbols associated with each regularly-spaced pattern. The first regularly-spaced pattern has an initial frequency offset (φ) of 0 and a time offset (ψ) of 4. The second regularly-spaced pattern has an initial frequency offset of 0 and a time offset of 8. The third regularly-spaced pattern has an initial frequency offset of 1 and a time offset of 0 and the fourth pattern has an initial frequency offset of 1 and a time offset of 12. The pilot symbols included in each subset are regularly-spaced apart in frequency (M=14 sub-carriers) and time (N=2). -
FIG. 4 shows an embodiment of how the pilotsymbol partition unit 134 groups a set of irregularly-spaced pilot symbols based on a priori LTE pilot spacing information. The pilotsymbol partition unit 134 partitions the irregularly-spaced LTE pilot symbol pattern into at least two regularly-spaced pilot patterns over the time-frequency window. The first regularly-spaced pattern has an initial frequency offset (φ) of 0 and a time offset (ψ) of 0. The second regularly-spaced pattern has an initial frequency offset of 4 and a time offset of 3. The pilot symbols included in each subset are regularly-spaced apart in frequency (M=6 sub-carriers) and time (N=7). - In yet another embodiment, irregularly-spaced OFDM pilot symbols can be grouped into subsets of regularly-spaced pilot symbols by blindly detecting the communication mode used to transmit the pilot symbols. The
baseband processor 130 and/or the pilotsymbol partition unit 134 can determine if a pilot symbol pattern is irregular based on the communication mode, and if so, whether the irregular pattern can be partitioned into smaller, regularly-spaced patters. The communication mode may correspond to the transmission technology (e.g., WiMAX, LTE, etc.) or can be any other type of information relating to the communication of information over a wireless channel that can be used to determine pilot spacing. The pilot symbols are then grouped into subsets of regularly-spaced pilot symbols based on the communication mode. In each pilot grouping embodiment, thechannel estimator 132 generates a composite channel estimate based on the smaller subsets of regularly-spaced pilot symbols instead of a single larger set of irregularly-spaced pilot symbols. -
FIG. 5 illustrates one embodiment where the intermediate quantities derived by thechannel estimator 132 for each subset of regularly-spaced pilot symbols are computed using an MMSE model. In more detail, a discrete frequency domain received OFDM sample can be expressed as: -
X[t,f]=H[t,f]A[t,f]+Z[t,f] (1) - where the index [t,f] corresponds to the fth frequency sub-carrier in the tth OFDM symbol, H[t,f] is the time-frequency response of the channel at a particular point, Λ[t,f] is the transmitted symbol and Z[t,f] represents Additive White Gaussian Noise (AWGN). The
baseband processor 130 estimates the channel response H[t,f] based on known pilot symbols and uses the channel response H[t,f] to coherently demodulate received data symbols. The pilot observations X[t,f] can be concisely expressed in matrix form by arranging the observations into a column vector as given by: -
X 1=Λ1 H 1 +Z 1 (2) - where Λ1 is a diagonal matrix containing the pilot symbols as diagonal elements and X1, H1 and Z1 are column vectors of the same size corresponding to the pilot observation, channel and noise, respectively.
- The observations from all regular pilots can be stacked into a column vector as given by:
-
- The column-vector form of equation (3) can be converted to matrix-form by introducing the subscript t as given by:
-
X t=Λt H t +Z t (4) - In one embodiment, the channel H[t, f] can be modeled as a two-dimensional, zero-mean White Sense Stationary (WSS) Gaussian random process having the following correlation:
-
Γ[t1−t2]≡E{H[t1,f1]H*[t2f2]} (5) - The channel correlation represented by equation (5) is typically known or can be estimated from past observation. The MMSE channel estimation can be formulated based on the channel statistics and the matrix representation of equation (4) as explained next.
- In more detail, let H denote the column vector containing the channel response at the locations to be estimated in the time-frequency domain. For example, this can be any part of the 16 OFDM symbols by 56 frequency sub-carriers shown in the window area of
FIG. 3 . The MMSE estimate of H is the mean of H conditioned on the observation Xt as given by: -
- where ΠHt=E{HtHt H} denotes the auto covariance matrix of Ht, ΠHHt=E{HHt H} is the covariance matrix between H and Ht and HHXt is the similarly defined covariance matrix between H and Xt. The elements in the different covariance matrices can be derived using the channel correlation function of equation (5). Accordingly, the MMSE channel estimation process becomes a linear operation that transforms the pilot observation vector Xt into a vector containing the channel estimates at the desired locations.
- The
pilot symbol observations 500 corresponding to the ith regular pilot symbol pattern over the time-frequency window limited by thesymbol range 0≦t<NSYM and thefrequency sub-carrier range 0≦f<NSUB are given by: -
- where φi represents frequency offset, ψi represents time offset, 0≦n<Q, 0≦m<K, NSYM=NQ and NSUB=MK . A more concise matrix expression of equation (4) when considering i subsets of regularly-spaced pilot symbols is given by:
-
X i;n,m=Λi H i;n,m +Z i;n,m (8) - According to the MMSE estimation embodiment, the intermediate quantity derived for each subset of regularly-spaced pilot symbols is an intermediate channel response estimate Ĥi[t, f] 510 computed using equations (6) and (8) where the index i corresponds to the ith regularly-spaced
pilot pattern 500 under consideration. Thus, each subset of regularly-spaced pilot symbols determined by the pilotsymbol partition unit 134 is used to generate an intermediate MMSE channel estimate Ĥi[t, f] 510. Asignal combiner 520 included in or associated with thechannel estimator 132 combines the different intermediate MMSE channel estimates Ĥi[t, f] to form a composite MMSE estimate of the channel as given by: -
-
FIG. 6 illustrates another embodiment where the intermediate quantities derived by thechannel estimator 132 for each subset of regularly-spaced pilot symbols are computed using a delay-Doppler model. In more detail, an intermediate delay-Doppler image 610 of the channel defined over thedelay range 0≦τ<K and theDoppler range 0≦v<Q and derived from the ithregular pilot pattern 600 is given by: -
- Each intermediate delay-Doppler image Ii[τ, v] 610 represents the two-dimensional DFT (discrete Fourier transform) of the
observation 600 of size (Q,K) corresponding to the ithregular pilot symbol pattern. Patterns of different offsets (φi,ψi)are phase modulated by the leading term in equation (10). Asignal combiner 620 included in or associated with thechannel estimator 132 combines the different intermediate delay-Doppler images Ii[τ,v] 610 to obtain a composite delay-Doppler image as given by: -
- The
baseband processor 130 and/or thechannel estimator 132 convert the composite delay-Doppler image ICOMP[τ, v] from the delay-Doppler domain to the time-frequency domain to obtain a composite estimate ĤCOMP of the channel. In one embodiment, the composite delay-Doppler image is converted to the time-frequency domain by a two-dimensional inverse DFT (IDFT) function 630 of size(NSYM,NSUB). In one embodiment, the composite delay-Doppler image ICOMP[τ,v] is filtered before conversion to the time-frequency domain. According to this embodiment, the two-dimensional IDFT function 630 is performed over the entire time-frequency window to yield the composite channel estimate ĤCOMP as given by: -
- where W[τ,v] is a windowing function for removing sampling artifacts. In one embodiment, the windowing function W[τ,v] is a two-dimensional brick-wall filter that eliminates non-zero elements of the composite delay-Doppler image outside the maximum delay-Doppler spread as given by:
-
- With the above range of variations and applications in mind, it should be understood that the present invention is not limited by the foregoing description, nor is it limited by the accompanying drawings. Instead, the present invention is limited only by the following claims, and their legal equivalents.
Claims (22)
1. A method of estimating channel response based on a set of irregularly-spaced pilot symbols transmitted over a time-frequency window, the method comprising:
grouping the pilot symbols into subsets of regularly-spaced pilot symbols;
generating an intermediate quantity for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset; and
estimating the channel response over the time-frequency window as a function of the intermediate quantities.
2. The method of claim 1 , comprising grouping the pilot symbols into subsets of regularly-spaced pilot symbols based on a priori pilot spacing information.
3. The method of claim 1 , wherein grouping the pilot symbols into subsets of regularly-spaced pilot symbols comprises:
blindly detecting a communication mode used to transmit the pilot symbols; and
grouping the pilot symbols into the subsets of regularly-spaced pilot symbols based on the communication mode.
4. The method of claim 1 , wherein grouping the pilot symbols into subsets of regularly-spaced pilot symbols comprises:
partitioning an irregularly-spaced pilot symbol pattern into a plurality of regularly-spaced pilot symbol patterns over the time-frequency window; and
identifying the pilot symbols associated with each regularly-spaced pilot symbol pattern.
5. The method of claim 4 , comprising partitioning the irregularly-spaced pilot symbol pattern into at least four regularly-spaced WiMax pilot symbol patterns over the time-frequency window.
6. The method of claim 4 , comprising partitioning the irregularly-spaced pilot symbol pattern into at least two regularly-spaced LTE pilot symbol patterns over the time-frequency window.
7. The method of claim 1 , wherein generating an intermediate quantity for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset comprises generating an intermediate minimum mean-square error channel estimate for each subset.
8. The method of claim 7 , wherein estimating the channel response as a function of the intermediate quantities comprises combining the intermediate minimum mean-square error channel estimates to form a composite minimum mean-square error channel estimate.
9. The method of claim 1 , wherein generating an intermediate quantity for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset comprises generating an intermediate delay-Doppler image for each subset.
10. The method of claim 9 , wherein estimating the channel response as a function of the intermediate quantities comprises:
combining the intermediate delay-Doppler images to form a composite delay-Doppler image; and
converting the composite delay-Doppler image from the delay-Doppler domain to the time-frequency domain.
11. The method of claim 10 , further comprising filtering the composite delay-Doppler image before conversion to the time-frequency domain.
12. The method of claim 11 , wherein filtering the composite delay-Doppler image before conversion to the time-frequency domain comprises reducing non-zero elements of the composite delay-Doppler image outside a predetermined delay-Doppler spread.
13. A receiver comprising a baseband processor configured to:
group a set of irregularly-spaced pilot symbols transmitted over a time-frequency window into subsets of regularly-spaced pilot symbols;
generate an intermediate quantity for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset; and
estimate channel response over the time-frequency window as a function of the intermediate quantities.
14. The receiver of claim 13 , wherein the baseband processor is configured to group the pilot symbols into subsets of regularly-spaced pilot symbols based on a priori pilot spacing information.
15. The receiver of claim 13 , wherein the baseband processor is configured to blindly detect a communication mode used to transmit the pilot symbols and group the pilot symbols into the subsets of regularly-spaced pilot symbols based on the communication mode.
16. The receiver of claim 13 , wherein the baseband processor is configured to partition an irregularly-spaced pilot symbol pattern into a plurality of regularly-spaced pilot symbol patterns over the time-frequency window and identify the pilot symbols associated with each regularly-spaced pilot symbol pattern.
17. The receiver of claim 16 , wherein the baseband processor is configured to partition the irregularly-spaced pilot symbol pattern into at least four regularly-spaced WiMax pilot symbol patterns over the time-frequency window.
18. The receiver of claim 16 , wherein the baseband processor is configured to partition the irregularly-spaced pilot symbol pattern into at least two regularly-spaced LTE pilot symbol patterns over the time-frequency window.
19. The receiver of claim 13 , wherein the baseband processor is configured to generate an intermediate minimum mean-square error channel estimate for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset.
20. The receiver of claim 19 , wherein the baseband processor is configured to combine the intermediate minimum mean-square error channel estimates to form a composite minimum mean-square error channel estimate.
21. The receiver of claim 13 , wherein the baseband processor is configured to generate an intermediate delay-Doppler image for each subset of regularly-spaced pilot symbols as a function of the pilot symbols included in the subset.
22. The receiver of claim 21 , wherein the baseband processor is configured to combine the intermediate delay-Doppler images to form a composite delay-Doppler image and convert the composite delay-Doppler image from the delay-Doppler domain to the time-frequency domain.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US13/277,754 US20120033754A1 (en) | 2008-11-05 | 2011-10-20 | Ofdm channel estimation method and apparatus |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US12/265,220 US8111787B2 (en) | 2008-11-05 | 2008-11-05 | OFDM channel estimation method and apparatus |
US13/277,754 US20120033754A1 (en) | 2008-11-05 | 2011-10-20 | Ofdm channel estimation method and apparatus |
Related Parent Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US12/265,220 Continuation US8111787B2 (en) | 2008-11-05 | 2008-11-05 | OFDM channel estimation method and apparatus |
Publications (1)
Publication Number | Publication Date |
---|---|
US20120033754A1 true US20120033754A1 (en) | 2012-02-09 |
Family
ID=41690259
Family Applications (2)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US12/265,220 Active 2030-07-15 US8111787B2 (en) | 2008-11-05 | 2008-11-05 | OFDM channel estimation method and apparatus |
US13/277,754 Abandoned US20120033754A1 (en) | 2008-11-05 | 2011-10-20 | Ofdm channel estimation method and apparatus |
Family Applications Before (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US12/265,220 Active 2030-07-15 US8111787B2 (en) | 2008-11-05 | 2008-11-05 | OFDM channel estimation method and apparatus |
Country Status (4)
Country | Link |
---|---|
US (2) | US8111787B2 (en) |
EP (1) | EP2353262B1 (en) |
CN (1) | CN102204197B (en) |
WO (1) | WO2010052539A1 (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20130070869A1 (en) * | 2011-09-20 | 2013-03-21 | Qualcomm Incorporated | Channel impulse response estimation for wireless receiver |
CN110971547A (en) * | 2019-11-20 | 2020-04-07 | 浙江大学 | Millimeter wave/terahertz-based broadband large-scale terminal detection and channel estimation method |
Families Citing this family (10)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US9203654B2 (en) | 2013-11-26 | 2015-12-01 | Plusn Llc | System and method for radio frequency carrier aggregation |
CN102223340B (en) * | 2011-06-20 | 2013-12-11 | 电子科技大学 | Terabit transmission rate coherent light orthogonal frequency division multiplexing (OFDM) system based on optical comb |
WO2014155650A1 (en) * | 2013-03-29 | 2014-10-02 | 株式会社日立製作所 | Information controller, information control system, and information control method |
EP3613243B1 (en) | 2017-04-21 | 2022-08-24 | Cohere Technologies, Inc. | Communication techniques using quasi-static properties of wireless channels |
CN110177062B (en) * | 2019-04-15 | 2020-07-10 | 浙江大学 | Terminal activation detection and channel estimation method |
US10979151B2 (en) * | 2019-05-22 | 2021-04-13 | At&T Intellectual Property I, L.P. | Multidimensional grid sampling for radio frequency power feedback |
US10886991B2 (en) * | 2019-05-22 | 2021-01-05 | At&T Intellectual Property I, L.P. | Facilitating sparsity adaptive feedback in the delay doppler domain in advanced networks |
US11824637B2 (en) | 2019-05-22 | 2023-11-21 | At&T Intellectual Property I, L.P. | Generating wireless reference signals in a different domain for transmission |
US11050530B2 (en) | 2019-06-27 | 2021-06-29 | At&T Intellectual Property I, L.P. | Generating wireless reference signals in a different domain for transmission with a collapsed time-frequency grid |
US11606240B1 (en) * | 2021-09-30 | 2023-03-14 | Silicon Laboratories Inc. | Using preamble portion having irregular carrier spacing for frequency synchronization |
Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20070211806A1 (en) * | 2006-03-10 | 2007-09-13 | Beceem Communications Inc. | System and method for channel estimation |
US20070263752A1 (en) * | 2006-05-11 | 2007-11-15 | Telefonaktiebolaget Lm Ericsson (Publ) | Delay-doppler channel response demodulation method and apparatus |
US20080165734A1 (en) * | 2006-12-21 | 2008-07-10 | Michael John Beems Hart | Communication systems |
US20090274200A1 (en) * | 2008-05-05 | 2009-11-05 | Muhammad Zubair Ikram | System and Method for Time Domain Interpolation of Signals for Channel Estimation |
US20100040156A1 (en) * | 2007-08-15 | 2010-02-18 | Mbit Wireless, Inc. | Dual-pass joint channel estimation and data demodulation for OFDM systems |
Family Cites Families (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2007029052A1 (en) | 2005-09-09 | 2007-03-15 | Freescale Semiconductor, Inc. | A receiver and a method for channel estimation |
CN1992690B (en) * | 2005-12-26 | 2010-05-05 | 华为技术有限公司 | Emitting method of pilot data, base station controller, channel evaluation method and apparatus |
-
2008
- 2008-11-05 US US12/265,220 patent/US8111787B2/en active Active
-
2009
- 2009-11-02 EP EP09756569.1A patent/EP2353262B1/en active Active
- 2009-11-02 CN CN200980144596.XA patent/CN102204197B/en active Active
- 2009-11-02 WO PCT/IB2009/007287 patent/WO2010052539A1/en active Application Filing
-
2011
- 2011-10-20 US US13/277,754 patent/US20120033754A1/en not_active Abandoned
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20070211806A1 (en) * | 2006-03-10 | 2007-09-13 | Beceem Communications Inc. | System and method for channel estimation |
US20070263752A1 (en) * | 2006-05-11 | 2007-11-15 | Telefonaktiebolaget Lm Ericsson (Publ) | Delay-doppler channel response demodulation method and apparatus |
US20080165734A1 (en) * | 2006-12-21 | 2008-07-10 | Michael John Beems Hart | Communication systems |
US20100040156A1 (en) * | 2007-08-15 | 2010-02-18 | Mbit Wireless, Inc. | Dual-pass joint channel estimation and data demodulation for OFDM systems |
US20090274200A1 (en) * | 2008-05-05 | 2009-11-05 | Muhammad Zubair Ikram | System and Method for Time Domain Interpolation of Signals for Channel Estimation |
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20130070869A1 (en) * | 2011-09-20 | 2013-03-21 | Qualcomm Incorporated | Channel impulse response estimation for wireless receiver |
US8718210B2 (en) * | 2011-09-20 | 2014-05-06 | Qualcomm Incorporated | Channel impulse response estimation for wireless receiver |
CN110971547A (en) * | 2019-11-20 | 2020-04-07 | 浙江大学 | Millimeter wave/terahertz-based broadband large-scale terminal detection and channel estimation method |
Also Published As
Publication number | Publication date |
---|---|
CN102204197A (en) | 2011-09-28 |
WO2010052539A1 (en) | 2010-05-14 |
EP2353262A1 (en) | 2011-08-10 |
US20100111231A1 (en) | 2010-05-06 |
US8111787B2 (en) | 2012-02-07 |
CN102204197B (en) | 2014-03-05 |
EP2353262B1 (en) | 2014-04-16 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
US8111787B2 (en) | OFDM channel estimation method and apparatus | |
CN101945073B (en) | Pilot frequency-based time offset estimation device and method | |
US7907593B2 (en) | Staggered pilot transmission for channel estimation and time tracking | |
US8553822B2 (en) | Time filtering for excess delay mitigation in OFDM systems | |
US8654879B2 (en) | Multi-antenna channel estimation method based on polyphase decomposition | |
US8605804B2 (en) | Method of channel estimation and a channel estimator | |
US8396169B2 (en) | Channel estimation method of the mobile communication system based on the time division pilot field | |
US8275053B2 (en) | Apparatus and method of estimating channel based on channel delay spread in mobile communication system | |
CN101064571B (en) | Apparatus for enhancing channel evaluation in OFDM receiver and its method | |
US8379773B2 (en) | Method and apparatus for enhanced channel estimation in wireless communication systems | |
US20100074348A1 (en) | Fine symbol timing synchronization method and apparatus in ofdm system | |
US6990153B1 (en) | Method and apparatus for semi-blind communication channel estimation | |
JP2008510362A (en) | Residual frequency offset determination method, communication system, message transmission method, transmitter, message processing method, and receiver | |
WO2006006044A1 (en) | High doppler channel estimation for ofd multiple antenna systems | |
CN105337906B (en) | Channel estimation methods and device | |
CN101939933A (en) | Methods relating to channel estimation | |
WO2012093333A1 (en) | Method of channel estimation, method of selecting pilot information, user equipment, and base station | |
Bhattacharjee et al. | Evaluation of orthogonal chirp division multiplexing for automotive integrated sensing and communications | |
US20090060063A1 (en) | Method and Apparatus for Robust Control Signaling Distribution in OFDM Systems | |
CN109617851B (en) | Channel estimation method and device based on DFT smooth filtering | |
CN101488939B (en) | Method, apparatus and receiver for implementing symbol synchronization in wireless communication system | |
CN106105121B (en) | For obtaining the method and apparatus of downlink data in extensive mimo system | |
CN103139108B (en) | A kind of three-dimensional MMSE channel estimation methods | |
US8457253B2 (en) | Apparatus and method for estimating a channel in a broadband wireless communication system | |
JP2012105079A (en) | Radio communication system, transmitter and receiver |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
AS | Assignment |
Owner name: TELEFONAKTIEBOLAGET LM ERICSSON (PUBL), SWEDEN Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:KOORAPATY, HAVISH;GUEY, JIANN-CHING;REEL/FRAME:027264/0377 Effective date: 20081105 |
|
STCB | Information on status: application discontinuation |
Free format text: ABANDONED -- FAILURE TO RESPOND TO AN OFFICE ACTION |