US11920960B2 - Capacitive measuring system - Google Patents

Capacitive measuring system Download PDF

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Publication number
US11920960B2
US11920960B2 US16/983,330 US202016983330A US11920960B2 US 11920960 B2 US11920960 B2 US 11920960B2 US 202016983330 A US202016983330 A US 202016983330A US 11920960 B2 US11920960 B2 US 11920960B2
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Prior art keywords
synchronous rectifier
signal
capacitive
multiplexer
measuring system
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US16/983,330
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US20200361408A1 (en
Inventor
Torben Zeleny
Uwe Borgmann
Jan Freiwald
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Kostal Automobil Elektrik GmbH and Co KG
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Kostal Automobil Elektrik GmbH and Co KG
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Assigned to KOSTAL AUTOMOBIL ELEKTRIK GMBH & CO. KG reassignment KOSTAL AUTOMOBIL ELEKTRIK GMBH & CO. KG ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: BORGMANN, UWE, Freiwald, Jan, ZELENY, Torben
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01D—MEASURING NOT SPECIALLY ADAPTED FOR A SPECIFIC VARIABLE; ARRANGEMENTS FOR MEASURING TWO OR MORE VARIABLES NOT COVERED IN A SINGLE OTHER SUBCLASS; TARIFF METERING APPARATUS; MEASURING OR TESTING NOT OTHERWISE PROVIDED FOR
    • G01D5/00—Mechanical means for transferring the output of a sensing member; Means for converting the output of a sensing member to another variable where the form or nature of the sensing member does not constrain the means for converting; Transducers not specially adapted for a specific variable
    • G01D5/12—Mechanical means for transferring the output of a sensing member; Means for converting the output of a sensing member to another variable where the form or nature of the sensing member does not constrain the means for converting; Transducers not specially adapted for a specific variable using electric or magnetic means
    • G01D5/14—Mechanical means for transferring the output of a sensing member; Means for converting the output of a sensing member to another variable where the form or nature of the sensing member does not constrain the means for converting; Transducers not specially adapted for a specific variable using electric or magnetic means influencing the magnitude of a current or voltage
    • G01D5/24—Mechanical means for transferring the output of a sensing member; Means for converting the output of a sensing member to another variable where the form or nature of the sensing member does not constrain the means for converting; Transducers not specially adapted for a specific variable using electric or magnetic means influencing the magnitude of a current or voltage by varying capacitance
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60R—VEHICLES, VEHICLE FITTINGS, OR VEHICLE PARTS, NOT OTHERWISE PROVIDED FOR
    • B60R21/00—Arrangements or fittings on vehicles for protecting or preventing injuries to occupants or pedestrians in case of accidents or other traffic risks
    • B60R21/01—Electrical circuits for triggering passive safety arrangements, e.g. airbags, safety belt tighteners, in case of vehicle accidents or impending vehicle accidents
    • B60R21/015—Electrical circuits for triggering passive safety arrangements, e.g. airbags, safety belt tighteners, in case of vehicle accidents or impending vehicle accidents including means for detecting the presence or position of passengers, passenger seats or child seats, and the related safety parameters therefor, e.g. speed or timing of airbag inflation in relation to occupant position or seat belt use
    • B60R21/01512—Passenger detection systems
    • B60R21/0153—Passenger detection systems using field detection presence sensors
    • B60R21/01532—Passenger detection systems using field detection presence sensors using electric or capacitive field sensors
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R27/00—Arrangements for measuring resistance, reactance, impedance, or electric characteristics derived therefrom
    • G01R27/02—Measuring real or complex resistance, reactance, impedance, or other two-pole characteristics derived therefrom, e.g. time constant
    • G01R27/26—Measuring inductance or capacitance; Measuring quality factor, e.g. by using the resonance method; Measuring loss factor; Measuring dielectric constants ; Measuring impedance or related variables
    • G01R27/2605—Measuring capacitance
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/94—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the way in which the control signals are generated
    • H03K17/96—Touch switches
    • H03K17/962—Capacitive touch switches
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
    • H03K2217/94—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00 characterised by the way in which the control signal is generated
    • H03K2217/9401—Calibration techniques
    • H03K2217/94026—Automatic threshold calibration; e.g. threshold automatically adapts to ambient conditions or follows variation of input
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
    • H03K2217/94—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00 characterised by the way in which the control signal is generated
    • H03K2217/96—Touch switches
    • H03K2217/9607—Capacitive touch switches
    • H03K2217/960755—Constructional details of capacitive touch and proximity switches
    • H03K2217/960765—Details of shielding arrangements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
    • H03K2217/94—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00 characterised by the way in which the control signal is generated
    • H03K2217/96—Touch switches
    • H03K2217/9607—Capacitive touch switches
    • H03K2217/960755—Constructional details of capacitive touch and proximity switches
    • H03K2217/96078—Sensor being a wire or a strip, e.g. used in automobile door handles or bumpers

Definitions

  • the present invention relates to a capacitive measuring system having multiple capacitive sensors and an evaluation circuit including a multi-channel, analog multiplexer and a synchronous rectifier, wherein the capacitive sensors are acted on by a mono-frequency voltage signal, output signals of the capacitive sensors are connected in alternation to the synchronous rectifier via the multiplexer, and signal amplification of output signals of the synchronous rectifier may be calibrated as a function of an activatable reference impedance.
  • capacitive measuring systems For determining capacitance values, capacitive measuring systems often use multi-frequency methods that employ a charge pump and an integrator. A conductive surface that forms a capacitor with ground is charged over multiple cycles, and the charges are stored in an integration capacitor. After a measuring cycle ends, the voltage is then evaluated via the integration capacitor.
  • EMC electromagnetic compatibility
  • the present invention relates to a capacitive measuring system for determining small changes in capacitance on large reference capacitors, making use of a mono-frequency measuring signal.
  • Such measuring systems may be used, for example, in motor vehicles for hands on/off detection on the steering wheel, for seat occupancy recognition, in capacitive pedals, occupancy recognition mats in the trunk, and for large surface switches in general.
  • DE 11 2014 001 880 T5 discloses a generic capacitive measuring system having an antenna electrode and an evaluation circuit.
  • the antenna electrode generates an alternating electric field as a reaction to an alternating voltage supplied to the antenna electrode.
  • the evaluation circuit has a transimpedance amplifier which, by supplying a current to the antenna electrode, holds the alternating voltage equal to a reference alternating voltage on a reference voltage node and measures the current.
  • the evaluation circuit further has a multiplexer and a microcontroller configured to control the multiplexer. The multiplexer switches the antenna electrode to a current input of the transimpedance amplifier and to the reference alternating voltage node in alternation.
  • the current input node of the transimpedance amplifier is alternating current-coupled to the reference voltage node by a protective capacitor.
  • a disadvantage of this capacitive measuring system is that the transimpedance amplifier and the multiplexer require the use of numerous active components that are significantly influenced by environmental conditions, in particular the ambient temperature.
  • a steering wheel sensor system would require, for example, letting go of the steering wheel during a calibration operation.
  • An object is a generic capacitive measuring system that combines high measuring sensitivity, and at the same time low sensitivity to external interfering influences, in particular temperature influences, and avoids the above-mentioned disadvantages.
  • An embodiment provides a capacitive measuring system including capacitive sensors and an evaluation circuit having a multi-channel, analog multiplexer and a synchronous rectifier.
  • a mono-frequency voltage signal is supplied to the capacitive sensors.
  • Output signals of the capacitive sensors are alternately linked to the synchronous rectifier by the multiplexer.
  • the signal strength of output signals of the synchronous rectifier is calibratable according to an activatable reference impedance.
  • the synchronous rectifier is formed by a MOS semiconductor switch.
  • the source-drain section of the MOS semiconductor switch forms a shunt that is controlled by the mono-frequency voltage signal.
  • At least one channel of the multiplexer is provided for transmitting a calibration or reference signal (“calibration signal”), generated by a reference voltage divider, to the synchronous rectifier alternately with the output signals of the capacitive sensors.
  • calibration signal generated by a reference voltage divider
  • a capacitive measuring system In carrying out at least one of the above and/or other objects, a capacitive measuring system is provided.
  • the capacitive measuring system includes capacitive sensors and an evaluation circuit having a multiplexer, a synchronous rectifier, a sinusoidal signal generator, and a reference voltage divider.
  • the capacitive sensors are acted on by a mono-frequency voltage signal generated by the sinusoidal signal generator, output signals of the capacitive sensors are transmitted in alternation to the synchronous rectifier via the multiplexer, and signal amplification of output signals of the synchronous rectifier are calibrated as a function of an activatable reference impedance.
  • the synchronous rectifier is formed by a MOS semiconductor switch.
  • a source-drain section of the MOS semiconductor switch forms a shunt that is controlled by the mono-frequency voltage signal.
  • a channel of the multiplexer is provided for transmitting a calibration signal, generated by the reference voltage divider, to the synchronous rectifier alternately with the output signals of the capacitive sensors.
  • the synchronous rectifier is formed by a MOS semiconductor switch
  • the source-drain section of the MOS semiconductor switch forms a shunt that is controlled by the mono-frequency voltage signal
  • at least one channel of the multiplexer is provided for transmitting a calibration signal, generated by a reference voltage divider, to the synchronous rectifier alternately with the output signals of the capacitive sensors.
  • Forming the synchronous rectifier by a MOS semiconductor switch is advantageous due to the fact that no temperature-sensitive component is connected in the signal path.
  • a half-wave of the measuring signal is switched to ground and thereby cut off.
  • the remaining half-wave remains completely uninfluenced by the switched-off MOS semiconductor switch, so that the one-way rectification also is not influenced by the ambient temperature.
  • the evaluation takes place based on a comparison (or comparative) voltage whose magnitude is influenced by at least one calibration signal.
  • the at least one calibration signal is generated by a reference voltage divider exposed to the same environmental conditions as the remaining capacitive measuring system, so that the calibration signal represents these environmental conditions.
  • the at least one calibration signal is routed via a channel of the multiplexer to the synchronous rectifier.
  • the at least one calibration signal takes the same signal path as the output signals of the capacitive sensors which are also routed via the multiplexer to the synchronous rectifier.
  • two reference voltage dividers which respectively set respective first and second calibration signals for an upper comparison value and a lower comparison value.
  • the cyclical evaluation of the output signals of the capacitive sensors does not have to be interrupted for the calibration; instead, the calibration takes place regularly as part of the evaluation cycle, “intermittently” in a manner of speaking.
  • FIG. 1 illustrates a first block diagram of a capacitive measuring system having a steering wheel sensor system
  • FIG. 2 illustrates a second block diagram of the capacitive measuring system
  • FIG. 3 illustrates a diagram of the structure of the steering wheel sensor system.
  • FIG. 1 illustrates a block diagram of the functional components of a capacitive measuring system.
  • the capacitive measuring system includes multiple capacitive sensors.
  • the capacitive sensors are situated on a steering wheel LR of a motor vehicle.
  • the capacitive sensors together form a steering wheel sensor system LS for recognizing contact of steering wheel LR by a human hand, particularly, a finger F.
  • FIG. 3 illustrates a schematic of the structural principle of steering wheel sensor system LS.
  • Steering wheel sensor system LS is made up of an arrangement of conductors L and insulators I layered in alternation.
  • Conductors L and insulators I are situated on or around the steering wheel rim, and optionally also on or around the spokes of steering wheel LR.
  • Conductors L are preferably made of copper foils or metal mesh.
  • Insulators I are preferably made of plastic films.
  • the conductive steering wheel core is labeled “Core” in FIG. 3 .
  • the shield conductor is labeled “Shield” in FIG. 3 .
  • the uppermost layer of conductors L is formed by multiple adjacently situated sensor foils SF 1 , SF 2 .
  • Sensor foils SF 1 , SF 2 in contrast to the other conductors L, are arranged not continuously, but, rather, in multiple separate adjacent sections on steering wheel LR.
  • Sensor foils SF 1 , SF 2 may have different shapes and sizes.
  • the diagram illustrated in FIG. 3 shows in particular an arrangement of two capacitive sensors S 1 , S 2 . The number of capacitive sensors may be easily increased to an intended value by adding additional sensor foils.
  • Capacitive sensors S 1 , S 2 divide the shield conductor.
  • the shield conductor is intended to shield sensor foils SF 1 , SF 2 from the grounded metal core of steering wheel LR.
  • sensor foils SF 1 , SF 2 overlap the shield conductor.
  • the capacitive measuring system further includes an evaluation circuit AS.
  • Evaluation circuit AS includes a micro-controller MC, a multi-channel analog multiplexer MUX, a synchronous rectifier SG, a sinusoidal signal generation device SIN, first and second reference voltage dividers REF, and a differential amplifier DV.
  • steering wheel sensor system LS illustrated in FIG. 1 is designed with six capacitive sensors (not illustrated in detail in FIG. 1 ) situated on steering wheel LR.
  • a total of six connecting lines L Sensor lead individually from the capacitive sensors on steering wheel LR to evaluation circuit AS.
  • Connecting lines L Sensor are connected to sensor foils SF 1 , SF 2 .
  • the number of connecting lines provided in each case is indicated in FIG. 1 by the information in parentheses (“6 ⁇ ”, “1 ⁇ ”, “1 ⁇ ”, for example).
  • connecting line L Core to the, metal core of steeling wheel LR is connected to the vehicle ground GND via a ground resistor R.
  • Connecting line L Shield to the shield conductor is coupled to the output of sinusoidal signal generation device SIN of evaluation circuit AS.
  • Connecting line L Shield to the shield conductor is used for coupling a mono-frequency sinusoidal signal U sin from sinusoidal signal generation device SIN into steering wheel sensor system LS.
  • the six sensor lines L Sensor are led in evaluation circuit AS to respective inputs of multiplexer MUX of evaluation circuit AS.
  • Two further inputs of multiplexer MUX (illustrated here with eight channels) are occupied by the respective center connection of the reference voltage dividers REF of evaluation circuit AS.
  • Multiplexer MUX is controlled by microcontroller MC of evaluation circuit AS.
  • a particularly simple and cost-efficient design of multiplexer MUX may be achieved in that multiplexer MUX is made up of a number of controllable analog switches that correspond to the intended number of channels.
  • the analog switches of multiplexer MUX are in each case controlled in alternation in a clocked manner via a programmable universal connection GPIO (general purpose input-output) of microcontroller MC.
  • GPIO general purpose input-output
  • sinusoidal signal U sin having a frequency in the range of 100 kHz is used as a measuring signal for steering wheel sensor system LS situated on steering wheel LR.
  • Sinusoidal signal U sin results from forming these pulse width-modulated signals PWM using a Chebyshev filter CF.
  • the signal generation is functionally illustrated here by a circuit block, referred to as sinusoidal signal generation device SIN.
  • sinusoidal signal U sin is applied to the shield conductor, which in each case forms a capacitive voltage divider with sensor foils SF 1 , SF 2 .
  • the capacitance values of capacitive sensors S 1 , S 2 are influenced by the presence of a hand or a finger, as the result of which the amplitudes of sensor signals S out present at sensor foils SF 1 , SF 2 change.
  • sensor signals S out outputted from capacitance sensors S 1 , S 2 are present at the inputs of multiplexer MUX and, controlled by microcontroller MC, are transmitted in succession to the output of multiplexer MUX in alternation.
  • Each signal MUX OUT present at the output of multiplexer MUX is relayed to the input of synchronous rectifier SG.
  • Synchronous rectifier SG is supplied with the mono-frequency sinusoidal signal U sin as a calibration signal.
  • Synchronous rectifier SG rectifies, on a frequency-selective basis, output signals MUX OUT of multiplexer MUX having the same frequency as the mono-frequency sinusoidal signal U sin , which is coupled into shield line L Shield . This effectively suppresses interference signals having different frequencies.
  • the output signal SG out of synchronous rectifier SG is amplified by a differential amplifier DV of evaluation circuit AS.
  • Differential amplifier DV is supplied with a comparison (or comparative) voltage V Bias for adapting the sensitivity.
  • the output signal OUT of differential amplifier DV is filtered via a further low pass circuit TP 2 and digitized by an analog-digital converter AD that is part of microcontroller MC, then evaluated and optionally used by microcontroller MC for controlling functions associated with the recognized signals.
  • Microcontroller MC computes the comparison voltage V Bias that is optimal in each case for adapting the sensitivity. To specify this comparison voltage for the differential amplifier DV, microcontroller MC influences the duty cycle of a pulse width-modulated signal PWM′. Pulse width-modulated signal PWM′ is smoothed with respect to comparison voltage V Bias by a low pass circuit TP.
  • Comparison voltage V Bias is a function of at least one calibration or reference voltage signal that is generated by at least one reference voltage divider REF.
  • the calibration voltage signal is affected by environmental influences of which the at least one reference voltage divider REF is exposed. If multiple reference voltage dividers REF, such as two in the present exemplary embodiment, are provided, then they may also specify multiple parameters such as a maximum value and a minimum value.
  • the calibration voltage signal present at each center tap of a reference voltage divider REF, is supplied in each case to an input of multiplexer MUX.
  • the calibration voltage signal thus passes through the same signal path as sensor signals S out , and at the end is likewise digitized by analog-digital converter AD and evaluated by microcontroller MC.
  • microcontroller MC may thus adapt comparison voltage V Bias to the instantaneously present calibration voltage values without having to interrupt the detection of the sensor signals at steering wheel LR.
  • evaluation circuit AS shows several individual circuit details with regard to the arrangement of electronic components.
  • Evaluation circuit AS is shown here also in a simplified, schematic illustration. In particular, for reasons of better clarity in FIG. 2 the illustration of microcontroller MC that carries out the control is omitted.
  • Various function blocks are designated in accordance with the corresponding function blocks in FIG. 1 . Since the basic operating principle has already been explained with reference to FIG. 1 , the explanation of FIG. 2 is limited to a few special features.
  • the circuit block depicts capacitive steering wheel sensor system LS illustrated in FIG. 3 based on an equivalent circuit diagram, which in particular shows that steering wheel sensor system LS forms one or multiple capacitive voltage dividers (in the present case, only one of multiple sensor lines L Sensor is illustrated).
  • human finger F is illustrated as an equivalent circuit diagram made up of capacitive and ohmic components that act electrically between one of sensor foils SF 1 , SF 2 and the vehicle ground.
  • Sensor line L Sensor leads to the input of an analog switch AN of multiplexer MUX.
  • multiplexer MUX contains eight individual analog switches AN, only one of which is depicted here. The inputs of six of these eight analog switches AN are occupied by sensor lines L Sensor , and two further inputs are connected to the center connections of a respective reference voltage divider REF (illustrated in FIG. 1 ).
  • reference voltage dividers REF illustrated in FIG. 1 , are used with known impedances.
  • reference voltage dividers REF may have a simple design as ohmic voltage dividers, whose external connections are each connected to a fixed potential, for example to the poles of the supply voltage of evaluation circuit AS.
  • Analog switches AN of multiplexer MUX are switched on in succession by microcontroller MC in alternation so that its respective input signal reaches the output of multiplexer MUX, and thus, also the input of synchronous rectifier SG.
  • output signal MUX OUT of multiplexer MUX is half-wave rectified with phase sensitivity via a switched shunt and is subsequently filtered by a low pass circuit TP 1 .
  • the switched shunt is in the form of the source-drain section SD of a MOSFET semiconductor switch FET, which forms synchronous rectifier SG.
  • the gate G of the MOSFET semiconductor switch FET is controlled by mono-frequency sinusoidal signal U sin .
  • Operational amplifier OP connected upstream from the gate G is used for level adjustment.
  • the difference between the filtered measuring signal and the comparison voltage V Bias is amplified in differential amplifier DV.
  • the sensitivity of the circuit is calibrated using the difference between comparison voltage V Bias and the measuring signal. Adapting the sensitivity of differential amplifier DV allows use to be made of the entire input voltage range of analog-digital converter AD for determining a useful signal.

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  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Engineering & Computer Science (AREA)
  • Mechanical Engineering (AREA)
  • Measurement Of Resistance Or Impedance (AREA)
  • Steering Controls (AREA)
US16/983,330 2018-02-03 2020-08-03 Capacitive measuring system Active 2041-07-04 US11920960B2 (en)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
DE102018000884.4A DE102018000884A1 (de) 2018-02-03 2018-02-03 Kapazitives Messsystem
DE102018000884.4 2018-02-03
PCT/EP2019/052525 WO2019149901A1 (de) 2018-02-03 2019-02-01 Kapazitives messsystem

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PCT/EP2019/052525 Continuation WO2019149901A1 (de) 2018-02-03 2019-02-01 Kapazitives messsystem

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US11920960B2 true US11920960B2 (en) 2024-03-05

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US (1) US11920960B2 (de)
EP (1) EP3746747B1 (de)
CN (1) CN112074707B (de)
DE (1) DE102018000884A1 (de)
ES (1) ES2908033T3 (de)
WO (1) WO2019149901A1 (de)

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CN113711064B (zh) * 2019-04-10 2024-03-08 Iee国际电子工程股份公司 多通道电容感测测量电路
DE102020103558A1 (de) * 2020-02-12 2021-08-12 Valeo Schalter Und Sensoren Gmbh Vorrichtung und verfahren zum kalibrieren eines kapazitiven berührungssensorsystems
FR3111110B1 (fr) * 2020-06-04 2022-07-15 Autoliv Dev procédé d’étalonnage d’un dispositif de mesure de volant de véhicule
DE102022105486A1 (de) * 2022-03-09 2023-09-14 Zf Automotive Germany Gmbh Handerkennungsvorrichtung für eine lenkradeinrichtung sowie lenkradanordnung mit der handerkennungsvorrichtung

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ES2908033T3 (es) 2022-04-27
DE102018000884A1 (de) 2019-08-08
EP3746747B1 (de) 2022-01-12
WO2019149901A1 (de) 2019-08-08
US20200361408A1 (en) 2020-11-19
CN112074707A (zh) 2020-12-11
EP3746747A1 (de) 2020-12-09
CN112074707B (zh) 2022-07-12

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