TWI500239B - Permanent magnetic synchronous motors and compressors using them - Google Patents
Permanent magnetic synchronous motors and compressors using them Download PDFInfo
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- TWI500239B TWI500239B TW102143577A TW102143577A TWI500239B TW I500239 B TWI500239 B TW I500239B TW 102143577 A TW102143577 A TW 102143577A TW 102143577 A TW102143577 A TW 102143577A TW I500239 B TWI500239 B TW I500239B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02K—DYNAMO-ELECTRIC MACHINES
- H02K1/00—Details of the magnetic circuit
- H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
- H02K1/22—Rotating parts of the magnetic circuit
- H02K1/27—Rotor cores with permanent magnets
- H02K1/2706—Inner rotors
- H02K1/272—Inner rotors the magnetisation axis of the magnets being perpendicular to the rotor axis
- H02K1/274—Inner rotors the magnetisation axis of the magnets being perpendicular to the rotor axis the rotor consisting of two or more circumferentially positioned magnets
- H02K1/2753—Inner rotors the magnetisation axis of the magnets being perpendicular to the rotor axis the rotor consisting of two or more circumferentially positioned magnets the rotor consisting of magnets or groups of magnets arranged with alternating polarity
- H02K1/276—Magnets embedded in the magnetic core, e.g. interior permanent magnets [IPM]
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02K—DYNAMO-ELECTRIC MACHINES
- H02K21/00—Synchronous motors having permanent magnets; Synchronous generators having permanent magnets
- H02K21/12—Synchronous motors having permanent magnets; Synchronous generators having permanent magnets with stationary armatures and rotating magnets
- H02K21/14—Synchronous motors having permanent magnets; Synchronous generators having permanent magnets with stationary armatures and rotating magnets with magnets rotating within the armatures
- H02K21/16—Synchronous motors having permanent magnets; Synchronous generators having permanent magnets with stationary armatures and rotating magnets with magnets rotating within the armatures having annular armature cores with salient poles
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02K—DYNAMO-ELECTRIC MACHINES
- H02K1/00—Details of the magnetic circuit
- H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
- H02K1/22—Rotating parts of the magnetic circuit
- H02K1/24—Rotor cores with salient poles ; Variable reluctance rotors
- H02K1/246—Variable reluctance rotors
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02K—DYNAMO-ELECTRIC MACHINES
- H02K2213/00—Specific aspects, not otherwise provided for and not covered by codes H02K2201/00 - H02K2211/00
- H02K2213/03—Machines characterised by numerical values, ranges, mathematical expressions or similar information
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Permanent Field Magnets Of Synchronous Machinery (AREA)
- Iron Core Of Rotating Electric Machines (AREA)
- Permanent Magnet Type Synchronous Machine (AREA)
Description
本發明係關於一種永久磁性同步電機及使用其之壓縮機者。The present invention relates to a permanent magnetic synchronous motor and a compressor using the same.
於永久磁性同步電機中，廣泛採用於轉子中埋設永久磁鐵之Interior Permanent Magnet(內置永久磁鐵)(以下，IPM)構造。於IPM構造中，由於直軸電感Ld與橫軸電感Lq之比、所謂之凸極比變大，故除了磁鐵轉矩以外亦可活用磁阻轉矩。In the permanent magnetic synchronous motor, an Interior Permanent Magnet (hereinafter, IPM) structure in which a permanent magnet is embedded in a rotor is widely used. In the IPM structure, since the ratio of the direct-axis inductance Ld to the horizontal-axis inductance Lq and the so-called salient pole ratio become large, reluctance torque can be utilized in addition to the magnet torque.
作為活用磁阻轉矩之永久磁性同步電機之先前技術，有日本專利特開2001-119875號公報(專利文獻1)所記載之同步電機。於該公報中，轉子100具有於軸向串聯結合磁性凸極型轉子部102與磁鐵型轉子部101之構造，磁性凸極型轉子部102之磁性凸極型場磁極之磁通及磁鐵型轉子部101永久磁鐵型場磁極之磁通係與共通之多層電樞線圈交鏈。藉由如此般構成，與產生磁性凸極型場磁極之磁阻轉矩與永久磁鐵型場磁極之磁鐵轉矩之合成轉矩之同步電機相比較，可最優設定兩轉子部之相對角度，而增大每永久磁鐵量之合成轉矩。A synchronous motor described in Japanese Laid-Open Patent Publication No. 2001-119875 (Patent Document 1) is known as a prior art. In this publication, the rotor 100 has a structure in which a magnetic salient pole type rotor portion 102 and a magnet type rotor portion 101 are coupled in series in the axial direction, and a magnetic salient pole type field magnetic pole magnetic flux and a magnet type rotor of the magnetic salient pole type rotor portion 102. The magnetic flux system of the permanent magnet field field pole of the portion 101 is interlinked with the common multilayer armature coil. With such a configuration, the relative angle between the two rotor portions can be optimally set as compared with a synchronous motor that generates a combined torque of the magnetic salient pole type field magnetic pole and the permanent magnet type field magnetic pole magnet torque. And increase the combined torque per permanent magnet amount.
[專利文獻1]日本專利特開2001-119875號公報[Patent Document 1] Japanese Patent Laid-Open Publication No. 2001-119875
在專利文獻1之同步電機中，藉由採用IPM構造而增大凸極比， 從而活用磁阻轉矩。然而，根據用途或輸出、及馬達實體形式，有即便採用IPM構造，即，即便增大凸極比亦難以活用磁阻轉矩者。此係由磁阻轉矩之大小並非僅依存於凸極比之大小，亦依存於與磁鐵轉矩之相對關係所致。In the synchronous motor of Patent Document 1, the salient pole ratio is increased by adopting the IPM structure, Therefore, the reluctance torque is utilized. However, depending on the application, the output, and the motor body form, even if the IPM structure is employed, even if the salient pole ratio is increased, it is difficult to utilize the reluctance torque. The magnitude of the reluctance torque is not dependent only on the salient pole ratio, but also on the relative relationship with the magnet torque.
然而，於先前之設計理論中忽視了此種觀點。因此，有無法活用磁阻轉矩而無法謀求輸出提高或效率提高，另一方面，由於凸極比較大故電感變大，而導致鐵損增加，而難以實現高速化之情形。However, this view has been ignored in previous design theories. Therefore, there is a possibility that the reluctance torque cannot be utilized, and the output can be improved or the efficiency can be improved. On the other hand, since the salient pole is relatively large, the inductance is increased, and the iron loss is increased, so that it is difficult to achieve high speed.
本發明之目的在於在永久磁性同步電機中，即使於難以活用磁阻轉矩之情形時，亦可實現轉矩提高、效率提高、高速旋轉化。An object of the present invention is to achieve torque improvement, efficiency improvement, and high-speed rotation in a permanent magnetic synchronous motor even when it is difficult to utilize reluctance torque.
為達成上述目的，於本發明中，於具有由以構成複數個極之方式配備之永久磁鐵構成之轉子之永久磁性同步電機中，上述永久磁鐵之定子線圈交鏈磁通Ψp與電流IArms通電時之直軸電感Ld及橫軸電感Lq滿足數1之關係，
且驅動時之定子交鏈磁通Ψ與上述Ψp滿足數2之關係，藉此，緩和定子鐵芯之磁性飽和。Further, the stator interlinkage magnetic flux 驱动 at the time of driving and the above Ψp satisfy the relationship of the number 2, thereby easing the magnetic saturation of the stator core.
根據本發明，轉矩及效率提高，且可實現高速旋轉化。According to the present invention, torque and efficiency are improved, and high-speed rotation can be achieved.
上述以外之問題、構成及效果，將根據以下之實施形態之說明而明確。The problems, configurations, and effects other than the above will be clarified by the following description of the embodiments.
1‧‧‧轉子1‧‧‧Rotor
2‧‧‧轉子鐵芯2‧‧‧Rotor core
3‧‧‧永久磁鐵3‧‧‧ permanent magnet
4‧‧‧永久磁鐵收納孔4‧‧‧Permanent magnet housing hole
5‧‧‧鉚接用鉚釘5‧‧‧ Rivet rivets
6‧‧‧軸或曲軸6‧‧‧Axis or crankshaft
7‧‧‧切口7‧‧‧ incision
7a‧‧‧切口7a‧‧‧ incision
7b‧‧‧切口7b‧‧‧ incision
8‧‧‧極8‧‧‧ pole
9‧‧‧定子9‧‧‧ Stator
10‧‧‧定子鐵芯10‧‧‧ Stator core
11‧‧‧齒狀部分11‧‧‧ toothed part
12(12u1、12u2、12u3、12v1、12v2、12v3、12w1、12w2、12w3)‧‧‧定子線圈12 (12u1, 12u2, 12u3, 12v1, 12v2, 12v3, 12w1, 12w2, 12w3) ‧‧‧ stator coil
13‧‧‧固定捲動構件13‧‧‧Fixed scrolling members
14‧‧‧端板14‧‧‧End board
15‧‧‧螺旋狀搭接15‧‧‧Spiral overlap
16‧‧‧旋轉捲動構件16‧‧‧Rotating scrolling member
17‧‧‧端板17‧‧‧End board
18‧‧‧螺旋狀搭接18‧‧‧Spiral overlap
19(19a、19b)‧‧‧壓縮室19 (19a, 19b) ‧ ‧ compression chamber
20‧‧‧噴出口20‧‧‧Spray outlet
21‧‧‧框架21‧‧‧Frame
22‧‧‧壓力容器22‧‧‧ Pressure vessel
23‧‧‧噴出管23‧‧‧Spray tube
24‧‧‧平衡重量24‧‧‧balance weight
25‧‧‧油積存部25‧‧‧ Oil accumulation department
26‧‧‧油孔26‧‧‧ oil hole
27‧‧‧滑動軸承27‧‧‧Sliding bearings
30‧‧‧端子箱30‧‧‧Terminal box
101‧‧‧磁鐵型轉子部101‧‧‧Magnetic rotor part
102‧‧‧肋102‧‧‧ rib
102‧‧‧磁性凸極型轉子部102‧‧‧Magnetic salient rotor
103‧‧‧q軸空孔103‧‧‧q shaft holes
103‧‧‧永久磁鐵馬達103‧‧‧Permanent magnet motor
圖1係對本發明之第1實施例之永久磁性同步電機，以垂直於旋轉軸之橫剖面顯示定子與轉子之圖。Fig. 1 is a view showing a stator and a rotor in a cross section perpendicular to a rotating shaft in a permanent magnetic synchronous motor according to a first embodiment of the present invention.
圖2係顯示本發明之數3之關係之圖。Fig. 2 is a view showing the relationship of the number 3 of the present invention.
圖3係本發明之第1實施例之轉矩特性之說明圖。Fig. 3 is an explanatory view showing the torque characteristics of the first embodiment of the present invention.
圖4係永久磁鐵馬達之矢量圖。Figure 4 is a vector diagram of a permanent magnet motor.
圖5係對本發明之第1實施例之永久磁性同步電機，以垂直於旋轉軸之橫剖面顯示轉子之圖。Fig. 5 is a view showing a permanent magnet synchronous motor according to a first embodiment of the present invention, showing a rotor in a cross section perpendicular to a rotating shaft.
圖6係對本發明之第1實施例之永久磁性同步電機，以垂直於旋轉軸之橫剖面顯示轉子之圖。Fig. 6 is a view showing a permanent magnet synchronous motor according to a first embodiment of the present invention, showing a rotor in a cross section perpendicular to a rotating shaft.
圖7係本發明之第2實施例之馬達特性之一例。Fig. 7 is a view showing an example of the motor characteristics of the second embodiment of the present invention.
圖8係6極9槽三相馬達之定子線圈連接圖。Figure 8 is a stator coil connection diagram of a 6-pole 9-slot three-phase motor.
圖9(a)-(c)係磁鐵轉矩與磁阻轉矩之原理說明圖。Fig. 9 (a) - (c) are diagrams illustrating the principle of magnet torque and reluctance torque.
圖10係永久磁鐵馬達之矢量圖。Figure 10 is a vector diagram of a permanent magnet motor.
圖11係以垂直於旋轉軸之橫剖面顯示與本發明為比較例之永久磁性同步電機之轉子之局部剖面圖。Figure 11 is a partial cross-sectional view showing the rotor of the permanent magnetic synchronous motor of the comparative example of the present invention in a cross section perpendicular to the rotation axis.
圖12係本發明之第3實施例之壓縮機之剖面構造圖。Figure 12 is a cross-sectional structural view showing a compressor according to a third embodiment of the present invention.
以下，對本發明之實施例參照圖式進行說明。於以下之說明中，對同一構成要素添附有同一記號。該等名稱及功能相同，而避免重複說明。又，於以下之說明中雖以內轉型轉子為對象，但本發明之效果並非限定於內轉型轉子者，亦可應用於具有相同之構成之外轉型轉子。Hereinafter, embodiments of the present invention will be described with reference to the drawings. In the following description, the same component is attached with the same symbol. These names and functions are the same and avoid repeating the instructions. Further, in the following description, the inner rotor is targeted, but the effect of the present invention is not limited to the inner rotor, and may be applied to a rotor having the same configuration.
又，定子之繞組方式既可為同心繞組亦可為分佈繞組。又，轉子之極數、定子線圈之相數亦非限定於實施例之構成者。又，於以下之說明中雖以變頻器驅動之永久磁鐵馬達為對象，但本發明之效果亦 可應用於自行啟動型永久磁鐵馬達。Moreover, the winding mode of the stator can be either a concentric winding or a distributed winding. Further, the number of poles of the rotor and the number of phases of the stator coil are not limited to those of the embodiment. Further, in the following description, the permanent magnet motor driven by the inverter is targeted, but the effect of the present invention is also It can be applied to self-starting permanent magnet motors.
以下，使用圖1至6，對本發明之第1實施例進行說明。又，於本實施例之說明時，參照圖8至11。Hereinafter, a first embodiment of the present invention will be described with reference to Figs. Further, in the description of the present embodiment, reference is made to Figs. 8 to 11.
圖1係對本發明之第1實施例之永久磁性同步電機，以垂直於旋轉軸之橫剖面顯示定子與轉子之圖。Fig. 1 is a view showing a stator and a rotor in a cross section perpendicular to a rotating shaft in a permanent magnetic synchronous motor according to a first embodiment of the present invention.
圖2係顯示本發明之數3之關係之圖。Fig. 2 is a view showing the relationship of the number 3 of the present invention.
圖3係本發明之第1實施例之轉矩特性之說明圖。Fig. 3 is an explanatory view showing the torque characteristics of the first embodiment of the present invention.
圖4係永久磁鐵馬達之矢量圖。Figure 4 is a vector diagram of a permanent magnet motor.
圖5及圖6係對本發明之第1實施例之永久磁性同步電機，以垂直於旋轉軸之橫剖面顯示轉子之圖。Fig. 5 and Fig. 6 are views showing a rotor of a permanent magnetic synchronous motor according to a first embodiment of the present invention, which is perpendicular to the rotation axis.
圖8係6極9槽三相馬達之定子線圈連接圖。Figure 8 is a stator coil connection diagram of a 6-pole 9-slot three-phase motor.
圖9係磁鐵轉矩與磁阻轉矩之原理說明圖。Figure 9 is a schematic diagram of the principle of magnet torque and reluctance torque.
圖10係永久磁鐵馬達之矢量圖。Figure 10 is a vector diagram of a permanent magnet motor.
圖11係以垂直於旋轉軸之橫剖面顯示與本發明為比較例之永久磁性同步電機之轉子之局部剖面圖。Figure 11 is a partial cross-sectional view showing the rotor of the permanent magnetic synchronous motor of the comparative example of the present invention in a cross section perpendicular to the rotation axis.
對本實施例之永久磁性同步電機，使用圖1進行說明。The permanent magnetic synchronous motor of this embodiment will be described using FIG.
在本實施例之永久磁性同步電機中，於定子9之內周側具備轉子1。將轉子1隔著間隙G利用未圖示之軸承旋轉自如地保持於定子9。In the permanent magnetic synchronous motor of the present embodiment, the rotor 1 is provided on the inner peripheral side of the stator 9. The rotor 1 is rotatably held by the stator 9 via a gap G through a bearing (not shown).
定子9包含具有齒狀部分11之定子鐵芯10與捲繞於齒狀部分11之定子繞組12。定子繞組12依次於周向配置三相之繞組U、V、W。U相、V相及W相之各相串聯連接有3個線圈(參照圖8)。將全部9個線圈12u1、12u2、12u3、12v1、12v2、12v3、12w1、12w2、12w3分開捲繞於各齒狀部分11，而構成同心繞組之永久磁性同步電機。The stator 9 includes a stator core 10 having a toothed portion 11 and a stator winding 12 wound around the toothed portion 11. The stator windings 12 are sequentially arranged with three-phase windings U, V, W in the circumferential direction. Three coils are connected in series to each of the U phase, the V phase, and the W phase (see Fig. 8). All of the nine coils 12u1, 12u2, 12u3, 12v1, 12v2, 12v3, 12w1, 12w2, and 12w3 are wound around the respective tooth portions 11 to form a concentric winding permanent magnetic synchronous motor.
因此，於定子9上，設置有9個齒狀部分11及槽。轉子1包含具備永久磁鐵收納孔4之轉子鐵芯2與以構成6極(極對數p=3)之方式配置之 永久磁鐵3。於轉子1之中心部分中，形成有軸(旋轉軸、輸出軸)6貫通之貫通孔6a，且於貫通孔6a中插通有軸6。Therefore, on the stator 9, nine tooth portions 11 and grooves are provided. The rotor 1 includes a rotor core 2 including a permanent magnet housing hole 4 and is configured to have six poles (pole pairs p=3). Permanent magnet 3. A through hole 6a through which the shaft (rotation shaft, output shaft) 6 penetrates is formed in a central portion of the rotor 1, and a shaft 6 is inserted into the through hole 6a.
本實施例之永久磁性同步電機如圖1所示，轉子1具有方形狀之磁鐵收納孔4，且於磁鐵收納孔4中埋設有永久磁鐵3。將永久磁鐵3***磁鐵收納孔4，且沿著周向設置複數個永久磁鐵3與磁鐵收納孔4，藉此，於轉子1之內部沿著周向構成複數個極8。As shown in FIG. 1, the permanent magnetic synchronous motor of the present embodiment has a rotor-shaped magnet housing hole 4 and a permanent magnet 3 embedded in the magnet housing hole 4. The permanent magnet 3 is inserted into the magnet housing hole 4, and a plurality of permanent magnets 3 and magnet housing holes 4 are provided along the circumferential direction, whereby a plurality of poles 8 are formed along the circumferential direction inside the rotor 1.
永久磁鐵3之定子線圈一相序部分之交鏈磁通Ψp(Wb)與對定子線圈通電相電流有效值Irms(Arms)時之直軸電感Ld(H)及橫軸電感Lq(H)具有下述之數3之關係。The interlinkage magnetic flux Ψp(Wb) of the phase coil portion of the stator coil of the permanent magnet 3 and the direct-axis inductance Ld(H) and the horizontal-axis inductance Lq(H) of the energizing phase current rms Irms (Arms) of the stator coil have The relationship of the number 3 below.
又，驅動時之定子交鏈磁通Ψ與上述Ψp滿足數4之關係。Further, the stator interlinkage magnetic flux 驱动 at the time of driving satisfies the relationship of the number 4 with respect to Ψp.
此處首先，關於數3之物理量及磁阻轉矩之產生原理，使用圖3、圖8及圖9進行說明。於本實施例中，雖對6極9槽之三相馬達進行說明，但亦可為具有4極6槽、或其他極數及槽數之三相馬達。First, the principle of generating the physical quantity and the reluctance torque of the number 3 will be described with reference to FIGS. 3, 8, and 9. In the present embodiment, a six-pole, nine-slot three-phase motor will be described, but a three-phase motor having four poles and six slots or other number of poles and slots may be used.
例如如圖8所示，對串聯連接之U相繞組12u1、12u2、12u3，自變頻器供給峰值I(將此時之有效值設為Irms)之交流電流iu。關於V相繞組12v1、12v2、12v3、W相繞組12w1、12w2、12w3雖亦相同，但各相之電流相位以電角度各偏移120°。I或Irms之大小可藉由使用瓦特計等機器求出。或，亦可藉由以示波器等取得電流波形並進行傅利葉分析而求出。For example, as shown in FIG. 8, the U-phase windings 12u1, 12u2, and 12u3 connected in series are supplied with an alternating current iu of a peak I (the effective value at this time is Irms) from the inverter. Although the V-phase windings 12v1, 12v2, and 12v3 and the W-phase windings 12w1, 12w2, and 12w3 are also the same, the current phases of the respective phases are shifted by 120 degrees at electrical angles. The size of I or Irms can be determined by using a wattmeter or the like. Alternatively, it can be obtained by taking a current waveform with an oscilloscope or the like and performing Fourier analysis.
藉由將與轉子1機械結合之軸6連結於負載，並適當選擇電流I之大小與相位，產生如與負載平衡般之旋轉轉矩Me。定子線圈一相序 部分之交鏈磁通Ψp可藉由在開放圖8所示之U、V、W之端子Tu、Tv、Tw之狀態下外部驅動轉子1，並測定此時之相電壓峰值E0、或線間電壓峰值E0×3而求出。具體而言，自數5求出以每分鐘之旋轉數N[rpm]外部驅動時之角頻率ω[rad/s]，並將其代入數6而獲得。其中，p為極對數。By connecting the shaft 6 mechanically coupled to the rotor 1 to the load, and appropriately selecting the magnitude and phase of the current I, a rotational torque Me such as that balanced with the load is generated. The interlinkage magnetic flux Ψp of a phase sequence portion of the stator coil can externally drive the rotor 1 by opening the terminals U, V, and W of the terminals U, V, and W shown in FIG. 8, and measuring the phase voltage peak at this time. E0, or line voltage peak E0 × 3 and find. Specifically, the angular frequency ω [rad/s] at the time of external driving with the number of revolutions per minute N [rpm] is obtained from the number 5, and is obtained by substituting the number 6 into the number 6. Where p is the pole logarithm.
然而，磁鐵馬達之轉矩Me一般係因定子繞組U、V、W各相之通電電流產生之旋轉磁場與轉子磁極之吸引．排斥而產生。所謂轉子磁極，於磁鐵馬達之情形時，指由磁鐵形成之磁場之情況較多，考慮磁阻轉矩時，若將藉由受旋轉磁場之影響轉子鐵芯磁化而形成之磁場亦認作磁極之一種則易於理解。However, the torque Me of the magnet motor is generally caused by the rotating magnetic field generated by the energizing current of each phase of the stator winding U, V, W and the magnetic pole of the rotor. Produced by exclusion. The term "rotor magnetic pole" refers to a magnetic field formed by a magnet in the case of a magnet motor. When a reluctance torque is considered, a magnetic field formed by magnetization of a rotor core by a rotating magnetic field is also regarded as a magnetic pole. One is easy to understand.
另，由於磁鐵馬達之同步運轉時之電流或磁通為交流量，故一般採用轉換成dq軸座標系(旋轉座標系)而作為直流量進行處理之方法。一般而言，於dq軸座標系中將轉子之磁極中心軸設為d軸，將相對d軸朝逆時針方向以電角度前進90°之軸、即極性不同之永久磁鐵間之中心軸設為q軸。該情形時，無論轉子位置於何，均可僅以dq軸與旋轉磁場之相對之位置關係考察轉矩等諸物理量。Further, since the current or the magnetic flux during the synchronous operation of the magnet motor is an alternating current amount, a method of converting into a dq-axis coordinate system (rotary coordinate system) and treating it as a direct current amount is generally employed. Generally, in the dq axis coordinate system, the central axis of the magnetic pole of the rotor is set to the d-axis, and the axis that advances by 90 degrees with respect to the d-axis in the counterclockwise direction, that is, the central axis between the permanent magnets having different polarities is set. Q axis. In this case, regardless of the position of the rotor, physical quantities such as torque can be inspected only by the relative positional relationship between the dq axis and the rotating magnetic field.
使用圖9說明磁鐵馬達之轉矩產生原理。於圖中，將逆時針方向設為正方向。(a)顯示磁鐵轉矩。(b)顯示d軸電流為負之情形時產生之磁阻轉矩，係由轉子q軸之磁化所致者。(c)顯示d軸電流為負之情形時產生之磁阻轉矩，係由轉子d軸之磁化所致者。The principle of torque generation of the magnet motor will be described using FIG. In the figure, the counterclockwise direction is set to the positive direction. (a) shows the magnet torque. (b) The reluctance torque generated when the d-axis current is negative is caused by the magnetization of the q-axis of the rotor. (c) The reluctance torque generated when the d-axis current is negative is caused by the magnetization of the d-axis of the rotor.
如(a)所示，磁鐵轉矩係因d軸上產生之磁鐵磁通與由q軸電流形 成之磁場之吸引及排斥而產生之轉矩。此時，於磁鐵磁通與d軸電流磁場之間雖產生徑向之斥力，但不會產生旋轉力。As shown in (a), the magnet torque is due to the magnet flux generated on the d-axis and the q-axis current The torque generated by the attraction and rejection of the magnetic field. At this time, although a radial repulsive force is generated between the magnet magnetic flux and the d-axis current magnetic field, no rotational force is generated.
另一方面，如(b)所示，轉子q軸因q軸電流磁場而磁化之情形時，於轉子q軸之磁化與d軸電流磁場之間產生引力及斥力。此係磁阻轉矩，於d軸電流為負之情形時即弱場磁運轉時獲得正轉矩，而於增磁作用時成為負轉矩。On the other hand, as shown in (b), when the q-axis of the rotor is magnetized by the q-axis current magnetic field, an attractive force and a repulsive force are generated between the magnetization of the q-axis of the rotor and the d-axis current magnetic field. This reluctance torque is a positive torque when the d-axis current is negative, that is, a weak field magnetic operation, and a negative torque when the magnetization is applied.
同樣地，如(c)所示般轉子d軸易磁化之情形時，亦在與q軸電流磁場之關係中產生磁阻轉矩，該等於弱場磁運轉時成為負轉矩，而於增磁作用時成為正轉矩(一般將(b)與(c)之和稱作磁阻轉矩)。Similarly, when the rotor d-axis is easily magnetized as shown in (c), reluctance torque is generated in the relationship with the q-axis current magnetic field, which is equivalent to the negative torque in the weak field magnetic operation, and is increased. It becomes a positive torque when magnetically acting (generally, the sum of (b) and (c) is called reluctance torque).
磁鐵轉矩若為q軸電流一定以下則與磁鐵所產生之磁通量成正比。即，為增加磁鐵轉矩需要增加磁鐵量，或使用高強度之磁鐵，而導致成本增加。與此相對，由於磁阻轉矩與q軸與d軸之電感之差成正比，故考慮可藉由以增大兩者之差之方式構成轉子磁性電路而謀求轉矩之增加。If the magnet torque is less than or equal to the q-axis current, it is proportional to the magnetic flux generated by the magnet. That is, in order to increase the magnet torque, it is necessary to increase the amount of magnets or use a high-strength magnet, resulting in an increase in cost. On the other hand, since the reluctance torque is proportional to the difference between the inductances of the q-axis and the d-axis, it is considered that the rotor magnetic circuit can be configured to increase the torque by increasing the difference between the two.
於是，相對於以上述要領求數3之構成物理量中之Ψp、Irms，關於Ld、Lq之求法，有如多爾頓．卡梅隆法等之轉子靜止法、或根據如以下將敍述般之矢量圖進行逆運算之方法。Therefore, with respect to Ψp and Irms in the constituent physical quantities of the above-mentioned method 3, the method of calculating Ld and Lq is like Dalton. The rotor static method of the Cameron method or the like, or the method of inverse calculation based on a vector diagram as will be described later.
使用圖10之dq軸座標系之矢量圖，對磁鐵馬達之同步運轉時之電流、電壓及磁通進行說明。The current, voltage, and magnetic flux during the synchronous operation of the magnet motor will be described using the vector diagram of the dq axis coordinate system of FIG.
以永久磁鐵之定子線圈一相序部分之交鏈磁通Ψp之相位為基準，並將此看作d軸，而Ψp之時間微分即感應電動勢E0產生於相位前進90°之q軸。施加於馬達之相電壓V與馬達中通電之相電流I相對E0分別具有θ、β之相位差時，可將V、I如數7及數8所示般分解為d軸成分、q軸成分。The phase of the interlinkage magnetic flux Ψp of the phase sequence of the stator coil of the permanent magnet is taken as the reference, and this is regarded as the d-axis, and the time differential of the Ψp, that is, the induced electromotive force E0 is generated in the q-axis whose phase advances by 90°. When the phase voltage V applied to the motor and the phase current I of the current supplied to the motor have a phase difference of θ and β, respectively, V and I can be decomposed into a d-axis component and a q-axis component as indicated by the numbers 7 and 8.
【數7】 Vd =-V．sinθ Vq =V．cosθ [Number 7] V d =-V. Sin θ V q =V. Cos θ
【數8】Id =-I．sinβ Iq =I．cosβ [Number 8] I d =-I. Sin β I q =I. Cos β
另，圖10之電阻R可藉由使用惠斯登電橋等電阻測試器而測量。又，關於電壓相位差角θ、電流相位差角β，可藉由取得E0、V、I之波形，算出各基本波成分之相位關係而求出。於圖10中雖表示使用相電壓、相電流之波形之情形，但例如代替相電壓而取得線間電壓之情形時，亦可藉由考慮相電壓與線間電壓之相位差同樣地求θ、β。In addition, the resistor R of FIG. 10 can be measured by using a resistance tester such as a Wheatstone bridge. Further, the voltage phase difference angle θ and the current phase difference angle β can be obtained by acquiring the waveforms of E0, V, and I and calculating the phase relationship of each fundamental wave component. Although the waveforms of the phase voltage and the phase current are used in FIG. 10, for example, when the line voltage is obtained instead of the phase voltage, θ may be obtained in consideration of the phase difference between the phase voltage and the line voltage. β.
使用上述獲得之物理量，Ld、Lq可自數9之電壓方程式求出。Using the physical quantities obtained above, Ld and Lq can be obtained from the voltage equation of the number 9.
【數9】Vd =R．Id -ω ．Lq ．Iq Vq =R．Iq +ω ．Ld ．Id +E0 [Number 9] V d = R. I d - ω . L q . I q V q =R. I q + ω . L d . I d +E 0
以上，關於數3之物理量及磁阻轉矩之產生原理予以說明。The principle of the generation of the physical quantity and the reluctance torque of the number 3 will be described above.
接著，說明藉由滿足本發明之基本原理、即數3之關係，且滿足數4之關係，可謀求轉矩提高、效率提高、高速旋轉化之原理。Next, the principle of satisfying the basic principle of the present invention, that is, the number 3, and satisfying the relationship of the number 4 will be described, and the principle of improving the torque, improving the efficiency, and rotating at a high speed can be achieved.
一般產生轉矩Me係以使用極對數p、永久磁鐵之定子線圈一相序部分之交鏈磁通Ψp、直軸電流Id、橫軸電流Iq以數10顯示之下式表示。Generally, the torque Me is expressed by using the pole pair p, the interlinkage magnetic flux Ψp of the phase sequence of the stator coil of the permanent magnet, the direct-axis current Id, and the horizontal-axis current Iq as the following formula.
其中，Id、Iq、Ψp為峰值。Among them, Id, Iq, and Ψp are peaks.
在數10中，{ }內第一項表示磁鐵轉矩，第二項表示磁阻轉矩。如自該式而明確般，磁阻轉矩分別與Lq-Ld、Id、Iq成正比。因此，先前作為磁阻轉矩之大小之指標使用凸極比Lq/Ld、或Lq-Ld。然而，磁阻轉矩對產生轉矩Me有多大幫助，係由與磁鐵轉矩之相對關 係決定。例如，磁阻轉矩相對磁鐵轉矩於極端較小之情形時，即便磁阻轉矩稍微變動(增減)，亦幾乎不會對產生轉矩Me有影響。因此，表示磁阻轉矩之大小之指標中，除了先前之凸極比以外，需要新導入可參考與磁鐵轉矩之相對關係之其他物理量。In the number 10, the first term in { } represents the magnet torque, and the second term represents the reluctance torque. As is clear from this formula, the reluctance torque is proportional to Lq-Ld, Id, Iq, respectively. Therefore, the salient pole ratio Lq/Ld or Lq-Ld has been used as an index of the magnitude of the reluctance torque. However, how much reluctance torque contributes to the generation of torque Me is related to the torque of the magnet. Department decided. For example, when the reluctance torque is extremely small with respect to the magnet torque, even if the reluctance torque slightly changes (increases or decreases), there is almost no influence on the generated torque Me. Therefore, in the index indicating the magnitude of the reluctance torque, in addition to the previous salient pole ratio, it is necessary to newly introduce other physical quantities which can be referred to the relative relationship with the magnet torque.
此處，磁鐵轉矩於電流相位差角β=0時成最大，其最大值Mp，max可由數8、數10以下式表示。Here, the magnet torque is maximized at a current phase difference angle β=0, and the maximum value Mp,max thereof can be expressed by a number of eight or ten.
另一方面，磁阻轉矩於β=π/4(電角度中45deg.)時成最大，其最大值Mr，max可由數8、數10以下式表示。On the other hand, the reluctance torque is maximum at β = π / 4 (45 deg. in the electrical angle), and the maximum value Mr, max can be expressed by the equations of 8 and 10.
由於數11與數12之比就是表示磁阻轉矩之大小之指標，故將該比定義為磁阻轉矩比α。使用電流峰值I之情形時，成，使用電流有效值Irms之情形時，成。於本發明中係使用利用電流有效值Irms之數14。Since the ratio of the number 11 to the number 12 is an index indicating the magnitude of the reluctance torque, the ratio is defined as the reluctance torque ratio α. When using the current peak I, When using the current rms Irms, . In the present invention, the number 14 using the current effective value Irms is used.
如自數14而明確般，可知作為表示磁阻轉矩之大小之指標，除了先前之Ld、Lq，新導入有Ψp、Irms。其中，Ψp係由永久磁鐵之物性與形狀、定子繞組規格、馬達剖面形狀決定，可自一般之感應電動勢測試試驗求出。同樣地，Ld、Lq亦係由馬達構成與通電電流Irms決 定，可自一般之馬達電感測試法求出。因此，Ψp、Ld、Lq係針對每個馬達決定之常數，而數14可作為α與Irms之線性函數處理。As is clear from the number 14, it can be seen that as an index indicating the magnitude of the reluctance torque, Ψp and Irms are newly introduced in addition to the previous Ld and Lq. Among them, Ψp is determined by the physical properties and shape of the permanent magnet, the stator winding specifications, and the motor cross-sectional shape, and can be obtained from a general induced electromotive force test. Similarly, Ld and Lq are also composed of a motor and the current Irms It can be determined from the general motor inductance test method. Therefore, Ψp, Ld, and Lq are constants determined for each motor, and the number 14 can be treated as a linear function of α and Irms.
磁阻轉矩比α雖藉由使數14之右邊、尤其電流值改變可採用任意之值，但自產生轉矩提高、效率提高之觀點而言，較理想為在如圖3所示般磁阻轉矩Mr成最大之β=45deg.中，產生轉矩Me為與磁鐵轉矩最大值Mp，max同等或為其以上。若再稍微詳細說明，則為永久磁性同步電機於進行效率最大化控制之情形時，於電流相位差角為0~45°之範圍中驅動。產生轉矩Me於電流相位差角為0°與45°時成為最小值。因此，於電流相位差角為0°與45°時，使產生轉矩Me為與磁鐵轉矩最大值Mp，max同等或為其以上，藉此，可活用磁阻轉矩。即，只要之關係成立即可。整理數15後，成為，進而使用數14進行變化後獲得下式。The reluctance torque ratio α can be arbitrarily changed by changing the right side of the number 14, especially the current value, but it is preferable to be magnetic as shown in FIG. 3 from the viewpoint of improving the torque generation and improving the efficiency. When the resistance torque Mr is the maximum β=45 deg., the generated torque Me is equal to or higher than the maximum value of the magnet torque Mp,max. If it is explained in more detail, the permanent magnetic synchronous motor is driven in the range of 0 to 45 degrees in the current phase difference angle when the efficiency is maximized. The generated torque Me becomes the minimum value when the current phase difference angle is 0° and 45°. Therefore, when the current phase difference angle is 0° and 45°, the generated torque Me is equal to or higher than the magnet torque maximum value Mp,max, whereby the reluctance torque can be utilized. That is, as long as The relationship can be established. After finishing the number 15, become Then, using the number 14 to change, the following formula is obtained.
根據以上，顯示作為表示磁阻轉矩之大小之指標，除了先前之Ld、Lq以外，需要導入Ψp、Irms，且為有效活用磁阻轉矩需要滿足數17之關係式。From the above, as an index indicating the magnitude of the reluctance torque, it is necessary to introduce Ψp and Irms in addition to the previous Ld and Lq, and it is necessary to satisfy the relationship of the number 17 in order to effectively utilize the reluctance torque.
然而，數17不成立之情形時、即數3之關係成立之情形時，難以活用磁阻轉矩。於此種狀況下，即便採用如圖11所示般之IPM構造，亦無法謀求輸出提高或效率提高，另一方面，由於因凸極比較大故q軸電感較大，故導致鐵損增加，而難以實現高速旋轉化。However, when the number 17 is not established, that is, when the relationship of the number 3 is established, it is difficult to utilize the reluctance torque. In such a situation, even if the IPM structure as shown in FIG. 11 is used, the output improvement or the efficiency improvement cannot be achieved. On the other hand, since the q-axis inductance is large due to the large salient pole, the iron loss is increased. It is difficult to achieve high-speed rotation.
因此，驅動時之定子交鏈磁通Ψ與上述Ψp滿足數4之關係此點較重要。對於該理由使用圖4進行說明。圖4係在dq軸上表示馬達驅動狀態之諸物理量者，關於與圖10重複之記號，由於其物理意義為同義故省略說明。Therefore, the relationship between the stator flux linkage 驱动 at the time of driving and the above Ψp satisfying the number 4 is important. This reason will be described using FIG. 4. 4 is a physical quantity indicating a motor driving state on the dq axis, and the symbols overlapping with FIG. 10 are omitted since their physical meanings are the same.
首先，驅動時之定子交鏈磁通Ψ以永久磁鐵3之定子線圈一相序部分之交鏈磁通Ψp(Wb)為起點，以因d軸電流Id產生之反作用磁通LdId與因q軸電流Iq產生之反作用磁通LqIq之矢量和表示。First, the stator interlinkage flux 驱动 at the time of driving is based on the interlinkage flux Ψp(Wb) of the phase sequence of the stator coil of the permanent magnet 3, and the reaction flux LdId and the q-axis generated by the d-axis current Id The vector sum representation of the reaction flux LqIq generated by the current Iq.
雖在圖4所示之dq軸上，Ψ為直流量，但自任意之定子線圈觀察之情形時為交流量，於捲繞有定子線圈之齒狀部分上，因Ψ之交流變化產生磁滯損與渦流損、即鐵損。由於一般磁滯損與Ψ之峰值成正比，渦流損與Ψ之峰值之平方成正比，故為減少鐵損，較理想為減小Ψ。然而，於先前之IPM構造中，由於一般為活用磁阻轉矩而增大Lq，故如自圖4亦明確般，伴隨LqIq矢量之伸長，Ψ易變得較Ψp更大。Although the Ψ is a direct current amount on the dq axis shown in FIG. 4, it is an alternating current amount when viewed from an arbitrary stator coil, and a hysteresis is generated due to a change in the alternating current on the toothed portion where the stator coil is wound. Damage and eddy current loss, ie iron loss. Since the general magnetic hysteresis loss is proportional to the peak value of enthalpy, the eddy current loss is proportional to the square of the peak value of enthalpy. Therefore, in order to reduce the iron loss, it is desirable to reduce enthalpy. However, in the previous IPM structure, since Lq is generally increased by utilizing the reluctance torque, as is clear from Fig. 4, the Ψ tends to become larger than Ψp with the elongation of the LqIq vector.
雖於可活用磁阻轉矩之情形時，由於必然流通負Id，故易利用LdId矢量抑制Ψ，但於無法活用磁阻轉矩之情形時，由於無須流通負Id，故無法抑制Ψ而導致鐵損增加。因此，於數3之關係成立之情形時、即無法活用磁阻轉矩之情形時，自減少鐵損之觀點出發同時滿足數4之關係此點極其重要。In the case where the reluctance torque can be used, since the negative Id is inevitably distributed, it is easy to suppress the enthalpy by using the LdId vector. However, when the reluctance torque cannot be utilized, since the negative Id does not need to be circulated, the enthalpy cannot be suppressed. Iron loss increased. Therefore, when the relationship of the number 3 is established, that is, when the reluctance torque cannot be utilized, it is extremely important to satisfy the relationship of the number 4 from the viewpoint of reducing the iron loss.
接著，對數4之重要性亦自高速旋轉化之觀點出發進行說明。於驅動時，若無視由定子線圈之電阻引起之電壓下降量，則可將馬達端子電壓V看作與定子交鏈磁通Ψ之時間微分等價，可以下式近似。另，如圖4所示，V以相對Ψ前進90deg.之矢量表示。Next, the importance of the logarithm 4 will be described from the viewpoint of high-speed rotation. When driving, regardless of the amount of voltage drop caused by the resistance of the stator coil, the motor terminal voltage V can be regarded as equivalent to the time differential of the stator flux linkage ,, and can be approximated by the following equation. In addition, as shown in FIG. 4, V is represented by a vector of 90 deg.
現在，若將馬達端子電壓之上限值設為Vmax，則如自數18而明 確般，可以減小Ψ之量增大ω，即可實現高速旋轉化。Now, if the upper limit of the motor terminal voltage is set to Vmax, then as shown in the number 18 Indeed, it is possible to reduce the amount of enthalpy and increase ω to achieve high-speed rotation.
根據以上，說明可藉由滿足數3之關係，且滿足數4之關係，謀求轉矩提高、效率提高、高速旋轉化之原理。From the above, it is explained that the principle of the torque increase, the efficiency improvement, and the high-speed rotation can be achieved by satisfying the relationship of the number 3 and satisfying the relationship of the number 4.
其中，作為如滿足數3之關係，且滿足數4之關係般之具體之構成，有如圖1所示般之轉子構造。Among them, as a specific configuration in which the relationship of the number 3 is satisfied and the relationship of the number 4 is satisfied, there is a rotor structure as shown in FIG.
在圖1中，於轉子1上，於永久磁鐵3之徑向外周部(外周側)配置有由非磁性體構成之切口7。又，鄰接之極8之磁極間之轉子鐵芯2構成為較上述永久磁鐵收納孔4之周向端部更向內周側凹陷。藉由設為此種構成降低q軸電感，緩和定子鐵芯之磁性飽和。尤其，藉由構成為使磁極間之轉子鐵芯2向內周側凹陷，可大幅減少欲透過永久磁鐵3之徑向內周部(內周側)之q軸磁通。根據以上之構成，可實現轉矩提高、鐵損減少、效率提高、及高速旋轉化。In FIG. 1, a slit 7 made of a non-magnetic material is disposed on the rotor 1 on the radially outer peripheral portion (outer peripheral side) of the permanent magnet 3. Further, the rotor core 2 between the magnetic poles of the adjacent poles 8 is formed to be recessed toward the inner peripheral side from the circumferential end portion of the permanent magnet housing hole 4. By setting this configuration as a q-axis inductance, the magnetic saturation of the stator core is alleviated. In particular, by arranging the rotor core 2 between the magnetic poles to be recessed toward the inner circumference side, the q-axis magnetic flux to be transmitted through the radially inner peripheral portion (inner circumferential side) of the permanent magnet 3 can be greatly reduced. According to the above configuration, the torque can be improved, the iron loss can be reduced, the efficiency can be improved, and the rotation can be performed at a high speed.
然而，驅動上述永久磁性同步電機之情形時，電流相位差角β雖可根據控制軟體之構成任意設定，但在滿足數3般之構成中，產生轉矩成最大之控制動作點存在於0deg.≦β≦22.5deg.之範圍。因此，藉由控制為成為上述相位，可更確實地謀求轉矩提高、效率提高。However, when the above-described permanent magnetic synchronous motor is driven, the current phase difference angle β can be arbitrarily set according to the configuration of the control software. However, in the configuration satisfying the number three, the control action point at which the maximum torque is generated exists at 0 deg. ≦β≦22.5deg. Therefore, by controlling to achieve the above-described phase, it is possible to more reliably improve the torque and improve the efficiency.
另，永久磁鐵3既可不於周向進行分割而一體地構成每1極，亦可於周向分割成複數個而配置。Further, the permanent magnets 3 may be integrally formed for each pole without being divided in the circumferential direction, or may be arranged in plural in the circumferential direction.
又，構成1極之永久磁鐵3及磁鐵收納孔4並不限定於1個。例如，亦可於周向分割構成1極之永久磁鐵3，並配合各個磁鐵設置磁鐵收納孔4，且於鄰接之收納孔之邊界上設置肋等。Further, the permanent magnet 3 and the magnet housing hole 4 constituting one pole are not limited to one. For example, the permanent magnet 3 that constitutes one pole may be divided in the circumferential direction, and the magnet housing hole 4 may be provided for each magnet, and ribs or the like may be provided on the boundary between the adjacent housing holes.
又，永久磁鐵3及磁鐵收納孔4既可於旋轉軸方向分割成複數個而構成，亦可不分割而一體地構成。Further, the permanent magnet 3 and the magnet housing hole 4 may be formed by being divided into a plurality of members in the direction of the rotation axis, or may be integrally formed without being divided.
轉子鐵芯2既可以於軸向堆疊之積層鋼板構成，亦可以壓製磁蕊等構成，且亦可以非晶質金屬等構成。The rotor core 2 may be formed of a laminated steel sheet which is stacked in the axial direction, or may be formed by pressing a magnetic core or the like, and may be formed of an amorphous metal or the like.
在本實施例中，磁鐵收納孔4形成為與構成1極之永久磁鐵之磁 極中心軸正交，又，自旋轉軸方向觀察為平板狀。收納於磁鐵收納孔4之永久磁鐵3亦配合磁鐵收納孔4之形狀而形成於平板上。由於藉由設為此種構成，除了可將磁鐵之成形製程抑制為最小限度，磁鐵之***步驟亦簡化，故可抑制製造成本。In the present embodiment, the magnet housing hole 4 is formed to be magnetic with a permanent magnet constituting one pole. The polar center axis is orthogonal, and is viewed as a flat plate from the direction of the rotating axis. The permanent magnet 3 accommodated in the magnet housing hole 4 is also formed on the flat plate in accordance with the shape of the magnet housing hole 4. According to this configuration, in addition to suppressing the molding process of the magnet to a minimum, the step of inserting the magnet is simplified, so that the manufacturing cost can be suppressed.
又，由於藉由將磁鐵收納孔設為平板狀，與V字狀之收納孔等相比較，可減小轉子鐵芯之每1極之外周部核心面積，故隨之可減小q軸電感。另，為減小轉子鐵芯之每1極之外周部核心面積，亦可以如向徑向外側凸出般之形狀而非平板狀構成磁鐵收納孔。In addition, since the magnet housing hole is formed in a flat shape, the core area of the outer peripheral portion of the rotor core can be reduced as compared with the V-shaped housing hole or the like, so that the q-axis inductance can be reduced. . Further, in order to reduce the core area of the outer peripheral portion of each of the rotor cores, the magnet housing holes may be formed in a shape that protrudes outward in the radial direction instead of the flat plate shape.
切口7只要配置為不會阻礙磁鐵磁通之透過的同時阻礙q軸磁通之透過即可，既可設為直線狀，亦可設為圓弧狀。又，既可一連串地構成，亦可以肋等分割而構成。又，於圖1中雖對每一極配置有4條，但若在可製作之範圍內則無論為幾條均可。又，各切口7之寬度既可為均一，亦可為不均一。The slit 7 may be arranged in a linear shape or an arc shape as long as it is disposed so as not to block the transmission of the magnetic flux of the magnet and hinder the transmission of the q-axis magnetic flux. Further, it may be configured in a series or in a rib or the like. Further, although four strips are arranged for each pole in Fig. 1, any number may be used in the range that can be produced. Moreover, the width of each slit 7 may be uniform or non-uniform.
切口7係如上述般阻礙q軸磁通之透過，而不會阻礙磁鐵磁通之透過。因此，切口7設置為相對在未設置有切口7之狀態下於轉子鐵芯2之永久磁鐵3之外周側產生之磁鐵磁通與q軸磁通，橫切q軸磁通，且設置為儘可能不橫切磁鐵磁通而沿著磁鐵磁通。若以符合該條件之方式設置切口7，則切口7成為於橫切q軸磁通之方向(沿著磁鐵磁通之方式)較長(尺寸較大)，而於橫切磁鐵磁通之方向(沿著q軸磁通之方向)較短(尺寸較小，或寬度較窄)之形狀。The slit 7 blocks the transmission of the q-axis magnetic flux as described above without hindering the transmission of the magnetic flux of the magnet. Therefore, the slit 7 is provided so as to be perpendicular to the q-axis magnetic flux and the q-axis magnetic flux generated on the outer peripheral side of the permanent magnet 3 of the rotor core 2 in a state where the slit 7 is not provided, and is set to be exhausted. It may not cross the magnet flux and follow the magnet flux. If the slit 7 is provided in such a manner that the condition is satisfied, the slit 7 becomes longer (larger in size) in the direction transverse to the q-axis magnetic flux (in the manner of the magnetic flux of the magnet), and is transverse to the direction of the magnetic flux of the magnet. (The direction along the q-axis flux) is shorter (smaller, or narrower) shape.
對切口7，參照圖5進一步詳細說明。圖5之構成與圖1不同之點為不僅於永久磁鐵3之徑向外周部(外周側)設置切口7a，亦於徑向內周部(內周側)設置有切口7b之點。The slit 7 will be described in further detail with reference to FIG. 5. The configuration of Fig. 5 is different from that of Fig. 1 in that not only the slit 7a is provided in the radially outer peripheral portion (outer peripheral side) of the permanent magnet 3 but also the slit 7b is provided on the radially inner peripheral portion (inner peripheral side).
在圖5中，d軸通過轉子1之旋轉中心(軸6之中心)O與磁鐵收納孔4之中央4o。永久磁鐵3以相對d軸線對稱之方式以嵌入之方式***至磁鐵收納孔4。永久磁鐵3亦可以留有空隙而非完全嵌入之方式***磁鐵 收納孔4。於本實施例中，由於d軸通過磁極之中央，故以下將d軸稱為磁極中央線30c1。In Fig. 5, the d-axis passes through the center of rotation of the rotor 1 (the center of the shaft 6) O and the center 4o of the magnet housing hole 4. The permanent magnet 3 is inserted into the magnet housing hole 4 so as to be symmetrical with respect to the d-axis. The permanent magnet 3 can also be inserted into the magnet without leaving a gap The hole 4 is accommodated. In the present embodiment, since the d-axis passes through the center of the magnetic pole, the d-axis is hereinafter referred to as a magnetic pole center line 30c1.
切口7a以在外周側接近磁極中央線30c1，於內周側遠離磁極中央線30c1之方式，相對磁極中央線30c1傾斜形成。即，切口7a以外周側端部相對內周側端部接近磁極中央線30c1之方式，相對磁極中央線30c1傾斜形成。具體而言，以自切口7a之中心線7ac1之外周側端部7ao降至磁極中央線30c1之垂線之長度(外周側端部7ao與磁極中央線30c1之距離)d7ao較自切口7a之中心線7ac1之內周側端部7ai降至磁極中央線30c1之垂線之長度(內周側端部7ai與磁極中央線30c1之距離)d7ai更短之方式，切口7a相對磁極中央線30c1傾斜。The slit 7a is formed to be inclined with respect to the magnetic pole center line 30c1 so as to be close to the magnetic pole center line 30c1 on the outer peripheral side and away from the magnetic pole center line 30c1 on the inner peripheral side. In other words, the outer peripheral end portion of the slit 7a is formed to be inclined with respect to the magnetic pole center line 30c1 so that the inner peripheral end portion is close to the magnetic pole center line 30c1. Specifically, the length from the outer peripheral side end portion 7ao of the center line 7ac1 of the slit 7a to the perpendicular line of the magnetic pole center line 30c1 (the distance between the outer peripheral side end portion 7ao and the magnetic pole center line 30c1) d7ao is smaller than the center line of the slit 7a. The inner peripheral end portion 7ai of 7ac1 is reduced to the length of the perpendicular line of the magnetic pole center line 30c1 (the distance between the inner peripheral side end portion 7ai and the magnetic pole center line 30c1) d7ai is shorter, and the slit 7a is inclined with respect to the magnetic pole center line 30c1.
切口7a在一個磁極中，至少形成於磁極中央線30c1之單側。本實施例之情形時，於磁極中央線30c1之兩側形成有切口7a。又，形成於磁極中央線30c1之兩側之切口7a形成為相對磁極中央線30c1線對稱。藉由將切口7a形成為相對磁極中央線30c1線對稱，關於磁鐵磁通與q軸磁通之透過性之設計變得容易。然而，並非必須將切口7a形成為相對磁極中央線30c1線對稱。The slit 7a is formed in at least one side of the magnetic pole center line 30c1 in one magnetic pole. In the case of this embodiment, slits 7a are formed on both sides of the magnetic pole center line 30c1. Further, the slits 7a formed on both sides of the magnetic pole center line 30c1 are formed to be line symmetrical with respect to the magnetic pole center line 30c1. By forming the slit 7a to be line-symmetric with respect to the magnetic pole center line 30c1, the design of the permeability of the magnetic flux of the magnet and the magnetic flux of the q-axis becomes easy. However, it is not necessary to form the slit 7a to be line symmetrical with respect to the magnetic pole center line 30c1.
切口7a在圖5中，雖以具有上述傾斜之方式形成為直線狀，但亦可形成為圓弧狀。將切口7a形成為圓弧狀之情形時，只要以沿著磁鐵磁通之方式向磁極中央線30c1描繪凸形狀之曲線即可。In FIG. 5, the slit 7a is formed in a linear shape so as to have the above-described inclination, but may be formed in an arc shape. When the slit 7a is formed in an arc shape, a curve of a convex shape may be drawn toward the magnetic pole center line 30c1 along the magnetic flux of the magnet.
接著，對圖5所示之切口7b進行說明。另，由於不設置切口7b之情形時亦可獲得由切口7a所致之效果，故並非必須設置切口7b。然而，藉由設置切口7b，可獲得以下說明之效果。Next, the slit 7b shown in Fig. 5 will be described. Further, since the effect by the slit 7a can be obtained even when the slit 7b is not provided, it is not necessary to provide the slit 7b. However, by providing the slit 7b, the effects described below can be obtained.
切口7b設置於永久磁鐵3之徑向內周部(內周側)，且與切口7a同樣地以非磁性體構成。The slit 7b is provided on the radially inner peripheral portion (inner peripheral side) of the permanent magnet 3, and is made of a non-magnetic material similarly to the slit 7a.
藉由設為此種構成，q軸電感之降低效果進一步提高，而可進一步緩和定子鐵芯之磁性飽和。藉此，可實現永久磁性同步電機之進一 步之高速旋轉驅動的同時可謀求進一步之轉矩提高及效率提高。切口7b只要配置為不會阻礙磁鐵磁通之透過的同時阻礙q軸磁通之透過即可，既可設為直線狀，亦可設為圓弧狀。又，既可一連串地構成，亦可以肋等分割而構成。又，若在可製作之範圍內則無論為幾條均可。又，各切口之寬度既可為均一，亦可為不均一。With such a configuration, the effect of reducing the q-axis inductance is further improved, and the magnetic saturation of the stator core can be further alleviated. Thereby, the permanent magnetic synchronous motor can be realized The high-speed rotary drive of the step can achieve further torque improvement and efficiency improvement. The slit 7b may be arranged so as not to block the transmission of the magnetic flux of the magnet and block the transmission of the q-axis magnetic flux, and may be linear or arcuate. Further, it may be configured in a series or in a rib or the like. Moreover, it can be any number if it is within the range that can be produced. Moreover, the width of each slit may be either uniform or non-uniform.
此處，作為切口7b之另一效果有永久磁鐵3之耐去磁性提高。永久磁鐵3之不可逆去磁之產生係於定子線圈於與永久磁鐵3之磁化方向為相反之方向產生過大之磁場時。定子線圈產生之磁場之大小雖與電流之大小與繞組之折回數、即安匝折回成正比，但若考慮安匝折回固定之情形，則施加於永久磁鐵3之磁場(以下，去磁磁場)之大小根據與間隙部分或定子鐵芯或轉子鐵芯之磁阻之兼顧而決定。即，永久磁鐵3以外之部分之磁阻越大，去磁磁場(施加於永久磁鐵3之磁場)越小。此處，若考慮無切口7b之情形，則由於永久磁鐵3之徑向內周部核心部分中無阻礙磁通之透過之因素，故磁阻非常小。與此相對，由於藉由設置切口7b，而磁通沿著切口7b透過，故限定磁路磁阻增加。藉此，由於可減小去磁磁場(施加於永久磁鐵3之磁場)，故永久磁鐵3之耐去磁性提高。Here, as another effect of the slit 7b, the demagnetization resistance of the permanent magnet 3 is improved. The irreversible demagnetization of the permanent magnet 3 is caused when the stator coil generates an excessive magnetic field in a direction opposite to the magnetization direction of the permanent magnet 3. The magnitude of the magnetic field generated by the stator coil is proportional to the magnitude of the current and the number of turns of the winding, that is, the fold of the ampoule. However, considering the case where the ampoule is folded back, the magnetic field applied to the permanent magnet 3 (hereinafter, the demagnetizing field) The size is determined according to the balance between the gap portion or the magnetic resistance of the stator core or the rotor core. That is, the larger the magnetic resistance of the portion other than the permanent magnet 3, the smaller the demagnetizing field (the magnetic field applied to the permanent magnet 3). Here, considering the case where the slit 7b is not provided, the magnetic resistance is extremely small because there is no factor that hinders the transmission of the magnetic flux in the core portion of the radially inner peripheral portion of the permanent magnet 3. On the other hand, since the magnetic flux is transmitted along the slit 7b by providing the slit 7b, the magnetic resistance of the magnetic path is limited to increase. Thereby, since the demagnetizing field (the magnetic field applied to the permanent magnet 3) can be reduced, the demagnetization resistance of the permanent magnet 3 is improved.
另，於如圖6所示般之構成中亦可獲得與本實施例中敍述之效果相同之效果。圖6之構成與圖5不同之點為於轉子鐵芯2之外周部之磁極間設置肋102，且於其內周側設置q軸空孔103之點。於設為此種構成之情形時亦可大幅降低欲透過永久磁鐵3之徑向內周部(內周側)之q軸磁通，而可緩和定子之磁性飽和。又，由於藉由設置肋102，相對於永久磁鐵3之外周部核心起作用之離心力載荷強度提高，故可實現進一步之高速旋轉化。設置肋102之位置，於圖6中雖設為較永久磁鐵3更靠向外周側，但若可獲得上述效果，則並非必須設為永久磁鐵3之外周側，既可與永久磁鐵3設置於同一圓周上附近，亦可設置於永久 磁鐵3之內周側。又，肋102之寬度可在可謀求永久磁鐵3之漏磁通減少與轉子強度提高之併存之範圍內任意設定。又，q軸空孔103在圖6中雖設為半圓狀之形狀，但若可減少q軸磁通，其形狀可並不一定為半圓狀。又，q軸空孔103在圖6中雖於極間每1部位僅設置有1個，但亦可設置2個或其以上之複數個。Further, in the configuration as shown in Fig. 6, the same effects as those described in the embodiment can be obtained. The configuration of Fig. 6 is different from that of Fig. 5 in that a rib 102 is provided between the magnetic poles on the outer peripheral portion of the rotor core 2, and a q-axis void 103 is provided on the inner peripheral side thereof. In the case of such a configuration, the q-axis magnetic flux to be transmitted through the radially inner peripheral portion (inner peripheral side) of the permanent magnet 3 can be greatly reduced, and the magnetic saturation of the stator can be alleviated. Further, since the rib 102 is provided, the centrifugal load load acting on the outer peripheral core of the permanent magnet 3 is increased, so that further high-speed rotation can be realized. Although the position of the rib 102 is set to be on the outer peripheral side of the permanent magnet 3 in FIG. 6, if the above effect is obtained, it is not necessarily required to be the outer peripheral side of the permanent magnet 3, and the permanent magnet 3 may be provided on the permanent magnet 3. Near the same circumference, it can also be set to permanent The inner peripheral side of the magnet 3. Further, the width of the rib 102 can be arbitrarily set within a range in which the leakage flux of the permanent magnet 3 is reduced and the strength of the rotor is increased. Further, although the q-axis void 103 has a semicircular shape in FIG. 6, the shape of the q-axis magnetic flux may not be semicircular. Further, although the q-axis hole 103 is provided in only one place per pole between the poles in FIG. 6, a plurality of two or more may be provided.
以下，使用圖7對本發明之第2實施例進行說明。圖7係本發明之第2實施例之馬達特性之一例。Hereinafter, a second embodiment of the present invention will be described with reference to Fig. 7 . Fig. 7 is a view showing an example of the motor characteristics of the second embodiment of the present invention.
在本實施例中，如圖7所示，於在最大電流通電狀態下產生最大轉矩Me，max之永久磁性同步電機中，藉由構成為將馬達端子電壓成為Vmax時之旋轉數設為Nsat，另一方面，將因外部驅動而產生之感應電動勢成為Vmax時之旋轉數設為Nmax，而Nmax<Nsat，可實現高速旋轉化。In the present embodiment, as shown in FIG. 7, in the permanent magnetic synchronous motor that generates the maximum torque Me,max in the maximum current energization state, the number of rotations when the motor terminal voltage becomes Vmax is set to Nsat. On the other hand, when the induced electromotive force generated by external driving is Vmax, the number of rotations is Nmax, and Nmax < Nsat, and high-speed rotation can be realized.
如實施例1中敍述般，由於電壓以數18表示，故於數4之關係成立之情形時，Nmax<Nsat成立。As described in the first embodiment, since the voltage is represented by the number 18, when the relationship of the number 4 is established, Nmax < Nsat is established.
以下，使用圖12對本發明之第3實施例進行說明。圖12係本實施例之壓縮機之剖面構造圖。Hereinafter, a third embodiment of the present invention will be described with reference to Fig. 12 . Figure 12 is a cross-sectional structural view of the compressor of the present embodiment.
在圖12中，壓縮機構部咬合直立於固定捲動構件13之端板14之螺旋狀搭接15與直立於旋轉捲動構件16之端板17之螺旋狀搭接18而形成。且，藉由利用曲軸6使旋轉捲動構件16旋轉運動而進行壓縮動作。包含固定捲動構件13及旋轉捲動構件16之壓縮室19(19a、19b、......)中，位於最外徑側之壓縮室19隨著旋轉運動向兩捲動構件13、16之中心移動，而容積逐漸縮小。In Fig. 12, the compression mechanism portion is formed by a helical overlap 15 which is erected to the end plate 14 of the fixed scroll member 13 and a spiral overlap 18 which is erected on the end plate 17 of the rotary scroll member 16. Further, the compression operation is performed by rotating the rotary scroll member 16 by the crankshaft 6. Among the compression chambers 19 (19a, 19b, ...) including the fixed scroll member 13 and the rotary scroll member 16, the compression chamber 19 on the outermost diameter side is rotated toward the two scroll members 13, The center of 16 moves, and the volume gradually shrinks.
兩壓縮室19a、19b到達兩捲動構件13、16之中心附近後，兩壓縮室19內之壓縮氣體自與壓縮室19連通之噴出口20噴出。噴出之壓縮氣 體通過設置於固定捲動構件13及框架21之氣體通路(未圖示)到達至框架21下部之壓力容器22內，且自設置於壓力容器22之側壁之噴出管23排出至壓縮機外。於壓力容器22內，內封包含定子9與轉子1之永久磁鐵馬達103，藉由轉子1旋轉，進行壓縮動作。於永久磁鐵馬達103之下部，設置有油積存部25。油積存部25內之油藉由因旋轉運動產生之壓力差，通過設置於曲軸6內之油孔26，供旋轉捲動構件16與曲軸6之滑動部、滑動軸承27等之潤滑。於壓力容器22之側壁設置用以將定子線圈12抽出至壓力容器22之外側之端子箱30，例如，三相永久磁鐵馬達之情形時，供應總計3個U、V、W各繞組之端子。藉由對永久磁鐵馬達103應用上述實施例1、或實施例2所記載之永久磁性同步電機，可驅動至更高速旋轉的同時可謀求轉矩提高及效率提高。After the two compression chambers 19a, 19b reach the vicinity of the center of the two scroll members 13, 16, the compressed gas in the two compression chambers 19 is ejected from the discharge port 20 that communicates with the compression chamber 19. Squirting compressed gas The body reaches the pressure vessel 22 at the lower portion of the frame 21 through a gas passage (not shown) provided in the fixed scroll member 13 and the frame 21, and is discharged from the discharge pipe 23 provided at the side wall of the pressure vessel 22 to the outside of the compressor. The permanent magnet motor 103 including the stator 9 and the rotor 1 is sealed in the pressure vessel 22, and the rotor 1 is rotated to perform a compression operation. An oil reservoir 25 is provided below the permanent magnet motor 103. The oil in the oil reservoir 25 is lubricated by the oil hole 26 provided in the crankshaft 6 by the pressure difference due to the rotational motion, and the sliding portion of the rotary scroll member 16 and the crankshaft 6, the sliding bearing 27, and the like are lubricated. A terminal box 30 for drawing the stator coil 12 to the outside of the pressure vessel 22 is provided on the side wall of the pressure vessel 22, for example, in the case of a three-phase permanent magnet motor, a total of three terminals of U, V, W windings are supplied. By applying the permanent magnetic synchronous motor described in the first embodiment or the second embodiment to the permanent magnet motor 103, it is possible to drive to a higher speed and to improve the torque and improve the efficiency.
然而，於現在之家庭用.工作用空調機中，於壓縮容器22內封入R410A冷媒者較多，而永久磁鐵馬達103之周圍溫度成為80℃以上之情形較多。由於今後若進一步採用地球溫室效應係數更小之R32冷媒則周圍溫度進一步上升，故磁鐵之Br降低更顯著。於此種情形時，藉由應用上述實施例1、或實施例2所記載之永久磁性同步電機，可彌補因Br降低引起之轉矩降低、效率降低。尤其於以鐵氧體磁鐵構成永久磁鐵3之情形時，由於以釹磁鐵將成為問題之高溫去磁原理上不會產生，故成為對伴隨R32冷媒採用之周圍溫度上升有效之對策。另，對本實施例之壓縮機應用上述實施例1、或實施例2所記載之永久磁性同步電機時，並不限制冷媒之種類。However, in the conventional home air conditioner, there are many cases in which the R410A refrigerant is sealed in the compression container 22, and the ambient temperature of the permanent magnet motor 103 is often 80 ° C or more. In the future, if the R32 refrigerant having a smaller global warming coefficient is further used, the ambient temperature is further increased, so that the Br reduction of the magnet is more remarkable. In such a case, by applying the permanent magnetic synchronous motor described in the first embodiment or the second embodiment, it is possible to compensate for the torque reduction and the efficiency reduction caused by the Br reduction. In particular, when the permanent magnet 3 is formed of a ferrite magnet, the high-temperature demagnetization which is a problem caused by the neodymium magnet does not occur in principle, and therefore it is effective for the increase in the ambient temperature accompanying the R32 refrigerant. Further, when the permanent magnetic synchronous motor described in the first embodiment or the second embodiment is applied to the compressor of the present embodiment, the type of the refrigerant is not limited.
另，壓縮機構成既可為圖12所記載之捲動壓縮機，亦可為旋轉壓縮機，且亦可為具有其他壓縮機構之構成。又，根據本發明，可如以上說明般實現小型且高輸出之馬達。於是可擴大可實現高速運轉等之運轉範圍，進而，於He或R32等冷媒中，與R22、R407C、R410A等冷媒相比較，由於自空隙之漏泄變大，尤其低速運轉時漏泄相對循環 量之比例顯著變大，故效率較低較大。藉由為提高低循環量(低速運轉)時之效率而將壓縮機構部小型化，且為獲得相同之循環量而提高旋轉數，減少漏泄損失雖可成為有效之方法，但為確保最大循環量亦需要提高最大旋轉數。根據具備本發明之永久磁性同步電機之壓縮機，可提高最大旋轉數，而成為對He或R32等冷媒之效率提高有效之機構。Further, the compressor configuration may be a scroll compressor as shown in FIG. 12, a rotary compressor, or a compression mechanism. Further, according to the present invention, a small and high output motor can be realized as described above. Therefore, the operating range such as high-speed operation can be expanded, and in the refrigerant such as He or R32, the leakage from the gap becomes larger than that of the refrigerant such as R22, R407C, and R410A, especially in the case of low-speed operation. The proportion of the amount is significantly larger, so the efficiency is lower. By reducing the efficiency of the low circulation amount (low speed operation) and miniaturizing the compression mechanism portion, it is effective to reduce the leakage loss in order to obtain the same circulation amount, and to reduce the leakage loss, but to ensure the maximum circulation amount. It is also necessary to increase the maximum number of rotations. According to the compressor including the permanent magnetic synchronous motor of the present invention, the maximum number of revolutions can be increased, and the mechanism for improving the efficiency of the refrigerant such as He or R32 can be obtained.
1‧‧‧轉子1‧‧‧Rotor
2‧‧‧轉子鐵芯2‧‧‧Rotor core
3‧‧‧永久磁鐵3‧‧‧ permanent magnet
4‧‧‧永久磁鐵收納孔4‧‧‧Permanent magnet housing hole
5‧‧‧鉚接用鉚釘5‧‧‧ Rivet rivets
6‧‧‧軸或曲軸6‧‧‧Axis or crankshaft
6a‧‧‧貫通孔6a‧‧‧through hole
7‧‧‧切口7‧‧‧ incision
8‧‧‧極8‧‧‧ pole
9‧‧‧定子9‧‧‧ Stator
10‧‧‧定子鐵芯10‧‧‧ Stator core
11‧‧‧齒狀部分11‧‧‧ toothed part
12u1、12u2、12u3、12v1、12v2、12v3、12w1、12w2、12w3‧‧‧定子線圈12u1, 12u2, 12u3, 12v1, 12v2, 12v3, 12w1, 12w2, 12w3‧‧‧ stator coil
Claims (11)
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| JP2013093174A JP6002625B2 (en) | 2013-04-26 | 2013-04-26 | Permanent magnet synchronous machine and compressor using the same |
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| TW201442398A TW201442398A (en) | 2014-11-01 |
| TWI500239B true TWI500239B (en) | 2015-09-11 |
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| JP (1) | JP6002625B2 (en) |
| CN (1) | CN105103412B (en) |
| TW (1) | TWI500239B (en) |
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| JP2017055583A (en) * | 2015-09-10 | 2017-03-16 | ジョンソンコントロールズ ヒタチ エア コンディショニング テクノロジー（ホンコン）リミテッド | Permanent magnet type rotary electrical machine and compressor using the same |
| JP6894663B2 (en) * | 2015-10-29 | 2021-06-30 | 株式会社富士通ゼネラル | Rotor and permanent magnet motor |
| JP6455725B2 (en) * | 2015-11-03 | 2019-01-23 | 株式会社デンソー | Rotating electric machine |
| CN105790458B (en) * | 2016-04-13 | 2018-07-27 | 广东美芝制冷设备有限公司 | Magneto and compressor, air conditioner with it |
| JP6381613B2 (en) * | 2016-11-28 | 2018-08-29 | 日立ジョンソンコントロールズ空調株式会社 | Permanent magnet type rotating electric machine and compressor using the same |
| CN106816973A (en) * | 2017-03-28 | 2017-06-09 | 梁洪炘 | DC low-speed motor and its large-scale ceiling fan and Amorphous Cores and its manufacturing process |
| DE102017208036A1 (en) * | 2017-05-12 | 2018-11-15 | Robert Bosch Gmbh | stator |
| JP6518720B2 (en) * | 2017-06-07 | 2019-05-22 | 日立ジョンソンコントロールズ空調株式会社 | Permanent magnet type rotary electric machine and compressor using the same |
| CN107394919B (en) * | 2017-07-28 | 2023-04-07 | 广东美芝制冷设备有限公司 | Compressor motor, inverter compressor and air conditioner |
| JP7126551B2 (en) * | 2018-08-28 | 2022-08-26 | 日立ジョンソンコントロールズ空調株式会社 | Permanent magnet type rotary electric machine and compressor using the same |
| JP2020188594A (en) * | 2019-05-15 | 2020-11-19 | 日立ジョンソンコントロールズ空調株式会社 | Permanent magnet type rotary electric machine and compressor using the same |
| JP2022086386A (en) * | 2020-11-30 | 2022-06-09 | 三菱重工サーマルシステムズ株式会社 | Electric motor |
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- 2013-11-28 TW TW102143577A patent/TWI500239B/en not_active IP Right Cessation
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- 2014-01-28 WO PCT/JP2014/051824 patent/WO2014174864A1/en active Application Filing
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| CN1098826A (en) * | 1993-04-30 | 1995-02-15 | 三洋电机株式会社 | The rotor of electric moto used in compressor |
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| JP2014217189A (en) | 2014-11-17 |
| JP6002625B2 (en) | 2016-10-05 |
| TW201442398A (en) | 2014-11-01 |
| CN105103412A (en) | 2015-11-25 |
| WO2014174864A1 (en) | 2014-10-30 |
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