TWI397250B - Two way full bridge zero-voltage and zero-current switching dc-dc converter - Google Patents
Two way full bridge zero-voltage and zero-current switching dc-dc converter Download PDFInfo
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Description
本發明係有關於一種雙向全橋式零電壓-零電流直流/直流轉換器，尤其是指一種具有隔離型式與雙向電能傳輸之直流/直流轉換器，其能利用在電力電子技術領域如：電池充放電系統、分散式電源供應系統、直流/直流電源供應器、不斷電系統等，以能經零電壓與零電流切換使得整體效率提升，而在其整體施行使用上更增實用功效特性的雙向全橋式零電壓-零電流直流/直流轉換器創新設計者。The invention relates to a bidirectional full-bridge zero-voltage-zero current DC/DC converter, in particular to a DC/DC converter with isolated type and bidirectional power transmission, which can be utilized in the field of power electronics technology such as battery Charge and discharge system, decentralized power supply system, DC/DC power supply, uninterruptible power system, etc., so that the overall efficiency can be improved by switching between zero voltage and zero current, and the utility model is more effective in its overall implementation. An innovative designer of bidirectional full-bridge zero-voltage-zero current DC/DC converters.
按，已知的雙向直流/直流轉換器可應用於電池充放電系統、分散式電源供應系統、不斷電系統的場合，其中，就現有雙向直流/直流轉換器的相關技術化如下：According to the known bidirectional DC/DC converter, it can be applied to a battery charging and discharging system, a distributed power supply system, and an uninterruptible power system. The related technicalization of the existing bidirectional DC/DC converter is as follows:
請參閱在93年9月11日所公告之「具中性點之雙向直流/直流轉換裝置」所示，其具有一第一直流電壓端點及一第二直流電壓端點用以作為能量雙向傳遞之輸入或輸出端。由於該第二直流電壓端點組之正端及負端之間的電壓等於該輸入直流電壓源之電壓及電容器之電壓串接相加，因此該第二直流電壓端點組之正端及負端之間的電壓等於該輸入直流電壓源電壓之兩倍，由於該電容器之電壓與該輸入直流電壓源之電壓相等，因此該第二直流電壓端點組之中性端之電壓恰等於該第二直流電壓端點組之正端及負端間電壓的一半，所以該等壓之中 性端視為中性點輸出，因此其在該能量傳遞方向可完成一具中性點輸出之倍壓功能，且該電容器之耐壓僅需該第二直流電壓端點組之正端及負端間電壓的一半，因此可降低該電容器之電壓額定。Please refer to the "Non-Directional DC/DC Converter with Neutral Point" announced on September 11, 1993, which has a first DC voltage endpoint and a second DC voltage endpoint for energy bidirectional The input or output that is passed. Since the voltage between the positive terminal and the negative terminal of the second DC voltage end group is equal to the voltage of the input DC voltage source and the voltage of the capacitor are connected in series, the positive terminal and the negative terminal of the second DC voltage end group The voltage between the terminals is equal to twice the voltage of the input DC voltage source. Since the voltage of the capacitor is equal to the voltage of the input DC voltage source, the voltage of the neutral terminal of the second DC voltage end group is exactly equal to the first Two voltages between the positive and negative terminals of the DC voltage end group, so the pressure is equal The sex end is regarded as the neutral point output, so it can complete the double voltage function of the neutral point output in the energy transfer direction, and the withstand voltage of the capacitor only needs the positive end and the negative end of the second DC voltage end point group. Half of the voltage between the terminals, thus reducing the voltage rating of the capacitor.
請再參閱98年1月1日所公告之「高效率單級式多重輸入雙向轉換器」所示，其利用潔淨能源具有電壓易隨負載變動而變化之自然特性，以及蓄電池之穩定電壓源特性，依據所規劃開關切換情形可操作於放電狀態、獨立狀態及充電狀態。兩者電壓源皆直接以電壓源型式作為三繞組耦合電感之輸入端。當蓄電池與潔淨能源同時聯合供電時，潔淨能源所屬之繞組電壓，將依據蓄電池所屬之繞組電壓做電壓調節，與蓄電池所屬之繞組電壓達成平衡，因此不需要複雜的控制方法及額外的電路設計，即可克服電壓源輸入時繞組電壓不一致之問題。充電迴路亦透過耦合電感做能量傳遞，具有低壓轉換形式，故能源利用率高於傳統輔助電源系統。所需之開關及二極體皆具有電壓箝制效果，有效處理漏感能量所造成之電壓突波現象，並利用漏感具限制電流瞬間變化之特性，使二極體無逆向高恢復電流。Please refer to the "High Efficiency Single-Phase Multiple Input Bidirectional Converter" announced on January 1, 1998. It uses clean energy to have the natural characteristics that the voltage is easy to change with load changes, and the stable voltage source characteristics of the battery. According to the planned switching situation, the battery can be operated in a discharging state, an independent state, and a charging state. Both voltage sources directly use the voltage source type as the input terminal of the three-winding coupled inductor. When the battery and the clean energy are jointly supplied, the winding voltage of the clean energy will be adjusted according to the winding voltage of the battery, and the winding voltage of the battery is balanced, so no complicated control method and additional circuit design are needed. It can overcome the problem of inconsistent winding voltage when the voltage source is input. The charging circuit also transmits energy through the coupled inductor, and has a low-voltage conversion form, so the energy utilization rate is higher than that of the conventional auxiliary power supply system. The required switches and diodes have a voltage clamping effect, which effectively processes the voltage surge caused by the leakage inductance energy, and utilizes the leakage inductance to limit the instantaneous change of the current, so that the diode has no reverse high recovery current.
請再參閱93年2月11日所公告之「雙向返馳切換式電源供應器」所示，其包括：一具有相互電感耦合之主繞組及次繞組的變壓器，該主繞組係耦合至該轉換器的電壓輸入，而該次繞組則係耦合至該轉換器的電壓輸出；一主控制單元，其包括 與該主繞組串聯配置的主切換開關；一次控制單元，其包含與該次繞組串聯配置的次切換開關；其特徵為，該主控制單元可用以補償輸入電壓變化，而其中該次控制單元則可用以在該次級側提供一受控制的輸出功率。該轉換器使用到兩個控制器：一個係主切換開關的控制器，另一個則係次切換開關的控制器，故增加了控制電路的複雜度。根據本發明，該兩個切換開關的控制信號之間的空滯時間以及正確的變壓器電流方向可以造成零電壓切換，因此降低切換損失。Please refer to the "bidirectional flyback switching power supply" announced on February 11, 1993, which includes: a transformer having a primary winding and a secondary winding inductively coupled to each other, the primary winding being coupled to the conversion Voltage input of the device, and the secondary winding is coupled to the voltage output of the converter; a main control unit, which includes a primary switching switch configured in series with the primary winding; a primary control unit including a secondary switching switch configured in series with the secondary winding; wherein the primary control unit is operable to compensate for input voltage changes, wherein the secondary control unit is It can be used to provide a controlled output power on the secondary side. The converter uses two controllers: one is the controller that switches the switch, and the other is the controller that switches the switch, which increases the complexity of the control circuit. According to the present invention, the dead time between the control signals of the two changeover switches and the correct direction of the transformer current can cause zero voltage switching, thus reducing switching losses.
請再參閱96年4月1日所公開之「用於燃料電池電動車驅動系統之雙向直流/直流轉換器」所示，其所揭示之隔離式雙向轉換器，依據電力潮流方向具有兩種操作模式。當昇壓模式時，此時電能轉換器係當作一電流源轉換器電路，以提升直流匯流排電壓。低壓側開關以非對稱方式操作，並具有一段很短的重疊導通區間，由於此導通區間非常短，因此大部分時間變壓器低壓側繞組電流僅流過一個開關，所以開關所造成的導通損失降低，並改善轉換器的效率。當所揭示之雙向電能轉換器操作於降壓模式時，高壓直流匯流排回充能量至蓄電池，此時電能轉換器可當作一具同步整流倍流器之非對稱半橋轉換器，高壓側開關亦以非對稱方式操作，並具有很短的盲時(Dead Time)區間。因開關皆以非對稱方式操作，故控制電路設計較不容易。Please refer to the "Bidirectional DC/DC Converter for Fuel Cell Electric Vehicle Drive System" published on April 1, 1996. The isolated bidirectional converter disclosed has two operations depending on the power flow direction. mode. When in boost mode, the power converter is now used as a current source converter circuit to boost the DC bus voltage. The low-voltage side switch operates in an asymmetric manner and has a short overlapping conduction interval. Since the conduction interval is very short, most of the time, the low-voltage side winding current of the transformer flows only through one switch, so the conduction loss caused by the switch is reduced. And improve the efficiency of the converter. When the disclosed bidirectional power converter operates in the buck mode, the high voltage DC bus recirculates back to the battery, and the power converter can be used as an asymmetric half bridge converter with a synchronous rectification current divider, the high voltage side The switch also operates in an asymmetrical manner with a short Dead Time interval. Since the switches operate in an asymmetric manner, the control circuit design is not easy.
本發明之雙向全橋式零電壓-零電流直流/直流轉換器，其主要是利用變壓器本身的等效漏電感量與一個電容來達到諧振電路，使得電路架構中主要開關，在導通與截止時皆操作於零電壓-零電流的狀態，降低了電路中開關的損耗，有助於整體系統上的效率提高，且運用同步整流技術，降低輸出二極體的高導通損耗；藉此，而在其整體施行使用上更增實用功效特性者。The bidirectional full-bridge zero-voltage-zero current DC/DC converter of the invention mainly utilizes the equivalent leakage inductance of the transformer itself and a capacitor to reach the resonant circuit, so that the main switch in the circuit structure is turned on and off. Both operate in a zero-voltage-zero current state, reducing the loss of the switch in the circuit, contributing to the efficiency improvement of the overall system, and using synchronous rectification technology to reduce the high conduction loss of the output diode; The overall implementation of the use of more practical features.
為令本發明所運用之技術內容、發明目的及其達成之功效有更完整且清楚的揭露，茲於下詳細說明之，並請一併參閱所揭之圖式及圖號：For a more complete and clear disclosure of the technical content, the purpose of the invention and the effects thereof achieved by the present invention, it is explained in detail below, and please refer to the drawings and drawings:
首先，請參閱第一圖本發明之主電路架構圖所示，本發明主要係包含：輸入電感(1)、(2)，主要是將輸入電壓轉換成一具有漣波小且平穩的直流輸入電流；一變壓器(3)，包含一次側繞組(31)及一二次側繞組(32)；一負載裝置(4)連接設置於放電時之電源輸出端〔請一併參閱第三圖本發明之轉換器於昇壓/放電模式電路圖所示〕；數第一開關元件(5)，其包含了寄生電容(51)與寄生二極體(52)，連接該變壓器(3)之一次側繞組(31)，以利用諧振電路的特徵，使得其在導通與截止於零電壓與零電流狀態下切換；數第二開關元件(6)，其同樣包含了寄生電容(61)與寄生二極體(62)，且可為一全橋式功率開關電路所組成，與該 變壓器(3)之二次側繞組(32)連接，主要是將該變壓器(3)所提供之交流電源整流成一直流電源；及輸入電感(1)、(2)分別與諧振電容(7)及電容(8)連接後，再令諧振電容(7)與第一開關元件(5)連接及令電容(8)與第二開關元件(6)連接。First, please refer to the first diagram of the main circuit architecture diagram of the present invention. The present invention mainly includes: input inductors (1), (2), mainly converting the input voltage into a small DC input current with a quiet and smooth current. a transformer (3) comprising a primary side winding (31) and a secondary side winding (32); a load device (4) connected to the power output end of the discharge device (please refer to the third figure of the present invention) The converter is shown in the step-up/discharge mode circuit diagram; the first switching element (5) includes a parasitic capacitor (51) and a parasitic diode (52) connected to the primary winding of the transformer (3) ( 31) to utilize the characteristics of the resonant circuit such that it switches between on and off zero voltage and zero current; the second switching element (6), which also contains parasitic capacitance (61) and parasitic diode ( 62), and may be composed of a full bridge power switch circuit, and The secondary winding (32) of the transformer (3) is connected, mainly to rectify the AC power supply provided by the transformer (3) into a DC power supply; and the input inductors (1), (2) and the resonant capacitor (7) and After the capacitor (8) is connected, the resonant capacitor (7) is connected to the first switching element (5) and the capacitor (8) is connected to the second switching element (6).
本發明於操作上可分為二種模式：降壓/充電模式與昇壓/放電模式。在降壓/充電模式時，請一併參閱第二圖本發明之轉換器於降壓/充電模式電路圖所示，將電路中之第一開關元件(5)Q 1 ~Q 4 作為主要開關使用，其中於Q 1 ~Q 4 中之C s 1 ~C s 4 及D s 1 ~D s 4 分別為第一開關元件(5)Q 1 ~Q 4 的寄生電容(51)及寄生二極體(52)〔Body Diode〕，而第二開關元件(6)Q a 1 ~Q a 4 則作為同步整流開關使用，輸入電感(1)L in 1 ，而變壓器(3)會產生漏電感(33)、(34)L lkp 、L lks 、諧振電容(7)C r 1 ，電容(8)C r 2 及負載裝置(4)R load ；而在昇壓/放電模式中，請一併參閱第三圖本發明之轉換器於昇壓/放電模式電路圖所示，則將第二開關元件(6)Q a 1 ~Q a 4 作為電路主要開關，其中C sa 1 ~C sa 4 及D sa 1 ~D sa 4 分別為Q a 1 ~Q a 4 主開關的寄生電容(61)及寄生二極體(62)〔Body Diode〕，而第一開關元件(5)Q 1 ~Q 4 則作為同步整流開關使用，輸入電感(2)L in 2 ，而變壓器(3)會產生漏電感(33)、(34)L lkp 、L lks 、諧振電容(7)C r 1 ，電容(8)C r 2 及負載裝置(4)R load 。請再一併參閱第四圖本發明之轉換器於降壓/充電模式時，開關主 要控制時序與零電壓-零電流切換的工作時序圖及第五圖本發明之轉換器於昇壓/放電模式時，開關主要控制時序與零電壓-零電流切換的工作時序圖所示，可以得知本發明之兩種模式的電路操作原理及開關達零電壓-零電流的切換效果皆相同。The present invention can be divided into two modes of operation: a buck/charge mode and a boost/discharge mode. In the buck/charge mode, please refer to the second diagram. The converter of the present invention is shown in the circuit diagram of the buck/charge mode, and the first switching element (5) Q 1 ~ Q 4 in the circuit is used as the main switch. , wherein Q is in the 1 ~ Q 4 C s 1 ~ C s 4 and D s 1 ~ D s 4 respectively, a first switching element (. 5) Q a parasitic capacitance (51) 1 ~ Q 4 and the parasitic diode of (52) [Body Diode], and the second switching element (6) Q a 1 ~ Q a 4 is used as a synchronous rectification switch, the input inductance (1) L in 1 , and the transformer (3) generates leakage inductance (33) ), (34) L lkp , L lks , resonant capacitor ( 7 ) C r 1 , capacitor ( 8 ) C r 2 and load device (4) R load ; in boost/discharge mode, please refer to In the circuit diagram of the boost/discharge mode of the converter of the present invention, the second switching element (6) Q a 1 ~ Q a 4 is used as the main circuit switch, wherein C sa 1 ~ C sa 4 and D sa 1 ~ D sa 4 is the parasitic capacitance (61) and the parasitic diode (62) of the Q a 1 ~ Q a 4 main switch, respectively, and the first switching element (5) Q 1 ~ Q 4 is used as the synchronization. The rectifier switch is used, the input inductor (2) L in 2 , and the transformer (3) will Leakage inductance (33), (34) L lkp , L lks , resonant capacitor (7) C r 1 , capacitor (8) C r 2 and load device (4) R load are generated . Please refer to the fourth diagram of the converter of the present invention in the buck/charge mode, the main timing of the switch and the zero-zero current switching operation timing diagram and the fifth diagram of the converter of the present invention in the boost / discharge In the mode, the switch main control timing and the zero voltage-zero current switching operation timing diagram are shown, it can be known that the circuit operation principle of the two modes of the invention and the switching effect of the switch to zero voltage-zero current are the same.
請再一併參閱第六圖本發明之轉換器於降壓/充電模式時的等效電路圖所示，本發明在一個切換週期內電路可分為六個工作模式，以下就六個模式之動作原理作說明：Referring to the sixth circuit diagram, the equivalent circuit diagram of the converter of the present invention in the step-down/charge mode is shown. The circuit of the present invention can be divided into six working modes in one switching cycle, and the following six modes of operation The principle is explained:
模式一 [t 0 t t 1 ]Mode one [ t 0 t t 1 ]
當t =t 0 - 時作為主要開關之第一開關元件(5)Q 1 及Q 4 的寄生電容(51)C s 1 和C s 4 的電壓已經完全的釋放完畢，直到t =t 0 時第一開關元件(5)Q 1 及Q 4 才導通，使得第一開關元件(5)Q 1 及Q 4 導通於零電壓切換，同時第一開關元件(5)Q 2 及Q 3 的寄生電容(51)C s 2 和C s 3 電壓，此時已經充電近似V cr 1 ；此時電流I in 持續的對諧振電容(7)C r 1 充電，同時電流經過變壓器(3)一次側繞組(31)的漏電感(33)L lkp 而形成一個並聯LC 諧振迴路，使電流形成一正弦波使得主要開關可以在零電壓及零電流的狀態下導通及截止，同時在作為同步整流開關第二開關元件(6)Q a 1 及Q a 4 也操作於零電流切換。此狀態下由於i p (t 0 )之電流僅有激磁電流i m ，因此激磁電流i m 之值很小，所以在此狀態下可以忽略此激磁電流值。When t = t 0 - t as a first switching element when the voltage of the main switch C s 1 and C s 4 has been completely released (5) Q 1 and a parasitic capacitance (51) Q 4 is completed, until t = 0 The first switching element (5) Q 1 and Q 4 are turned on, so that the first switching element (5) Q 1 and Q 4 are turned on for zero voltage switching, and the parasitic capacitance of the first switching element (5) Q 2 and Q 3 (51) C s 2 and C s 3 voltages, at this time already charged approximately V cr 1 ; at this time the current I in continues to charge the resonant capacitor (7) C r 1 while the current passes through the transformer (3) primary winding ( 31) Leakage inductance (33) L lkp forms a parallel LC resonant circuit, so that the current forms a sine wave so that the main switch can be turned on and off in the state of zero voltage and zero current, and at the same time as the second switch of the synchronous rectification switch Element (6) Q a 1 and Q a 4 also operate at zero current switching. In this state, since the current of i p ( t 0 ) has only the exciting current i m , the value of the exciting current i m is small, so the exciting current value can be ignored in this state.
模式二 [t 1 t t 2 ]Mode two [ t 1 t t 2 ]
當時間t =t 1 諧振電路結束工作，電路上僅剩下激磁電流的 情況下，此時作為主要開關之第一開關元件(5)Q 1 及Q 4 截止且Q 2 和Q 3 尚未導通，第一開關元件(5)Q 2 及Q 3 的寄生電容(51)V ds 2 、V ds 3 電壓近似V cr 1 ，第一開關元件(5)Q 1 及Q 4 的寄生電容(51)C s 1 、C s 4 電壓為零，同一時間激磁電流i m 會開始對寄生電容(51)C s 1 、C s 4 充電，並且寄生電容(51)C s 2 和C s 3 也開始放電。當寄生電容(51)C s 2 及C s 3 持續放電到V ds 2 =0、V ds 3 =0時，激磁電流i m 流經D s 2 及D s 3 ，v p 電壓等於V cr 1 (t )，此時寄生電容(51)C s 1 、C s 4 電壓為V ds 1 =V cr 1 (t )、V ds 4 =V c 1 (t )，此狀態到此結束。In the case where time t = t 1 the resonance circuit end of the work, leaving only the excitation current on the circuit, this time as the main switch of the first switching element (5) Q 1 and Q 4 is turned off, and Q 3 and Q 2 has not been turned on, The first switching element (5) Q 2 and Q 3 parasitic capacitance (51) V ds 2 , V ds 3 voltage is approximately V cr 1 , the first switching element (5) Q 1 and Q 4 parasitic capacitance (51) C The voltages of s 1 and C s 4 are zero, and the excitation current i m starts to charge the parasitic capacitances (51) C s 1 and C s 4 at the same time, and the parasitic capacitances (51) C s 2 and C s 3 also begin to discharge. When the parasitic capacitances (51) C s 2 and C s 3 continue to discharge until V ds 2 =0, V ds 3 =0, the excitation current i m flows through D s 2 and D s 3 , and the v p voltage is equal to V cr 1 ( t ), at this time, the parasitic capacitance (51) C s 1 , C s 4 voltage is V ds 1 = V cr 1 ( t ), V ds 4 = V c 1 ( t ), and this state ends here.
模式三 [t 2 t t 3 ]Mode three [ t 2 t t 3 ]
此時因激磁電流i m 流經作為主要開關之第一開關元件(5)Q 2 及Q 3 的寄生電容(51)D s 2 及D s 3 ，與變壓器(3)一次側繞組(31)形成一迴路，同時激磁電流i m 對第一開關元件(5)Q 1 及Q 4 的寄生電容(51)C s 1 、C s 4 充電。同時輸入電感(1)電流會持續的向諧振電容(7)C r 1 充電，V cr (t )電壓會一直持續的上升，並且v s 電壓近似於V cr (t )。At this time, the excitation current i m flows through the parasitic capacitances (51) D s 2 and D s 3 of the first switching elements (5) Q 2 and Q 3 as main switches, and the primary winding (31) of the transformer (3) A loop is formed while the exciting current i m charges the parasitic capacitances (51) C s 1 , C s 4 of the first switching elements (5) Q 1 and Q 4 . At the same time, the input inductor (1) current will continue to charge the resonant capacitor (7) C r 1 , the V cr ( t ) voltage will continue to rise continuously, and the v s voltage is approximately V cr ( t ).
而因模式四[t 3 t t 4 ]、模式五[t 4 t t 5 ]、模式六[t 5 t t 6 ]之操作模式分別與模式一[t 0 t t 1 ]、模式二[t 1 t t 2 ]、模式三[t 2 t t 3 ]為完全對稱，所以在此不再另外做詳細的說明。且請一併參閱第七圖本發明之轉換器於昇壓/放電模式時的等效電路圖所示，此電路分析六個模式之動作原理與降壓/充電模式相似，在此將同樣不再描述。And because of mode four [ t 3 t t 4 ], mode five [ t 4 t t 5 ], mode six [ t 5 t t 6 ] operating mode and mode one [ t 0 t t 1 ], mode 2 [ t 1 t t 2 ], mode three [ t 2 t t 3 ] is completely symmetrical, so no further detailed description will be given here. Please also refer to the seventh circuit diagram of the equivalent circuit diagram of the converter of the present invention in the boost/discharge mode. This circuit analyzes the operation modes of the six modes similarly to the buck/charge mode, and will no longer be the same here. description.
請再一併參閱第八圖本發明之轉換器於降壓/充電模式時開關零電壓切換實驗圖所示，由其中可以輕易的看到在V ds 1 及V ds 2 到達零時，開關V gs 1 及V gs 2 才導通。使主要開關導通及截止狀態皆操作於零電壓的情況底下。Please refer to the eighth diagram again. The converter of the present invention is shown in the experimental diagram of switching zero voltage switching in the buck/charge mode. It can be easily seen that when V ds 1 and V ds 2 reach zero, the switch V Gs 1 and V gs 2 are turned on. The main switch is turned on and off in the case of zero voltage.
請再一併參閱第九圖本發明之轉換器於降壓/充電模式時開關零電流切換實驗圖所示，可以由圖中明顯的看出主要開關於降壓/充電模式時，皆操作在零電壓-零電流的切換狀態。Please refer to the ninth figure of the converter of the present invention in the step of switching the zero current switching in the buck/charge mode. It can be clearly seen from the figure that the main switch operates in the buck/charge mode. Zero voltage - zero current switching state.
請再一併參閱第十圖本發明之轉換器於昇壓/放電模式時開關零電壓切換實驗圖所示，由其中可以輕易的看到在V dsa 1 及V dsa 2 到達零時，開關V gsa 1 及V gsa 2 才導通。使主要開關導通及截止狀態皆操作於零電壓的情況底下。Please refer to the tenth figure again. The converter zero voltage switching experiment diagram of the converter in the boost/discharge mode is shown in the figure. It can be easily seen that when V dsa 1 and V dsa 2 reach zero, the switch V Gsa 1 and V gsa 2 are turned on. The main switch is turned on and off in the case of zero voltage.
請再一併參閱第十一圖本發明之轉換器於昇壓/放電模式時開關零電流切換實驗圖所示，可以由圖中明顯的看出主開關於昇壓/放電模式時，皆操作在零電壓-零電流的切換狀態。Please refer to the eleventh figure for the switch zero current switching experiment diagram of the converter of the present invention in the boost/discharge mode. It can be clearly seen from the figure that the main switch operates in the boost/discharge mode. In the zero voltage - zero current switching state.
然而前述之實施例或圖式並非限定本發明之產品結構或使用方式，任何所屬技術領域中具有通常知識者之適當變化或修飾，皆應視為不脫離本發明之專利範疇。However, the above-described embodiments or drawings are not intended to limit the structure or the use of the present invention, and any suitable variations or modifications of the invention will be apparent to those skilled in the art.
藉由以上所述，本發明之元件組成與使用實施說明可知，本發明與現有結構相較之下，本發明由於具有輸入電流漣波小、且具有柔性開關切換的技術，故可減少開關的切換損失，讓整體轉換器效率提高，且為全橋式電路架構，使得控制器設計容易，而在其整體施行使用上更增實用價值性者。As described above, the component composition and the implementation description of the present invention show that, compared with the prior art, the present invention can reduce the switch by having a technique of small input current ripple and flexible switch switching. Switching losses, the overall converter efficiency is improved, and the full-bridge circuit architecture makes the controller design easy, and more practical value in its overall implementation.
綜上所述，本發明實施例確能達到所預期之使用功效，又其所揭露之具體構造，不僅未曾見諸於同類產品中，亦未曾公開於申請前，誠已完全符合專利法之規定與要求，爰依法提出發明專利之申請，懇請惠予審查，並賜准專利，則實感德便。In summary, the embodiments of the present invention can achieve the expected use efficiency, and the specific structure disclosed therein has not been seen in similar products, nor has it been disclosed before the application, and has completely complied with the provisions of the Patent Law. And the request, the application for the invention of a patent in accordance with the law, please forgive the review, and grant the patent, it is really sensible.
(1)‧‧‧輸入電感(1)‧‧‧Input inductance
(2)‧‧‧輸入電感(2)‧‧‧Input inductance
(3)‧‧‧變壓器(3)‧‧‧Transformers
(31)‧‧‧一次側繞組(31) ‧‧‧ primary winding
(32)‧‧‧二次側繞組(32)‧‧‧secondary winding
(33)‧‧‧漏電感(33) ‧‧‧Leakage inductance
(34)‧‧‧漏電感(34) ‧‧‧Leakage inductance
(4)‧‧‧負載裝置(4) ‧‧‧Loading device
(5)‧‧‧第一開關元件(5) ‧‧‧First switching element
(51)‧‧‧寄生電容(51)‧‧‧Parasitic capacitance
(52)‧‧‧寄生二極體(52)‧‧‧ Parasitic diodes
(6)‧‧‧第二開關元件(6)‧‧‧Second switching element
(61)‧‧‧寄生電容(61)‧‧‧Parasitic capacitance
(62)‧‧‧寄生二極體(62)‧‧‧ Parasitic diodes
(7)‧‧‧諧振電容(7)‧‧‧Resonance capacitor
(8)‧‧‧電容(8)‧‧‧ Capacitance
第一圖：本發明之主電路架構圖First picture: main circuit architecture diagram of the present invention
第二圖：本發明之轉換器於降壓/充電模式電路圖Second picture: circuit diagram of the converter of the present invention in the buck/charge mode
第三圖：本發明之轉換器於昇壓/放電模式電路圖Third diagram: circuit diagram of the converter of the present invention in the boost/discharge mode
第四圖：本發明之轉換器於降壓/充電模式時，開關主要控制時序與零電壓-零電流切換的工作時序圖Figure 4: Operation timing diagram of the main control timing and zero voltage-zero current switching of the switch of the present invention in the buck/charge mode
第五圖：本發明之轉換器於昇壓/放電模式時，開關主要控制時序與零電壓-零電流切換的工作時序圖Figure 5: Operation timing diagram of the main control timing and zero voltage-zero current switching of the switch of the present invention in the boost/discharge mode
第六圖：本發明之轉換器於降壓/充電模式時的等效電路圖Figure 6: Equivalent circuit diagram of the converter of the present invention in the buck/charge mode
第七圖：本發明之轉換器於昇壓/放電模式時的等效電路圖Figure 7: Equivalent circuit diagram of the converter of the present invention in boost/discharge mode
第八圖：本發明之轉換器於降壓/充電模式時開關零電壓切換實驗圖Figure 8: Experimental diagram of switching zero voltage switching in the buck/charge mode of the converter of the present invention
第九圖：本發明之轉換器於降壓/充電模式時開關零電流切換實驗圖Ninth diagram: Experimental diagram of switching zero current switching in the buck/charge mode of the converter of the present invention
第十圖：本發明之轉換器於昇壓/放電模式時開關零電壓切換實驗圖Figure 10: Experimental diagram of switching zero voltage switching in the boost/discharge mode of the converter of the present invention
第十一圖：本發明之轉換器於昇壓/放電模式時開關零電流切換實驗圖Figure 11: Experimental diagram of switching zero current switching in the boost/discharge mode of the converter of the present invention
(1)‧‧‧輸入電感(1)‧‧‧Input inductance
(2)‧‧‧輸入電感(2)‧‧‧Input inductance
(3)‧‧‧變壓器(3)‧‧‧Transformers
(31)‧‧‧一次側繞組(31) ‧‧‧ primary winding
(32)‧‧‧二次側繞組(32)‧‧‧secondary winding
(5)‧‧‧第一開關元件(5) ‧‧‧First switching element
(51)‧‧‧寄生電容(51)‧‧‧Parasitic capacitance
(52)‧‧‧寄生二極體(52)‧‧‧ Parasitic diodes
(6)‧‧‧第二開關元件(6)‧‧‧Second switching element
(61)‧‧‧寄生電容(61)‧‧‧Parasitic capacitance
(62)‧‧‧寄生二極體(62)‧‧‧ Parasitic diodes
(7)‧‧‧諧振電容(7)‧‧‧Resonance capacitor
(8)‧‧‧電容(8)‧‧‧ Capacitance
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| TWI495244B (en) * | 2013-11-14 | 2015-08-01 | Nat Univ Tsing Hua | Bidirectional dc-dc converter system and circuit thereof |
| CN104868741A (en) * | 2015-05-15 | 2015-08-26 | 西交利物浦大学 | DC converter efficiency optimization method based on minimum reactive power loss |
| TWI602388B (en) * | 2016-03-10 | 2017-10-11 | 盈正豫順電子股份有限公司 | Bidirectional isolated multi-level dc-dc converter and method thereof |
Families Citing this family (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| TWI413336B (en) * | 2011-06-08 | 2013-10-21 | Nat Univ Chung Cheng | Device of bi-directional inverter and direct current power system thereof |
| JP5575731B2 (en) * | 2011-11-17 | 2014-08-20 | 株式会社日立情報通信エンジニアリング | Power supply device and control method of power supply device |
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Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20060139823A1 (en) * | 2004-12-28 | 2006-06-29 | Hitachi, Ltd. | Isolated bidirectional DC-DC converter |
| TW200713763A (en) * | 2005-09-21 | 2007-04-01 | Lin Hui Ching | A bidirectional DC/DC converter for fuel cell electric vehicle driving system |
| US20090034299A1 (en) * | 2007-07-31 | 2009-02-05 | Dubitsky Lev | Apparatus and method for high efficiency isolated power converter |
-
2009
- 2009-04-28 TW TW098114049A patent/TWI397250B/en not_active IP Right Cessation
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20060139823A1 (en) * | 2004-12-28 | 2006-06-29 | Hitachi, Ltd. | Isolated bidirectional DC-DC converter |
| TW200713763A (en) * | 2005-09-21 | 2007-04-01 | Lin Hui Ching | A bidirectional DC/DC converter for fuel cell electric vehicle driving system |
| US20090034299A1 (en) * | 2007-07-31 | 2009-02-05 | Dubitsky Lev | Apparatus and method for high efficiency isolated power converter |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| TWI495244B (en) * | 2013-11-14 | 2015-08-01 | Nat Univ Tsing Hua | Bidirectional dc-dc converter system and circuit thereof |
| CN104868741A (en) * | 2015-05-15 | 2015-08-26 | 西交利物浦大学 | DC converter efficiency optimization method based on minimum reactive power loss |
| CN104868741B (en) * | 2015-05-15 | 2017-07-18 | 西交利物浦大学 | A kind of DC converter efficiency optimization method based on minimum reactive power loss |
| TWI602388B (en) * | 2016-03-10 | 2017-10-11 | 盈正豫順電子股份有限公司 | Bidirectional isolated multi-level dc-dc converter and method thereof |
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