1309144 九、發明說明： 【發明所屬之技術領域】 _轉換：降==元: 使成為早級高功因電子安定器，當並聯迴 ^ =:愈多。此外，為降低電路的切換損失，二= 將升屋式職綠雜錢續電顧式，同_ d類 器的切換頻率操作在高於電路共振頻率情況下’以_二二 均^柔性切換，其主要目的是在於改善主動開關元件的 以達到電路的高效率。 、相失 【先前技術】 此 按’電子安定器大多採用共振式換流器（Res〇喊^㈣ =主要的電路架構’以功率半導體元件為開關，作高頻的切換動 2 ’配合負載共振電路，提供螢光燈負載所需的高頻電流 提供共振式換雜所需的錢龍，—般的蚊从多利用 二極«式整流電路或倍壓整流電路將市電的交流電源轉換成直 流電壓。而為了獲得穩定的直流電壓，必需在直流侧並聯一大 =以降低直流電壓的毅成分，由於大電容將直流維持在固 使得整流電路的二極體只在交流電源的電壓高於直流 電壓㈣導通，導通時間非常短，且導通時電路阻抗相當低。因 ’會有很大的脈波狀消入電流。這種脈波電流波形含大量窄波 (Hann〇nic)，導致極低的功率因數，亦會造成輸入電壓波形的 5 1309144 因此，欲達到高功因及低總證波失真 的電力紐桃。濾、波電路 可概:為被動式錢電路與主動式仙修正電路触ve1309144 IX. Description of invention: [Technical field to which the invention belongs] _Conversion: Drop == Yuan: To make the early stage high-power electronic stabilizer, when paralleled back ^ =: more. In addition, in order to reduce the switching loss of the circuit, the second = will continue to upgrade the power of the house, and the switching frequency of the same class _ d is more flexible than the circuit resonance frequency. Its main purpose is to improve the active switching elements to achieve high efficiency of the circuit. Loss [previous technology] This type of electronic ballast mostly uses a resonant converter (Res shout ^ (four) = the main circuit architecture 'power semiconductor components for the switch, for high-frequency switching 2 ' with load resonance The circuit provides the high-frequency current required for the fluorescent lamp load to provide the energy required for the resonant type change. The general mosquito converts the commercial AC power into DC by using the two-pole rectifier circuit or the voltage doubler rectifier circuit. In order to obtain a stable DC voltage, it is necessary to connect a large amount of DC on the DC side to reduce the component of the DC voltage. Since the large capacitor maintains the DC at a solid state, the voltage of the rectifier circuit is only higher than the DC voltage of the AC power source. The voltage (4) is turned on, the on-time is very short, and the circuit impedance is quite low when turned on. Because there is a large pulse-like current, this pulse current waveform contains a large number of narrow waves (Hann〇nic), resulting in extremely low The power factor will also cause the input voltage waveform of 5 1309144. Therefore, the power of the power to achieve high power factor and low total syndrome distortion. Filter, wave circuit can be: passive passive circuit and the main Dynamic fairy correction circuit touches ve
pFe) °傳統的被赋纽電路是由被 匕括：電感、電容和被動開關（二極體），利用改變 ^電流流人直流驗電容的路徑與時間來改善輸人電流的波形 ^目位，設計適當的參數可料成—定程度的功因修正功 月1^優點為電路結構簡單、堅固耐用、成本低廉。然而，被動 式滤波電路工作頻率與市電_，其元件的體積大、重量重，且 低頻工作的電感易產生哼哼聲等諸多的缺點。除此之外，被動式 滤波電路由於不含主動元件，無法目應輸人電贱負載的變化， 調即直流鏈電壓。因此，必須針對特錄人電壓及錄設計，一 旦輸入電壓或負載有所變化，功因改善及諧波消除的效果就不如 預期。 主動式功□修正電路由儲能元件、切換開關元件及控制電路电 成，似是在整流電路與錢鏈電容之間。控㈣路驅動開關元 件作南頻切換，並侧輸人和輸出電壓，_不同功率負載的需 求’來控制主動開關切換的時機，使儲能電感進行能量儲存與釋 放’以改變輸入功率與電流波形。經由適當的操作程序，可精碑 地控制輸人錢的波形及大小，使成為高_脈紐形，其波包 或平均值能追隨交流電源電壓波形，並且保制相位，達到功因 修正及穩壓的魏。目前，e有乡觀路賴被顧於主動式功 因修正電路，如降駐轉換Hdk Converter)、升壓式轉換器 (Boost Converter)、降升壓式（Buck_B〇〇st c〇nverter)、返^ 轉換器(Flyback Converter)·..等，及錄㈣方式，如電壓追隨 1309144 法(Voltage Follower)、誤差相乘法(Error Multiplier)、磁滯 電机控制法（Hysteresis Current Control)···等，均可將功因提 同至接近1，總諧波失真可被抑制到1〇%以下，功因修正的效果非 常良好。 1交W直流轉換ϋ作為功因修正電路，其常見的電路架構有 升壓式轉換H、降升壓式及返馳式轉換器。設計儲能電感工作於 =，電流模式（Discontinu〇us Current 她；Da〇時，可以使 安定器工作於高功態。當輸人電壓變動時，以改變主動開關 =件的工作鮮或責任獅（Duty版⑹來達職定的輸出功 2升壓式轉換器的輸出輕高於電源電壓，開關元件與直流鍵 ^及整流後的電源電壓成共地的連接方式。與共振式換流器整 :二=多加-個二極體來避免換流器能量流人轉_，整合 功因:正;二電路較為簡單。以降升壓式作為 、同侧奴11 ’由於輸人電源的極性，盥轉 換㈣輸出電源極性顛倒，造成實際使用上的不方便。反之^ ::?力換器作為功因修正電路之單級高功因安 里轉換時麵隔離的作用，然而 得」掩供月匕 磁現象與電路干擾也較嚴重。坪有較大損失’漏 用於單級高_電子式安定器、。、° ，升壓式轉換ϋ較適合應 【發明内容】 錢顺路成本，減 光燈電子安定器。 > 率之早級鬲功因升壓式多燈管螢 1309144pFe) ° The traditional circuit of the circuit is composed of: inductance, capacitance and passive switch (diode), using the path and time of changing the current and current capacitance of the current to improve the waveform of the input current. The design of appropriate parameters can be expected to be a certain degree of power factor correction power month 1 ^ advantages of simple circuit structure, rugged and durable, low cost. However, the passive filter circuit operating frequency and the mains _, its components are large, heavy, and the low-frequency operating inductance is prone to hum and many other shortcomings. In addition, since the passive filter circuit does not contain active components, it cannot be seen as a change in the input load of the input power, which is the DC link voltage. Therefore, it is necessary to adjust the voltage and load of the special recording, and the effect of improvement and harmonic elimination is not as good as expected. The active power correction circuit is composed of an energy storage component, a switching component, and a control circuit, and appears to be between the rectifier circuit and the money chain capacitor. Control (four) drive switch components for south frequency switching, and side input and output voltage, _ different power load requirements 'to control the timing of active switch switching, so that the energy storage inductors for energy storage and release 'to change the input power and current Waveform. Through appropriate operating procedures, the waveform and size of the input money can be controlled intensively, so that it becomes a high-pulse shape, and its wave packet or average value can follow the waveform of the AC power supply voltage, and the phase is preserved, and the power factor correction is achieved. Regulated Wei. At present, e has a hometown view, relying on active power correction circuits, such as down conversion Hdk Converter, Boost Converter, Buck_B〇〇st c〇nverter, Return to the converter (Flyback Converter), etc., and record (4), such as voltage follow 1309144 method (Voltage Follower), error multiplier (Error Multiplier), Hysteresis Current Control (Hysteresis Current Control) ·Whether, the power factor can be brought to near 1 and the total harmonic distortion can be suppressed to less than 1%. The effect of the correction is very good. 1 AC W DC conversion ϋ as a power factor correction circuit, its common circuit structure is boost conversion H, drop boost and flyback converter. Design the energy storage inductor to work in =, current mode (Discontinu〇us Current her; DaD, can make the ballast work in high power state. When the input voltage changes, to change the active switch = piece of work fresh or responsible lion (Duty version (6) The output of the booster converter is lower than the power supply voltage, and the switching element is connected to the DC key and the rectified power supply voltage. The resonant converter Whole: two = more plus - a diode to avoid converter energy flow _, integrated power factor: positive; two circuits are relatively simple. With the boost type as the same side, the same side slave 11 ' due to the polarity of the input power supply,盥 conversion (4) The polarity of the output power supply is reversed, which causes inconvenience in practical use. Conversely, the ^:? force converter acts as a single-stage high-power function of the power correction circuit, because of the effect of surface isolation during the conversion of the Anri, but Magnetic phenomenon and circuit interference are also serious. Ping has a large loss 'leakage for single-stage high _ electronic ballast, ., °, boost type conversion ϋ is more suitable [invention content] Qianshun road cost, dimming light Electronic ballast. >鬲 功 due to boost type multi-tube firefly 1309144
定器明特徵是在—單級高功因升壓式錄f螢光燈電子安 ^03有.一低通濾波器，係由電感與電容串接於電源輸 亡端’橋式整流器，係連接於被動遽波器之後級；一升壓轉換 °°、並聯於橋式整流器之輸出端，係由功率開關元件沿中之主動 1關Q _極冑及與~、儲能電感^與直流鏈電容&所組成； 負載共振電路’係、由電感Ls卜電容Csl與燈管/Ζ/所組成；一 D類,、振換机器’包含功率開關元件幻中之第一主動開關qi、功 率開關元件S2中之第二主動觸q2、二極體Λ、&與你7、~ ”直飢鏈· &及負載共振電路所組成；將該升壓轉換器之主動 =關Q2與D類共振換流器第二主動開關吸設為同一開關以簡化 电路使成為單級南功因電子安定器，並藉由調整開關的導通時 間來調節輸人電流，使其達到功率隨修正與調變輸人功率的目 的。 ^發明之另-特徵是在—單級高功因升壓式多燈管螢光燈電 子安定器’其储时壓轉換紅直流,The characteristic of the device is that the single-stage high-power boost-type recording f-fluorescent lamp electronic security ^03 has a low-pass filter, which is connected by the inductor and the capacitor in series with the power supply and death terminal 'bridge rectifier. Connected to the stage after the passive chopper; a boost conversion ° °, parallel to the output of the bridge rectifier, is the active switching of the power switching element along the Q _ pole 胄 and ~, energy storage inductance ^ and DC The chain capacitance & is composed; the load resonance circuit 'is composed of the inductance Ls capacitor Csl and the lamp / Ζ /; a class D, the vibration exchange machine' contains the first active switch qi of the power switch element The second active contact q2, the diode Λ, & in the power switching element S2 is composed of your 7, 直 链 chain & and load resonance circuit; the boost converter active = off Q2 and The second active switching of the class D resonant converter is set to the same switch to simplify the circuit to become a single-stage south power electronic ballast, and adjust the input current to adjust the input current to achieve the power with correction. The purpose of modulating the input power. ^The other part of the invention is characterized by - single-stage high-power boosting Multi-lamp fluorescent lamp electronic ballast' its storage time voltage conversion red DC,
並在直流鏈電容&兩端並聯數個負載共振電路ΐ3、Μ、i5、W ^個主_關將升壓轉換器與D類共振式換 流器整合在―起，節省部份主動關使成為單級高補電子安定 當並聯迴路愈多時所節省的主動_元件也就愈多，由該種 早級的電路結構同軸存了 轉換器與D料振換 與優點。 寸 【實施方式】 —有關本發㈤為達上述之·目的及功效，所_之技術手段， 茲舉出較佳可行之實施例，並配合圖式所示，詳加說明如下： 1309144 首先請參閱第_®所示為傳統雙級高功因電子安定器電路架 構’其前級財壓職ϋ作為拥修正電路；後級以㈣共振換 流器驅動燈管。本發明係將第一圖中的開關&與開㈣整合共、 用’以節省-組控制電路與_個主朗關，整合後的安定器為單 級單切換開關的電路架構如第二圖所示，其係由一低通渡波器 ίο、橋式整流η、升壓轉換n 12與D類共振換流器13所組成， 其輸入端的小型低通遽波器10係由電感域電容㈣組成，是 用來消除輸入電流的高頻諧波，橋式整流器j卜係將交流電源轉 籲換成直流電源，功率開關元件汾及&分別由主動開關仍、必與反 向並聯二極體所組成，升壓轉換器12由換流器中的主動 開關必、二極體以及升壓電感及直流鏈電容&所組成， 而D類共振式換流器包括有，及主動開關Q2、二極體从、你 與从/、/k與直流鏈電容〇^及由電感、電容與燈管 所組成之負載共振電路13，而共振電流/r則經由二極體处成迴 路，且其中電容負責在燈管啟動的暫態過程中，提供足夠高的 啟動電壓，並於穩態工作時提供適當的燈絲電流。當主動開關级 _ 截止時’域電流城過二減伽將能量傳遞至直鱗電容^ 藉由調整開關你的導通時間來調節輸入電流，使其達到功率因數 修正與調變輸入功率的目的，且將升壓轉換器與D類共振矣換流 器整合在一起，部份元件使成為單級高功因電子安定器，當並聯 迴路愈多時所節省的主動開關元件也就愈多。 本發明電路由於減少一個主動開關與飛輪二極體，使控制電 路將更為簡單，電路成本因而降低，並且因為減少了能量轉換流 程，電路效率因而提高，當主動開關设截止時，電感電流办通過 1309144 電容.藉由調整開關㈣導通 電流’使_]功__賴輸入功率的 =。本發明電路將第二圖之電子安定ϋ基核構，以並聯辦加 的方式，改成多燈管同時運作的電路，如第三圖所^。 ‘、、、月匕各別控制每-支燈管，所有的共振迴路都分別保 的主動開關，即圖中的㈣5等四個開關元件，該多迴路〇類共 振換流器’係共用升壓轉換器之直流鏈電容O/c、主動開關㈣ 由主動開關㈣、㈣5，並與二極❹士 你、你與數個負載共振電路13、14、 — 電路係由共振電感4 所構成；母一個共振 =FL_〜瓜)與啟動電容G (〇〜⑼戶斤構成，此種單級的 =路結構同時保存了升壓轉換輯D類共振換流器的特性與優 ^5 ° 在非_藏紐繼控财，·㈣_彳由兩個互補 的閉級峨與所觸發，兩者之間有著短暫的急遲時間 二:防纷_時導通。若我憤、略這段時間，將開關元 件_導通率表示為D，則開關元件㈣導通率即為(卜仍 計共振電路的參數時，—般都將驗器之切換鮮設計的比共振 共振頻率還高’使得電路呈現電感性負載，讓開關導通瞬 間此達到零電«零電流切換導通’以減少開關元件的切換損 ί °、升㈣主動功因修正電路中的賴電流可肛作在連續電流 拉式或不連續電流模模式其元件之切換損失 較小、控制電路較簡單，適用於小功率電路；而連續電流模式則 能降低開航件的傳導損失_流應力，惟其控制電路較複雜， 適用於大轉祕。本發縣電駐作在不_棘狀，使得 1309144 元件均能達到零電壓切換導通，同時藉由調變開關的 总、、’間’以控制電路之輸人功率。將第三圖的電路，當控制燈 g並糾支數增加或減少時，貞載功率縣變化，開關公之導通 2也須加㈣整’因此，根據&導通率D的大小與共振電流、 電感電流之間相對應的關係，電路可分為二種操作狀態：本叶畫 =負載較大（撕以上）、與負載較小時(權以下）兩種情形為^ 刀別進仃分析。同時’在後面的分析中，本文先作了部分理相化 的織，以簡化問題的複雜性：⑴電源頻率遠低於切換頻率了故 ^在每自尚頻週期中，低頻輸入電源電歷可視為定值；⑵〇類 、振式換流||_換頻率高於共振電路的共振鮮，意㈣類妓 =換流H電路呈現電感性，共振電流落後於換流器的輸出電 於⑶假設負載共振電路的品f因數足夠高，所以共振電流可趨 弦波。基独上的假設，單級高升壓式錄管螢光燈 电子安定器的簡化電路如圖4所示。 A.狀態一（負載較大時）： 第五圖所不為工作狀態中各開關元件電屋、電流之理論波 =根據功率開關元件的動作狀態，此電路在—個高頻的週期内 可匀為六個操作模式： ti (1)工作模式一（&〈广< 進入工作模式—之前，共振電流[為負值，並經由二極體 成的迴路’同時電感電流此降為零。讀模式—開始後， =訊號較料通，整流後的輸人電壓跨在電感 6 ’故電感電流h呈線性增加。此時共振電流"仍為負值，流 11 1309144 2一極體細I直流鏈電容Ca而成迴路，但共振電流々與電感電 & 的電流路徑方向是相反的，因此開關元件社的電流 ids2^ ^和域者相減所得，在此工侧式—前半辦暇共振電流心 較^於後半階段電感電流A越趨增加，所以電流^才會由負 的k慢變為正的。在共振電鱗紅值時，電路進人 。 ⑵工作模式二（h ㈦：And in the DC link capacitor & both ends connected several load resonance circuits ΐ3, Μ, i5, W ^ main _ off the boost converter and the D-type resonant converter integrated, saving some active off To become a single-stage high-compensation electronic stability, the more active _ components are saved when the parallel circuit is more, the converter circuit and D material vibration exchange and advantages are co-existed by the early-stage circuit structure.寸 [Embodiment] - The relevant technical means for achieving the above-mentioned purpose and effect, and the preferred embodiment are shown in the figure, and the details are as follows: 1309144 First, please Refer to the _® for the traditional two-stage high-power electronic ballast circuit architecture's pre-level financial operation as a correction circuit; the latter stage uses a (four) resonant converter to drive the lamp. The invention combines the switch & and the open (four) in the first figure, and uses the 'save-group control circuit and the _ master switch, and the integrated ballast is a single-stage single-switch switch circuit structure as the second As shown in the figure, it consists of a low-pass ferrite, a bridge rectifier η, a boost converter n 12 and a class D resonant converter 13. The small low-pass chopper 10 at its input is composed of an inductor domain capacitor. (4) The composition is used to eliminate the high-frequency harmonics of the input current. The bridge rectifier converts the AC power supply into a DC power supply, and the power switching components & and & are respectively activated by the active switch. The pole body is composed of a boost converter 12 composed of an active switch must be in the converter, a boost inductor and a DC link capacitor & and the class D resonant converter includes, and an active switch Q2, the diode from, the /, /k and DC link capacitors and the load resonance circuit 13 composed of the inductor, the capacitor and the lamp, and the resonant current /r is looped through the diode. And wherein the capacitor is responsible for providing a sufficiently high temperature during the transient process of the lamp start Actuation voltage, and provide the appropriate filament current at steady state operation. When the active switching stage _ is off, the domain current passes through the second gamma to transfer the energy to the straight scale capacitor. ^ By adjusting the switching time of your switch to adjust the input current to achieve the power factor correction and modulation input power, Moreover, the boost converter is integrated with the class D resonant 矣 inverter, and some components make it a single-stage high-power electronic ballast. The more the parallel circuit, the more active switching components are saved. The circuit of the invention reduces the control circuit and the flywheel diode, so that the control circuit is simpler, the circuit cost is reduced, and the circuit efficiency is improved because the energy conversion process is reduced. When the active switch is turned off, the inductor current is Pass the 1309144 capacitor. By adjusting the switch (four) to conduct current 'make _' work __ lie the input power =. The circuit of the present invention converts the electronic stability of the second figure into a nuclear structure, and converts it into a circuit in which multiple lamps are simultaneously operated in a parallel manner, as shown in the third figure. ',,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,, The DC link capacitor O/c of the voltage converter, the active switch (4) consists of the active switch (4), (4) 5, and with the two-pole gentleman, you and several load resonant circuits 13, 14, - the circuit is composed of the resonant inductor 4; The mother has a resonance = FL_~ melon) and the starting capacitor G (〇~(9) is composed of a kilometer. This single-stage = road structure simultaneously preserves the characteristics of the boost converter series D-type resonant converter and excellent ^5 ° _ Tibetan New Zealand succeeds in controlling money, (4) _ 彳 is triggered by two complementary closed-level shackles, and there is a short period of urgency between the two: the prevention of _ _ conduction. If I am angry, this time, will When the switching element _ conduction rate is expressed as D, the conduction ratio of the switching element (4) is (when the parameters of the resonant circuit are still counted, the switching of the detector is generally designed to be higher than the resonant resonant frequency), so that the circuit is inductive. Load, let the switch turn on instantly, this reaches zero electricity «zero current switching conduction' to reduce Switching component switching loss ί °, liter (4) active power factor correction circuit in the current can be anus in continuous current pull or discontinuous current mode mode, its component switching loss is small, the control circuit is simple, suitable for low power The continuous current mode can reduce the conduction loss of the starting part _ flow stress, but its control circuit is more complicated, suitable for large transfer. The power station of this county is not thorn-like, so that 1309144 components can reach zero voltage. Switching on, and controlling the input power of the circuit by adjusting the total and 'inter' of the switch. When the circuit of the third figure increases or decreases the number of corrections, the load power county changes. The switch's conduction 2 must also be added (4). Therefore, according to the relationship between the magnitude of the & conductance D and the resonant current and the inductor current, the circuit can be divided into two operating states: the present leaf painting = the load is large ( Tear the above), and when the load is small (below the weight), the two cases are analyzed. At the same time, in the following analysis, the paper firstly makes a phased weaving to simplify the complexity of the problem: (1) Electricity The frequency is much lower than the switching frequency. Therefore, in every self-frequency cycle, the low-frequency input power supply can be regarded as a fixed value; (2) 〇, vibration type commutation ||_ change frequency is higher than the resonant circuit resonance, meaning (4) Class 妓 = commutating H circuit exhibits inductivity, resonant current lags behind the output of the converter. (3) Assume that the product f factor of the load resonant circuit is sufficiently high, so the resonant current can be sinusoidal. The simplified circuit of the high-boosted fluorescent lamp electronic ballast is shown in Figure 4. A. State 1 (when the load is large): The fifth figure is not the theory of the electrical and electrical current of each switching component in the working state. Wave = According to the operating state of the power switching element, the circuit can be evenly divided into six operating modes during a high frequency period: ti (1) operating mode one (&<wide< before entering the operating mode - before the resonant current [Negative, and the loop through the diodes' simultaneously reduces the inductor current to zero. Read mode—After the start, the = signal is turned on, and the rectified input voltage crosses the inductor 6 ′, so the inductor current h increases linearly. At this time, the resonant current " is still negative, and the flow 11 1130944 2 one-pole thin I DC link capacitor Ca becomes a loop, but the resonant current 々 is opposite to the current path of the inductor electric & The current ids2^^ and the domain are subtracted. In this work-side, the resonant current of the first half is higher than that of the latter half, so the current ^ will change from negative k to positive. When the resonance scale is red, the circuit enters. (2) Working mode 2 (h (seven):
、工他式二開始後，共振電流iV換向成為正值，流經原已導 k的力率開關純直流鏈電容&形成迴路，同時直流鏈電容& 上的《「&將二频麟域止。由於碰錢 =時流經開關…所以術即為該二電流之、姊，= 止時’電路進入工作模式三。 (3)工作模式三（^ < ^ < & ): 在工作模式三巾’ _ 觸發峨^為低準位 止，此時f感f流/礎由三極體對錢鏈f容&充電 ^率為負而共振電流β制於二極體㈣阻斷，會經由二極❹ 構成-共振迴路。當共振電流值降為料，電路即進人工作模式 (4)工作模式四（&< ί < "): 狀態-是負載功率較大的情況，因此當電路進人卫作模 時’電感電流_鎌大。此時共振電流ir換向成，、心 感電流域經過二極心，且關，所以共振電流 極體你7、㈣成一個共振迴路。在此工作模式期間，二極 因有電感電流域共振電流y道過，所明發訊號&對功^ 關必並無作用，直到電感電流&小於共振電流A，電路才進入^ 12 1309144 式五。 (5)工作模式五（匕 <，< 纺）： 此階段的電感電流.之值已不再大於共振電流"，所 ^自賴止，同時，早已存在_發訊號會在胸. 使其導通’這意味著_岐鱗電_始切換導 進入工作模式六。 观電“降到謝，此時即 (6)工作模式六（纺< f < & ): 在此工作模式中，已無電感電流h且共振電 m經由功率開關_二極❹7構成迴路^功率開關 必截止、必導通時，再次回到工作模式一。 狀態一（負载較小時）： 據：==;=：r:r，根 態-的工作^作、二、五，這三飯储式中與狀 於此五通狀態和等效電路是相同的，故 +又不再重複贅述’町直接進人工作模式三。 工作模式三（。< 广< &): 相同三時 ，，而電感電流對直流鍵振迴 進入工作斤以電感電崎先行降為零，並使電路 13 1309144 (4) 工作模式四（h ί < &): 狀態-是負載功率較大的情況，·當電路進人工作模式四 時’電感電流础鎌大。此時共振電流換向成貞電流， 感電流滅經過二極體如’且小所以共振電流A改 二極體~、_成-個共振迴路。在此工作模式期間，二極體 因有電感電流i樓共振電流yr流過，所以觸發^ ^並無作用，直到電感電流』，小於共振電流&，電路才進场 式五。 、 (5) 工作模式五（&< f < & ), 此階段的電感電流从值已不再大於共振電流》，所以 體⑽自然截止，同時，早已存在的觸發訊號&會在& 動功率開_使其導通，這意味著·岐於零電流開始切換導 ==式會一直持續到電感電流麵為止，此時即 (6) 工作模式六（纺 < 力< & ): 在此工作模式中，已無電感電流且 負電流，並經由功率開關㈣二極體轉二二，為反向的 _止、_通時，再相虹作模式_。、路’相功率開關 】的视_的工作模式，我們可以發現，&論功率大 J、的皮化如何，開關元件導通率變大或變小 、、、力羊大 是電感性的，颇有開關元件在因應_大小均 電壓切換導通。 燹動日·ί，均可於零 電路操作在最大導通率時，其電感電流_設計操作於連續 14 1309144 ^不連續之邊界，這也是不連續電流模式t具有最低峰值電流的 財，，此情況只有在電源電屢為峰值且導通率D最大時才會 現也就疋上述狀態—中的工作模式六，電感電流不會提早下 到零，會是在不連續的邊界上，操作在此邊界上只是狀一之特 例，其餘在電源電驗稍微小一點或導通率較低時，電感電产都 =降到零;致於放電的速度快慢，則視當時的電源電壓和 工要=流; 模式五之中截止。 其實可能在模式三到 當電子蚊n由市敍流電源供電，射㈣ :換源的峰值電壓。在實際電路的設計中= 個二=期:：=:此情形下，的每- 元件的切換損失太定值。為了減少開關 ^τ.,4 本翻電路設計使升壓域電流趣持在不速 =作，式’由前述虹倾式分析中所描述的狀態— 在功率開關料通之後，電感電流值由零開始上升二 :;關&截止期間，其電流值由蜂值下降到零。第七：:： 通時，電為嫩電的時間。因此，#切換開關料 郎兩端之電壓將等於整後的電源電壓： 經過心的導通時職，電感的電流達到峰值7.6， 為電源’ d為_率ϋ/ζ 田切換開關S罐止時，電感電流流經直流鏈電容，電感兩端 15 1309144 之電壓成為： vl(t) = /vinI - Vdc 其中V&為直流鏈電壓。 由於整流後的電源電流等於電感電流，因此每個切換週期内 的平均輸入電流可以輕易地求得。而電感平均電流之示意波形如 第八圖所示。 心 夕 如果功率開關元件级的導通率與開關切換頻率固定，電 壓比α值越小（電壓比的定義為輸人交流電壓源峰值與直流鍵電 壓之比），則輸人電流的平均值會越接近正弦波並與電源電壓同 步變化。反之’電壓比〇：值越接近於i，輸入電流波形畸變會越嚴 重’無法成為正弦波形。ϋ此，要達聰高的功率因數，必項抓 計使直流鏈電壓比輸人峰值大上許多，然後再於輸入端2 =組小渡波器來齡高頻成份，即可制良好的拥修正效果。 第九圖所示即為不同的電壓比設計下’輸人 ^波形之變化情 輸入功率為開關元件&的導通料和直流鏈㈣的函數， 因此^要操作不同支數的辟，_.鱗_ _導 D和直流鏈電壓I以便能正確地控制電子紋器之輸入功率。 流電源操作—週射，高功因安定㈣輸入電流與 此利用此關係可知功率因數PF為電壓比-的 於0 8時係如料_示。_中可看出#電壓比α小 於〇· 8時，其功率因數PF即可高達到〇. 95以上’作是當電壓比 “增加到◦. 9以上時，功率因數PF會急據下降。所以，在設計不 16 1309144 擇電路參==:==電子安定器時’必需謹慎的選 定器，是採的:::功因升屋式多燈管螢光燈電子安 支數時的_，因此不Π、ΓΙ指㈣躺方式，應不同燈管 直流鏈而負载量就有不—樣的開關導通率D以及 點亮的燈管較嫩維㈣味於任何 共振式換流器輪入電„本波有效㈣，因的 越遠’其所對應的直流鏈顏Vdc將越高離0·5 流鏈電將出7 ’ =的直 低元件的電繼，糊雜 的時候’仍具有相同的直流鍵電Mvdc。 心 第十-圖是本發明專利所提出的單級高功因升 螢光燈電子鍵器操作在四支燈管情況下所測量出來= 二二出端、以及各主要開關元件上的電壓、電流波形，測； 、n不在驅動四支燈管情況下其功率因數PF為G996; 失真THD為8.8%。第十二圖是操作在三支辟纽下所測量出來 的電源曰輸人端、輸出端、以及各主要_元件上的電壓、電流波 形’測量結果顯示在驅動三支燈管情況下其功率因數押為〇奶 總譜波失冑勸為9.8%。第十三圖是操作在兩支燈管情況下測 量出來的電源輸人端、輸出端、以及各主要_元件上的電壓、 電流波形’測量結果顯示在驅動兩支燈管情況下其功率因數押為 0.998 ·，缝波失真THD為7·〇〇/ο。第十四圖是操作在—支燈管产 況下所測量出來的電源輪人端、輸出端、以及各主要開關 17 1309144 的電壓、電錢形’測量絲顯示在驅動—支燈管情況下其功率 因數PF為0.995 ;總諧波失真伽為9 8%。由第十一圖至第十 =圖^波树知，轉單級高韻升壓式多燈管螢光燈電子安 定器操作在較燈管的情況下，電路輪人端的電流波形都非常理 〜力率因數均非常接近於j，且其總譜波失真率全部在以 下。 【圖式簡單說明】After the start of the second mode, the resonance current iV commutates to a positive value, and the pure DC link capacitor & which flows through the original k-switching force switch forms a loop, and the "DC converter & Frequency ribs stop. Because the money = when the flow through the switch ... so the surgery is the two current, 姊, = stop the circuit into the working mode three. (3) working mode three (^ < ^ <& ) : In the working mode, the three towels ' _ trigger 峨 ^ is low level, at this time, f sense f flow / foundation by the triode to the money chain f capacity & charging rate is negative and resonance current β is made in the diode (4) Blocking, which will form a resonance circuit through the two poles. When the resonance current value falls to the material, the circuit enters the working mode (4) working mode four (&< ί <"): state - is the load The power is large, so when the circuit enters the mode, the inductor current _ 镰 is large. At this time, the resonant current ir is commutated, the sense current field passes through the center of the pole, and is turned off, so the resonant current body is 7 And (4) forming a resonant circuit. During this mode of operation, the two poles have an inductor current domain resonance current y, and the signal is & The function ^ does not work until the inductor current & is less than the resonant current A, the circuit enters ^ 12 1309144 Equation 5. (5) Working mode five (匕 <, < spinning): The inductor current at this stage. The value is no longer greater than the resonance current ", it depends on, at the same time, already exists _ signal will be in the chest. Make it conductive 'This means _ 岐 电 _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ Drop to Xie, at this time (6) working mode six (spinning < f <& ): In this mode of operation, there is no inductor current h and the resonant power m is formed by the power switch _ diode ❹ 7 When the switch must be turned off and must be turned on, return to the working mode again. State one (when the load is small): According to: ==;=:r:r, the root state - the work ^, two, five, the three rice storage and the five-way state and the equivalent circuit is The same, so + no longer repeat the description of the town directly into the work mode three. Working mode three (. < wide <&): the same three times, while the inductor current is oscillating back to the DC key into the working pin to inductive electric saki first down to zero, and the circuit 13 1309144 (4) working mode four (h ί <&): State - is the case where the load power is large. · When the circuit enters the working mode four, the inductor current is large. At this time, the resonant current is commutated into a 贞 current, and the sense current is extinguished through the diode such as 'and the resonant current A is changed to the diode~, _ into a resonant loop. During this mode of operation, the diode flows through the resonant current yr, so the trigger does not act until the inductor current is less than the resonant current & the circuit enters mode 5. (5) Working mode 5 (&< f <& ), the inductor current value at this stage is no longer greater than the resonant current, so the body (10) naturally cuts off, and at the same time, the already existing trigger signal & In & dynamic power on _ to make it on, which means that 岐 零 零 零 零 零 = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = &): In this mode of operation, there is no inductor current and negative current, and the power switch (4) diode is turned to two or two, which is the reverse _ stop, _ pass, and then the phase _. , the road 'phase power switch' of the working mode of the _, we can find, & on the power of J, the leather, how the switching element conduction rate becomes larger or smaller, and the force of the sheep is inductive, Quite a switching element is switched on in response to the _ size and voltage.燹日·ί, can operate in zero circuit at the maximum conduction rate, its inductor current _ designed to operate on the continuous 14 1309144 ^ discontinuous boundary, which is also the discontinuous current mode t has the lowest peak current, this The situation is only when the power supply is repeatedly peaked and the conduction rate D is maximum. Now the current state is the same. In the working mode six, the inductor current will not advance to zero, which will be on the discontinuous boundary. The boundary is only a special case. When the power supply is slightly smaller or the conduction rate is lower, the inductance is reduced to zero. The speed of the discharge is dependent on the power supply voltage and the current flow. ; Mode 5 is cut off. In fact, it may be in mode three. When the electronic mosquito n is powered by the city's power supply, shoot (four): change the peak voltage of the source. In the design of the actual circuit = two = period =: = =: In this case, the switching loss per component is too constant. In order to reduce the switch ^τ., 4 turns the circuit design so that the boost domain current is held at the non-speed =, the state described by the aforementioned rainbow-dip analysis - after the power switch is turned on, the inductor current value is Zero starts to rise two:; off & cutoff period, its current value drops from zero to zero. Seventh::: All time, electricity is the time of tender electricity. Therefore, the voltage between the two ends of the switch switch will be equal to the whole power supply voltage: After the conduction of the heart, the current of the inductor reaches the peak value of 7.6, which is the power supply 'd is _ rate ϋ / ζ field switch S tank stop The inductor current flows through the DC link capacitor. The voltage at 15 1309144 across the inductor becomes: vl(t) = /vinI - Vdc where V& is the DC link voltage. Since the rectified supply current is equal to the inductor current, the average input current during each switching cycle can be easily determined. The schematic waveform of the average current of the inductor is shown in Figure 8. If the conduction ratio of the power switching element stage is fixed to the switching frequency of the switch, and the voltage ratio α is smaller (the voltage ratio is defined as the ratio of the input AC voltage source peak to the DC key voltage), the average value of the input current will be The closer to the sine wave and the change with the supply voltage. Conversely, the voltage ratio 〇: the closer the value is to i, the more severe the distortion of the input current waveform will be. Therefore, to achieve the power factor of Conggao, it is necessary to grasp that the DC link voltage is much larger than the input peak, and then at the input end 2 = group small ferrites to age high-frequency components, you can make a good correction. effect. The ninth figure shows the difference between the input voltage of the input voltage and the DC link (4) of the input voltage of the input voltage. Therefore, it is necessary to operate different counts. Scale _ _ D and DC link voltage I in order to properly control the input power of the electronic stencil. Streaming power supply operation - cycle, high power due to stability (four) input current and this use of this relationship can be seen that the power factor PF is the voltage ratio - at 0 8 is as shown. _ can be seen that #voltage ratio α is less than 〇·8, its power factor PF can be as high as 〇. 95 or more 'When the voltage ratio is increased to ◦. 9 or more, the power factor PF will be reduced sharply. Therefore, when the design is not 16 1309144, the circuit selector ==:== electronic ballasts must be carefully selected. It is taken::: The power of the house is increased by the number of lamps and lanterns. Therefore, the Π ΓΙ ΓΙ 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四 四This wave is valid (four), because the farther away, the corresponding DC link Vdc will be higher from 0. 5. The streamline will output 7' = the low-level component of the electric relay. When it is mixed, it still has the same DC button power Mvdc. The tenth-figure of the heart is the single-stage high-power fluorescent lamp electronic key device operation proposed by the present invention, which is measured in the case of four lamps; the second and second ends, and the voltages on the main switching elements, Current waveform, measured; n does not drive four lamps with a power factor PF of G996; distortion THD is 8.8%. The twelfth figure shows the voltage and current waveforms measured by the power supply at the human terminal, the output terminal, and the main components measured under the three branches. The measurement results show the power in the case of driving three lamps. The factor was squandered as a total score of 9.8%. The thirteenth picture shows the voltage and current waveforms of the power input, output, and main components measured in the case of two lamps. The measurement results show the power factor in the case of driving two lamps. The beating is 0.998 ·, and the stitching distortion THD is 7·〇〇/ο. The fourteenth figure shows the voltage of the power wheel, the output end, and the voltage of each main switch 17 1309144 measured under the condition of the lamp, and the electric wire shape measurement wire is displayed in the case of the driving lamp. Its power factor PF is 0.995; the total harmonic distortion gamma is 9 8%. From the eleventh figure to the tenth = figure ^ wave tree know, the single-stage high rhythm boost type multi-lamp fluorescent lamp electronic ballast operation in the case of the lamp, the current waveform of the circuit wheel human end is very reasonable ~ force The rate factors are very close to j, and their total spectral distortion rates are all below. [Simple description of the map]
第一圖傳統雙級高功因電子安定器。 第二圖單級高功因電子安定器。 電子安定器的簡化電路。 弟一圖單級兩功因多燈管電子安定器。 第四圖單級高功目升壓Μ燈管螢光燈 第五圖狀態一之理論波形。 第六圖狀態二之理論波形。 第七圖電感平均電流ib之示意波形。 第八圖電感電流的示意波形。 第九圖電耻α對輸人電流麟之影響。 第十圖功率因數PF與α之關係圖。 第十一圖驅動四支燈管之量測波形。 第十二圖驅動三支燈管之量測波形。 第十二圖驅動二支燈管之量測波形。 弟十四圖驅動一支燈管之量測波形。 【主要元件符號說明】 18 1309144 低通濾波器ίο 橋式整流11 D類共振換流器 升壓轉換器12 直流鏈電容6^ 負載共振電路13、14、15、16 升壓電感hThe first figure is a traditional two-stage high-power electronic stabilizer. The second figure is a single-stage high-power electronic stabilizer. A simplified circuit for an electronic ballast. The younger brother has a single-stage two-function multi-lamp electronic ballast. The fourth figure is a single-stage high-power booster xenon lamp fluorescent lamp. The theoretical waveform of state two of the sixth figure. The seventh figure shows the schematic waveform of the average current ib of the inductor. Figure 8 shows the schematic waveform of the inductor current. The ninth figure shows the influence of electric shame α on the input current. The tenth graph shows the relationship between the power factor PF and α. The eleventh figure drives the measurement waveform of the four lamps. The twelfth diagram drives the measurement waveforms of the three lamps. Figure 12 shows the measurement waveform of the two lamps. The fourteenth figure drives the measurement waveform of a lamp. [Main component symbol description] 18 1309144 Low-pass filter ίο Bridge rectifier 11 Class D resonant converter Boost converter 12 DC link capacitor 6^ Load resonance circuit 13, 14, 15, 16 Boost inductor h
Lm、Lsi、Ls2、LS3、LS4 功率開關元件& 主動開關必、你、级、级、体 二極後 Dml、Dm2、Dm3、Dm4、Dm5、Dl、D2、D3、D4、D5、De、D7、D8 電容 Cm ' Csl ' Cs2、Cs3 ' Cs4、Cpl、Cp2、Cp3、Cp4、 湾if FL1、FL2、FL3' FL4Lm, Lsi, Ls2, LS3, LS4 power switching components & active switch must, you, level, level, body two poles Dml, Dm2, Dm3, Dm4, Dm5, Dl, D2, D3, D4, D5, De, D7, D8 capacitor Cm ' Csl ' Cs2, Cs3 ' Cs4, Cpl, Cp2, Cp3, Cp4, Bay if FL1, FL2, FL3' FL4
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