1281105 九、發明說明·· 【發明所屬之技術領域】 本發明係提供一種且L-r /pr ^ . 法及裝置，尤产在如Γ ° -待械功率損耗之轉換控制力 效能與極低之彳犧功率消耗。 相^之轉摘 【先前技術】</ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> <RTIgt; Sacrifice power consumption. Transfer of phase
限管因:種能源的開發與能源使用的 對能源運用制定適當“源政】：二曰等先進國家已針 (S副by mode)中之功率消^值^t產1在待機模式 (G_ Power) ’ 一般大多訂定在〇 5瓦=色U p_ x下將”、、，口目刖低待機損耗交換式電源供 應°°及其相闞控制器所使用之習知技術。 供麻t閱第—圖’第一圖為習知低待機損耗交換式電源 i、應為1之電路架構示意圖。一般而言，主流/ 直流轉換單元1G及直流/直流轉換單元11串接，1中交流 :直:換單元1(3其作用乃是將系統輸入之交流輸入電壓 =轉換為第—直流電壓Vdcu。而交流/直流轉換單元 所串接之直流/直流轉換單幻1，將交流/直流轉換 輸出之第—直流電壓Vdc11轉換為所需之第二直 肌電[Vdcl2如3. 3V、5V、12V、24V、術或是其他規格 1281105 電壓等。 其中直流/直流轉換單元U所採用之架構可使用隔離 型或非隔離型轉換器架構，目前在交換式電源供應器中， 返馳式（Flyb^k)轉換n因其架構簡單及成本低廉，故被廣 泛的使用目&在U/直流轉換器架構中被大幅使用之返 ，式轉換n，除其本身在正常負載條件所使用之控制器（功 能）外，在綠色電源規範要求下，額外使用叢發模式（Burst mode)作為待機模式下之控制方式。 明麥閱第一圖，第二圖為習知技術於待機模式中之控 制k序與輸出電壓之示意圖。當負載在輕載或空載之條件 下’。習知低待_耗交換電源供㈣巾之後級錢/直流轉 換單兀y，除將工作週期（Duty cycle)調整至最大外，並 以叢發模式（Burst mode)方式，間歇控制功率晶體之導通 及開關。-般而言，在輕載或空載的條件下，以最大的工 作週期’僅需幾個週期就可使直流輸出電壓恤12維持在 某-範圍内（即輸出電壓上限值刪與輸出電壓下限 VB22之間），當輸出電壓Vdcl2高於輸出電壓上限值v 時系統可關閉功率晶體之控制訊號，直至直流輪出電壓 Vdcl2低於輸出電壓下限值體，系統重新輸出對 體之控制職，能減少在姆及空載條件下， = 功率晶體之切換次數及系統之切換損失。 曰 由於返馳式轉換器必須額外使用緩震 (Snubber) ’以降低漏感與寄生電容振盈造成之電壓作 (voltage-spike)，緩震電路的使用亦伴隨著功 红大_ 者-般之返馳式轉鋪在未使用特殊控制或辅助開 況下，並無法達成軟切換（s〇f卜⑽以也丨呢）之目 、二 功率 1281105 晶體的硬切換（hard—switching)方式同樣也伴隨著功浐 緣=本創作人有感上34缺失之可改善，乃特潛心研 九並配δ學理之運用，終於提出一種設計合理 上述缺失之本創作。 ,欢改善 【發明内容】 本發明之用途係為改善f知交換式電源供應器之 功率消耗問題並可提高系統之轉換效率。為了達成上述之 目的’、本發明藉由共振式轉換裝置中諧振元件之頻率響應 及負載條件，並採賴整城鮮作為卿及穩定輸^ 壓之控制策略’同時利用共振式轉換裝置能量轉換之特 能輕易地完成零電壓切換，達成較高之轉換器效能。 在大負載電流之輸出規格條件下，並採用同步整流電路， 更能提高全機之轉換效率。此外採用磁滯比較控制之概 念’能在適當時機（一般而言是極輕載及空載條件下）控制 共振式轉縣置之動條況，來達成待機模式時極低之 率消耗。 一 /本發明之具極傾機功率損耗之共控制裝置 係包括·-交流/直流轉換單元、一直流/直流轉換單元、 /直直*轉換控制單元及一待機模式控制單元。同時視 系統及規格S求，該交流/錢轉換單元射使用—功率因 數4口壓整流器。為因應大負载電流需求，可在 ▲ ί"1:’直/讀鮮70巾制Θ步整流電路。該料因數修 正為或該倍壓整流H，係用於進行交流/直流電力轉換。其 1281105 中柄率因數修正II具功率因數修正及前置調節器穩壓之 =用’以輸出穩定之第-直流電壓；而該倍壓整流器則可 藉自動切換或手動切換以符合系統輸入電 源電壓要求。 兩j直流/直流轉換單元用於將第一直流電壓轉換為所 而之f二直流電壓，並採用調整切換頻率方式，根據負載 周即及蚊輸出之第二直流電壓。其中該直流/直流轉 :早元之輸出整流||(Qutput R⑽出⑷可採用二極體或 =步整流電路。該直流/直流轉換控制單元，主要是接收 ς，直流/直流轉換單元輸出電壓之回授信號，藉以調整 直流轉換單元之功率晶體控制信號的頻率，以穩定 二鏟2出電壓。該直流/直流轉換控制單元在該直流/直 衫使_步整流電路時，亦必須 率晶體之控制信號。 =機模式控制單元係魏該直流/直流轉換單元所 出—控狀況後，分別輸 ，控制單元，二 ==== 直机轉換早兀之電路動作。 待機模式控制二:轉==: i:=控制單元。其中該直流/直流轉換單元‘ 之二共:式轉換控制方法 壓邊限條件值判斷目前系心定之三個電 第-心 個電璧邊限條件值分別為. 界值、—弟二臨界值及1三臨界值。三個邊^ 1281105 件之關係為第一臨界值大於第二臨界值大於第三臨界值。 由此三個臨界值將系統之操作模式分為四個狀態區間，分 述如下： 刀 首先若第二直流電壓之電壓準位穩定位於第一臨界值 及第二臨界值所涵蓋之磁滯比較電壓範圍内，則為一正常 穩定之電壓，其值將是由系統所決定之額定電壓值。此昉 該功率因數修正器、該倍壓整流器及該直流/直流轉換: 均正常運作。、凡 但若第二直流電壓位於第一臨界值或第二臨界值之 時，則進行包括下列步驟·· (1) 先判斷第二直流電壓是否超出第一臨界值，若是， 則使該功率因數修正器及該直流/直流轉換單元均停^運 作，此時第一直流電壓之最低值仍大於市電之整流電壓 值，最大值為正常運作時穩定第一直流電壓值。 & (2) 若第一直流電壓低於第二臨界值，則使該直流/ 直流轉換單元正常運作，而該功率因數修正器維持關閉L。 (3) 當該直流/直流轉換單元恢復運作後，所偵測之 第二直流電壓仍繼續低於第二臨界值，並低於第三臨界值 時，則使該功率因數修正器及該直流/直流轉換單元 運作。 本發明具極低待機功率損耗之共振式轉換控制方法及 裝置’可以有效地減少正常操作下之切換功率損失。同時 在不同負載及電壓條件下，能控制該功率因數修正器與直 流/纽職單认動作狀況’目越有效降低待機模/式下 之功率消耗。更甚者，由於與習知技術相較下，不須使用 額外的缓振電路，又在輕載或空載的條件下，系統^喿作在 9 1281105 =頻土其鐵心損失之功率與切 貫施者。故能降低系統在待機模式τ之系統功率=技咖 2了:吏貴審查委員能更進一步暸解本發 專 ^谷^残本發明之詳細說明與關，然而所^ ”僅提供*考與說㈣，並非用來對本發明加以限制者、。 【實施方式】 ，_三目’第三圖為本發明具極低待機功率 之八振式轉換控制裝置之架構示意 ^ 機功率祕之舰式轉魅難置3純括： 轉換單元30、一直流/直流轉 η、ϋ= 及規林=制単元313。同時视系統 ί規袼吊求，可在交流/直流轉換單元30使用一功率因^ ^ = Γ1為第—實施態樣(詳見第三A ®);或使用-倍 ^正机益303為另-實施態樣(詳見第三B圖）。其、、: 換二:振式轉換器311a;直流/直‘ .=312可為一共振式轉換器控制器；312a;待機握 :工制單兀313則可為-待機模式控制器313&。為因應 垂載電流需求’可在直流/直流轉換器311中使用同步^ 電，。功率因數修正器則或倍壓整流器3〇3，係二: 仃乂流/直流電力轉換。其中倍壓整流器3〇3中更可包括一 ，波器。以下詳述本發明之具極低待機功率祕之 轉換控制裝置3之技術特徵。 "^ 一父流電壓vac3傳送至功率因數修正器3〇1進六、、六 /直流電力轉換、功率因數修正及前置調節穩壓後，或= 1281105 倍壓六器整流濾、波後，輸出第-直流電壓vdc31。而直流 /直，轉，單元311接受功率因數修正器3〇1所輪出之第一 直流電壓Vddi，直流/直流轉換單元311將第一直流電壓 vd:轉換為所需之第二直流電壓Vd^2。直流/直流轉換控 制單元312藉調整直流/直流轉換單元311之功率晶體控制 信號的頻率，以穩定輸出第二直流電壓V-2，此外此^流 /直流轉換控制單元312在直流/直流轉換單元3H使用同 步整流電路時，亦必須提供同步整流功率晶體之控制信 唬。待機模式控制單元313,係接收直流/直流轉換單元311 所輸出之第二直流電壓Vdc32後，並判斷目前負載狀況後， 分別輸出一控制訊號回授至一功率因數修正器控制器3⑽ 及直流/直流轉換控制單元312，以控制功率因數修正器 301及直流/直流轉換單元311之電路動作。 ^請參閱第四周，第四圖為本發明所提之直流/直流轉換 單元架構具體實施例。直流/直流轉換單元311可為一共振 式轉換器311a，其所使用之轉換架構可為一單晶式E類轉 換杀構、一多晶橋式轉換架構或一多晶推挽式轉換架構。 根據其諧振元件與負載之連接方式，又可區分為一串聯共 振式、一並聯共振式或一串並聯共振式三種形式。另外在 輸出整流部分大致分為一般整流器或同步整流電路兩種。 请參閱第五圖，第五圖為本發明所提之直流/直流轉換 控制單元具體實施例。直流/直流轉換控制單元312可為一 共振式轉換器控制器312a，其為一具有電壓控制振盪器 (Voltage Control 〇sciiiator，vco)功能之功率晶體控制信號 產生為’可接收來自回授電壓控制信號，改變功率晶體控 制信號頻率之控制器。 11 1281105 …請參閱第六圖，第六圖為本發料提之待機模式控制 單兀具體實施例。待機模式控制單元313可為一待機模 控制益313a，ϋ由設定邊界條件可界定操作狀態區域 電，供應器操作於輕載或空載之負载條件下，利用待機控 制單元313内之磁滯比較器（即一操作模式邊界設定條件 設定單元及一操作狀態判斷單元），採取磁滯比較控制之概 心作為觸發訊號的產生’以便控制功率因數修正單元3 〇 1及 直流/直流換器311。 請參閱第七圖並配合第三圖及第三Α圖，第七圖為本 發明具極低待機功率損耗之共振式轉換控制方法之時序與 輸出電壓座標示意圖。待機模式控制單元313以輸出電^ 為比較參考對象，在待機模式控制單元313内可設定三個 輸出電壓臨界值，分別為輸出電壓第一臨界值v〇4i、第二 Bs界值V〇42及弟三臨界值v〇43。三個臨界值將系統之操作 模式分為四個狀態區間，分述如下（其中輸出電壓 Vdc32): ⑴ t〇<t<tl 此時當系統操作於正常條件下，輸出可以穩定控制在 一定範圍之内，即ν042<ν〇<νο41，此時功率因數修正器301 及直流/對直流轉換單元311之電路均正常運作。 (2) t!<t<t2 由直流/對直流轉換單元311之頻率響應知當t=tl時負 載電流降低，此時，當輸出電壓V。上升，直至t=t2時V。 大於Vw，此時待機控制單元313會產生控制訊號，控制 使功率因數修正器301及直流/對直流轉換單元311之電路 進入關機(Shutdown)狀況。 12 1281105 (3) t2<t<t3 一當t—2時，功率因數修正器301及直流/對直流轉換單 兀311進入關機狀況，此時輸出電壓％會持續下降，直至 ㈣3時，輸出電壓低於、後再次開啟直流/直流轉換單元 311。使輸出電壓v〇上升。 (4) t3<t<t4 § t-h日守，直流/對直流轉換單元311重新開機，在相 同的負載條件下，此時輪出電壓VG會開始上升，直至輸出 電壓V〇回復至正常情況，此時功率因數修正器仍未動 作’而直流/對直流轉換單幻11進入待機模式，以叢發模 式控制穩定輸出電壓。 (5) t4<t<t5 虽t=t4日寻 ，負載電流突然增加，造成輸出電壓快速| tri，對直流轉換單元311重新仍在啟動狀況，^ …、法、，隹持輸出電壓的穩定，當t=t5時輸出電壓v〇降至I (6)t5<t<t6 當二5時，輸出電壓％降至I，待機模式控制單: 达出仏諕，重新啟動功率因數修正器3〇ι及 轉換單元3H，使輸出電屡％回復至正常電屢範圍。 即你’只要採料#之功率級電路參數設計 线之條件下，亦可達到零電㈣換。同日 :要撕增加緩振電路，因此全機在空載條 呈 極低之待機功率消耗。 裝置mi低待機功率損耗之共振式轉換控制方法； 工载（或輕載)條件下仍具有零電壓切換之直流 13 1281105 •對直流轉換單元311，可以有效減少正常操作下之切換損 ^。另外利用輪出電壓與臨界電壓之磁滯比較功能執行^ 發模式(Burst m〇de)功能，在不同之輸出電壓條件中， 功率因數修正單元301及直流/對直流轉換單元311，二 降低待機下之功率消耗。 ^ 更有甚者，本發’須使用額外之緩振電路 ==或空載麵下，系統乃是以較高頻率切:於 :r待機模式下伽率消耗，=:::: 方二筆為：不可多得之發明創作裳置及 明專利申請要件生及進步性’完全符合發 本案專利，以保障輸之^出申請，敬請詳查物 惟以上所述，僅為本創作 ，圖式，非因此即拘限施=詳細說 本創作說明書及圖式内容所為故舉凡運用 明之領域内，可輕易=二該項技藝者在本發 案之專利範圍。文或l飾皆可涵蓋在以下本 【圖式簡單說明】 第m圖t知低待機損耗交換式電卵^ 構不意圖； 、电々界彳八應态之電路架 14 1281105 第技術於待機模式中之控制㈣ 第具ί低待機功率損耗之共振式轉換控 制ι置之架構示意圖； 第三Α圖為本發明具極低待機功率損耗之共振式轉換 控制裝置之第一實施態樣； 、 第三B圖為本發明具極低待機功率損耗之共振式轉換 控制裝置之另一實施態樣； 、 第=本發明所提之直流/直流轉換單元架構具體 第本發明所提之直流/直流轉換控制單元具體 第：圖】本發明所提之待機模式控制單元具體實施 第極低待機功率損耗之共振式轉換控 制方法之日守序與輸出電壓座標示意圖。 【主要元件符號說明】 第一圖： 1 10 習知具低待機損耗之交換式電源供應器 交流/直流轉換單元Restricted by: the development of energy sources and the use of energy for the appropriate use of energy policy: the second country and other advanced countries have the power (s vice by mode) in the power consumption ^ ^ production 1 in standby mode (G_ Power) 'Generally, most of them are set at 〇5 watts = color U p_ x will be,", and the standard is used to reduce the standby loss switching power supply ° ° and its associated controller. For the first time, the first picture is a schematic diagram of the circuit structure of the low standby loss exchange power supply. In general, the main/DC conversion unit 1G and the DC/DC conversion unit 11 are connected in series, and the AC in the 1st: straight: the replacement unit 1 (3 is used to convert the AC input voltage of the system input to the first DC voltage Vdcu And the AC/DC conversion unit is connected in series with DC/DC conversion, and the first DC voltage Vdc11 of the AC/DC conversion output is converted into the required second rectus muscle [Vdcl2 such as 3. 3V, 5V, 12V, 24V, surgery or other specifications 1281105 voltage, etc. The architecture of the DC/DC converter unit U can use an isolated or non-isolated converter architecture, currently in the switching power supply, flyback (Flyb ^k) Conversion n is widely used in the U/DC converter architecture because of its simple architecture and low cost. It is used in the U/DC converter architecture, except for its own control under normal load conditions. In addition to the device (function), in addition to the requirements of the green power specification, the Burst mode is additionally used as the control mode in the standby mode. The first picture of Ming Mai, the second picture is the control of the conventional technology in the standby mode. k order and Schematic diagram of the output voltage. When the load is under light load or no load condition. 'Traditional low standby _ consumption exchange power supply (four) towel after the level of money / DC conversion unit y, in addition to the duty cycle (Duty cycle) to the maximum In addition, the Burst mode is used to intermittently control the conduction and switching of the power crystal. In general, under the condition of light load or no load, the maximum duty cycle can be only a few cycles. The DC output voltage shirt 12 is maintained within a certain range (ie, between the output voltage upper limit value and the output voltage lower limit VB22), and the system can turn off the control signal of the power crystal when the output voltage Vdcl2 is higher than the output voltage upper limit value v. Until the DC output voltage Vdcl2 is lower than the output voltage lower limit body, the system re-outputs the control of the body, which can reduce the switching times of the power crystal and the switching loss of the system under the condition of m and no load. Chi-type converters must additionally use Snubber's to reduce the voltage-spike caused by leakage inductance and parasitic capacitance. The use of the cushioning circuit is also accompanied by a big red _ Turn The hard-switching method of the second power 1281105 crystal is also accompanied by the work of the soft-switching without the use of special control or auxiliary opening conditions (s〇f (10) is also ambiguous).缘=The creator has the feeling that 34 is missing and can be improved. He is dedicated to the study of ninth and with the application of δ theory. Finally, he proposes a design that is reasonable in design. The improvement is invented. Improve the power consumption problem of the switching power supply and improve the conversion efficiency of the system. In order to achieve the above purpose, the present invention adopts the frequency response and load conditions of the resonant component in the resonant converter device, and adopts the whole city. As a control strategy for Qing and stable voltage control, the zero-voltage switching can be easily accomplished by using the energy conversion of the resonant converter to achieve higher converter performance. Under the condition of large load current output specification and synchronous rectifier circuit, the conversion efficiency of the whole machine can be improved. In addition, the concept of hysteresis comparison control can be used to control the dynamic state of the resonance type at an appropriate timing (generally under extremely light load and no-load conditions) to achieve a very low rate of consumption in the standby mode. A common control device with extreme tilt power loss of the present invention includes an AC/DC conversion unit, a DC/DC conversion unit, a /straight* conversion control unit, and a standby mode control unit. At the same time, depending on the system and the specification S, the AC/money conversion unit uses the power factor 4-port voltage rectifier. In order to meet the demand of large load current, it can be used in ▲ ί"1:’ straight/read fresh 70 towel step-by-step rectifier circuit. The material factor is corrected to or the voltage doubler rectification H, which is used for AC/DC power conversion. Its 1281105 medium handle factor correction II has power factor correction and pre-regulator regulation = 'to output stable first-DC voltage; and the voltage doubler rectifier can be switched automatically or manually to comply with system input power Voltage requirements. The two-dc/DC conversion unit is used to convert the first DC voltage into the f-DC voltage, and adopts an adjustment switching frequency mode according to the load cycle and the second DC voltage of the mosquito output. The DC/DC turn: early output rectification||(Qutput R(10) out (4) can adopt diode or = step rectification circuit. The DC/DC conversion control unit mainly receives ς, DC/DC conversion unit output voltage The feedback signal is used to adjust the frequency of the power crystal control signal of the DC conversion unit to stabilize the voltage of the second shovel 2, and the DC/DC conversion control unit must also have a crystal when the DC/straight shirt makes the _ step rectifier circuit Control signal. = Machine mode control unit is the DC/DC conversion unit. After the control status, respectively, the control unit, the second ==== straight machine conversion early circuit operation. Standby mode control two: turn ==: i:= control unit. Among them, the DC/DC conversion unit's total: type conversion control method, the value of the margin limit value is judged, and the current three-phase-heart-edge threshold values are The boundary value, the second threshold value and the third critical value. The relationship between the three sides ^ 1281105 is that the first critical value is greater than the second critical value is greater than the third critical value. Thus the three critical values will operate the system Divided into four The status interval is as follows: The knife firstly is a normal stable voltage if the voltage level of the second DC voltage is stable within the hysteresis comparison voltage range covered by the first threshold and the second threshold. It will be the rated voltage value determined by the system. The power factor corrector, the voltage doubler rectifier and the DC/DC converter are all operating normally. If the second DC voltage is at the first threshold or the second At the critical value, the following steps are performed: (1) determining whether the second DC voltage exceeds the first critical value, and if so, causing the power factor corrector and the DC/DC conversion unit to stop operating, The minimum value of the first DC voltage is still greater than the rectified voltage value of the mains, and the maximum value is the stable first DC voltage value during normal operation. (2) If the first DC voltage is lower than the second threshold, the DC/ The DC conversion unit operates normally, and the power factor corrector maintains the shutdown L. (3) When the DC/DC conversion unit resumes operation, the detected second DC voltage continues to be lower than the second When the threshold value is lower than the third critical value, the power factor corrector and the DC/DC conversion unit are operated. The resonant conversion control method and apparatus with extremely low standby power loss of the present invention can effectively reduce the normality. Switching power loss under operation. At the same time, under different load and voltage conditions, it can control the power factor corrector and DC/New job single-action operation status to reduce the power consumption under standby mode. Compared with the conventional technology, it is not necessary to use an additional vibration-damping circuit, and under light load or no-load condition, the system works at 9 1281105 = frequency and its core loss power and cut-off. Therefore, the system power of the system in the standby mode τ can be reduced = the technical coffee 2: The review committee of the company can further understand the detailed description and the details of the invention of the invention. However, only the test and the test are provided. (4) It is not intended to limit the invention. [Embodiment], _Sanmu' The third figure is the architecture diagram of the eight-vibration type conversion control device with very low standby power in the present invention. The machine power is secreted. The conversion unit 30, always Flow/DC to η, ϋ = and 林 = 単 313. At the same time, depending on the system, the AC/DC conversion unit 30 can use a power factor ^^ = Γ1 as the first implementation mode (see the third A ® for details); or use - times ^ positive machine benefit 303 Another - implementation aspect (see Figure 3B for details). The second: vibrating converter 311a; DC/straight '.=312 can be a resonant converter controller; 312a; standby grip: the industrial unit 313 can be a - standby mode controller 313 & . Synchronous power can be used in the DC/DC converter 311 in response to the load current demand. The power factor corrector is either a voltage doubler rectifier 3〇3, two: turbulence/DC power conversion. Among them, the voltage doubler rectifier 3〇3 may further include a wave device. The technical features of the switching control device 3 of the present invention having extremely low standby power are detailed below. "^ A parental voltage vac3 is transmitted to the power factor corrector 3〇1 into six, six/DC power conversion, power factor correction and pre-regulation regulation, or = 1281105 voltage doubler rectifier filter, wave after , output the first DC voltage vdc31. And the DC/DC, turn, unit 311 receives the first DC voltage Vddi rotated by the power factor corrector 3〇1, and the DC/DC conversion unit 311 converts the first DC voltage vd: into the required second DC voltage Vd. ^2. The DC/DC conversion control unit 312 adjusts the frequency of the power crystal control signal of the DC/DC conversion unit 311 to stably output the second DC voltage V-2, and furthermore, the DC/DC conversion control unit 312 is in the DC/DC conversion unit. When the 3H uses a synchronous rectification circuit, it must also provide a control signal for the synchronous rectification power crystal. The standby mode control unit 313 receives the second DC voltage Vdc32 outputted by the DC/DC conversion unit 311, and determines the current load condition, and outputs a control signal to a power factor corrector controller 3 (10) and DC/ The DC conversion control unit 312 controls the circuit operations of the power factor corrector 301 and the DC/DC conversion unit 311. ^ Please refer to the fourth week, and the fourth figure is a specific embodiment of the DC/DC conversion unit architecture proposed by the present invention. The DC/DC conversion unit 311 can be a resonant converter 311a, and the conversion architecture used can be a single crystal type E conversion, a polycrystalline bridge conversion architecture or a polycrystalline push-pull conversion architecture. According to the connection mode of the resonant element and the load, it can be divided into three types: a series resonant mode, a parallel resonant type or a series parallel resonant type. In addition, the output rectification section is roughly classified into two types: a general rectifier or a synchronous rectification circuit. Please refer to the fifth figure. The fifth figure is a specific embodiment of the DC/DC conversion control unit proposed by the present invention. The DC/DC conversion control unit 312 can be a resonant converter controller 312a, which is a power crystal control signal with a voltage controlled oscillator (VCO) function generated as 'receivable from feedback voltage control. Signal, a controller that changes the frequency of the power crystal control signal. 11 1281105 ... Please refer to the sixth figure. The sixth figure is a specific embodiment of the standby mode control unit of the present invention. The standby mode control unit 313 can be a standby mode control benefit 313a, which can define the operating state area power by setting boundary conditions, and the supplier operates under light load or no-load load conditions, and utilizes hysteresis comparison in the standby control unit 313. The device (i.e., an operation mode boundary setting condition setting unit and an operation state determining unit) adopts an overview of the hysteresis comparison control as the generation of the trigger signal to control the power factor correction unit 3 〇1 and the DC/DC converter 311. Please refer to the seventh figure and the third figure and the third figure. The seventh figure is a schematic diagram of the timing and output voltage coordinates of the resonant type conversion control method with very low standby power loss. The standby mode control unit 313 compares the reference object with the output power, and three threshold values of the output voltage can be set in the standby mode control unit 313, which are the output voltage first threshold value v〇4i and the second Bs threshold value V〇42. And the three critical values of the brother v〇43. The three thresholds divide the operating mode of the system into four state intervals, which are described below (where the output voltage is Vdc32): (1) t〇<t<tl At this time, when the system is operating under normal conditions, the output can be stably controlled at a certain level. Within the range, that is, ν042 < ν 〇 < νο 41, at this time, the circuits of the power factor corrector 301 and the DC/DC converting unit 311 operate normally. (2) t!<t<t2 The frequency response of the DC/DC conversion unit 311 is known to be reduced when t=tl, and at this time, the voltage V is output. Rise until V at t=t2. When it is greater than Vw, the standby control unit 313 generates a control signal to control the circuit of the power factor corrector 301 and the DC/DC conversion unit 311 to enter a Shutdown condition. 12 1281105 (3) t2<t<t3 When t-2, the power factor corrector 301 and the DC/DC converter unit 311 enter the shutdown state, at which time the output voltage % will continue to drop until (4) 3, the output voltage The DC/DC conversion unit 311 is turned on again afterwards. The output voltage v〇 is raised. (4) t3<t<t4 § th day guard, DC/DC conversion unit 311 is restarted. Under the same load condition, the wheel-out voltage VG will start to rise until the output voltage V〇 returns to normal. At this time, the power factor corrector is still not operating, and the DC/DC conversion single magic 11 enters the standby mode, and the stable output voltage is controlled in the burst mode. (5) t4<t<t5 Although t=t4 day search, the load current suddenly increases, causing the output voltage to be fast | tri, the DC conversion unit 311 is still in the startup state, ^ ..., method, and the output voltage is stable When t=t5, the output voltage v〇 falls to I (6)t5<t<t6 When the second 5 is, the output voltage % drops to I, the standby mode control list: When the output is reached, the power factor corrector is restarted 3 〇ι and conversion unit 3H, so that the output power is restored to the normal power range. That is, you can also achieve zero (four) change under the condition of the power level circuit parameter design line of the material #. On the same day: To reduce the vibration-increasing circuit, the whole machine has extremely low standby power consumption in the no-load bar. Resonance conversion control method for low standby power loss of device mi; DC with zero voltage switching under load (or light load) conditions 13 1281105 • For DC conversion unit 311, the switching loss under normal operation can be effectively reduced. In addition, the hysteresis comparison function of the wheel voltage and the threshold voltage is used to perform the Burst function, and in different output voltage conditions, the power factor correction unit 301 and the DC/DC conversion unit 311 are reduced in standby. The power consumption below. ^ What's more, the hair 'has to use an additional vibration-damping circuit == or under the no-load surface, the system is cut at a higher frequency: in: r standby mode gamma consumption, =:::: The pen is: rare inventions, creations, and patent applications, and the progress of the patents are fully in line with the patents issued to protect the application of the case. Please check the details of the above, only for this creation. The schema is not limited to the application of the application. In detail, the scope of the creation of the manual and the contents of the schema can be easily used in the field of patent application. The text or the decoration can be covered in the following [Simplified description of the drawing] The mth figure t knows that the low standby loss exchange type electric egg is not intentional; the circuit frame of the electric field is eight-way state 14 1281105 Control in the mode (4) The schematic diagram of the resonant conversion control of the low standby power loss ι; the third diagram is the first embodiment of the resonant conversion control device with extremely low standby power loss; FIG. 3B is another embodiment of the resonant type conversion control device with extremely low standby power loss according to the present invention; and the DC/DC conversion unit structure of the present invention is specifically the DC/DC provided by the present invention. The conversion control unit is specifically shown in the figure: The standby mode and the output voltage coordinate diagram of the resonance mode conversion control method for implementing the extremely low standby power loss by the standby mode control unit of the present invention. [Main component symbol description] First picture: 1 10 Conventional switching power supply with low standby loss AC/DC conversion unit
Vacl Vdcll Vdcl2 直流/直流轉換單元 交流輸入電壓 第一電壓 第二電壓 15 11 1281105 第二圖： 輸出電壓上限值 Vb21 輸出電壓下限值 VB22 第三圖： 本發明具極低待機功率損耗之共振式轉換控制裝置3 • 交流/直流轉換單元 30 直流/對直流轉換單元 311 籲直流/對直流轉換控制單元 312 待機模式控制單元 313 交流輸入電壓 Vac3 第一直流電壓 Vdc31 第二直流電壓 Vdc32 第三A圖： 功率因數修正器 301 鲁 功率因數修正器控制器 302 共振式轉換器 311a 共振式轉換器控制器 312a 待機模式控制器 313a 第三B圖 倍壓整流器 303 第七圖： 16Vacl Vdcll Vdcl2 DC/DC converter unit AC input voltage First voltage Second voltage 15 11 1281105 Second diagram: Output voltage upper limit value Vb21 Output voltage lower limit value VB22 Third figure: The present invention has a very low standby power loss resonance Switching control device 3 • AC/DC converter unit 30 DC/DC converter unit 311 DC/DC converter control unit 312 Standby mode control unit 313 AC input voltage Vac3 First DC voltage Vdc31 Second DC voltage Vdc32 Third A Figure: Power Factor Corrector 301 Lu Power Factor Corrector Controller 302 Resonant Converter 311a Resonant Converter Controller 312a Standby Mode Controller 313a Third B Picture Voltage Multiplier 303 Figure 7: 16
1281105 輸出電壓第一臨界值 V〇41 輸出電壓第二臨界值 V〇42 輸出電壓第三臨界值 V〇43 171281105 Output voltage first critical value V〇41 Output voltage second critical value V〇42 Output voltage third critical value V〇43 17